CN103501126A - Method for asymmetrically controlling simplified-type three-phase three-level direct-current converter - Google Patents
Method for asymmetrically controlling simplified-type three-phase three-level direct-current converter Download PDFInfo
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Abstract
The invention discloses a method for asymmetrically controlling a simplified-type three-phase three-level direct-current converter. According to a control timing sequence, the conductive time of a first switching tube, the conductive time of a third switching tube and the conductive time of a fifth switching tube are the same, the variation range of the duty ratio is 0-1/2, the turn-on time of the first switch, the turn-on time of the third switching tube and the turn-on time of the fifth switching tube are separated by 1/3 switching period, and output voltages are controlled by adjusting the duty ratio of the first switching tube, the duty ratio of the third switching tube and the duty ratio of the fifth switching tube. The conductive time of a second switching tube, the conductive time of a fourth switching tube and the conductive time of a sixth switching tube are the same and are correspondingly and complementarily conductive with the fifth switching tube, the first switching tube and the third switching tube respectively, and the certain delay time is reserved between every two complementary switching tubes. According to the method, voltage stresses of all the switching tubes are all a half of input voltages, the current stresses and output filter inductances of the switching tubes can be reduced, the zero voltage switching of the switching tubes can be achieved, and the automatic equalization of input partial pressure capacitor voltages can be achieved.
Description
Technical field
The present invention relates to a kind of asymmetric control method of reduced form three-phase tri-level DC converter, belong to the DC converting field of Technics of Power Electronic Conversion technology.
Background technology
Full-bridge converter has that circuit structure is simple, constant frequency is controlled, switching tube can be realized the advantages such as soft switch, therefore is widely used in middle high power DC conversion occasion.Along with the increase of converter power output, the current stress of switching tube also increases thereupon, now can be by a plurality of converter parallel connections or switching device parallel connection, but can bring such as current-sharing and control the problems such as complicated.For addressing this problem, can adopt the three phase full bridge DC converter, it is to increase a brachium pontis on the basis of full-bridge converter, transformer and rectifier bridge are three-phase structure.This converter can effectively reduce the switching tube current stress, can significantly improve input and output current pulsation frequency, and then reduce filter simultaneously.But this topology is to be developed by full-bridge converter, and the voltage stress of switching tube is still input voltage.
For reducing switch tube voltage stress, to adapt to high voltage input demand, there is the scholar to propose three-phase tri-level DC converter topology, wherein the inventor discloses the patent of invention (patent No. 201010598995.8) of a kind of three-phase tri-level DC converter and symmetrical control method thereof, this circuit structure is simple, the switch tube voltage current stress is low, is applicable to the high-power application scenario.It adopts a kind of symmetrical control mode, can significantly improve input and output current pulsation frequency, reduces the filter volume weight.But under this control mode, must there be the turn-off time simultaneously in two switching tubes of same brachium pontis, within this period, two switching tube junction capacitance participate in resonance simultaneously, can't guarantee that the lucky resonance of its both end voltage is to zero before switching tube is opened, therefore switching tube is hard switching, has larger switching loss.
Summary of the invention
The problem existed for solving the above-mentioned background technology, the present invention seeks to, for reduced form three-phase tri-level DC converter, to propose a kind of asymmetric control method, realizes high efficiency, high power density and the high reliability of converter.
In order to realize above-mentioned technical purpose, technical scheme of the present invention is:
A kind of asymmetric control method of reduced form three-phase tri-level DC converter, reduced form three-phase tri-level DC converter wherein comprises input dividing potential drop condenser network, half-bridge three-level unit, full bridge unit, three-phase isolation transformer and rectification and filter circuit.Wherein, the half-bridge three-level unit comprises the first and second afterflow diodes, striding capacitance and first, the 3rd, the 4th and the 6th switching tube.Full bridge unit comprise first, second, the 4th and the 5th switching tube, full bridge unit and half-bridge three-level units shared first and the 4th switching tube.The drain electrode of the 6th switching tube connects the positive input terminal of input dividing potential drop condenser network, the source electrode of the 3rd switching tube connects the negative input end of input dividing potential drop condenser network, the source electrode of the 6th switching tube connects respectively the negative electrode of the first fly-wheel diode, an end of striding capacitance, the drain electrode of the first switching tube and the drain electrode of the 5th switching tube, and the drain electrode of the 3rd switching tube connects respectively the anode of the second fly-wheel diode, the other end of striding capacitance, the source electrode of the 4th switching tube and the source electrode of second switch pipe.Control method of the present invention is: the first, the 3rd is identical with the ON time of the 5th switching tube, its change in duty cycle scope is 0～1/2, its service time 1/3 switch periods of being separated by, by regulating first, the 3rd and the duty of the 5th switching tube recently control output voltage.The second, the 4th identical with the ON time of the 6th switching tube and respectively with the 5th, first and the 3rd switching tube corresponding complementary conducting, between two complementary switching tubes, arranged time of delay.
Adopt above-mentioned technical scheme, the present invention has following technique effect:
(1) can reduce switching tube electric current quota, half that all switch tube voltage stress is input voltage, can reduce output inductor simultaneously;
(2) can utilize transformer leakage inductance or extra resonance inductance and switching tube junction capacitance resonance, realize the zero voltage switch of switching tube, converter has high efficiency;
(3) can effectively realize inputting the equilibrium of dividing potential drop capacitance voltage.
The accompanying drawing explanation
Fig. 1 is the reduced form three-phase tri-level DC converter electrical block diagram the present invention relates to.
Fig. 2 is the switching sequence figure of asymmetric control method of the present invention.
Fig. 3 is the waveform schematic diagram of the present invention under little duty cycle mode.
Fig. 4 is the waveform schematic diagram of the present invention under middle duty cycle mode.
Fig. 5 is the waveform schematic diagram of the present invention under the big space rate pattern.
Fig. 6 ~ Figure 11 is the equivalent circuit diagram of the present invention's 1～6 switch mode under little duty cycle mode.
Figure 12 is the present invention's equivalent circuit diagram of switch mode after t5 under little duty cycle mode.
Figure 13 is the output inductor correlation curve figure of different converters.
Figure 14 is the switching tube current stress correlation curve figure of different converters.
Figure 15 is that the present invention Cd1, Cd2 under little duty cycle mode discharge and recharge working waveform figure.
Figure 16 is that the present invention Cd1, Cd2 under middle duty cycle mode discharge and recharge working waveform figure.
Figure 17 is the soft switching waveform figure of the present invention Q2 under middle duty cycle mode.
Figure 18 is the soft switching waveform figure of the present invention Q5 under middle duty cycle mode.
Figure 19 is the soft switching waveform figure of the present invention Q2 under little duty cycle mode.
Figure 20 is the soft switching waveform figure of the present invention Q5 under little duty cycle mode.
The label declaration of accompanying drawing 1: 1---input dividing potential drop condenser network, 2---the half-bridge three-level unit,
3---full bridge unit, 4---three-phase isolation transformer, 5---rectification and filter circuit.
Main designation in above-mentioned accompanying drawing: Vin is input direct voltage; Cd1, Cd2 are input dividing potential drop electric capacity; Q1～Q6 is the first～six switching tube; C1～C6 is the first～six switching tube parasitic capacitance; D1～D6 is the first～six switching tube body diode; Df1, Df2 are fly-wheel diodes; Css is striding capacitance; Tra, Trb, Trc are a phase, b phase and the c phases of three-phase isolation transformer; Llka, Llkb, Llkc are the parasitic leakage inductances in the former limit of isolating transformer; DR1 ~ DR6 is the secondary rectifier diode; Lf is output inductor; Cf is output filter capacitor; RLd is load; VAB is A and B point-to-point transmission voltage; VAC is A and C point-to-point transmission voltage; VBC is B and C point-to-point transmission voltage; Vrect is the secondary commutating voltage; Vo is output voltage; IA, iB, iC flow out the electric current that A point, B point and C are ordered; Ipa, ipb, ipc are the primary currents of isolating transformer a phase, b phase and c phase; Isa, isb, isc are the secondary currents of isolating transformer a phase, b phase and c phase.
Embodiment
Below with reference to accompanying drawing, technical scheme of the present invention is elaborated.
Fig. 1 means reduced form three-phase tri-level DC converter structural representation involved in the present invention, input dividing potential drop condenser network 1, half-bridge three-level unit 2, full bridge unit 3, three-phase isolation transformer 4, rectification and filter circuit 5, consists of.The half-bridge three-level unit is comprised of switching tube Q1, Q3, Q4 and Q6 and body diode separately thereof and parasitic capacitance, sustained diode f1 and Df2 and striding capacitance Css; Full bridge unit is comprised of switching tube Q1, Q2, Q4 and Q5.The former limit winding of three-phase isolation transformer adopts the triangle connected mode, and the secondary winding adopts the Y-connection mode, and secondary adopts three-phase bridge rectifier circuit, DR1-DR6 is the secondary rectifier diode, Lf is output inductor, and Cf is output filter capacitor, and RLd is load.
Fig. 2 narrates the switching sequence figure of control method of the present invention, and wherein abscissa t means the time, and ordinate D means duty ratio.As shown in the figure, the ON time of Q1, Q3 and Q5 is identical, and the change in duty cycle scope is 0 ~ 1/2, its service time 1/3 switch periods of being separated by, recently control output voltage by the duty of regulating Q1, Q3 and Q5.Q2, Q4 and Q6 respectively with the complementary conducting of Q5, Q1 and Q3, between two complementary switching tubes, reserved certain time of delay, prevent bridge arm direct pass on the one hand, realizes ZVS for switching tube on the other hand condition is provided.Due to the ON time difference of two groups of switching tubes, therefore be referred to as asymmetric control mode.
According to the difference of duty ratio, there are three kinds of mode of operations in converter, when duty ratio is less than 1/3, is defined as little duty cycle mode; When duty ratio, when 1/3 arrives between the critical duty ratio of pressure-adjustable (its value is determined by the side circuit parameter), be middle duty cycle mode; When duty ratio is greater than the critical duty ratio of pressure-adjustable, it is the big space rate pattern.Fig. 3,4,5 has provided respectively the main oscillogram under the different working modes.Wherein, under middle or small duty cycle mode, regulate duty ratio and can change output voltage values, and under the big space rate pattern, as shown in Figure 5, in a switch periods, there are two level values in secondary commutating voltage vrect, is respectively 0.75kVin and kVin, and k is the secondary former limit of transformer no-load voltage ratio.These two corresponding time periods of level value are certain values, and under this pattern, output voltage is non-adjustable, so do not allow converter to be operated under this pattern during actual design.
Narrate below in conjunction with Fig. 3 ~ Figure 12 the specific works principle that reduced form three-phase tri-level DC converter adopts asymmetric control mode.A switch periods, 18 kinds of switch mode are arranged by known this converter of accompanying drawing 3, wherein, [t0 in the past, t5] is front 1/3 cycle, and all the other are rear 2/3 cycle.Below the working condition of each switch mode is made a concrete analysis of.
Before analyzing, make the following assumptions: 1. all switching tubes and diode are desirable device; 2. all inductance, electric capacity and isolating transformer are desirable component; 3. striding capacitance Css is enough large, and during stable state, its voltage is Vin/2; 4. output inductor is enough large, in a switch periods, can be regarded as the constant-current source that a current value is Io, and wherein Io is output current.
1. switch mode 1 [t0 in the past] [corresponding to Fig. 6]
T0 constantly before, switching tube Q1, Q2 and Q6 conducting, secondary only has rectifying tube DR1 and DR6 conducting.VAB=Vin/2 now, vBC=0, vCA=-Vin/2, can obtain according to transformer primary secondary voltage relation, vrect=kVin, k is the no-load voltage ratio of the every phase secondary of transformer to former limit.
2. switch mode 2 [t0-t1] [corresponding to Fig. 7]
Constantly, Q1 turn-offs t0, and iA charges to C1, and simultaneously to the C4 electric discharge, vrect starts linear decline.Because C1 and C4 have limited the voltage build-up rate of Q1, so Q1 is that no-voltage is turn-offed.Constantly, C1 and C4 discharge and recharge end to t1, the D4 conducting, and vrect drops to zero.
3. switch mode 3 [t1-t2] [corresponding to Fig. 8]
After C1 and C4 discharge and recharge end, the current transfer of the C1 that originally flowed through, to striding capacitance Css, slightly raises the Css both end voltage, so Df2 turn-offs.Open Q4 in this mode, due to before opening, the voltage at Q4 two ends is clamped at zero by D4, so Q4 is that no-voltage is open-minded, flows through the current transfer of D4 to the raceway groove of Q4.Secondary rectifying tube DR1, DR6 conducting, vrect is zero.
4. switch mode 4 [t2-t3] [corresponding to Fig. 9]
Constantly, switching tube Q6 turn-offs t2, and vAB oppositely increases, and vBA starts to rise, if vpa remains unchanged, now is equivalent to apply the voltage of one and current opposite in direction on Llka, so ipa can reduce, and be not enough to provide load current, thereby DR3 is open-minded.After this, junction capacitance C3, C6 and leakage inductance and extra resonance inductance generation resonance, ipa resonance reduces.When the C3 both end voltage reduces to zero, the conducting of D3 nature.
5. switch mode 5 [t3-t4] [corresponding to Figure 10]
Can open Q3 after the D3 conducting, because the Q3 both end voltage is clamped at zero by D3, so it is zero voltage switch.In this mode, switching tube Q2, Q3, Q4 conducting, secondary rectifying tube DR1, DR3, DR6 conducting.vAB=－Vin/2，vBC=Vin/2，vCA=0，vrect=0。The current value of noticing DR1 is reducing always, and when isa is reduced to zero, DR1 turn-offs, and DR2 is open-minded.
6. switch mode 6 [t4-t5] [corresponding to Figure 11]
In this mode, can try to achieve vrect according to former secondary voltage relation is 0.75kVin.The current value of noticing DR6 is reducing.When isc is reduced to zero, DR6 turn-offs, and the former secondary current of Trc is zero.
After this, switching tube Q2, Q3 and Q4 conducting, secondary rectifying tube DR2 and DR3 conducting, vrect is kVin, is similar to mode 1, its equivalent circuit diagram is as shown in figure 12.
Under control mode of the present invention, owing to adopting the three-phase circuit structure, secondary commutating voltage frequency is 1.5 times of traditional single phase converter, therefore can effectively reduce the output inductor current pulsation, further reduces output inductor.Figure 13 provides the correlation curve of three-phase tri-level converter and half-bridge three-level converter output inductor, and wherein design parameter is: Vin=540V ~ 660V, Vo=48V, fs=50kHz, Io=20A, Δ iLf=4 A.As shown in Figure 5, with half-bridge three-level converter, compare, adopt the three-phase tri-level converter of asymmetric control mode can obviously reduce output inductor, under above-mentioned design parameter, only be equivalent to 51.4% of half-bridge three-level converter.
Owing to adopting the three-phase circuit structure, converter can reduce the switching tube current effective value equally.Figure 14 provides the correlation curve of switching tube current effective value in asymmetric control mode three-phase tri-level converter and phase shifting control half-bridge three-level converter, and design parameter is the same.Therefrom find out, compare with half-bridge three-level converter, the three-phase tri-level converter can effectively reduce the switching tube current effective value.
In the three-phase tri-level inverter main circuit topology the present invention relates to, input side is connected to dividing potential drop capacitor C d1 and Cd2, and its capacity is very large and equal.Owing to adopting asymmetric control mode, the voltage of two dividing potential drop electric capacity may be unbalanced, and then cause half-bridge three-level unit midpoint potential imbalance, needs to analyze the voltage-sharing of dividing potential drop electric capacity for this reason.To simplify the analysis, ignore the impact of resonant inductance and leakage inductance.
Figure 15 and 16 has provided respectively the work wave that under little duty cycle mode and middle duty cycle mode, Cd1, Cd2 discharge and recharge.The table 1 of below has provided the energy increase and decrease situation of two kinds of next switch periods of different working modes interior Cd1, Cd2, and wherein " ↑ " means capacitor discharge, and " ↓ " means capacitor charging.
Table 1
Associative list 1 and Figure 13 can draw the following conclusions: under little duty cycle mode, Δ T2=2 Δ T1, equal the twice of its charging current on Cd1 discharging current numerical value, and therefore, the energy that in this two time periods, Cd1 discharge and recharge equates, its both end voltage remains unchanged.The Cd2 charge status is fully contrary.Hence one can see that, in a switch periods, and Cd1, the Cd2 conservation of energy, its voltage is half of input voltage vin, i.e. Vcd1=Vcd2=Vin/2.
In like manner, can analyze under middle duty cycle mode, the energy of Cd1, Cd2 is also conservation.
In sum, although adopt asymmetric control mode, dividing potential drop capacitor C d1, Cd2 all can realize discharging and recharging balance under different working modes, and its voltage remains unchanged, and is half of input voltage vin.
A specific embodiment of the present invention: input direct voltage: Vin=540 ~ 660V; Output dc voltage: Vo=48V; Output current: Io=20A; The secondary former limit of three-phase transformer no-load voltage ratio is 1:9; Output inductor: Lf=22uH; MOSFET (Q1-Q6): IPW65R080CFD; Fly-wheel diode (Df1, Df2): DSEI30-06A; Secondary rectifier diode (DR1-DR6): DSEP30-03A; Switching frequency: fs=50kHz.
Figure 17 ~ Figure 20 has provided respectively the driving voltage V that Vin is 540V and 660V, output full load switching tube Q2 and Q5
gS, drain-source voltage V
dSwith drain current I
dwaveform, now converter is operated in respectively under middle duty cycle mode and little duty cycle mode.As seen from the figure, the voltage stress of all switching tubes is half of input voltage, and before switching tube is opened, there is reverse current in its drain electrode, and its anti-and diode current flow, the switching tube both end voltage is clamped to zero, so it is that no-voltage is open-minded.The switching tube waveform of all the other two groups of brachium pontis is similar with it.
Above embodiment only, for explanation technological thought of the present invention, can not limit protection scope of the present invention with this, every technological thought proposed according to the present invention, and any change of doing on the technical scheme basis, within all falling into protection range of the present invention.
Claims (1)
1. the asymmetric control method of a reduced form three-phase tri-level DC converter, related reduced form three-phase tri-level DC converter comprises input dividing potential drop condenser network, the half-bridge three-level unit, full bridge unit, three-phase isolation transformer and rectification and filter circuit, wherein the half-bridge three-level unit comprises the first and second fly-wheel diodes, striding capacitance and first, the 3rd, the the 4th and the 6th switching tube, full bridge unit comprises first, second, the the 4th and the 5th switching tube, full bridge unit and half-bridge three-level units shared first and the 4th switching tube, the drain electrode of the 6th switching tube connects the positive input terminal of input dividing potential drop condenser network, the source electrode of the 3rd switching tube connects the negative input end of input dividing potential drop condenser network, the source electrode of the 6th switching tube connects respectively the negative electrode of the first fly-wheel diode, one end of striding capacitance, the drain electrode of the drain electrode of the first switching tube and the 5th switching tube, the drain electrode of the 3rd switching tube connects respectively the anode of the second fly-wheel diode, the other end of striding capacitance, the source electrode of the source electrode of the 4th switching tube and second switch pipe, the first fly-wheel diode anode is connected the tie point of the first dividing potential drop electric capacity other end and the second dividing potential drop electric capacity other end in input dividing potential drop condenser network with the tie point of the second fly-wheel diode negative electrode, the first switching tube source electrode is connected the Same Name of Ends of the former limit of a phase transformer winding with the tie point of the 4th switching tube drain electrode by the parasitic leakage inductance in the former limit of a phase transformer, the first fly-wheel diode anode is connected the Same Name of Ends of the former limit of b phase transformer winding with the tie point of the second fly-wheel diode negative electrode by the parasitic leakage inductance in the former limit of b phase transformer, the 5th switching tube source electrode is connected the Same Name of Ends of the former limit of c phase transformer winding with the tie point of second switch pipe drain electrode by the parasitic leakage inductance in the former limit of c phase transformer, the Same Name of Ends of a phase transformer secondary winding connects the tie point of the first rectifier diode anode and the second rectifier diode negative electrode, the Same Name of Ends of b phase transformer secondary winding connects the tie point of the 3rd rectifier diode anode and the 4th rectifier diode negative electrode, the Same Name of Ends of c phase transformer secondary winding connects the tie point of the 5th rectifier diode anode and the 6th rectifier diode negative electrode, it is characterized in that: first, the 3rd is identical with the ON time of the 5th switching tube, its change in duty cycle scope is 0～1/2, its service time 1/3 switch periods of being separated by, by regulating first, the 3rd and the duty of the 5th switching tube recently control output voltage, the second, the 4th identical with the ON time of the 6th switching tube and respectively with the 5th, first and the 3rd switching tube corresponding complementary conducting, between two complementary switching tubes, arranged time of delay.
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Cited By (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN104022653A (en) * | 2014-06-03 | 2014-09-03 | 南京航空航天大学 | Boost type three-phase three-level direct current converter and control method thereof |
| CN106329941A (en) * | 2015-06-17 | 2017-01-11 | 联想(北京)有限公司 | Full-bridge converter and soft switching realization method |
Citations (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101860206A (en) * | 2010-05-12 | 2010-10-13 | 杭州矽力杰半导体技术有限公司 | Three-level buck convertor |
| CN102025280A (en) * | 2010-12-22 | 2011-04-20 | 南京航空航天大学 | Symmetry control type three-phase three-level direct current converter and symmetry control method thereof |
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Patent Citations (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101860206A (en) * | 2010-05-12 | 2010-10-13 | 杭州矽力杰半导体技术有限公司 | Three-level buck convertor |
| CN102025280A (en) * | 2010-12-22 | 2011-04-20 | 南京航空航天大学 | Symmetry control type three-phase three-level direct current converter and symmetry control method thereof |
Cited By (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN104022653A (en) * | 2014-06-03 | 2014-09-03 | 南京航空航天大学 | Boost type three-phase three-level direct current converter and control method thereof |
| CN106329941A (en) * | 2015-06-17 | 2017-01-11 | 联想(北京)有限公司 | Full-bridge converter and soft switching realization method |
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