CN102969912A - Control and drive circuit and method - Google Patents
Control and drive circuit and method Download PDFInfo
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- CN102969912A CN102969912A CN2012104073407A CN201210407340A CN102969912A CN 102969912 A CN102969912 A CN 102969912A CN 2012104073407 A CN2012104073407 A CN 2012104073407A CN 201210407340 A CN201210407340 A CN 201210407340A CN 102969912 A CN102969912 A CN 102969912A
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
- H02M3/33576—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
- H02M3/33592—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer having a synchronous rectifier circuit or a synchronous freewheeling circuit at the secondary side of an isolation transformer
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33507—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters
- H02M3/33523—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters with galvanic isolation between input and output of both the power stage and the feedback loop
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33538—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only of the forward type
- H02M3/33546—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only of the forward type with automatic control of the output voltage or current
- H02M3/33553—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only of the forward type with automatic control of the output voltage or current with galvanic isolation between input and output of both the power stage and the feedback loop
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Dc-Dc Converters (AREA)
- Rectifiers (AREA)
Abstract
The invention provides a control and drive circuit applied to a synchronous rectification switching mode power supply. The circuit comprises a primary switching tube controller, a logic circuit, a switching circuit and a synchronous rectifier tube controller, wherein the primary switching tube controller is used for generating a primary switching tube control signal, the logic circuit is used for generating a first control signal according to received primary switching tube control signal, the switching circuit is used for generating a second control signal according to the received first control signal, and the synchronous rectifier tube controller is used for generating a synchronous rectifier tube control signal according to the received second control signal and guaranteeing phases of the primary switching tube control signal and the synchronous rectifier tube control signal to be the same or inverse according to a topological structure of the synchronous rectification switching mode power supply. The invention further provides a control and drive method, so that the synchronous rectifier tube control signal for controlling on and off of a synchronous rectifier tube is generated according to the primary switching tube control signal, the problem of cross connection of the synchronous rectification power supply is solved, and high frequency, low cost, small size and high efficiency of the synchronous rectification switching mode power supply are achieved.
Description
Technical field
The present invention relates to field of switch power, relate in particular to a kind of driving circuits and method.
Background technology
Along with the development of switch power technology, the low-voltage, high-current Switching Power Supply more and more becomes a kind of important development trend, and efficiency is a theme of the low-voltage, high-current Switching Power Supply rule of development all the time.Synchronous rectification is a kind of method that the low-voltage, high-current occasion is raised the efficiency common employing, can reduce the loss of synchronous rectifying switching power source by synchronous rectification.The key of synchronous rectification is the type of drive of synchronous rectifier, and different type of drive is that very large difference is arranged on the impact of efficient.
Referring to Figure 1A, shown in the figure is the driving control mode of existing the first inverse-excitation type synchronous rectifying Switching Power Supply.Its operation principle is: former limit switching regulator controller U
1Produce a pwm signal and control former limit switching tube Q
1Turn on and off, when this pwm signal is high level when effective, former limit switching tube Q
1Conducting, transformer storage power, at this moment synchronous rectifier Q
2Drain-source voltage V
DSGreater than zero, synchronous rectification tube controller U
3Detect V
DSAfter＞0, control synchronous rectifier Q
2Turn-off; When this pwm signal is low level when invalid, former limit switching tube Q
1Turn-off, transformer energy is delivered to secondary by former limit, and secondary current flows through synchronous rectifier Q
2Inner anti-paralleled diode D causes synchronous rectifier Q
2The voltage at drain-source two ends becomes V
DS=-V
DF, V wherein
DFBe the forward conduction voltage drop of anti-paralleled diode D, this explanation synchronous rectifier Q this moment
2Drain-source voltage V
DSLess than zero, the synchronous rectifier driver detects V
DSAfter＜0, control synchronous rectifier Q
2Open-minded, secondary current flows through synchronous rectifier Q
2And no longer flow through anti-paralleled diode D, until exporting high level signal again, former limit switching regulator controller controls former limit switching tube Q
1Conducting, synchronous rectifier Q
2To again be turned off.The metal-oxide-semiconductor that this synchronous rectification control mode has a low on-resistance by employing substitutes the fast recovery diode in the common inverse excitation type converter, has realized the lifting to flyback power supply efficient.But, in this scheme, if when secondary current does not drop to zero, former limit switching tube driver U
1Controlled former limit switching tube Q
1Conducting then can cause converter the phenomenon of simultaneously conductings of two switching tubes (being cross-conduction) to occur.For avoiding the appearance of cross-conduction, this control mode mainly be applicable to be operated in the inverse excitation type converter of discontinuous conduction mode (DCM) or secondary current can the LLC converter of zero passage in, the scope of application is narrower.In addition, in synchronous rectifying switching power source, the ON time of anti-paralleled diode D is less, and the whole efficiency of power supply is higher, still, in this scheme, synchronous rectifier Q
2Turn-on and turn-off control more complicated, be difficult to reduce the ON time of anti-paralleled diode D, thereby be difficult to further improve power-efficient.
Referring to Figure 1B, shown in the figure is the driving control mode of existing the second inverse-excitation type synchronous rectifying Switching Power Supply.Wherein, former limit switching regulator controller U
1For generation of two-way pwm signal V
G1And V
G2P, and pwm signal V
G1With pwm signal V
G2PBe complementary signal, transformer T
2Be used for transmission pwm signal V
G2PTo secondary.Its operation principle is as follows: as pwm signal V
G1Be high level when effective, complementary PWM signals V
G2PFor low level is invalid, pwm signal V
G1Control former limit switching tube Q
1Conducting, complementary PWM signals V
G2PThrough transformer T
2Be transferred to secondary, be converted to synchronous rectifier control signal V through the synchronous rectification tube controller
G2, this moment synchronous rectifier control signal V
G2Also be low level, synchronous rectifier Q
2Turn-off; As pwm signal V
G1Become low level when invalid, complementary PWM signals V
G2PIt is effective to become high level, pwm signal V
G1Control former limit switching tube Q
1Turn-off, at this moment synchronous rectifier control signal V
G2Become high level control synchronous rectifier Q
2Open-minded.This shows that this scheme can solve the cross-conduction problem that exists in the first scheme, and, synchronous rectifier Q
2Turn-on and turn-off control also simple than the first.But, because transformer T
2Existence, volume and the cost of circuit greatly increase, and transformer T
2Be difficult to transmit fast-changing duty cycle signals.
Therefore, how in high frequency electric source, to obtain rapidly and accurately the driving signal of synchronous rectifier according to the driving signal of former limit switching tube, satisfy simultaneously the requirement of low cost, small size, high efficiency, high reliability, and solve the problem of cross-conduction, become the key of design synchronous rectifying switching power source drive circuit.
Summary of the invention
The purpose of this invention is to provide a kind of driving circuits and method, be applied in the synchronous rectifying switching power source, can produce opening and turn-offing of the former limit former limit of switch controlled signal controlling switching tube, simultaneously produce corresponding the first control signal according to one of them former limit switch controlled signal, this first control signal obtains the second control signal after processing through change-over circuit, and then the synchronous rectification tube controller produces synchronous rectifier according to this second control signal and drives opening and turn-offing of signal controlling synchronous rectifier.The present invention can solve the cross-conduction problem that occurs in the conventional synchronization rectifier switch power supply, simultaneously can accurately control rapidly opening and turn-offing of synchronous rectifier according to one of them former limit switch controlled signal, realize high frequency, low cost, small size and the high efficiency of synchronous rectifying switching power source.In addition, the present invention also adopts a buffer circuit that former border district and the secondary ground of synchronous rectifying switching power source is isolated, thereby has guaranteed the safe and reliable work of synchronous rectifying switching power source.
For achieving the above object, the invention provides a kind of driving circuits, be applied to comprise in the synchronous rectifying switching power source: former limit switching regulator controller, for generation of former limit switch controlled signal; Logical circuit is used for producing the first control signal according to the described former limit switch controlled signal that receives; Change-over circuit is used for producing the second control signal according to described the first control signal that receives; The synchronous rectification tube controller, be used for producing the synchronous rectifier control signal according to described the second control signal that receives, and according to the topological structure of described synchronous rectifying switching power source, guarantee described former limit switch controlled signal and described synchronous rectifier control signal homophase or anti-phase.
Further, when the on off state of the former limit switching tube in the described synchronous rectifying switching power source and synchronous rectifier is opposite, described logical circuit comprises delay circuit and inverter, delays time with anti-phase control to produce described the first control signal according to described former limit switch controlled signal; Described synchronous rectification tube controller produces described synchronous rectifier control signal constantly according to the zero passage of described the second control signal.
Further, when the on off state of the former limit switching tube in the described synchronous rectifying switching power source and synchronous rectifier is opposite, described logical circuit comprises delay circuit and inverter, and the described former limit switch controlled signal that described delay circuit is used for receiving delays time to produce described the first control signal; Described synchronous rectification tube controller produces the 3rd control signal constantly according to the zero passage of described the second control signal; Described inverter is used for described the 3rd control signal is carried out anti-phase to produce described synchronous rectifier control signal.
Further, when the on off state of the former limit switching tube in the described synchronous rectifying switching power source and synchronous rectifier is consistent, described logical circuit comprises delay circuit, and the described former limit switch controlled signal that described delay circuit is used for receiving delays time to produce described the first control signal; Described synchronous rectification tube controller produces described synchronous rectifier control signal constantly according to the zero passage of described the second control signal.
Further, described change-over circuit comprises differential capacitance and differential resistance.
Further, described driving circuits also comprises the former border district that is connected across described synchronous rectifying switching power source and the buffer circuit between the secondary ground, is used for isolating former border district and the secondary ground of described synchronous rectifying switching power source.
Further, described buffer circuit comprises isolation capacitance.
Further, described driving circuits also comprises the first clamp circuit, the second clamp circuit, and described the first clamp circuit is for the protection of described former limit switching regulator controller; Described the second clamp circuit is for the protection of described synchronous rectification tube controller.
Further, described the first clamp circuit comprises the first diode, the second diode, the first clamp voltage and the second clamp voltage, when the amplitude of described the first control signal during greater than described the first clamp voltage or less than described the second clamp voltage, described the first clamp circuit is clamped to described the first clamp voltage or described the second clamp voltage with the amplitude of described the first control signal; Described the second clamp circuit comprises the 3rd diode, the 4th diode, the 3rd clamp voltage and the 4th clamp voltage, when the amplitude of described the second control signal during greater than described the 3rd clamp voltage or less than described the 4th clamp voltage, described the second clamp circuit is clamped to described the 3rd clamp voltage or described the 4th clamp voltage with the amplitude of described the second control signal.
According to a further aspect in the invention, provide a kind of control and driving method, be applied to may further comprise the steps in the synchronous rectifying switching power source:
Produce described former limit switch controlled signal;
To produce the first control signal after the logical operation of described former limit switch controlled signal process;
To produce the second control signal after the conversion of described the first control signal process differential;
Described the second control signal is produced the synchronous rectifier control signal through after controlling.
Further, described control and driving method also comprise former border district and secondary ground are isolated.
Further, when the on off state of the former limit switching tube in the described synchronous rectifying switching power source and synchronous rectifier is opposite, described logic control comprise to described former limit switch controlled signal carry out anti-phase and time-delay control obtaining described the first control signal, described synchronous rectifier control signal produces described synchronous rectifier control signal with described former limit switch controlled signal inversion according to described the second control signal.
Further, when the on off state of the former limit switching tube in the described synchronous rectifying switching power source and synchronous rectifier is consistent, described logic control comprises delays time control to obtain described the first control signal to described former limit switch controlled signal, and described synchronous rectifier control signal is according to the described synchronous rectifier control signal of described the second control signal generation with described former limit switch controlled signal homophase.
This shows, the present invention is by the sequential relationship of described the first control signal of control and described former limit switch controlled signal, can produce described the first control signal according to described former limit switch controlled signal, simultaneously by adopting described change-over circuit rapidly and accurately described the first control signal to be converted to described the second control signal, and by described synchronous rectification tube controller described the second control signal is converted to described synchronous rectifier control signal, to realize the control to described synchronous rectifier.This scheme not only can be avoided the cross-conduction of described former limit switching tube and described synchronous rectifier, can also reduce as much as possible the ON time of the anti-paralleled diode of described synchronous rectifier, farthest improves system effectiveness.Because in the present embodiment, described change-over circuit adopts the RC differential circuit to realize, compare and adopt the transformer signal transmission among Figure 1B, Cost reduction and volume improve power density widely.In addition, buffer circuit in the present embodiment adopts electric capacity to realize, can suppress common mode disturbances, prevent that capacitor lost efficacy after, can not cause shocking by electricity, jeopardizing the problem of personal safety, strengthen reliability and the fail safe of synchronous rectifying switching power source.
In addition, the present invention adopts described the first clamp circuit and described the second clamp circuit to protect described former limit switching regulator controller and the normal operation of described synchronous rectification tube controller.
In the different topology structure.Those of ordinary skills can be according to the logical relation of the control signal of former limit switching tube and synchronous rectifier, selects among the present invention suitable drive circuit to realize the synchronous rectifying switching power source of different topology structure is controlled.
Description of drawings
Figure 1A is the theory diagram of the first inverse-excitation type synchronous rectifying Switching Power Supply in the prior art;
Figure 1B is the theory diagram of the second inverse-excitation type synchronous rectifying Switching Power Supply in the prior art;
Fig. 2 A is the theory diagram of inverse-excitation type synchronous rectifying Switching Power Supply in the embodiment of the invention one;
Fig. 2 B is the working waveform figure of inverse-excitation type synchronous rectifying Switching Power Supply among Fig. 2 A of the present invention;
Fig. 2 C is the schematic diagram of a kind of embodiment of logical circuit in the inverse-excitation type synchronous rectifying Switching Power Supply shown in Fig. 2 A of the present invention;
Fig. 2 D is the schematic diagram of a kind of embodiment of synchronous rectification tube controller in the inverse-excitation type synchronous rectifying Switching Power Supply shown in Fig. 2 A of the present invention;
Fig. 2 E is the signal waveforms of synchronous rectification tube controller shown in Fig. 2 D of the present invention;
Fig. 3 is the theory diagram of inverse-excitation type synchronous rectifying Switching Power Supply in the embodiment of the invention two;
Fig. 4 is the theory diagram of positive activation type synchronous rectifying switching power source in the embodiment of the invention three;
Fig. 5 is the theory diagram of push-pull type synchronous rectifying switching power source in the embodiment of the invention four;
Fig. 6 is the theory diagram of full-bridge type synchronous rectifying switching power source in the embodiment of the invention five;
Fig. 7 A is the flow chart of the first embodiment of control of the present invention and driving method;
Fig. 7 B is the flow chart of the second embodiment of control of the present invention and driving method.
Embodiment
For above-mentioned purpose of the present invention, feature and advantage can be become apparent more, below in conjunction with accompanying drawing the specific embodiment of the present invention is described in detail.
A lot of details have been set forth in the following description so that fully understand the present invention.But the present invention can implement much to be different from alternate manner described here, and those skilled in the art can do similar popularization in the situation of intension of the present invention, so the present invention is not subjected to the restriction of following public implementation.
[embodiment one]
Embodiment shown in Fig. 2 A is a kind of inverse-excitation type synchronous rectifying Switching Power Supply.Described inverse-excitation type synchronous rectifying Switching Power Supply comprises power stage circuit and drive circuit, is used for direct voltage V
INBe converted to output voltage V
Out, wherein said power stage circuit comprises filter capacitor C
1, transformer T, former limit switching tube Q
1, synchronous rectifier Q
2With output filter capacitor C
OutDescribed drive circuit comprises former limit switching regulator controller U
1, logical circuit U
2, change-over circuit 201 and synchronous rectification tube controller U
3Described former limit switching regulator controller U
1For generation of former limit switch controlled signal V
GPTo control described former limit switching tube Q
1Open and turn-off, its first output connects described former limit switching tube Q
1Control end and described logical circuit U
2Input; Described logical circuit U
2Be used for receiving described former limit switch controlled signal V
GPTo produce the first control signal V
GP1, its output connects the input of described change-over circuit 201; Described change-over circuit 201 is used for receiving described the first control signal V
GP1To produce the second control signal V
GS1, its output connects described synchronous rectification tube controller U
3Input; Described synchronous rectification tube controller U
3Be used for receiving described the second control signal V
GS1To produce synchronous rectifier control signal V
GSControl described synchronous rectifier Q
2Open and turn-off, its output connects described synchronous rectifier Q
2Control end.
In the present embodiment, described change-over circuit 201 can be by differential capacitance C
YaWith differential resistance R
YaThe differential circuit that is connected in series composition is realized differential capacitance C
YaSpan can be 0.1pF～100pF, described differential resistance R
YaSpan can be 1k Ω～1M Ω.
In conjunction with the working waveform figure of the inverse-excitation type synchronous rectifying Switching Power Supply shown in Fig. 2 B, its operation principle can be described below: at t
1Constantly, described former limit switching regulator controller U
1Control described former limit switch controlled signal V
GpSaltus step is that high level signal is so that described former limit switching tube Q
1Conducting is through ON time t
OnAfter, at t
2Constantly, described former limit switch controlled signal V
GpSaltus step is that low level signal is controlled described former limit switching tube Q
1Turn-off, opposite, through turn-off time t
OffAfter, at t
3Constantly, described former limit switch controlled signal V
GPSaltus step is that high level signal is controlled described former limit switching tube Q again
1Conducting; Described former limit switch controlled signal V
GPThrough logical circuit U
2Time-delay and anti-phase processing after can obtain described the first control signal V
GPlWherein delay time can be made as t
dThereby, at t
4Constantly, described the first control signal V
GP1Be high level signal by the low level signal saltus step, at this moment, because the differential capacitance C in the described change-over circuit 201
YaOn voltage can not suddenly change, be equivalent to short circuit, described former limit switching tube drives signal V
GPBe added in differential resistance R fully
YaOn, cause described the second control signal V
GS1Moment rises, and producing one is positive spike, and its amplitude and described former limit switching tube drive signal V
GPAmplitude identical, afterwards, differential capacitance C
YaPress the index law charging, differential resistance R
YaTherefore upper voltage pressed index law and descended this positive spike elapsed time t
wAfterwards at t
5Constantly arrive zero, meanwhile, described synchronous rectification tube controller U
3According to described the second control signal V that detects
GS1The negative sense zero cross signal control described synchronous rectifier control signal V
GSSaltus step is high level; ON time t through described the first control signal
On(wherein, t
On=t
Off), at t
6Constantly, described the first control signal V
GP1Be low level signal by the high level signal saltus step, because the differential capacitance C in the change-over circuit 201
YaThe voltage of upper storage can not suddenly change, and causes described the second control signal V
GS1Moment descends, and begins to produce a undershoot, afterwards, and differential capacitance C
YaPress the index law discharge, this undershoot elapsed time t
wAfterwards at t
7Constantly arrive zero, meanwhile, described synchronous rectification tube controller U
3According to described the second control signal V that detects
GS1The positive going zeror crossing signal control described synchronous rectifier control signal V
GSSaltus step is low level; With this driving control that circulates and realize synchronous rectifying switching power source.
In order to raise the efficiency to greatest extent, can strictly control former limit switching tube Q
1With synchronous rectifier Q
2Switching sequence, as described former limit switching tube Q
1During shutoff, control described synchronous rectifier Q
2Conducting is as described synchronous rectifier Q
2During shutoff, control described former limit switching tube Q
1Conducting.In the present embodiment, can control described former limit switching tube Q by width and described delay time that described spiking is set
1With described synchronous rectifier Q
2Switching sequence, at first the spiking width can be set to t
w=3 * τ, wherein, τ=R
Ya* C
Ya, and delay time is set to t
d=T-t
w, wherein T is the cycle of switching tube,, it should be noted that arranging of spiking width need to satisfy t here
w＜t
OnAnd t
w＜t
Off, wherein, t
OnBe the ON time of described former limit switching tube, t
OffBe the turn-off time of described former limit switching tube.
In the present embodiment, the width of described spiking is set to t
w=3 * τ is because common differential capacitance C
YaThrough 3 RC timeconstantτs, can substantially reach amplitude.Certainly, this spiking width also can be set to other values, for example t
w=4 * τ, t
w=5 * τ or t
w=6 * τ etc.
With reference to figure 2C, be depicted as shown in Fig. 2 A the first execution mode of logical circuit in the inverse-excitation type synchronous rectifying Switching Power Supply.Described logical circuit U
2 Comprise delay circuit 210 and inverter 211, described delay circuit 210 is for the described former limit switch controlled signal V that will receive
GPDescribed delay time t delays time
d, its input connects described former limit switching regulator controller U
1Output, output connects the input of described inverter 211; Described former limit switch controlled signal V after described inverter 211 is used for delaying time
GPAnti-phase, its output connects described change-over circuit 201.In the present embodiment, described delay circuit 210 can be by resistance R
2And capacitor C
2Realize described delay time t
dCan pass through regulating resistance R
2And capacitor C
2Parameter obtain; Described inverter 211 can be by not gate A
1Realize.
Except execution mode shown in Fig. 2 C, described logical circuit U
2Function also can realize by the link position of the described delay circuit 210 among the transposing Fig. 2 C and described inverter 211.Certainly, described logical circuit U
2Also can be by other any the electric circuit constitutes that can realize its function.
With reference to figure 2D, be depicted as a kind of execution mode of synchronous rectification tube controller in the inverse-excitation type synchronous rectifying Switching Power Supply shown in Fig. 2 A.Described synchronous rectification tube controller U
3Comprise zero cross detection circuit 220 and the first rest-set flip-flop 222, described zero cross detection circuit 220 comprises the first comparator 220, the second comparator 221, the first monopulse generator 224 and the second monopulse generator 225, the in-phase input end of described the first comparator 222 be connected the common output that connects described change-over circuit 201 of inverting input of the second comparator 223, in order to receive described the second control signal V
GS1The inverting input of described the first comparator 222 is used for receiving the first reference voltage V
Ref1, output produces the first comparison signal V
C1Give the input of the first monopulse generator 224; The output of the first monopulse generator 224 produces reset signal V
RGive the reset terminal R of described the first rest-set flip-flop 221 with the described synchronous rectifier control signal V that resets
GSThe inverting input of described the second comparator 223 is used for receiving the second reference voltage V
Ref2, output produces the second comparison signal V
C2Give the input of the second monopulse generator 225; The output of the second monopulse generator 225 produces asserts signal V
SGive the set end S of described the first rest-set flip-flop 221 with the described synchronous rectifier control signal of set V
GSThe Q end of described the first rest-set flip-flop 221 connects described synchronous rectifier Q
2Control end in order to produce described synchronous rectifier control signal V
GSWherein, described the first reference voltage V
Ref1Can be set to be slightly less than zero, described the second reference voltage V
Ref2Can be set to be slightly larger than zero.In conjunction with Fig. 2 E, be depicted as the signal waveforms of way of example among Fig. 2 D, its operation principle can be described below: at t
8Constantly, as described the second control signal V
GS1Produce undershoot and less than described the first reference voltage V
Ref1With the second reference voltage V
Ref2The time, described the first comparison signal V
C1Saltus step is low level, described the second comparison signal V
C2Be high level, described synchronous rectifier control signal V
GSBecause set is high level; At t
9Constantly, as described the second control signal V
GS1Forward arrives described the first reference voltage V
Ref1The time, described the first comparison signal V
C1Saltus step is high level, and described the first monopulse generator 224 produces the reset signal V of a pulse
RSo that described synchronous rectifier control signal V
GSBecause the saltus step that resets is low level; At t
10Constantly, as described the second control signal V
GS1Produce positive spike and greater than described the second reference voltage V
Ref2The time, described the second comparison signal V
C2Saltus step is low level, described synchronous rectifier control signal V
GSStill be low level because resetting; At t
11Constantly, as described the second control signal V
GS1Negative sense arrives described the second reference voltage V
Ref2The time, described the second comparison signal V
C2Saltus step is high level, and described the second monopulse generator 225 produces the asserts signal V of a pulse
SSo that described synchronous rectifier control signal V
GSBecause the set saltus step is high level; With this repeatedly, synchronous rectification tube controller U
3Can be according to described the second control signal V
GS1Produce described synchronous rectifier control signal V
GS
Except execution mode shown in Fig. 2 D, described synchronous rectification tube controller U
3Function also can be realized by other circuit.
In the embodiment shown in Fig. 2 C and Fig. 2 D, adopt at described logical circuit U
2 Middle adding inverter 211 is with the described synchronous rectifier control signal of final realization V
GSWith described former limit switch controlled signal V
GPAnti-phase.Those of ordinary skill in the art can be known by inference thus, also can pass through only at described logical circuit U
2The described delay circuit 210 of middle adding, and at described synchronous rectification tube controller U
3Middle adding inverter is with the described synchronous rectifier control signal of final realization V
GSWith described former limit switch controlled signal V
GPAnti-phase.
In addition, in the present embodiment, described inverse-excitation type synchronous rectifying Switching Power Supply also comprises a buffer circuit 202, and described buffer circuit 202 can be by isolation capacitance C
YbRealize.Described isolation capacitance C
YbBe connected across between former border district and the secondary ground, be used for the former border district GND to described inverse-excitation type synchronous rectifying Switching Power Supply
1With secondary ground GND
2Isolate.At this, described former limit switching regulator controller U
1Reference ground be former border district GND
1, described synchronous rectifier driver U
3Reference ground be secondary ground GND
2
This shows, in the present embodiment, by controlling described the first control signal V
GP1With described former limit switch controlled signal V
GPSequential relationship, can be according to described former limit switch controlled signal V
GPProduce described the first control signal V
GP1, simultaneously by adopting described change-over circuit 201, can be rapidly and accurately with described the first control signal V
GP1Be converted to described the second control signal V
GS1, and by described synchronous rectification tube controller U
3With described the second control signal V
GS1Be converted to described synchronous rectifier control signal V
GS, to realize described synchronous rectifier Q
2Control.This scheme not only can be avoided described former limit switching tube Q
1With described synchronous rectifier Q
2Cross-conduction, can also reduce as much as possible described synchronous rectifier Q
2The ON time of anti-paralleled diode D, farthest improve system effectiveness.Because in the present embodiment, described change-over circuit adopts differential capacitance C
YaWith differential resistance R
YaRealize that compare and adopt the transformer signal transmission among Figure 1B, Cost reduction and volume improve power density widely.In addition, the buffer circuit in the present embodiment 202 adopts isolation capacitance C
YbRealize, can suppress common mode disturbances, prevent that capacitor lost efficacy after, can not cause shocking by electricity, jeopardizing the problem of personal safety, strengthen reliability and the fail safe of synchronous rectifying switching power source.
[embodiment two]
Embodiment as shown in Figure 3 is a kind of inverse-excitation type synchronous rectifying Switching Power Supply after improve on the basis of Fig. 2 A circuit.Different from inverse-excitation type synchronous rectifying Switching Power Supply shown in Fig. 2 A is, for protecting described former limit switching regulator controller U
1With described synchronous rectification tube controller U
3, present embodiment has added the first clamp circuit 301 and the second clamp circuit 302.Described the first clamp circuit 301 comprises the first diode D
1, the second diode D
2, the first clamp voltage V
CLP1With the second clamp voltage V
CLP2, described the first diode D
1Negative electrode be connected to the first clamp voltage V
CLP1, described the second diode D of anodic bonding
2Negative electrode, its common port connects the input of described change-over circuit 201, described the second diode D
2Anodic bonding the second clamp voltage V
CLP2Described the second clamp circuit 302 comprises the 3rd diode D
3, the 4th diode D
4, the 3rd clamp voltage V
CLP3With the 4th clamp voltage V
CLP4, described the 3rd diode D
3Negative electrode be connected to the 3rd clamp voltage V
CLP3, anodic bonding the 4th diode D
4Negative electrode, the output of its common port change-over circuit 201, described the 4th diode D
4Anodic bonding to the four clamp voltage V
CLP4Wherein, described the first clamp voltage V is set
CLP1A little more than the first control signal V
GP1Maximum, described the second clamp voltage V
CLP2Be slightly less than described the first control signal V
GP1Minimum value, described the first clamp voltage V
CLP1With described the second clamp voltage V
CLP2All with former border district GND
1As reference ground; Described the 3rd clamp voltage V is set
CLP3Value be slightly larger than described differential signal V
G2SMaximum, described the 4th clamp voltage V
CLP4Value be slightly less than described the second control signal V
GS1Minimum value, described the 3rd clamp voltage V
CLP3With described the 4th clamp voltage V
CLP4All with secondary ground GND
2As reference ground.
Because the existence of described the first clamp circuit 301 is as described the first control signal V
GP1Voltage produce because being interfered the fluctuation cause its maximum to be higher than V
CLP1The time, described the first diode D
1Conducting is with the first control signal V
GP1Voltage clamping to described the first clamp voltage V
CLP1As described the first control signal V
GP1Voltage produce because being interfered the fluctuation cause its minimum value to be lower than V
CLP2The time, described the second diode D
2Conducting is with the first control signal V
GP1Voltage clamping to described the second clamp voltage V
CLP2
In like manner, because the existence of described the second clamp circuit 302, as described the second control signal V
GS1Producing fluctuation because being interfered causes its maximum to be higher than V
CLP3The time, described the 3rd diode D
3Conducting is with described the second control signal V
GS1Voltage clamping to described the 3rd clamp voltage V
CLP3As described the second control signal V
GS1Voltage produce because being interfered the fluctuation cause its minimum value to be lower than V
CLP4The time, described the 4th diode D
4Conducting is with described the second control signal V
GS1Voltage clamping to described the 4th clamp voltage V
CLP4
Except the first clamp circuit 301 and the second clamp circuit 302, the remainder circuit structure in the present embodiment is identical with inverse-excitation type synchronous rectifying Switching Power Supply shown in Fig. 2 A with operation principle, will repeat no more at this.
Hence one can see that, because the existence of described the first clamp circuit 301 and described the second clamp circuit 302 can be avoided causing described the first control signal V because of interference
GP1With described the second control signal V
GS1The phenomenon that amplitude is excessive or too small is to protect described former limit switching regulator controller U
1With described synchronous rectification tube controller U
3Normal operation.
In addition, described the 3rd clamp voltage V
CLP3Can also be described synchronous rectification tube controller U
3Provide bias voltage, described differential capacitance C
YaCan also be described synchronous rectification tube controller U
3Driving-energy is provided.
Those of ordinary skills as can be known, described the first clamp circuit 301 and described the second clamp circuit 302 also can be realized by other appropriate circuitry.
[embodiment three]
Be illustrated in figure 4 as positive activation type synchronous rectifying switching power source in the embodiment of the invention three.Described positive activation type synchronous rectifying switching power source comprises power stage circuit and drive circuit, and wherein said power stage circuit comprises filter capacitor C
1, transformer T, former limit switching tube Q
1, synchronous rectifier Q
2, synchronous rectifier Q
3With output filter capacitor C
OutDescribed drive circuit comprises former limit switching regulator controller U
1, logical circuit U
2, change-over circuit 201 and synchronous rectification tube controller U
3Different from inverse-excitation type synchronous rectifying Switching Power Supply in Fig. 2 A illustrated embodiment one is that in the present embodiment, described transformer T is that Same Name of Ends connects described synchronous freewheeling pipe Q
3With described output filter capacitor C
OutBe connected in parallel described synchronous rectification tube controller U
3Except producing described synchronous rectifier control signal V
GSAlso produce simultaneously a synchronous continued flow tube control signal V outward,
Gs' to control described synchronous freewheeling pipe Q
3Open and turn-off, synchronous rectification tube controller U herein
3Execution mode can adopt the illustrated embodiment such as Fig. 2 D, wherein, the non-end of Q of the first rest-set flip-flop 221 is used for exporting described synchronous freewheeling management and control signal V processed among Fig. 2 D embodiment
Gs'; The connected mode of the remainder of described positive activation type synchronous rectifying switching power source and major function, and described differential capacitance C
Ya, isolation capacitance C
YbWith described differential resistance R
YaSpan all with Fig. 2 A illustrated embodiment one in the inverse-excitation type synchronous rectifying Switching Power Supply similar, will repeat no more at this.
It should be noted that since the power stage circuit topological structure of present embodiment from different shown in Fig. 2 A, former limit switching tube Q described in the present embodiment
1During conducting, described synchronous rectifier Q
2Simultaneously conducting; Described former limit switching tube Q
1During shutoff, described synchronous rectifier Q
2Also turn-off simultaneously.Therefore, the operation principle of the positive activation type synchronous rectifying switching power source drive circuit in the present embodiment is slightly different from the inverse-excitation type synchronous rectifying switch power source driving circuit shown in Fig. 2 A to Fig. 2 D.Its difference is, in the present embodiment since synchronous rectifier Q2 all the time with former limit switching tube Q1 homophase, thereby do not need at described logical circuit U
2Perhaps described synchronous rectification tube controller U
3The described inverter 211 of middle adding, i.e. described the first control signal V
GP1By described former limit switch controlled signal V
GPThrough described logical circuit U
2Obtain described synchronous rectifier control signal V through time-delay
GSBy the second control signal V
GS1Through synchronous rectification tube controller U
3Obtain; And the remainder operation principle is all similar with the inverse-excitation type synchronous rectifying switch power source driving circuit, will repeat no more at this.
In the present embodiment, the width of spiking and the setting of delay time are also similar with the inverse-excitation type synchronous rectifying switch power source driving circuit, will repeat no more at this.
[embodiment four]
Be illustrated in figure 5 as push-pull type synchronous rectifying switching power source in the embodiment of the invention four.Different from positive activation type synchronous rectifying switching power source in embodiment illustrated in fig. 4 three is, the power stage circuit in the present embodiment adopts the push-pull type topology, and its structure is well known to those of ordinary skill in the art, will repeat no more at this.For adapting to push-pull type topological structure, described former limit switching regulator controller U
1With described synchronous rectification tube controller U
3All need to produce two path control signal, in this embodiment, because described former limit switching tube Q
1With described synchronous rectifier Q
2Control signal remain homophase, therefore can realize control to the described push-pull type synchronous rectifying switching power source of present embodiment according to the drive circuit of positive activation type synchronous rectifying switching power source shown in Figure 4; In addition, because former limit switching tube Q
1With synchronous rectifier Q
4Control signal anti-phase all the time, therefore also can realize control to the described push-pull type synchronous rectifying switching power source of present embodiment according to the drive circuit of inverse-excitation type synchronous rectifying Switching Power Supply shown in Fig. 2 A; Similarly, also can be according to former limit switching tube Q
3With synchronous rectifier Q
2Perhaps with synchronous rectifier Q
4The relation of control signal, select embodiment adopts among Fig. 2 A or Fig. 4 type of drive to realize control to the described push-pull type synchronous rectifying switching power source of present embodiment.
Thus, as can be known, those of ordinary skills can be according to the logical relation of the on off state of the former limit switching tube in the synchronous rectifying switching power source of different topology structure and synchronous rectifier, selects among the present invention suitable drive circuit to control.For example as logical circuit U
2The former limit switching tube on off state of institute's foundation and synchronous rectification tube controller U
3The first output (U of synchronous rectification tube controller shown in Fig. 2 D for example
3When the synchronous rectifier on off state of the Q end of the first rest-set flip-flop 221 of embodiment) controlling is anti-phase, can be according to the principle design drive circuit of inverse-excitation type synchronous rectifying switch power source driving circuit among Fig. 2 A.As logical circuit U
2The former limit switching tube on off state of institute's foundation and synchronous rectification tube controller U
3The first output (U of synchronous rectification tube controller shown in Fig. 2 D for example
3The Q of the first rest-set flip-flop 221 of embodiment end) the synchronous rectifier on off state of controlling is same phase time, can according to positive activation type circuit of synchronous rectification among Fig. 4 the principle design drive circuit.The difference of the drive circuit of Fig. 2 A illustrated embodiment and drive circuit shown in Figure 4 is that Fig. 2 A illustrated embodiment is at former limit switching regulator controller U
1Perhaps synchronous rectification tube controller U
3In added inverter.
[embodiment five]
Be illustrated in figure 6 as full-bridge type synchronous rectifying switching power source in the embodiment of the invention five.The drive circuit of present embodiment can be realized according to the principle of push-pull type synchronous rectifying switching power source drive circuit among the embodiment four, will be repeated no more at this.
Those of ordinary skills as can be known, the present invention embodiment shown in Figure 3 is equally applicable to the embodiment shown in Fig. 4, Fig. 5, Fig. 6 for the improvement of the embodiment shown in Fig. 2 A.
Be depicted as the flow chart of the first embodiment of control of the present invention and driving method such as Fig. 7 A, it may further comprise the steps:
S701: when described former limit switching tube on off state and described synchronous rectifier on off state each other during inversion signal, produce described former limit switch controlled signal;
S702: carry out anti-phase and time-delay control to described former limit switch controlled signal, obtain the first control signal;
S703: described the first control signal is carried out the differential conversion, obtain the second control signal;
S704: according to described the second control signal, the described synchronous rectifier control signal of generation one and described former limit switch controlled signal inversion.
Wherein, also can only comprise time-delay control among the step S702, and in step S704, produce the 3rd control signal according to described the second control signal, to described the 3rd control signal carry out anti-phase control with produce one with the described synchronous rectifier control signal of described former limit switch controlled signal inversion.
Be depicted as the flow chart of the second embodiment of control of the present invention and driving method such as Fig. 7 B, it may further comprise the steps:
S705: when described former limit switching tube on off state is consistent with described synchronous rectifier on off state, produce described former limit switch controlled signal;
S706: to the control of delaying time of described former limit switch controlled signal, obtain the first control signal;
S707: described the first control signal is carried out the differential conversion, obtain the second control signal;
S708: according to described the second control signal, the described synchronous rectifier control signal of generation one and described former limit switch controlled signal homophase;
Wherein, described former limit switch controlled signal and described synchronous rectifier control signal are respectively applied to control opening and turn-offing of former limit switching tube in the described synchronous rectifying switching power source power stage circuit and synchronous rectifier.
In step S701 and step S705, further comprise, when having more than one former limit switching tube in the described synchronous rectifying switching power source power stage circuit, the control signal that can set as required one of them former limit switching tube is described former limit switch controlled signal, and the control signal of remaining former limit switching tube can produce according to its logical relation with the former limit that sets switch controlled signal;
In step S702 and step S706, can be by RC delay circuit realization to the time-delay control of described former limit switch controlled signal.
In addition, in step S702, can be by inverter realization to the anti-phase control of described former limit switch controlled signal.
In step S703 and step S707, can be by RC differential circuit realization to the differential conversion of described the first control signal.
In step S704 and step S708, can according to described the second control signal, adopt a zero cross detection circuit and a rest-set flip-flop to produce described synchronous rectifier control signal.Equally, further comprise, when having an above synchronous rectifier in the described synchronous rectifying switching power source power stage circuit, the control signal that can set as required one of them synchronous rectifier is described synchronous rectifier control signal, and the control signal of remaining synchronous rectifier can produce according to the logical relation with the synchronous rectifier control signal that sets.
In addition, in the present embodiment, comprise that also former border district and the secondary ground to described synchronous rectifying switching power source power stage circuit isolates, this isolation can realize by an electric capacity.
Certainly, the anti-phase control in the present embodiment, time-delay are controlled, also can be realized by other the suitable circuit structure known to those of ordinary skills producing method and the isolation method of the conversion of described the first control signal, described synchronous rectifier control signal.
Cited inverse-excitation type, positive activation type, push-pull type, the full-bridge type topological structure, the present invention also can be applicable in other proper topologies structures in the embodiment of the invention.
More than synchronous rectifying switching power source drive circuit and the control method of the switch type regulator of foundation the preferred embodiments of the present invention have been carried out detailed description, those of ordinary skills can know accordingly other technologies or structure and circuit layout, element etc. by inference and all can be applicable to described embodiment.
Identical similar part is mutually referring to getting final product between each embodiment in this specification, and each embodiment stresses is difference with other embodiment.Can select according to the actual needs wherein some or all of module to realize the purpose of present embodiment scheme.Those of ordinary skills namely can understand and implement in the situation of not paying creative work.
As indicated above according to embodiments of the invention, these embodiment do not have all details of detailed descriptionthe, do not limit this invention yet and only are described specific embodiment.Obviously, according to above description, can make many modifications and variations.These embodiment are chosen and specifically described to this specification, is in order to explain better principle of the present invention and practical application, thereby the technical field technical staff can utilize the present invention and the modification on basis of the present invention to use well under making.The present invention only is subjected to the restriction of claims and four corner and equivalent.
Claims (13)
1. a driving circuits is applied to it is characterized in that in the synchronous rectifying switching power source, comprising:
Former limit switching regulator controller is for generation of former limit switch controlled signal;
Logical circuit is used for producing the first control signal according to the described former limit switch controlled signal that receives;
Change-over circuit is used for producing the second control signal according to described the first control signal that receives;
The synchronous rectification tube controller, be used for producing the synchronous rectifier control signal according to described the second control signal that receives, and according to the topological structure of described synchronous rectifying switching power source, guarantee described former limit switch controlled signal and described synchronous rectifier control signal homophase or anti-phase.
2. driving circuits according to claim 1 is characterized in that, when the on off state of the former limit switching tube in the described synchronous rectifying switching power source and synchronous rectifier is opposite,
Described logical circuit comprises delay circuit and inverter, delays time with anti-phase control to produce described the first control signal according to described former limit switch controlled signal;
Described synchronous rectification tube controller produces described synchronous rectifier control signal constantly according to the zero passage of described the second control signal.
3. driving circuits according to claim 1 is characterized in that, when the on off state of the former limit switching tube in the described synchronous rectifying switching power source and synchronous rectifier is opposite,
Described logical circuit comprises delay circuit and inverter, and the described former limit switch controlled signal that described delay circuit is used for receiving delays time to produce described the first control signal;
Described synchronous rectification tube controller produces the 3rd control signal constantly according to the zero passage of described the second control signal;
Described inverter is used for described the 3rd control signal is carried out anti-phase to produce described synchronous rectifier control signal.
4. driving circuits according to claim 1 is characterized in that, when the on off state of the former limit switching tube in the described synchronous rectifying switching power source and synchronous rectifier is consistent,
Described logical circuit comprises delay circuit, and the described former limit switch controlled signal that described delay circuit is used for receiving delays time to produce described the first control signal;
Described synchronous rectification tube controller produces described synchronous rectifier control signal constantly according to the zero passage of described the second control signal.
5. driving circuits according to claim 1 is characterized in that, described change-over circuit comprises differential capacitance and differential resistance.
6. driving circuits according to claim 1, it is characterized in that, further comprise the former border district that is connected across described synchronous rectifying switching power source and the buffer circuit between the secondary ground, be used for isolating former border district and the secondary ground of described synchronous rectifying switching power source.
7. driving circuits according to claim 6 is characterized in that, described buffer circuit comprises isolation capacitance.
8. described driving circuits according to claim 1 is characterized in that, further comprises the first clamp circuit, the second clamp circuit, and described the first clamp circuit is for the protection of described former limit switching regulator controller; Described the second clamp circuit is for the protection of described synchronous rectification tube controller.
9. described driving circuits according to claim 8, it is characterized in that, described the first clamp circuit comprises the first diode, the second diode, the first clamp voltage and the second clamp voltage, when the amplitude of described the first control signal during greater than described the first clamp voltage or less than described the second clamp voltage, described the first clamp circuit is clamped to described the first clamp voltage or described the second clamp voltage with the amplitude of described the first control signal; Described the second clamp circuit comprises the 3rd diode, the 4th diode, the 3rd clamp voltage and the 4th clamp voltage, when the amplitude of described the second control signal during greater than described the 3rd clamp voltage or less than described the 4th clamp voltage, described the second clamp circuit is clamped to described the 3rd clamp voltage or described the 4th clamp voltage with the amplitude of described the second control signal.
10. control and driving method for one kind, be applied to it is characterized in that in the synchronous rectifying switching power source, may further comprise the steps:
Produce described former limit switch controlled signal;
To produce the first control signal after the logical operation of described former limit switch controlled signal process;
To produce the second control signal after the conversion of described the first control signal process differential;
Described the second control signal is produced the synchronous rectifier control signal through after controlling.
11. control according to claim 10 and driving method is characterized in that, further comprise former border district and secondary ground are isolated.
12. control according to claim 10 and driving method, it is characterized in that, when the on off state of the former limit switching tube in the described synchronous rectifying switching power source and synchronous rectifier is opposite, described logic control comprise to described former limit switch controlled signal carry out anti-phase and time-delay control obtaining described the first control signal, described synchronous rectifier control signal produces described synchronous rectifier control signal with described former limit switch controlled signal inversion according to described the second control signal.
13. control according to claim 10 and driving method, it is characterized in that, when the on off state of the former limit switching tube in the described synchronous rectifying switching power source and synchronous rectifier is consistent, described logic control comprises delays time control to obtain described the first control signal to described former limit switch controlled signal, and described synchronous rectifier control signal is according to the described synchronous rectifier control signal of described the second control signal generation with described former limit switch controlled signal homophase.
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| TW102130828A TWI504122B (en) | 2012-10-23 | 2013-08-28 | Control and drive circuits and methods |
| US14/024,813 US9525357B2 (en) | 2012-10-23 | 2013-09-12 | Control and drive circuit and method |
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Also Published As
| Publication number | Publication date |
|---|---|
| TW201417487A (en) | 2014-05-01 |
| CN102969912B (en) | 2014-08-13 |
| US9525357B2 (en) | 2016-12-20 |
| TWI504122B (en) | 2015-10-11 |
| US20140112031A1 (en) | 2014-04-24 |
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