CN102891606B - Switching power supply - Google Patents
Switching power supply Download PDFInfo
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- CN102891606B CN102891606B CN201210331309.XA CN201210331309A CN102891606B CN 102891606 B CN102891606 B CN 102891606B CN 201210331309 A CN201210331309 A CN 201210331309A CN 102891606 B CN102891606 B CN 102891606B
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Abstract
The invention discloses a kind of Switching Power Supply, wherein said Switching Power Supply comprises: a flyback output unit, a linear voltage stabilization unit, a pwm signal unit and a normal shock output unit; Described linear voltage stabilization unit and pwm signal unit is serially connected with respectively between described flyback output unit and described normal shock output unit; Wherein said flyback output unit exports a flyback voltage signal and an anti-phase pwm signal; Described linear voltage stabilization unit carries out voltage stabilizing to described flyback voltage signal; Described pwm signal unit is used for described anti-phase pwm signal to be converted into a positive pwm signal; Described normal shock output unit exports normal shock voltage signal based on the described flyback voltage signal after voltage stabilizing and described positive pwm signal.Switching Power Supply of the present invention, Forward-flyback is combined by the mode exported by the control of flyback loop, linear voltage stabilization, normal shock, reduces load regulation to the impact of IGBT driving voltage, and improves defencive function.
Description
Technical field
The present invention relates to a kind of Switching Power Supply, particularly relate to a kind of Switching Power Supply being applicable to frequency converter.
Background technology
The small-power switching power-supply (especially the Switching Power Supply of below 50W) of current frequency converter mostly is single-end flyback switching power supply, because frequency converter needs Multiple isolated outputs usually, switching mode power supply transformer winding is multilayer mechanism, because the leakage inductance of each winding is different, when each winding strap carries situation difference, output voltage will produce larger change.The fluctuation of voltage is concerning the IGBT(insulated gate bipolar transistor of frequency converter) inverter bridge, directly can have influence on the consistency of IGBT switch, frequency converter failure rate will be caused to rise.
The mode increasing dummy load or quadratic linear voltage stabilizing that adopts is improved IGBT driving voltage more at present, but these two kinds of modes all exist certain deficiency.
Suitable increase dummy load, degree that can be certain is optimized the load regulation of inverse-excitation type switch power-supply, but dummy load can increase the excess loss of power supply, and reduce the efficiency of power supply, and dummy load is larger, load regulation could be better.Owing to being subject to the restriction of switch power efficiency, dummy load generally can not be too large, and the output of power supply still can have larger fluctuation with the load variations of power supply.And larger resistance dummy load also needs to occupy larger PCB(printed circuit board (PCB)) space.
Can well solve the problem of IGBT driving voltage waveform by the mode of quadratic linear voltage stabilizing, but the isolation and amplifier of multichannel needs to isolate voltage stabilizing circuit, and whole switching power source device will be caused various, circuit is complicated.And when load short circuits, the short-circuit protection function of common inverse-excitation type switch power-supply effectively cannot be protected linear voltage-stabilizing circuit, easily causes voltage stabilizing circuit to lose efficacy, frequency converter is shut down and is even damaged converter power supply.
Summary of the invention
The technical problem to be solved in the present invention be in order to overcome the load regulation of single-end flyback switching power supply in prior art affect IGBT driving voltage, cannot when load short circuits for Switching Power Supply provides the defect cannot protecting IGBT pipe when available protecting and the former limit switching tube short circuit in Switching Power Supply; a kind of Switching Power Supply is provided; Forward-flyback is combined by the mode exported by the control of flyback loop, linear voltage stabilization, normal shock; reduce load regulation to the impact of IGBT driving voltage, and improve defencive function.
The present invention solves above-mentioned technical problem by following technical proposals:
The invention provides a kind of Switching Power Supply, be characterized in, described Switching Power Supply comprises:
One flyback output unit, a linear voltage stabilization unit, a PWM(pulse-width signal) signal element and a normal shock output unit;
Wherein said flyback output unit exports a flyback voltage signal and an anti-phase pwm signal;
Described linear voltage stabilization unit carries out voltage stabilizing to described flyback voltage signal;
Described pwm signal unit is used for described anti-phase pwm signal to be converted into a positive pwm signal;
Described normal shock output unit exports normal shock voltage signal based on the described flyback voltage signal after voltage stabilizing and described positive pwm signal.
Wherein said flyback output unit and normal shock output unit are power output unit usual in this area, so be no longer described in detail herein.
And be anti-phase relation between the pwm signal of the output unit of flyback described in the present invention output and the pwm signal of normal shock output unit, so the pwm signal that flyback output unit exports is defined as inversion signal in the present invention, the pwm signal being suitable for normal shock output unit is defined as positive phase signals, described pwm signal unit is made up of negative circuit, and realizes the anti-phase of pwm signal.
Preferably, described linear voltage stabilization unit is LDO circuit (low pressure difference linear voltage regulator), bootstrap circuit boost, Buck circuit (Buck conversion circuit), Boost circuit (switch DC booster circuit) or Buck-Boost circuit (buck or boost translation circuit) etc.
The flyback voltage signal that the unit of linear voltage stabilization described in the present invention exports for stablizing described flyback output unit, so the circuit that in prior art, any one can realize voltage regulation result all can be used as linear voltage stabilization unit of the present invention.
Preferably, described pwm signal unit comprises a bleeder circuit and a negative circuit, wherein said bleeder circuit obtains anti-phase pwm signal from described flyback output unit, and described bleeder circuit and negative circuit are passed through described anti-phase pwm signal dividing potential drop and the described positive pwm signal of anti-phase acquisition.
Because the duty ratio of the pwm signal in flyback output unit is generally all less than 0.5, can normally work to allow normal shock output unit, in the present invention, described negative circuit is carried out anti-phase to pwm signal, but also make pwm signal can mate the PWM input voltage requirement of normal shock output unit by bleeder circuit.
Preferably, described Switching Power Supply also comprises a current limiting unit, when the electric current of flyback voltage signal is more than a threshold value, disconnects the electrical connection of described pwm signal unit and linear voltage stabilization unit and described normal shock output unit.
Preferably, described current limiting unit can adopt peak limiter circuit, and described current limiting unit can also be made up of exclusive circuit in addition.
In the present invention by current limiting unit when electric current is excessive, described current limiting unit stops described positive pwm signal to be delivered to described normal shock output unit, thus protects described pwm signal unit and linear voltage stabilization unit.Described peak limiter circuit and exclusive circuit are the common circuit technology of Limited Current in prior art, so be no longer described in detail herein.
Preferably, described flyback output unit also comprises one first rectification filtering unit, and described first rectification filtering unit is used for the flyback voltage signal rectification that exports described flyback output unit and filtering, and exports described linear voltage stabilization unit to.
Preferably, described normal shock output unit also comprises one second rectification filtering unit, described second rectification filtering unit is used for the normal shock voltage signal rectification that exports described normal shock output unit and filtering, and the described normal shock voltage signal after rectifying and wave-filtering is maintained the peak value of the described normal shock voltage signal before rectifying and wave-filtering by wherein said second rectification filtering unit.
Positive progressive effect of the present invention is:
Switching Power Supply of the present invention, Forward-flyback combines by the mode that flyback loop control excessively, linear voltage stabilization, normal shock export, and reduces load regulation to the impact of IGBT driving voltage, and improves defencive function.
Existing Switching Power Supply first carries out isolation and amplifier, then carries out linear voltage stabilizing to every road isolation and amplifier.How many roads isolation and amplifier is had just to have how many linear voltage stabilizing circuit.Circuit is complicated, and component number is many, and the reliability of whole circuit is lowered.
Linear voltage stabilizing is placed on the prime of isolation and amplifier by the present invention, and when load short circuits, normal shock exports and turned off by current limiting unit, and the linear voltage stabilizing circuit of prime stops exporting energy.Linear voltage stabilizing circuit will well be protected.
In addition, Switching Power Supply of the present invention, when former limit switching tube short circuit, can also protect IGBT to manage effectively.And IGBT driving power is become normal shock output by the output of original flyback by the present invention, blocks other road load variations to the impact of IGBT driving voltage.And the mode that directly employing uses PWM from flyback output carries out normal shock output, does not need extra PWM circuit for generating.
Accompanying drawing explanation
Fig. 1 is the structural representation of the preferred embodiment of switching power supply of frequency converter of the present invention.
Fig. 2 is the circuit structure block diagram of the preferred embodiment of switching power supply of frequency converter of the present invention.
Embodiment
Present pre-ferred embodiments is provided, to describe technical scheme of the present invention in detail below in conjunction with accompanying drawing.
As shown in Figure 1, the Switching Power Supply for frequency converter of the present embodiment comprises flyback output unit 1, linear voltage stabilization unit 2, pwm signal unit 3, normal shock output unit 4 and a current limiting unit 5.
Described flyback output unit 1 is electrically connected with described linear voltage stabilization unit 2 and pwm signal unit 3 respectively, and described linear voltage stabilization unit 2 and pwm signal unit 3 are also electrically connected with described normal shock output unit 4.
Wherein said flyback output unit 1 and normal shock output unit 4 are power output unit usual in this area, as shown in Figure 2, take Vo as the feedback of flyback output unit 1, thus can be the main digital-to-analog circuit supply of circuit board; Vo_U, Vo_V, Vo_W and Vo_N are the IGBT driving power of normal shock output unit 4 pairs of frequency converters, Vo1 and Vo2 is other insulating power supplies that frequency converter needs.
And the output unit of flyback described in the present embodiment 1 is formed primarily of the peripheral circuit of transformer T1 and corresponding coupling, described normal shock output unit 4 is formed primarily of the peripheral circuit of transformer T2 and corresponding coupling equally.Wherein 33 and 34 pin of the T1 of transformer described in Fig. 2 are as the output of flyback output unit 1, namely export flyback voltage signal by 33 and 34 pin of described transformer T1.Described transformer T2 exports normal shock voltage signal by Vo_U, Vo_V, Vo_W and Vo_N.
And the secondary of the secondary of flyback output unit and normal shock output unit can change the way of output according to actual needs, increasing minimizing can.Namely the way that described normal shock output unit 4 and flyback output unit 1 export can adjust, but should note when normal shock exports and flyback exports and divides: if load variations is larger as far as possible, quality of voltage requires that comparatively Gao mono-tunnel exports as flyback, and Bing Yongci road exports and does FEEDBACK CONTROL; If load variations is little, quality of voltage requires higher, and the substantially identical several roads of load export and export as normal shock; If load variations is comparatively large, quality of voltage requires that relatively low several roads export, and exports as common flyback.
Described flyback output unit 1 comprises one first rectification filtering unit 11, and wherein as shown in Figure 2, described first rectification filtering unit is for form current rectifying and wave filtering circuit by diode D28, electric capacity C55 and electric capacity C56.It is the current rectifying and wave filtering circuit that this area is commonly used that described diode D28, electric capacity C55 and electric capacity C56 form current rectifying and wave filtering circuit, so be no longer described in detail the specific works principle of described current rectifying and wave filtering circuit herein.
Equally, Vo_U is comprised because described normal shock output unit 4 has, Vo_V, the output of Vo_W and Vo_N, and the output unit of normal shock described in the present embodiment 4 comprises one second rectification filtering unit 41, wherein diode D19 and electric capacity C44 is as the rectifying and wave-filtering of Vo_U, the i.e. rectifying and wave-filtering of the IGBT driving power on U road, diode D20 and electric capacity C45 is as the rectifying and wave-filtering of Vo_V, the i.e. rectifying and wave-filtering of V road IGBT driving power, diode D21 and electric capacity C46 is as the rectifying and wave-filtering of Vo_W, the i.e. rectifying and wave-filtering of W road IGBT driving power, diode D22, electric capacity C48 is as the rectifying and wave-filtering of Vo_N, the i.e. rectifying and wave-filtering of N road IGBT driving power.Current rectifying and wave filtering circuit structure described above, the described normal shock voltage signal after rectifying and wave-filtering can be maintained the peak value of the described normal shock voltage signal before rectifying and wave-filtering by described second rectification filtering unit 41 of the present embodiment.
In addition the dummy load that in the output unit of normal shock described in the present embodiment 4, resistance R85, R86, R88 and R89 export as IGBT driving power, described diode D23 is used for the rectification of degaussing winding.And described transformer T2, switching tube Q9 and resistance R96 form the loop, former limit in normal shock output unit 4.
33 and 34 pin of linear voltage stabilization unit 2 to described transformer T1 of the present embodiment export flyback voltage signal and carry out voltage stabilizing.Wherein as shown in Figure 2, the linear voltage stabilization unit 2 of the present embodiment is the linear voltage-stabilizing circuit be made up of triode Q6, three-terminal voltage-stabilizing pipe U2, resistance R73, R87, R83 and R84 and electric capacity C47, C49 and C52.Wherein resistance R83 and R84 carries out dividing potential drop to flyback voltage signal, as the FEEDBACK CONTROL end of three-terminal voltage-stabilizing pipe U2, is controlled the conducting of triode Q6 by three-terminal voltage-stabilizing pipe U2.
So the control end threshold voltage vt h*(R83+R84 of the final voltage U=three-terminal voltage-stabilizing pipe U2 exported of linear voltage stabilization unit 2)/R84.
Described linear voltage-stabilizing circuit is the usual voltage stabilizing circuit in this area, so be no longer described in detail its workflow herein, and described linear voltage stabilization unit 2 can also adopt any voltage stabilizing circuit that can realize voltage stabilizing function, such as LDO circuit, bootstrap circuit boost, Buck circuit, Boost circuit or Buck-Boost circuit etc.
The described pwm signal unit 3 of the present embodiment is converted into positive pwm signal for the anti-phase pwm signal exported by described flyback output unit 1.The present embodiment can normally work to allow normal shock output unit 4, undertaken anti-phase by the anti-phase pwm signal that flyback output unit 1 is exported, but also make described anti-phase pwm signal can mate the PWM input voltage requirement of normal shock output unit 4 by bleeder circuit.
So as shown in Figure 2, the described pwm signal unit 3 of the present embodiment comprises a bleeder circuit and a negative circuit.Wherein in the present embodiment, the anode of diode D24 is directly received on 34 pin of transformer T1, thus draws anti-phase pwm signal.The anti-phase pwm signal exported by the coil of transformer T1 is drawn before filtering, then through diode D24 rectification, produces the pwm signal that is only had malleation.
Then the bleeder circuit that resistance R93 and R94 is formed carries out dividing potential drop to anti-phase pwm signal, described driven MOS pipe (metal oxide semiconductcor field effect transistor) Q7, resistance R81 and R82 form negative circuit, wherein driven MOS pipe Q7 is again anti-phase by anti-phase pwm signal, the pwm signal of positive is produced together with resistance R81 with R82, thus the switching tube Q9 of normal shock output unit 4.
The current limiting unit 5 of the present embodiment is for when the electric current of flyback voltage signal is more than a threshold value, and described current limiting unit 5 stops described positive pwm signal being delivered to described normal shock output unit 4 thus protecting described pwm signal unit 3 and linear voltage stabilization unit 2.As shown in Figure 2, described current limiting unit 5 comprises resistance R96 and R90, electric capacity C57 and triode Q8.
When adopting triode Q8 as current limiting unit 5, once peak current exceedes setting threshold, switching tube Q9 grid is blocked and drags down, and switching tube Q9 turns off.Electricity in electric capacity C57 is by resistance R90 and R96 bleed off, and triode Q8 turns off, and switching tube Q9 grid blocks and removed, then during the arrival of next Continuity signal, and switching tube Q9 can normal switch, and normal shock output circuit part can normally export.
In addition replace triode Q8 according to exclusive circuit, when peak current exceedes setting threshold, exclusive circuit will drag down the grid of switching tube Q9 for a long time, only has the thorough power-off of Switching Power Supply, re-powers and could unlock.Otherwise normal shock efferent branch is in blocked styate always.
So can effectively effectively be protected abnormal conditions such as normal shock output short-circuit, heavy duties by current limiting unit 5.
In flyback output unit 1 in the present embodiment, the maximum duty cycle of anti-phase pwm signal is set in less than 0.5, just allows normal shock output unit 4 also can normally work.And normal shock output unit 4 directly uses capacitor filtering.Capacitance output current as required and power supply ripple require to determine.
Namely directly adopt the way of output of bulky capacitor filtering in the present embodiment, do not need fly-wheel diode, be very different with LC filtering.The tributary output voltage finally obtained is:
Final VD=DC input voitage * transformer coil turn ratio
According to output current size, reasonably determine the capacitance of filter capacitor, and the minimum duty cycle of control PWM to a certain extent, the so transformer coil turn ratio one timing, final VD is only determined by DC input voitage.DC input voitage because of forward converter is obtained by linear voltage stabilizing circuit, the direct voltage fixed can be thought, so can obtain stable VD, this voltage by the impact of PWM duty ratio, also would not be subject to the impact of circuit of reversed excitation output loading change and input voltage fluctuation.In addition, owing to being normal shock mode of operation, the load that each road of normal shock exports is when changing, very little to the voltage influence on other road.
Adopt the voltage stabilizing of advanced line shape in the present embodiment, then carry out the mode of isolation and amplifier.Only need a linear voltage regulation unit 2 just can realize voltage stabilizing function.And linear voltage stabilizing is placed on the prime of isolation and amplifier by the present embodiment; when load short circuits; the switching tube Q9 that normal shock exports will be turned off by current limiting unit 5, and the linear voltage regulation unit 2 of prime stops exporting energy, so linear voltage regulation unit 2 will well be protected.
The Switching Power Supply of the present embodiment can as the positive-negative power of the comparison amplifying circuit of frequency converter, fan and relay power, CPU(central processing unit) and peripheral circuit power supply and IGBT driving power etc.
Although the foregoing describe the specific embodiment of the present invention, it will be understood by those of skill in the art that these only illustrate, protection scope of the present invention is defined by the appended claims.Those skilled in the art, under the prerequisite not deviating from principle of the present invention and essence, can make various changes or modifications to these execution modes, but these change and amendment all falls into protection scope of the present invention.
Claims (6)
1. a Switching Power Supply, is characterized in that, described Switching Power Supply comprises: a flyback output unit, a linear voltage stabilization unit, a pwm signal unit and a normal shock output unit;
Described flyback output unit is electrically connected with described linear voltage stabilization unit and pwm signal unit respectively, and described linear voltage stabilization unit and pwm signal unit are also electrically connected with described normal shock output unit;
Wherein said flyback output unit exports a flyback voltage signal and an anti-phase pwm signal; Described linear voltage stabilization unit carries out voltage stabilizing to described flyback voltage signal; Described pwm signal unit is used for described anti-phase pwm signal to be converted into a positive pwm signal; Described normal shock output unit exports normal shock voltage signal based on the described flyback voltage signal after voltage stabilizing and described positive pwm signal,
Described pwm signal unit comprises a bleeder circuit and a negative circuit, wherein said bleeder circuit obtains anti-phase pwm signal from described flyback output unit, and described bleeder circuit and negative circuit are to described anti-phase pwm signal dividing potential drop and the described positive pwm signal of anti-phase acquisition.
2. Switching Power Supply as claimed in claim 1, it is characterized in that, described linear voltage stabilization unit is LDO circuit, bootstrap circuit boost, Buck circuit, Boost circuit or Buck-Boost circuit.
3. Switching Power Supply as claimed in claim 1, it is characterized in that, described Switching Power Supply also comprises a current limiting unit, and when the electric current of flyback voltage signal is more than a threshold value, described current limiting unit stops described positive pwm signal to be delivered to described normal shock output unit.
4. Switching Power Supply as claimed in claim 3, it is characterized in that, described current limiting unit is peak limiter circuit or exclusive circuit.
5. Switching Power Supply as claimed in claim 1, it is characterized in that, described flyback output unit also comprises one first rectification filtering unit, and described first rectification filtering unit is used for the flyback voltage signal rectification that exports described flyback output unit and filtering, and exports described linear voltage stabilization unit to.
6. Switching Power Supply as claimed in claim 1, it is characterized in that, described normal shock output unit also comprises one second rectification filtering unit, described second rectification filtering unit is used for the normal shock voltage signal rectification that exports described normal shock output unit and filtering, and the described normal shock voltage signal after rectifying and wave-filtering is maintained the peak value of the described normal shock voltage signal before rectifying and wave-filtering by wherein said second rectification filtering unit.
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| CN201210331309.XA CN102891606B (en) | 2012-09-07 | 2012-09-07 | Switching power supply |
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| CN201210331309.XA CN102891606B (en) | 2012-09-07 | 2012-09-07 | Switching power supply |
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| CN102891606A CN102891606A (en) | 2013-01-23 |
| CN102891606B true CN102891606B (en) | 2015-11-25 |
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Families Citing this family (6)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| TWI511430B (en) * | 2013-03-14 | 2015-12-01 | Fsp Technology Inc | Power supply apparatus |
| CN105553278A (en) * | 2016-01-27 | 2016-05-04 | 苏州时运机器人有限公司 | Flyback switching power supply and power output transformer thereof |
| CN105867502B (en) * | 2016-05-18 | 2017-10-10 | 湖州绿明微电子有限公司 | LDO pressure regulators, alternating current equipment |
| CN107681900B (en) * | 2017-10-27 | 2020-05-22 | 中国航空无线电电子研究所 | Multi-mode output power/pulse modulation conversion multiplexing module |
| CN110912409B (en) * | 2019-11-07 | 2020-12-18 | 广州金升阳科技有限公司 | Forward and reverse excitation type switching power supply circuit |
| CN112098708B (en) * | 2020-11-23 | 2021-02-02 | 成都市易冲半导体有限公司 | Line voltage information detection circuit and detection method for secondary side PD controller |
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| CN102044971A (en) * | 2009-10-14 | 2011-05-04 | Smk株式会社 | Self-excited switching power supply circuit |
| CN102570838A (en) * | 2012-03-06 | 2012-07-11 | 厦门巨益科技有限公司 | Bilaterally and continuously adjustable regulated power supply |
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| Publication number | Priority date | Publication date | Assignee | Title |
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| JPH10201230A (en) * | 1996-12-27 | 1998-07-31 | Nagano Aichi Denki Kk | Dc high voltage power supply drive circuit |
| JP2010234255A (en) * | 2009-03-31 | 2010-10-21 | Yamatake Corp | Gas treatment apparatus |
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| Publication number | Priority date | Publication date | Assignee | Title |
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| CN102044971A (en) * | 2009-10-14 | 2011-05-04 | Smk株式会社 | Self-excited switching power supply circuit |
| CN102570838A (en) * | 2012-03-06 | 2012-07-11 | 厦门巨益科技有限公司 | Bilaterally and continuously adjustable regulated power supply |
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