CN102891606A - Switching power supply - Google Patents
Switching power supply Download PDFInfo
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- CN102891606A CN102891606A CN201210331309XA CN201210331309A CN102891606A CN 102891606 A CN102891606 A CN 102891606A CN 201210331309X A CN201210331309X A CN 201210331309XA CN 201210331309 A CN201210331309 A CN 201210331309A CN 102891606 A CN102891606 A CN 102891606A
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Abstract
The invention discloses a switching power supply, wherein the switching power supply comprises a flyback output unit, a linear voltage-stabilizing unit, a pulse-width modulation (PWM) signal unit and a forward output unit; the linear voltage-stabilizing unit and the PWM signal unit are connected between the flyback output unit and the forward output unit in series respectively, wherein the flyback output unit outputs a flyback voltage signal and a reverse phase PWM signal; the linear voltage-stabilizing unit stabilizes the voltage of the flyback voltage signal; the PWM signal unit is used for transforming the reverse phase PWM signal to a forward PWM signal; based on the stabilized flyback voltage signal and the normal phase PWM signal, the forward output unit outputs the forward voltage signal. Through flyback loop control, linear voltage stabilization and forward output, the switching power supply provided by the invention can combine the forward and flyback together, so that the influence of load adjusting rate on an insulated gate bipolar translator (IGBT) driving voltage is reduced, and the protection function is perfected.
Description
Technical field
The present invention relates to a kind of Switching Power Supply, particularly relate to a kind of Switching Power Supply that is applicable to frequency converter.
Background technology
The small-power switching power-supply that present frequency converter is used (the especially following Switching Power Supply of 50W) mostly is single-end flyback switching power supply, because frequency converter needs Multiple isolated outputs usually, the switching mode power supply transformer winding is multilayer mechanism, because the leakage inductance of each winding is different, when each winding band carries situation not simultaneously, output voltage will produce larger variation.The fluctuation of voltage is concerning the IGBT(insulated gate bipolar transistor of frequency converter) the inverter bridge, can directly have influence on the consistency of IGBT switch, will cause the frequency converter failure rate to rise.
The modes that increase dummy load or secondary linear voltage stabilization that adopt are improved the IGBT driving voltage more at present, but all there is certain deficiency in this dual mode.
Suitable increase dummy load, the load regulation of optimization inverse-excitation type switch power-supply on degree that can be certain, but the dummy load meeting increases the excess loss of power supply, reduce the efficient of power supply, and dummy load is larger, and load regulation could be better.Because be subject to the restriction of switch power efficiency, dummy load generally can not be too large, the output of power supply still can have with the load variations of power supply larger fluctuation.And larger resistance dummy load also needs to occupy larger PCB(printed circuit board (PCB)) space.
Can well solve the problem of IGBT driving voltage waveform with the mode of secondary linear voltage stabilization, but the isolation of multichannel output needs the isolation voltage stabilizing circuit, will cause whole switching power source device various, circuit is complicated.And when load short circuits, the short-circuit protection function of common inverse-excitation type switch power-supply can't effectively be protected linear voltage-stabilizing circuit, causes easily voltage stabilizing circuit to lose efficacy, and frequency converter is shut down even the infringement converter power supply.
Summary of the invention
The technical problem to be solved in the present invention is the defective that affects the IGBT driving voltage, can't be when the load short circuits provides effective protection for Switching Power Supply and can't protect the IGBT pipe during in the switching tube short circuit of the former limit of Switching Power Supply in order to overcome the load regulation of single-end flyback switching power supply in the prior art; a kind of Switching Power Supply is provided; swash the mode of loop control, linear voltage stabilization, normal shock output with positive and negative sharp combining by anti-; reduce load regulation to the impact of IGBT driving voltage, and improve defencive function.
The present invention solves above-mentioned technical problem by following technical proposals:
The invention provides a kind of Switching Power Supply, be characterized in, described Switching Power Supply comprises:
One anti-sharp output unit, a linear voltage stabilization unit, a PWM(pulse-width signal) signal element and a normal shock output unit;
Wherein said anti-output unit output one anti-sharp voltage signal and the anti-phase pwm signal that swash;
Described linear voltage stabilization unit carries out voltage stabilizing to described anti-sharp voltage signal;
Described pwm signal unit is used for described anti-phase pwm signal is converted into a positive pwm signal;
Described anti-after based on voltage stabilizing of described normal shock output unit swashs voltage signal and described positive pwm signal output normal shock voltage signal.
Wherein said anti-sharp output unit and normal shock output unit are power supply output unit habitual in this area, so give unnecessary details no longer in detail herein.
And be anti-phase relation between the pwm signal of the pwm signal of anti-sharp output unit output described in the present invention and normal shock output unit, be defined as inversion signal so will instead swash the pwm signal of output unit output among the present invention, the pwm signal that will be suitable for the normal shock output unit is defined as positive phase signals, described pwm signal unit is made of negative circuit, and realizes the anti-phase of pwm signal.
Preferably, described linear voltage stabilization unit is LDO circuit (low pressure difference linear voltage regulator), bootstrap circuit boost, Buck circuit (Buck conversion circuit), Boost circuit (switch DC booster circuit) or Buck-Boost circuit (buck or boost translation circuit) etc.
The unit of linear voltage stabilization described in the present invention is for stablizing the described anti-anti-sharp voltage signal that swashs output unit output, so any circuit of voltage regulation result of can realizing all can be used as linear voltage stabilization of the present invention unit in the prior art.
Preferably, described pwm signal unit comprises a bleeder circuit and a negative circuit, wherein said bleeder circuit obtains anti-phase pwm signal from described anti-sharp output unit, and described bleeder circuit and negative circuit are passed through described anti-phase pwm signal dividing potential drop and the described positive pwm signal of anti-phase acquisition.
Because the duty ratio of the pwm signal in the anti-sharp output unit is general all less than 0.5, for the normal shock output unit can be worked, among the present invention described negative circuit is carried out anti-phasely to pwm signal, but also come so that pwm signal can mate the PWM input voltage requirement of normal shock output unit by bleeder circuit.
Preferably, described Switching Power Supply also comprises a current limiting unit, when the anti-electric current that swashs voltage signal surpasses a threshold value, disconnects being electrically connected of described pwm signal unit and linear voltage stabilization unit and described normal shock output unit.
Preferably, described current limiting unit can adopt peak limiter circuit, and described current limiting unit can also be made of exclusive circuit in addition.
Among the present invention by current limiting unit when electric current is excessive, described current limiting unit stops described positive pwm signal is delivered to described normal shock output unit, thereby described pwm signal unit and linear voltage stabilization unit are protected.Described peak limiter circuit and exclusive circuit are the common circuit technology of Limited Current in the prior art, so give unnecessary details no longer in detail herein.
Preferably, describedly anti-swash output unit and also comprise one first rectification filtering unit, described the first rectification filtering unit is used for instead swashing the anti-of output unit output and swashing voltage signal rectification and filtering described, and exports described linear voltage stabilization unit to.
Preferably, described normal shock output unit also comprises one second rectification filtering unit, described the second rectification filtering unit is used for the rectification of normal shock voltage signal and the filtering to described normal shock output unit output, and the described normal shock voltage signal of wherein said the second rectification filtering unit after with rectifying and wave-filtering maintains the peak value of the described normal shock voltage signal before the rectifying and wave-filtering.
Positive progressive effect of the present invention is:
Switching Power Supply of the present invention is crossed the anti-mode that swashs loop control, linear voltage stabilization, normal shock output with positive and negative sharp combining, and reduces load regulation to the impact of IGBT driving voltage, and improves defencive function.
Existing Switching Power Supply is to isolate first output, then linear voltage stabilizing is carried out in the isolation output of every road.There are how many road isolation outputs how many route voltage stabilizing circuits are just arranged.Circuit is complicated, and component number is many, and the reliability of whole circuit is lowered.
The present invention is placed on the prime that isolation is exported with linear voltage stabilizing, and when load short circuits, normal shock output is turn-offed by current limiting unit, and the linear voltage stabilizing circuit of prime stops to export energy.Linear voltage stabilizing circuit will well be protected.
In addition, Switching Power Supply of the present invention can also be protected the IGBT pipe effectively when the switching tube short circuit of former limit.And the present invention instead swashs the IGBT driving power output and becomes normal shock output by original, blocks other road load variations to the impact of IGBT driving voltage.And directly adopt from the anti-sharp mode of using PWM of exporting and carry out normal shock output, do not need extra PWM circuit for generating.
Description of drawings
Fig. 1 is the structural representation of the preferred embodiment of switching power supply of frequency converter of the present invention.
Fig. 2 is the circuit structure block diagram of the preferred embodiment of switching power supply of frequency converter of the present invention.
Embodiment
Provide preferred embodiment of the present invention below in conjunction with accompanying drawing, to describe technical scheme of the present invention in detail.
As shown in Figure 1, the Switching Power Supply that is used for frequency converter of present embodiment comprises an anti-sharp output unit 1, a linear voltage stabilization unit 2, a pwm signal unit 3, a normal shock output unit 4 and a current limiting unit 5.
Described anti-sharp output unit 1 is electrically connected with described linear voltage stabilization unit 2 and pwm signal unit 3 respectively, and described linear voltage stabilization unit 2 and pwm signal unit 3 also are electrically connected with described normal shock output unit 4.
Wherein said anti-sharp output unit 1 and normal shock output unit 4 are power supply output unit habitual in this area, as shown in Figure 2, take Vo as the anti-feedback that swashs output unit 1, thereby can be the main digital-to-analog circuit supply of circuit board; Vo_U, Vo_V, Vo_W and Vo_N are the IGBT driving power of 4 pairs of frequency converters of normal shock output unit, and Vo1 and Vo2 are other insulating power supplies that frequency converter needs.
And anti-sharp output unit 1 mainly is made of the peripheral circuit of transformer T1 and corresponding coupling described in the present embodiment, and described normal shock output unit 4 same main peripheral circuits by transformer T2 and corresponding coupling consist of.Wherein 33 and 34 pin of the T1 of transformer described in Fig. 2 are namely exported the anti-voltage signal that swashs by 33 and 34 pin of described transformer T1 as the anti-output that swashs output unit 1.Described transformer T2 is by Vo_U, Vo_V, Vo_W and Vo_N output normal shock voltage signal.
And the secondary that instead swashs the secondary of output unit and normal shock output unit can change the way of output according to actual needs, increases that reduce can.Be that described normal shock output unit 4 and the anti-way that swashs output unit 1 output can be adjusted, but should note in normal shock output and anti-sharp output when dividing: if load variations is larger as far as possible, the road conduct that quality of voltage is had relatively high expectations is anti-to swash output, and does FEEDBACK CONTROL with this road output; If load variations is little, quality of voltage is had relatively high expectations, and the essentially identical several roads output of load is exported as normal shock; If load variations is larger, quality of voltage requires relatively low several roads output, as common anti-sharp output.
Described anti-sharp output unit 1 comprises one first rectification filtering unit 11, and wherein as shown in Figure 2, described the first rectification filtering unit is for to consist of current rectifying and wave filtering circuit by diode D28, capacitor C 55 and capacitor C 56.It is this area current rectifying and wave filtering circuit commonly used that described diode D28, capacitor C 55 and capacitor C 56 consist of current rectifying and wave filtering circuit, so give unnecessary details no longer in detail the specific works principle of described current rectifying and wave filtering circuit herein.
Equally, because described normal shock output unit 4 has the Vo_U of comprising, Vo_V, the output of Vo_W and Vo_N, and the output unit of normal shock described in the present embodiment 4 comprises one second rectification filtering unit 41, wherein diode D19 and capacitor C 44 are as the rectifying and wave-filtering of Vo_U, it is the rectifying and wave-filtering of the IGBT driving power on U road, diode D20 and capacitor C 45 are as the rectifying and wave-filtering of Vo_V, it is the rectifying and wave-filtering of V road IGBT driving power, diode D21 and capacitor C 46 are as the rectifying and wave-filtering of Vo_W, it is the rectifying and wave-filtering of W road IGBT driving power, diode D22, capacitor C 48 is as the rectifying and wave-filtering of Vo_N, i.e. the rectifying and wave-filtering of N road IGBT driving power.Current rectifying and wave filtering circuit structure as mentioned above, described second rectification filtering unit 41 of present embodiment can maintain the described normal shock voltage signal behind the rectifying and wave-filtering peak value of the described normal shock voltage signal before the rectifying and wave-filtering.
Resistance R 85, R86, R88 and R89 are as the dummy load of IGBT driving power output in the output unit 4 of normal shock described in the present embodiment in addition, and described diode D23 is used for the rectification of degaussing winding.And the loop, former limit in described transformer T2, switching tube Q9 and the resistance R 96 composition normal shock output units 4.
The anti-sharp voltage signal of the 33 and 34 pin output of the 2 couples of described transformer T1 in linear voltage stabilization unit of present embodiment carries out voltage stabilizing.Wherein as shown in Figure 2, the linear voltage stabilization unit 2 of present embodiment is the linear voltage-stabilizing circuit that is comprised of triode Q6, three-terminal voltage-stabilizing pipe U2, resistance R 73, R87, R83 and R84 and capacitor C 47, C49 and C52.Wherein resistance R 83 and R84 carry out dividing potential drop to anti-sharp voltage signal, as the FEEDBACK CONTROL end of three-terminal voltage-stabilizing pipe U2, by the conducting of three-terminal voltage-stabilizing pipe U2 control triode Q6.
So the control end threshold voltage vt h*(R83+R84 of the voltage U of linear voltage stabilization unit 2 final outputs=three-terminal voltage-stabilizing pipe U2)/R84.
Described linear voltage-stabilizing circuit is the habitual voltage stabilizing circuit in this area, so give unnecessary details no longer in detail its workflow herein, and described linear voltage stabilization unit 2 can also adopt any voltage stabilizing circuit that can realize voltage stabilizing function, such as LDO circuit, bootstrap circuit boost, Buck circuit, Boost circuit or Buck-Boost circuit etc.
The described pwm signal unit 3 of present embodiment is used for the described anti-anti-phase pwm signal that swashs output unit 1 output is converted into the positive pwm signal.Present embodiment is for normal shock output unit 4 can be worked, undertaken anti-phasely by the anti-phase pwm signal that will instead swash output unit 1 output, but also come so that described anti-phase pwm signal can mate the PWM input voltage requirement of normal shock output unit 4 by bleeder circuit.
So as shown in Figure 2, the described pwm signal unit 3 of present embodiment comprises a bleeder circuit and a negative circuit.Wherein the anode of diode D24 is directly received on 34 pin of transformer T1 in the present embodiment, thereby draws anti-phase pwm signal.The anti-phase pwm signal that is about to the coil output of transformer T1 is drawn before filtering, then through diode D24 rectification, produces a pwm signal that only has malleation.
Then the bleeder circuit of resistance R 93 and R94 formation carries out dividing potential drop to anti-phase pwm signal, described driven MOS pipe (metal oxide semiconductcor field effect transistor) Q7, resistance R 81 and R82 consist of negative circuit, wherein driven MOS pipe Q7 is again anti-phase with anti-phase pwm signal, produce the pwm signal of positive with resistance R 81 and R82, thus the switching tube Q9 of normal shock output unit 4.
The current limiting unit 5 of present embodiment is used for protecting described pwm signal unit 3 and linear voltage stabilization unit 2 thereby described current limiting unit 5 stops that described positive pwm signal is delivered to described normal shock output unit 4 when the anti-electric current that swashs voltage signal surpasses a threshold value.As shown in Figure 2, described current limiting unit 5 comprises resistance R 96 and R90, capacitor C 57 and triode Q8.
When adopting triode Q8 as current limiting unit 5, in case peak current surpasses setting threshold, switching tube Q9 grid is blocked and drags down, and switching tube Q9 turn-offs.Electric weight in the capacitor C 57 is by resistance R 90 and R96 bleed off, and triode Q8 turn-offs, and switching tube Q9 grid blocks and is disengaged, when next Continuity signal arrives again, but switching tube Q9 normal switch, the normal shock output circuit part can normally be exported.
If adopt in addition exclusive circuit to replace triode Q8, when peak current surpassed setting threshold, exclusive circuit will drag down the grid of switching tube Q9 for a long time, only has Switching Power Supply thoroughly to cut off the power supply, and re-powering could release.Otherwise normal shock efferent branch is in blocked styate always.
So can effectively effectively protect abnormal conditions such as normal shock output short-circuit, heavy duties by current limiting unit 5.
The anti-maximum duty cycle that swashs anti-phase pwm signal in the output unit 1 in the present embodiment is set in below 0.5, just allows normal shock output unit 4 also can work.And normal shock output unit 4 is directly used capacitor filtering.Capacitance output current and power supply ripple as required requires to determine.
Be the way of output that directly adopts large capacitor filtering in the present embodiment, do not need fly-wheel diode, be very different with LC filtering.The tributary output voltage that finally obtains is:
Final VD=DC input voitage * transformer coil the turn ratio
According to the output current size, reasonably determine the appearance value of filter capacitor, and control to a certain extent the minimum duty cycle of PWM, the so transformer coil turn ratio one timing, final VD is only determined by DC input voitage.Because the DC input voitage of forward converter is to be obtained by linear voltage stabilizing circuit, can think the direct voltage fixed, so can obtain stable VD, this voltage is not subjected to the impact of PWM duty ratio, just can not be subject to the impact of circuit of reversed excitation output loading variation and input voltage fluctuation yet.In addition, owing to be the normal shock mode of operation, loading on when changing of each road output of normal shock, very little to the voltage influence on other road.
Adopt the voltage stabilizing of advanced line shape, the mode of isolating again output in the present embodiment.Only need a linear voltage regulation unit 2 just can realize voltage stabilizing function.And present embodiment is placed on linear voltage stabilizing the prime of isolation output; when load short circuits; the switching tube Q9 of normal shock output will be turn-offed by current limiting unit 5, and the linear voltage regulation unit 2 of prime stops to export energy, so linear voltage regulation unit 2 will well be protected.
The Switching Power Supply of present embodiment can be used as positive-negative power, fan and relay power, the CPU(central processing unit of the comparison amplifying circuit of frequency converter) and peripheral circuit power supply and IGBT driving power etc.
Although more than described the specific embodiment of the present invention, it will be understood by those of skill in the art that these only illustrate, protection scope of the present invention is limited by appended claims.Those skilled in the art can make various changes or modifications to these execution modes under the prerequisite that does not deviate from principle of the present invention and essence, but these changes and modification all fall into protection scope of the present invention.
Claims (7)
1. a Switching Power Supply is characterized in that, described Switching Power Supply comprises: an anti-sharp output unit, a linear voltage stabilization unit, a pwm signal unit and a normal shock output unit;
Described anti-sharp output unit is electrically connected with described linear voltage stabilization unit and pwm signal unit respectively, and described linear voltage stabilization unit and pwm signal unit also are electrically connected with described normal shock output unit;
Wherein said anti-output unit output one anti-sharp voltage signal and the anti-phase pwm signal that swash; Described linear voltage stabilization unit carries out voltage stabilizing to described anti-sharp voltage signal; Described pwm signal unit is used for described anti-phase pwm signal is converted into a positive pwm signal; Described anti-after based on voltage stabilizing of described normal shock output unit swashs voltage signal and described positive pwm signal output normal shock voltage signal.
2. Switching Power Supply as claimed in claim 1 is characterized in that, described linear voltage stabilization unit is LDO circuit, bootstrap circuit boost, Buck circuit, Boost circuit or Buck-Boost circuit.
3. Switching Power Supply as claimed in claim 1, it is characterized in that, described pwm signal unit comprises a bleeder circuit and a negative circuit, wherein said bleeder circuit obtains anti-phase pwm signal from described anti-sharp output unit, and described bleeder circuit and negative circuit are to described anti-phase pwm signal dividing potential drop and the described positive pwm signal of anti-phase acquisition.
4. Switching Power Supply as claimed in claim 1, it is characterized in that, described Switching Power Supply also comprises a current limiting unit, and when the anti-electric current that swashs voltage signal surpassed a threshold value, described current limiting unit stopped described positive pwm signal is delivered to described normal shock output unit.
5. Switching Power Supply as claimed in claim 4 is characterized in that, described current limiting unit is peak limiter circuit or exclusive circuit.
6. Switching Power Supply as claimed in claim 1, it is characterized in that, describedly anti-swash output unit and also comprise one first rectification filtering unit, described the first rectification filtering unit is used for instead swashing the anti-of output unit output and swashing voltage signal rectification and filtering described, and exports described linear voltage stabilization unit to.
7. Switching Power Supply as claimed in claim 1, it is characterized in that, described normal shock output unit also comprises one second rectification filtering unit, described the second rectification filtering unit is used for the rectification of normal shock voltage signal and the filtering to described normal shock output unit output, and the described normal shock voltage signal of wherein said the second rectification filtering unit after with rectifying and wave-filtering maintains the peak value of the described normal shock voltage signal before the rectifying and wave-filtering.
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| CN201210331309.XA CN102891606B (en) | 2012-09-07 | 2012-09-07 | Switching power supply |
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| CN201210331309.XA CN102891606B (en) | 2012-09-07 | 2012-09-07 | Switching power supply |
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Cited By (6)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN104079187A (en) * | 2013-03-14 | 2014-10-01 | 全汉企业股份有限公司 | Power supply apparatus |
| CN105553278A (en) * | 2016-01-27 | 2016-05-04 | 苏州时运机器人有限公司 | Flyback switching power supply and power output transformer thereof |
| CN105867502A (en) * | 2016-05-18 | 2016-08-17 | 湖州绿明微电子有限公司 | LDO voltage regulator and alternating-current equipment |
| CN107681900A (en) * | 2017-10-27 | 2018-02-09 | 中国航空无线电电子研究所 | The power supply of multimode output/impulse modulation conversion Multiplexing module |
| CN110912409A (en) * | 2019-11-07 | 2020-03-24 | 广州金升阳科技有限公司 | Forward and reverse excitation type switching power supply circuit |
| CN112098708A (en) * | 2020-11-23 | 2020-12-18 | 成都市易冲半导体有限公司 | Line voltage information detection circuit and detection method for secondary side PD controller |
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| Publication number | Priority date | Publication date | Assignee | Title |
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| CN104079187A (en) * | 2013-03-14 | 2014-10-01 | 全汉企业股份有限公司 | Power supply apparatus |
| CN105553278A (en) * | 2016-01-27 | 2016-05-04 | 苏州时运机器人有限公司 | Flyback switching power supply and power output transformer thereof |
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| CN107681900A (en) * | 2017-10-27 | 2018-02-09 | 中国航空无线电电子研究所 | The power supply of multimode output/impulse modulation conversion Multiplexing module |
| CN110912409A (en) * | 2019-11-07 | 2020-03-24 | 广州金升阳科技有限公司 | Forward and reverse excitation type switching power supply circuit |
| CN110912409B (en) * | 2019-11-07 | 2020-12-18 | 广州金升阳科技有限公司 | Forward and reverse excitation type switching power supply circuit |
| CN112098708A (en) * | 2020-11-23 | 2020-12-18 | 成都市易冲半导体有限公司 | Line voltage information detection circuit and detection method for secondary side PD controller |
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| CN102891606B (en) | 2015-11-25 |
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