CN102223101A - Control method for dual-bucking full-bridge grid-connected inverter - Google Patents
Control method for dual-bucking full-bridge grid-connected inverter Download PDFInfo
- Publication number
- CN102223101A CN102223101A CN2011101670721A CN201110167072A CN102223101A CN 102223101 A CN102223101 A CN 102223101A CN 2011101670721 A CN2011101670721 A CN 2011101670721A CN 201110167072 A CN201110167072 A CN 201110167072A CN 102223101 A CN102223101 A CN 102223101A
- Authority
- CN
- China
- Prior art keywords
- power switch
- switch tube
- grid
- power
- signal
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Pending
Links
- 238000000034 method Methods 0.000 title claims abstract description 15
- 238000005070 sampling Methods 0.000 claims description 9
- 238000006243 chemical reaction Methods 0.000 abstract description 2
- 238000010586 diagram Methods 0.000 description 9
- 230000003247 decreasing effect Effects 0.000 description 8
- 239000000446 fuel Substances 0.000 description 2
- 238000010248 power generation Methods 0.000 description 2
- 238000004088 simulation Methods 0.000 description 2
- 230000007547 defect Effects 0.000 description 1
- 230000009977 dual effect Effects 0.000 description 1
- 238000003912 environmental pollution Methods 0.000 description 1
Images
Landscapes
- Inverter Devices (AREA)
Abstract
The invention discloses a control method for a dual-bucking full-bridge grid-connected inverter, belonging to an inverter control method. In the invention, the grid current of the grid-connected inverter is sampled by a current sensor; the network voltage is sampled by a voltage sensor; the grid current given having the same frequency and the same phase with the network voltage is output by a phase locking ring; a grid current ring receives the grid current given and the grid current feedback signal and outputs the voltage given 1. A PWM (pulse-width modulation) generating circuit receives the voltage given 1 and outputs logic control signals PWM1 and PWM2. A power switch tube drives the logic circuit to receive the logic control signals PWM1 and the PWM 2 as well as the network voltage feedback signal, and outputs the high and low level driving signals of all power switch tubes. In the invention, single-polarity frequency-doubling control is realized, the volume and the weight of a filter are reduced, the problem of zero crossing point distortion occurring to the traditional single-polarity modulation network current does not exist, only two power switch tube high-frequency switches are used in every half working frequency period, and the conversion efficiency is improved.
Description
Technical Field
The invention relates to a control method of an inverter, in particular to a control method of a double-buck full-bridge grid-connected inverter.
Background
With the continuous shortage of fossil energy and the increasing increase of environmental pollution, renewable energy sources such as solar energy and fuel cells are more and more concerned by people in distributed power generation systems due to the characteristics of cleanness, safety, no pollution, renewability and the like. However, since the output of a solar cell, a fuel cell, or the like is direct current and the grid voltage is alternating current, a grid-connected inverter becomes an important component in a distributed power generation system. In order to ensure the normal operation of the power grid, the grid-connected inverter is required to have high reliability. The traditional bridge grid-connected inverter has the problem of bridge arm direct connection, so that in order to ensure that the power switch tubes of the bridge arms are not direct connected, the power switch tubes of the same bridge arm must be provided with dead time, and the waveform quality of the network access current is reduced. The double-buck full-bridge grid-connected inverter has no problem of direct connection of bridge arm power switch tubes of the traditional bridge-type inverter, so that the reliability of the system is improved. However, the grid-connected inverter adopts bipolar modulation, and the size and the weight of a filter are increased compared with those of a filter with single polarity. And the traditional unipolar modulation method has the problem of zero crossing distortion.
Disclosure of Invention
The invention aims to solve the technical problem of providing a control method of a double-buck full-bridge grid-connected inverter aiming at the defects of the prior art.
The invention relates to a control method of a double-buck full-bridge grid-connected inverter, which comprises a power grid, a power supply, a first filter inductor, a first power switch tube, a first fly-wheel diode, a second filter inductor, a second power switch tube, a second fly-wheel diode, a third filter inductor, a third power switch tube, a third fly-wheel diode, a fourth filter inductor, a fourth power switch tube and a fourth fly-wheel diode, wherein the positive pole of the power supply is respectively connected with the drain electrode of the first power switch tube, the cathode of the second fly-wheel diode, the drain electrode of the third power switch tube and the cathode of the fourth fly-wheel diode, the source electrode of the first power switch tube is respectively connected with the cathode of the first fly-wheel diode and the input end of the first filter inductor, the output end of the first filter inductor is respectively connected with the positive pole of the power grid and the output end of the second filter inductor, the input end of the second filter inductor is respectively connected with the anode of a second fly-wheel diode and the drain electrode of a second power switch tube, the source electrode of the second power switch tube is respectively connected with the cathode of a power supply, the source electrode of a fourth power switch tube, the anode of a first fly-wheel diode and the anode of a third fly-wheel diode, the cathode of the third fly-wheel diode is respectively connected with the input end of a third filter inductor and the source electrode of a third power switch tube, the drain electrode of the fourth power switch tube is respectively connected with the input end of a fourth filter inductor and the anode of the fourth fly-wheel diode, and the output end of the third filter inductor is respectively connected with the cathode of a power grid and the output end of the fourth filter inductor and grounded; sampling the network access current by adopting a current sensor and outputting a network access current feedback signal; sampling the power grid voltage by using a voltage sampling circuit to output a power grid voltage feedback signal; outputting the network voltage feedback signal to a given network current with the same frequency and phase as the network voltage through a phase-locked loop; outputting a power frequency switch logic signal by the power grid voltage feedback signal through a first comparator; outputting a non-signal of the power frequency switch logic signal through a first NOT gate; subtracting the network inlet current feedback signal from the network inlet current given signal, and outputting a voltage given value 1 through a network inlet current regulator; outputting a logic control signal PWM1 by a second comparator by the voltage given 1 and the triangular carrier signal; after the voltage given by 1 is given by 2 through the output voltage of the inverter, the logic control signal PWM2 is output together with the triangular carrier signal through a third comparator; outputting a switching logic signal of a first power switching tube by the logic control signal PWM1 and the power frequency switching logic signal through a first AND gate, and driving the first power switching tube by the switching logic signal of the first power switching tube through a first driving circuit; the logic control signal PWM1 passes through a second NOT gate and then outputs a switch logic signal of a second power switch tube together with a NOT signal of the power frequency switch logic through a second AND gate, and the switch logic signal of the second power switch tube drives the second power switch tube through a second driving circuit; outputting a switching logic signal of a third power switching tube by a non-signal of the logic control signal PWM2 and the power frequency switching logic through a third AND gate, and driving the third power switching tube by the switching logic signal of the third power switching tube through a third driving circuit; and outputting a switching logic signal of a fourth power switching tube by the logic control signal PWM2 through a third NOT gate and the power frequency switching logic signal through a fourth AND gate, and driving the fourth power switching tube by the switching logic signal of the fourth power switching tube through a fourth driving circuit.
The invention only needs 1 current sensor, thus reducing the cost; compared with unipolar modulation, the volume and the weight of the filter can be further reduced by adopting unipolar frequency multiplication modulation, and the problem of zero crossing distortion of the current of the traditional unipolar modulation in a network does not exist; compared with the traditional full-bridge inverter, each half power frequency period is only provided with 2 power switch tubes for high-frequency switching, and the conversion efficiency is improved.
Drawings
FIG. 1: the invention is a control system block diagram;
FIG. 2: the main waveform of the invention is shown schematically;
FIG. 3: the working principle diagram of the invention in the switch mode 1;
FIG. 4: the working principle diagram of the invention in the switch mode 2;
FIG. 5: the working principle diagram of the invention in the switch mode 3;
FIG. 6: the working principle diagram of the invention in the switch mode 4;
FIG. 7: the working principle diagram of the invention in the switch mode 5;
FIG. 8: the working principle diagram of the invention in the switch mode 6;
FIG. 9: comparing the network access current with the prior art, the invention simulates a oscillogram;
FIG. 10: the invention compares the first positive half cycle voltage of the filter with the prior art to simulate a waveform diagram.
Detailed Description
As shown in fig. 1. A control method for a double-step-down full-bridge grid-connected inverter comprises a power grid griduAnd a power supply inUA first filter inductorL 1A first power switch tube S1A first freewheeling diode D1A second filter inductorL 2A second power switch tube S2A second freewheeling diode D2And a third filter inductorL 3The third power switch tube S3A third freewheeling diode D3And a fourth filter inductorL 4The fourth power switch tube S4And a fourth freewheeling diode D4Wherein the power supply inURespectively with the first power switch tube S1Drain electrode of (1), second freewheeling diode D2Cathode of the third power switch tube S3Drain electrode of and a fourth freewheeling diode D4Is connected to the cathode of the first power switch tube S1Respectively with the source electrode ofFirst freewheeling diode D1Cathode and first filter inductorL 1Is connected with the first filter inductorL 1Respectively with the power grid griduPositive pole and second filter inductanceL 2Is connected to the output terminal of the second filter inductorL 2Respectively with a second freewheeling diode D2And a second power switch tube S2Is connected to the drain of the second power switch tube S2Respectively with a power supply inUNegative pole of (1), fourth power switch tube S4Source electrode of, first freewheeling diode D1And a third freewheeling diode D3Is connected to the anode of a third freewheeling diode D3Respectively with a third filter inductorL 3And a third power switch tube S3Is connected to the source of the fourth power switch tube S4Respectively with the fourth filter inductorL 4And a fourth freewheeling diode D4Anode connection of, a third filter inductanceL 3Respectively with the power grid griduNegative pole and fourth filter inductanceL 4The output end of the transformer is connected with the ground;
the control method comprises the following steps: sampling of grid-in current using current sensors giOutputting a current feedback signal gfi(ii) a Sampling power grid voltage by adopting voltage sampling circuit griduOutputting a grid voltage feedback signal gridfu(ii) a Feeding back the grid voltage gridfuOutputting and network voltage by phase-locked loop PLL griduSame-frequency and same-phase network access current setting refi(ii) a Feeding back the grid voltage gridfuOutputting a power frequency switch logic signal through a first comparator; outputting a non-signal of the power frequency switch logic signal through a first NOT gate; setting the network inlet current to refiAnd the current feedback signal of the network gfiThe output voltage through the grid-inlet current regulator after subtraction is given by 1 refu 1(ii) a Giving the voltage 1 refu 1And a triangular carrier signal cuOutputting a logic control signal PWM1 through a second comparator; giving the voltage 1 refu 1Given by inverter output voltage 2 refu 2Rear and triangular carrier signals cuOutputting a logic control signal PWM2 through a third comparator; outputting the logic control signal PWM1 and the power frequency switch logic signal to a first power switch tube S through a first AND gate1The first power switch tube S1The switch logic signal drives a first power switch tube S through a first drive circuit1(ii) a The logic control signal PWM1 passes through a second NOT gate and then outputs a NOT signal of the logic with the power frequency switch through a second AND gate to a second power switch tube S2The second power switch tube S2The switch logic signal drives a second power switch tube S through a second drive circuit2(ii) a Outputting a non-signal of the logic control signal PWM2 and the power frequency switch logic to a third power switch tube S through a third AND gate3The third power switch tube S3The switch logic signal drives a third power switch tube S through a third driving circuit3(ii) a The logic control signal PWM2 passes through a third NOT gate and then is output to a fourth power switch tube S together with a power frequency switch logic signal through a fourth AND gate4Said fourth power switch tube S4The switch logic signal drives a fourth power switch tube S through a fourth driving circuit4。
Fig. 2 is a schematic diagram of main waveforms of the dual buck full-bridge grid-connected inverter according to the present invention. When in use gridu>0, the second power switch tube S2And a third power switch tube S3Turn-off, first power switch tube S1And a fourth power switch tube S4Is staggered by 180◦High-frequency modulation, wherein the inverter has 3 working modes, namely a switching mode 1, a switching mode 2 and a switching mode 3; when in use gridu<0, the first power switch tube S1And a fourth power switch tube S4Turn-off, second power switch tube S2And a third power switch tube S3Is staggered by 180◦And (3) high-frequency modulation, wherein the inverter has 3 working modes, namely a switching mode 4, a switching mode 5 and a switching mode 6.
As shown in fig. 3, switching mode 1:
second power switch tube S2And a third power switch tube S3Turn-off, first power switch tube S1And a fourth power switch tube S4On, power supply inUIs supplied by a power supply inUThe positive pole of the first power switch tube S passes through the first power switch tube S in turn1First filter inductorL 1Electric network griduFourth filter inductorL 4Fourth power switch tube S4Back to the power supply inUNegative pole of (2), current of entering network giPositive increase, A, D voltage between two pointsU ADIs turned into inU。
As shown in fig. 4, switching mode 2:
second power switch tube S2The third power switch tube S3And a fourth power switch tube S4Turn-off, first power switch tube S1Conducting current from the power supply inUThe positive pole of the first power switch tube S passes through the first power switch tube S in turn1First filter inductorL 1Electric network griduFourth filter inductorL 4Fourth freewheeling diode D4Returning to the positive pole of the power supply and supplying current to the network giThe forward direction is decreased and the forward direction is decreased,U ADis 0.
As shown in fig. 5, switching mode 3:
first power switch tube S1A second power switch tube S2And a third power switch tube S3Turn-off, fourth power switch tube S4Conducting current from the power supply inUIs sequentially passed through the first freewheeling diode D1First filter inductorL 1Electric network griduFourth filter inductorL 4Fourth power switch tube S4Returning to the negative pole of the power supply and supplying current to the network giThe forward direction is decreased and the forward direction is decreased,U ADis 0.
As shown in fig. 6, switching mode 4:
first power switch tube S1And a fourth power switch tube S4Turn-off, second power switch tube S2And a third power switch tube S3On, power supply inUIs supplied by a power supply inUThe anode of the first power switch tube passes through the third power switch tube S in turn3Third filter inductanceL 3Electric network griduSecond filter inductorL 2Second power switch tube S2Back to the power supply inUNegative pole of (2), current of entering network giIncreasing negatively B, C voltage between two pointsU BCFor the purpose of inU。
As shown in fig. 7, switching mode 5:
first power switch tube S1The third power switch tube S3And a fourth power switch tube S4Turn-off, second power switch tube S2Conducting current from the power supply inUIs sequentially passed through a third freewheeling diode D3Third filter inductanceL 3Electric network griduSecond filter inductorL 2Second power switch tube S2Back to the power supply inUNegative pole of (2), current of entering network giThe negative direction is decreased, and the negative direction is decreased,U BCis 0.
As shown in fig. 8, switching mode 6:
first power switch tube S1A second power switch tube S2And a fourth power switch tube S4Turn-off, third power switch tube S3Conducting current from the power supply inUThe anode of the first power switch tube passes through the third power switch tube S in turn3Third filter inductanceL 3Electric network griduSecond, secondFilter inductorL 2Second freewheeling diode D2Back to the power supply inUPositive electrode of (2), current of entering network giThe negative direction is decreased, and the negative direction is decreased,U BCis 0.
A simulation comparison study was conducted on the present invention and the prior art as shown in fig. 9 and 10. Wherein, gi 1、 gi 2and gi 3according to the invention, the network access current is controlled by bipolar and traditional unipolar;u AD1、u AD2andu AD3respectively, the first positive half cycle voltage of the filter under bipolar and traditional unipolar control. The specific simulation parameters are as follows:
1) power supply inU：360V；
2) Filter inductorL 1~ L 4:550μH；
3) Electric network gridu：220V/50Hz；
4) Output power: 1 kW;
5) triangular carrier signal cuFrequency of (d): 50 kHz.
As can be seen from fig. 9, the network access current waveform quality of the present invention is the best, and the network access current has severe zero-crossing distortion in the conventional unipolar modulation control method, which greatly reduces the network access current waveform quality. The total harmonic content of the network-incoming current under the control of the bipolar and the traditional unipolar of the invention is 5.854%, 14.02% and 22.53%, respectively. Therefore, under the condition of the same filter parameters, compared with the prior art, the harmonic content of the network access current is the lowest, and the waveform quality of the network access current is greatly improved. As can be seen from fig. 10, the frequency of the first positive half cycle voltage of the filter of the present invention is 2 times that of the prior art at the same switching frequency. Similarly, the voltage of the first and second half cycles of the filter has similar conclusions.
In summary, compared with the prior art, the method has the following advantages under the condition of keeping the same quality of the network inlet current waveform:
1) compared with a common unipolar grid-connected inverter, the problem of zero crossing distortion of the traditional unipolar modulation grid-connected current does not exist, the frequency in front of the filter is 2 times of the switching frequency, and the volume and weight of the filter are reduced;
2) compared with the traditional bipolar double-buck full-bridge grid-connected inverter, the filter volume and weight are greatly reduced under the condition of the same switching frequency.
Claims (1)
1. A control method of a double-buck full-bridge grid-connected inverter comprises a power grid (A)u grid ) Power supply (a)U in ) A first filter inductor (L 1) A first power switch tube (S)1) A first freewheeling diode (D)1) A second filter inductor (L 2) A second power switch tube (S)2) A second freewheeling diode (D)2) A third filter inductor (L 3) And the third power switch tube (S)3) A third freewheeling diode (D)3) A fourth filter inductor (L 4) And the fourth power switch tube (S)4) And a fourth freewheeling diode (D)4) Wherein the power supply (U in ) Respectively with the first power switch tube (S)1) Drain electrode of (1), second freewheeling diode (D)2) Cathode of (2), third power switch tube (S)3) And a fourth freewheeling diode (D)4) Is connected to the cathode of the first power switch tube (S)1) Respectively with a first freewheeling diode (D)1) And a first filter inductor (L 1) Is connected to the first filter inductor (L 1) Respectively with the grid (u grid ) And the second filter inductance (L 2) Is connected to the output terminal of the second filter inductor (L 2) Respectively with a second freewheeling diode (D)2) And a second power switch tube (S)2) Is connected to the drain of the second power switch tube (S)2) Respectively with a power supplyU in ) Negative pole of (1), fourth power switch tube (S)4) Source electrode of (D), first freewheeling diode (D)1) And a third freewheeling diode (D)3) Is connected to the anode of a third freewheeling diode (D)3) Respectively with the third filter inductor (L 3) And a third power switch tube (S)3) Is connected to the source of the fourth power switch tube (S)4) And the drain electrode of (1) is respectively connected with a fourth filter inductorL 4) And a fourth freewheeling diode (D)4) Anode connection of (1), third filter inductanceL 3) Respectively with the grid (u grid ) Negative pole and fourth filter inductor: (L 4) The output end of the transformer is connected with the ground;
the method is characterized in that: sampling the grid-in current by current sensor gi) Output the current feedback signal of the network ( gfi) (ii) a Sampling the grid voltage by a voltage sampling circuit ( gridu) Output grid voltage feedback signal: ( gridfu) (ii) a (ii) feeding back the grid voltage signal: ( gridfu) Output and grid voltage by phase-locked loop (PLL) (( gridu) Same frequency and same phase network inlet current given ( refi) (ii) a (ii) feeding back the grid voltage signal: ( gridfu) Outputting a power frequency switch logic signal through a first comparator; outputting a non-signal of the power frequency switch logic signal through a first NOT gate; the network inlet current is given by ( refi) And a network current feedback signal ( gfi) The output voltage after subtraction is given by the grid-in current regulator 1 refu 1) (ii) a The voltage is given by 1 ( refu 1) And a triangular carrier signal ( cu) Outputting a logic control signal PWM1 through a second comparator; the voltage is given by 1 ( refu 1) Given by inverter output voltage 2: ( refu 2) Rear and triangular carrier signals: ( cu) Outputting a logic control signal PWM2 through a third comparator; the logic control signal PWM1 and the power frequency switch logic signal are output to a first power switch tube through a first AND gate (S)1) Said first power switch tube (S)1) The switch logic signal drives the first power switch tube through the first drive circuit (S)1) (ii) a The logic control signal PWM1 passes through a second NOT gate and then outputs a NOT signal of the logic with the power frequency switch to a second power switch tube through a second AND gate (S)2) Said second power switch tube (S)2) The switch logic signal drives a second power switch tube through a second drive circuit (S)2) (ii) a Outputting the logical control signal PWM2 and the logical negation signal of the power frequency switch to a third power switch tube through a third AND gate (S)3) Said third power switch tube (S)3) The switch logic signal drives a third power switch tube through a third driving circuit (S)3) (ii) a Passing the logic control signal PWM2 through a third NOT gate and then switching the logic control signal with power frequencyA fourth power switch tube (S) is output through a fourth AND gate4) Said fourth power switch tube (S)4) The switch logic signal drives a fourth power switch tube through a fourth driving circuit (S)4）。
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN2011101670721A CN102223101A (en) | 2011-06-21 | 2011-06-21 | Control method for dual-bucking full-bridge grid-connected inverter |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN2011101670721A CN102223101A (en) | 2011-06-21 | 2011-06-21 | Control method for dual-bucking full-bridge grid-connected inverter |
Publications (1)
| Publication Number | Publication Date |
|---|---|
| CN102223101A true CN102223101A (en) | 2011-10-19 |
Family
ID=44779547
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN2011101670721A Pending CN102223101A (en) | 2011-06-21 | 2011-06-21 | Control method for dual-bucking full-bridge grid-connected inverter |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN102223101A (en) |
Cited By (13)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN102570872A (en) * | 2012-02-23 | 2012-07-11 | 石家庄通合电子有限公司 | Single-phase grid-connection inverter circuit |
| CN104578852A (en) * | 2013-10-11 | 2015-04-29 | 台达电子工业股份有限公司 | Solar photocell source converting system and operation method thereof |
| TWI485968B (en) * | 2014-01-29 | 2015-05-21 | Delta Electronics Inc | Power conversion system and method of operating the same |
| CN104716858A (en) * | 2015-03-13 | 2015-06-17 | 浙江乔兴建设集团湖州智能科技有限公司 | Zero-current-ripple full-bridge grid-connected inverter circuit |
| CN104753378A (en) * | 2015-04-03 | 2015-07-01 | 成都麦隆电气有限公司 | Three-level inverter midpoint potential balance control method |
| TWI508424B (en) * | 2013-10-11 | 2015-11-11 | Delta Electronics Inc | Solar photovoltaic power conversion system and method of operating the same |
| CN105262356A (en) * | 2015-09-25 | 2016-01-20 | 河海大学 | Input capacitance self voltage-equalizing method for five-level full bridge grid-connected inverter |
| CN107196547A (en) * | 2017-06-22 | 2017-09-22 | 南京航空航天大学 | A kind of symmetrical complete period modulator approach of the double buck combining inverters of three-phase |
| CN107196491A (en) * | 2017-06-22 | 2017-09-22 | 南京航空航天大学 | A kind of pair of buck combining inverter half periods current distortion suppression system and its method |
| CN107425744A (en) * | 2017-07-10 | 2017-12-01 | 南京航空航天大学 | The output waveform of inverter improves and the control method of low-loss short circuit operation |
| CN108736758A (en) * | 2018-06-26 | 2018-11-02 | 西南石油大学 | A kind of double bucking full-bridge grid-connected inverters based on multiple-frequency modulation |
| TWI696341B (en) * | 2019-01-24 | 2020-06-11 | 達方電子股份有限公司 | Power conversion system and operating method |
| CN114498643A (en) * | 2022-01-25 | 2022-05-13 | 上海电力大学 | Grid-connected current harmonic suppression method based on improved phase-locked loop |
Citations (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN1595782A (en) * | 2004-07-01 | 2005-03-16 | 南京航空航天大学 | Double output double step-down type half bridge inverter, and control and modulation method |
| CN101388617A (en) * | 2008-11-05 | 2009-03-18 | 南京航空航天大学 | Double step-down bridge type inverter controlling method for single current sensor |
| CN101951185A (en) * | 2010-11-04 | 2011-01-19 | 盐城工学院 | Method for controlling dual buck grid-connected inverter |
-
2011
- 2011-06-21 CN CN2011101670721A patent/CN102223101A/en active Pending
Patent Citations (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN1595782A (en) * | 2004-07-01 | 2005-03-16 | 南京航空航天大学 | Double output double step-down type half bridge inverter, and control and modulation method |
| CN101388617A (en) * | 2008-11-05 | 2009-03-18 | 南京航空航天大学 | Double step-down bridge type inverter controlling method for single current sensor |
| CN101951185A (en) * | 2010-11-04 | 2011-01-19 | 盐城工学院 | Method for controlling dual buck grid-connected inverter |
Cited By (19)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN102570872A (en) * | 2012-02-23 | 2012-07-11 | 石家庄通合电子有限公司 | Single-phase grid-connection inverter circuit |
| CN104578852A (en) * | 2013-10-11 | 2015-04-29 | 台达电子工业股份有限公司 | Solar photocell source converting system and operation method thereof |
| TWI508424B (en) * | 2013-10-11 | 2015-11-11 | Delta Electronics Inc | Solar photovoltaic power conversion system and method of operating the same |
| CN104578852B (en) * | 2013-10-11 | 2017-05-10 | 台达电子工业股份有限公司 | Solar photocell source converting system and operation method thereof |
| US9300225B2 (en) | 2013-10-11 | 2016-03-29 | Delta Electronics, Inc. | Solar photovoltaic power conversion system and method of operating the same |
| US9306474B2 (en) | 2014-01-29 | 2016-04-05 | Delta Electronics, Inc. | Power conversion system and method of operating the same |
| TWI485968B (en) * | 2014-01-29 | 2015-05-21 | Delta Electronics Inc | Power conversion system and method of operating the same |
| CN104716858A (en) * | 2015-03-13 | 2015-06-17 | 浙江乔兴建设集团湖州智能科技有限公司 | Zero-current-ripple full-bridge grid-connected inverter circuit |
| CN104753378A (en) * | 2015-04-03 | 2015-07-01 | 成都麦隆电气有限公司 | Three-level inverter midpoint potential balance control method |
| CN105262356A (en) * | 2015-09-25 | 2016-01-20 | 河海大学 | Input capacitance self voltage-equalizing method for five-level full bridge grid-connected inverter |
| CN105262356B (en) * | 2015-09-25 | 2017-09-15 | 河海大学 | A kind of five Level Full Bridge combining inverter input capacitances are from method for equalizing voltage |
| CN107196547A (en) * | 2017-06-22 | 2017-09-22 | 南京航空航天大学 | A kind of symmetrical complete period modulator approach of the double buck combining inverters of three-phase |
| CN107196491A (en) * | 2017-06-22 | 2017-09-22 | 南京航空航天大学 | A kind of pair of buck combining inverter half periods current distortion suppression system and its method |
| CN107425744A (en) * | 2017-07-10 | 2017-12-01 | 南京航空航天大学 | The output waveform of inverter improves and the control method of low-loss short circuit operation |
| CN108736758A (en) * | 2018-06-26 | 2018-11-02 | 西南石油大学 | A kind of double bucking full-bridge grid-connected inverters based on multiple-frequency modulation |
| CN108736758B (en) * | 2018-06-26 | 2019-12-17 | 西南石油大学 | Double-buck full-bridge grid-connected inverter based on frequency multiplication modulation |
| TWI696341B (en) * | 2019-01-24 | 2020-06-11 | 達方電子股份有限公司 | Power conversion system and operating method |
| CN114498643A (en) * | 2022-01-25 | 2022-05-13 | 上海电力大学 | Grid-connected current harmonic suppression method based on improved phase-locked loop |
| CN114498643B (en) * | 2022-01-25 | 2024-04-19 | 上海电力大学 | Grid-connected current harmonic suppression method based on improved phase-locked loop |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| CN102223101A (en) | Control method for dual-bucking full-bridge grid-connected inverter | |
| CN102437772B (en) | Bipolar modulation control device of high frequency pulse alternating current link inverter | |
| CN101951185B (en) | Method for controlling dual buck grid-connected inverter | |
| CN102005962B (en) | Buck-boost grid-connected inverter and control method thereof | |
| CN104796030A (en) | Quasi-Z-source inverter based single-phase photovoltaic off-grid inverter and soft switch control method thereof | |
| CN206698111U (en) | It is a kind of using switched inductors and the quasi- boost switching DC DC converters of switching capacity | |
| CN102856916A (en) | Reactive power control method and circuit of single-phase photovoltaic inverter | |
| EP2731251B1 (en) | Inverter circuit and control method therefor, and inverter circuit control device | |
| CN101958660A (en) | Dual-Sepic buck-boost output parallel combined inverter | |
| CN102255544A (en) | DC (direct current)/AC (alternating current) inverter circuit | |
| CN101388616A (en) | Double step-down combining inverter | |
| CN103312165A (en) | High-frequency multiphase interleaved conversion device and control method | |
| CN202260487U (en) | Control device for single-phase photovoltaic grid-connected power generation system | |
| CN104158427B (en) | Single-phase transless isolated form Z source photovoltaic combining inverter and modulator approach | |
| CN205377786U (en) | Two pressure reducing type photovoltaic power generation system | |
| CN207720041U (en) | From grid-connected city's power production photovoltaic battery integration inverter | |
| CN109873559A (en) | The double BUCK-BOOST bucks of modularization export the combined inverter of inverse parallel | |
| CN205847090U (en) | A kind of mixed type quasi-boost switching DC DC changer | |
| CN204947919U (en) | A kind of parallel resonance no-voltage photovoltaic power generation apparatus | |
| CN109412447B (en) | Phase-shifting three-phase high-frequency chain matrix inverter topological structure and modulation method | |
| CN204948016U (en) | A kind of photovoltaic power generation apparatus adopting zero voltage switch auxiliary resonance | |
| CN111277160A (en) | Six-switch power decoupling circuit and control method thereof | |
| CN203562977U (en) | Photovoltaic inverter of Buck-Boost type topological structure | |
| CN103762880B (en) | Single-phase full bridge crisscross parallel photovoltaic combining inverter | |
| CN113224964B (en) | Control method of single-phase single-stage boost inverter |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| C06 | Publication | ||
| PB01 | Publication | ||
| C10 | Entry into substantive examination | ||
| SE01 | Entry into force of request for substantive examination | ||
| C02 | Deemed withdrawal of patent application after publication (patent law 2001) | ||
| WD01 | Invention patent application deemed withdrawn after publication |
Application publication date: 20111019 |