CN108736758B - Double-buck full-bridge grid-connected inverter based on frequency multiplication modulation - Google Patents

Double-buck full-bridge grid-connected inverter based on frequency multiplication modulation Download PDF

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CN108736758B
CN108736758B CN201810668373.4A CN201810668373A CN108736758B CN 108736758 B CN108736758 B CN 108736758B CN 201810668373 A CN201810668373 A CN 201810668373A CN 108736758 B CN108736758 B CN 108736758B
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switch tube
power switch
diode
grid
inductor
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CN108736758A (en
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代云中
李佳
李祎
杜程茂
庄圣贤
张荣飞
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Southwest Petroleum University
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H02M7/5387—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration

Abstract

the invention discloses a double-buck full-bridge grid-connected inverter based on frequency multiplication modulation, which comprises a power switch tube S5Drain electrode of and DC voltage Udcpositive electrode phase connection, S5Respectively connected with the power switch tubeS1Drain electrode of (2), diode D2Negative electrode of (1), power switch tube S3And diode D4Are connected with each other. The inverter of the invention adopts frequency multiplication modulation in control, and can be increased by 2 times compared with the original inverter when the switching frequency is not changed, thereby obtaining higher output voltage frequency and improving the grid-connected electric energy quality; the isolation of an alternating current side and a direct current side is realized structurally, and the direct current component of grid-connected voltage is reduced; and the switching tube is in a half-cycle working mode, so that the switching loss is reduced, and the grid-connected current of the follow current loop does not pass through the body diode with poor performance, so that the invention has the advantages of low total harmonic distortion rate of the current of the power grid and high reliability.

Description

Double-buck full-bridge grid-connected inverter based on frequency multiplication modulation
Technical Field
The invention relates to the field of photovoltaic grid-connected inverters, in particular to a double-buck full-bridge grid-connected inverter based on frequency multiplication modulation.
Background
Although the existing double-Buck full-bridge grid-connected inverter has the advantages of high direct-current voltage utilization rate, no common-mode leakage current, three-level output, low loss and the like, two direct-current inductors exist in a circuit, the size is large, and only one inductor is in a working state all the time when the circuit works, so that the utilization rate of a magnetic element is low, the system cost is high, and the power density is low; in addition, decoupling is not realized between the direct current side and the alternating current side of the inverter, so that the content of direct current components of grid-connected current is high. If a bipolar frequency multiplication modulation strategy is adopted, the equivalent working frequency of the grid-connected inverter topology is 2 times of the original equivalent working frequency, so that output current ripples are reduced, the harmonic content and the THD value of grid-connected current are reduced, the grid-connected electric energy quality is improved, and the volume and the loss of an output filter are reduced. And if the double step-down grid-connected inverter adopts frequency multiplication modulation, larger common mode leakage current can be generated.
Disclosure of Invention
Aiming at the defects in the prior art, the double-buck full-bridge grid-connected inverter based on frequency multiplication modulation solves the problems of large current harmonic content, large leakage current, large filter inductance volume and high cost of the conventional double-buck grid-connected inverter.
The technical scheme for solving the technical problems is as follows: a double-step-down full-bridge grid-connected inverter based on frequency multiplication modulation comprises a power switch tube S5said power switch tube S5Drain electrode of and DC voltage UdcThe positive electrodes are connected, and the power switch tube S5Respectively with the power switch tube S1Drain electrode of (2), diode D2Negative electrode of (1), power switch tube S3And diode D4The negative electrodes are connected; the power switch tube S6Source and U ofdcThe negative pole is connected with the power switch tube S6Respectively with the power switch tube S2Source electrode of (2), diode D1Positive electrode of (2), power switch tube S4Source and diode D3The positive electrodes of the two electrodes are connected; the power switch tube S1With the gate of the transistor as a node A and a diode D respectively1Negative electrode and inductor LAOne end of the two ends are connected; the power switch tube S1as node A and respectively with D1negative electrode and inductor LAOne end of the two ends are connected; the inductance LDThe other end of the first switch is used as an output end G which is grounded;
the diode D2With the positive pole of the switch tube S as the node B2Drain electrode and inductor L ofBOne end of the two ends are connected; the power switch tube S3With the source as node D and respectively connected with diode D3Negative electrode, inductor LBOne terminal of (1) and an inductance LDOne end of the two ends are connected; the diode D4As node C and respectively with S4Drain electrode of (1), inductor LAOne terminal of (1) and an inductance LCOne end phase ofAnd (4) connecting.
On the basis of the technical scheme, the invention can be further improved as follows.
Further, the power switch tube S1Power switch tube S2Power switch tube S3Power switch tube S4Power switch tube S5And a power switch tube S6are all metal oxide semiconductor field effect transistors.
Further, the inductance LAInductor LBInductor LCAnd an inductance LDAre all filter inductors.
The invention has the beneficial effects that:
1. The inverter of the invention adopts frequency multiplication modulation in control, and the switching frequency is improved to 2 times of the original switching frequency, thereby obtaining higher output voltage frequency and improving the quality of grid-connected electric energy. The inverter structurally realizes the isolation of an alternating current side and a direct current side, and reduces the direct current component of grid-connected voltage. In addition, a switching tube of the inverter is in a half-cycle working mode, switching loss is reduced, and grid-connected current of the follow current loop does not pass through a body diode with poor performance. Therefore, the invention has the advantages of low total harmonic distortion rate of the power grid current, high efficiency and high reliability.
2. The common-mode voltage of the invention in the whole power frequency period is Udc/2. Therefore, the invention can eliminate the common-mode leakage current of the existing double-buck grid-connected inverter.
Drawings
FIG. 1 is a schematic circuit diagram of the present invention;
FIG. 2 shows the driving and output voltage u of the present invention under unipolar modulationAB，uCDOscillogram and power switch tube S1～S6A driving waveform diagram;
FIG. 3 is a diagram of an equivalent common mode resonant circuit of DPGCI in the positive half cycle;
FIG. 4 is a diagram of an equivalent common mode resonant circuit of DPGCI in a negative half cycle;
FIG. 5 is an equivalent circuit diagram of DPGCI in working mode 1;
Fig. 6 is an equivalent circuit diagram of the DPGCI in the operating mode 2;
fig. 7 is an equivalent circuit diagram of the DPGCI in the working mode 3;
Fig. 8 is an equivalent circuit diagram of the DPGCI in the operating mode 4;
Fig. 9 is an equivalent circuit diagram of the DPGCI in the working mode 5;
Fig. 10 is an equivalent circuit diagram of the DPGCI in the operating mode 6;
FIG. 11 is a grid-connected current and voltage experimental waveform modulated by frequency doubling SPWM;
FIG. 12 is an experimental waveform of output voltage and leakage current modulated by frequency doubling SPWM;
FIG. 13 shows u modulated with frequency doubled SPWMAN、uBNAnd ucmExperimental waveforms;
FIG. 14 shows u modulated with frequency doubled SPWMAN、uBNAnd ucmAmplifying the experimental waveform in the positive half period part;
Fig. 15 is a DPGCI simulation waveform using frequency doubled SPWM modulation.
Detailed Description
The following description of the embodiments of the present invention is provided to facilitate the understanding of the present invention by those skilled in the art, but it should be understood that the present invention is not limited to the scope of the embodiments, and it will be apparent to those skilled in the art that various changes may be made without departing from the spirit and scope of the invention as defined and defined in the appended claims, and all matters produced by the invention using the inventive concept are protected.
As shown in fig. 1, a double-buck full-bridge grid-connected inverter based on frequency doubling modulation includes a power switch tube S5Power switch tube S5Drain electrode of and DC voltage UdcPositive electrode phase connection, S5Respectively with the power switch tube S1Drain electrode of (2), diode D2Negative electrode of (1), power switch tube S3And diode D4The negative electrodes are connected; power switch tube S6Source and U ofdcNegative electrode phase connection, S6Respectively with the power switch tube S2Source electrode of (2), diode D1The positive electrode of,Power switch tube S4Source and diode D3the positive electrodes of the two electrodes are connected; s1As node A and respectively with D1Negative electrode and inductor LAOne end of the two ends are connected; diode D2With the positive pole of the switch tube S as the node B2Drain electrode and inductor L ofBone end of the two ends are connected; s3With the source as node D and respectively connected with diode D3Negative electrode, inductor LBone terminal of (1) and an inductance LDOne end of the two ends are connected; diode D4As node C and respectively with S4Drain electrode of (1), inductor LAone terminal of (1) and an inductance LCOne end of the two ends are connected; inductor LDThe other end of the first switch is used as an output end G, and the output end G is grounded.
Power switch tube S1Power switch tube S2Power switch tube S3Power switch tube S4Power switch tube S5And a power switch tube S6Are all metal oxide semiconductor field effect transistors. Inductor LAAnd an inductance LBAre all filter inductors.
Hereinafter S1、S2、S3、S4、S5And S6Respectively representing power switching tubes S1Power switch tube S2Power switch tube S3Power switch tube S4Power switch tube S5And a power switch tube S6；LA、LB、LCAnd LDRespectively representing inductances LAInductor LBInductor LCAnd an inductance LD；D1、D2、D3and D4Respectively represent a diode D1And a diode D2diode D3And a diode D4。
In one embodiment of the invention, the power switch tube S is used for reducing the device1～S6The DPGCI operates in a half-cycle controlled manner. Power switch tube S1、S2、S5、S6Operating in the positive half-cycle, the power switch tube S3、S4、S5、S6Operating in the negative half cycle. Driving and output voltage u of system under frequency multiplication SPWM (sinusoidal pulse Width modulation) strategyAB，uCDThe waveform is shown in fig. 2. Wherein the power switch tube S5The driving signal is in the positive half period and the power switch tube S4In the same way as the power switch tube S in the negative half period2the same is true.
In order to analyze the common-mode leakage current of the inverter, a common-mode equivalent resonant circuit of the DPGCI is required to be established. Grounding capacitor CPVHas the function of isolating the DC power supply, so that the common-mode leakage current itcmOnly with respect to the ac voltage source. When the DC power supply U is not considereddcTo itcmIn the case of (3), it can be seen from fig. 3 that the power switch tube S is operated in the positive half-cycle1、S2、S5、S6Working, power switching tube S3、S4Always off, the equivalent common mode resonant circuit in the positive half cycle of DPGCI available in connection with fig. 1 is shown in fig. 3. Similarly, fig. 4 is an equivalent common mode resonant circuit for a negative half cycle. Wherein u isAN、uBN、uCNAnd uDNRespectively, between inverter leg midpoint A, B, C, D and dc voltage negative N.
according to the prior art for an inverter an effective common-mode voltage uecmcan be derived from u of FIG. 3ecmComprises the following steps:
In the formula (1), uecmIs an equivalent common mode voltage, ucmIs a common mode voltage, udmIs the differential mode voltage, and:
udm＝uAB＝uAN-uBN (3)
According to the formula (1), when L isC+LA≠LD+LBwhen u is turned ondmThe product term is not zero. Therefore, to eliminate udmInfluence on common mode leakage current, let L1+LA＝L4+LB. To facilitate analysisC＝LD；LA＝LBThen, formula (1) can be rewritten as:
Calculating the leakage current itcmthe formula can be expressed as:
In formula (5), CPVIs a grounding capacitor, and t is a time variable;
If u is represented by the combination of formula (4) and formula (5)AN+uBNAnd the common mode leakage current of the positive half period can be effectively inhibited if the positive half period is kept constant. Similarly, the u of the negative half cycle can be obtained from FIG. 4ecmComprises the following steps:
Therefore, if uCN+uDNAnd the common mode leakage current of the negative half period can be effectively inhibited if the negative half period is kept constant.
Setting the positive half period i for analyzing the working condition of the DPGCI in the positive and negative half periodsgpositive when flowing from point A to point B, in a negative half period igPositive when moving from point C to point D. According to igDirection of and power switch tube S1～S6the DPGCI has six operation modes in a single power frequency period, and equivalent circuits of the DPGCI are respectively shown in fig. 5, fig. 6, fig. 7, fig. 8, fig. 9 and fig. 10.
Working mode 1: FIG. 5 shows the equation when ig>0, power switch tube S1、S2、S5、S6Switching-on, power switch tube S3、S4When the circuit is turned off, the circuit is an equivalent circuit of the working mode 1. At this time S5、S1、LA、LC、ugid、LD、LB、S2And S6Form a forward charging closed loop igIncreasing in the positive direction. As can be seen from fig. 5:
uAB＝+udc (7)
uAN＝uAB＝+udc (8)
uBN＝0 (9)
By substituting the formula (8) and the formula (9) into the formula (4), the common mode voltage of the working mode 1 is uecm：
And (3) working mode 2: FIG. 6 shows the equation when ig>0，S2、S5conduction, S1、S3、S4、S6When the circuit is turned off, the circuit is an equivalent circuit of the working mode 2. At this time LA、LC、ugid、LD、LB、S2And D1Form a forward discharge follow current loop igThe positive direction decreases. The follow current path does not pass through a body diode with poor performance, reverse recovery loss is reduced, isolation of a power grid and direct-current voltage of the inverter in a follow current stage is achieved, and efficiency and reliability of the inverter can be improved. As can be seen from fig. 6:
uAB＝0 (11)
When S is1And S6When the switching tubes are of the same type, S1and S6Is the same as the voltage stress, i.e.
In formula (12), Vs1And Vs6Are respectively S1And S6the voltage across. From FIG. 6, it can be derived from Kirchhoff's Voltage Law (KVL):
The united type (12) and the formula (13) can obtain:
Substitution of formula (14) for formula (4) yields u of the operating mode 2ecmComprises the following steps:
Working mode 3: FIG. 7 shows the equation when ig<0，S1、S6Conduction, S2、S5、S3、S4When the circuit is turned off, the circuit is an equivalent circuit of the working mode 3. At this time LA、LC、ugid、LD、LB、D3And S1Form another loop, igthe positive direction decreases. The follow current path does not pass through a body diode with poor performance, reverse recovery loss is reduced, isolation of a power grid and direct-current voltage of the inverter in a follow current stage is achieved, and efficiency and reliability of the inverter can be improved. As can be seen from fig. 7:
uAB＝0 (16)
When S is2And S5When the switching tubes are of the same type, S2and S5Is the same as the voltage stress, i.e.
In the formula (17), Vs2And Vs5Are respectively S2And S5the voltage across. From FIG. 7, it can be derived from Kirchhoff's Voltage Law (KVL):
Substitution of formula (17) and formula (18) for formula (6) can yield u of the operating mode 3ecmcomprises the following steps:
the working mode 4 is as follows: FIG. 8 shows the equation when ig<0，S3、S4、S5、S6Conduction, S1、S2When the circuit is turned off, the circuit is an equivalent circuit of the working mode 4. At this time S5、S3、LD、ugid、LC、S4And S6form a reverse charging loop igincreasing in the negative direction. Analysis of FIG. 8 yields:
uCD＝-udc (20)
uDN＝uDC＝+udc (21)
uCN＝0 (22)
By substituting the formula (21) and the formula (22) into the formula (6), the common mode voltage of the operation mode 4 is uecm：
Working mode 5: when i is shown in FIG. 9g<0，S1、S2、S4、S5Closing, S3、S6And opening the equivalent circuit of the working mode 5. Inductor current iLWarp LD、ugid、LC、D4And S3follow current igand inversely decreases. The follow current path does not pass through a body diode with poor performance, reverse recovery loss is reduced, isolation of a power grid and direct-current voltage of the inverter in a follow current stage is achieved, and efficiency and reliability of the inverter can be improved. As can be seen from fig. 9:
uCD＝0 (24)
When S is4And S5When the switching tubes are of the same type, S4And S5Is the same as the voltage stress, i.e.
In the formula (25), Vs4And Vs5Are respectively S4And S5The voltage across. From FIG. 9, it can be derived from Kirchhoff's Voltage Law (KVL):
The united type (25) and the formula (26) can obtain:
U of the operation mode 5 can be obtained by substituting the formula (27) for the formula (6)ecmComprises the following steps:
The working mode 6 is as follows: when i is shown in FIG. 10g<0，S1、S2、S3、S6Closing, S4、S5And opening the equivalent circuit of the working mode 6. Inductor current iLWarp LD、ugid、LC、S4And D3Follow current igdAnd inversely decreases. The follow current path does not pass through a body diode with poor performance, reverse recovery loss is reduced, isolation of a power grid and direct-current voltage of the inverter in a follow current stage is achieved, and efficiency and reliability of the inverter can be improved. Analysis of FIG. 10 yields:
uCD＝0 (29)
As can be seen from FIG. 10, when S is3And S6When the switching tubes are of the same type, S3And S6Is the same as the voltage stress, i.e.
In the formula (30), Vs3And Vs6Are respectively a switch tube S3And S6The voltage across. From FIG. 10, from KVL:
the combined type (30) and the formula (31) can obtain:
Substitution of formula (32) for formula (6) results in u of the operating mode 6ecmComprises the following steps:
According to the formula (5), the DPGCI topology and the modulation strategy thereof provided by the invention can effectively inhibit the common-mode leakage current of the double-Buck grid-connected inverter.
in summary, the DPGCI operation modes and u shown in Table 1 are obtainedcmThe relationship is as follows:
Table 1: DPGCI operation mode and ucm
analysis table 1 shows that the common-mode voltage u of the novel double-buck grid-connected inverter in the whole working periodecm＝UdcAnd/2, keeping the same, and obtaining the common-mode leakage current by the formula (5):
Therefore, when the influence of the junction capacitance of the switching tube on the common-mode voltage is not considered, the DPGCI adopts the common-mode leakage current i of a frequency multiplication SPWM (sinusoidal pulse width modulation) modetcm＝0。
In order to verify the correctness of theoretical analysis and the reasonability of parameter design, a simulation platform is set up in MATLAB7.1 simulation software to respectively perform simulation verification on DPGCI adopting a frequency doubling SPWM modulation strategy.
Specific experimental parameters of the main circuit of the DPGCI are shown in table 2:
TABLE 2 simulation parameters
FIG. 11 shows the grid voltage ugidAnd net-entering current igCan be seen from the figure, ugidAnd igKeeping the same phase and outputting a grid-connected voltage ugid220V, grid-connected current igIs 15A.
FIG. 12 shows the inverted output voltage uABAnd common mode leakage current itcmThe waveform of (2). As can be seen from the figure, the inverse output voltage u of the positive half period and the negative half period is realized by the frequency multiplication SPWM (sinusoidal pulse width modulation) strategyABThe frequency of 2 times of switching frequency, namely 10KHZ, is changed between 0V and 360V and between 0V and-360V respectively, so that the THD value is reduced, and the grid-connected power quality is improved. Common mode leakage current itcmBasically keeps about 5mA, has larger amplitude only at the zero crossing point, does not exceed 90mA at the maximum, and meets the standard of DIN V VDE V0126-1-1.
FIG. 13 shows uAN、uBNAnd ucmThe waveform of (2).
FIG. 14 shows uAN、uBNAnd ucmThe waveform amplified in the positive half cycle, u, can be seen in the figureANalternating between 180V and 360V, negative half period, uBNalternating between 180V and 0V, uANAnd uBNAre completely complementary; from this, a common mode voltage u can be obtainedcmFluctuating around 180V, u over the entire periodcmAnd remain constant.
As can be seen from fig. 15, simulation shows that only THD is 0.15% when the DPGCI adopts frequency doubling modulation, which reduces the THD value by nearly 85% compared with the conventional double-Buck inverter adopting a unipolar SPWM modulation strategy, and greatly improves the grid-connected current quality; due to the switch tube S5、S6The decoupling of the direct current side and the alternating current side is realized, so that the direct current component of the grid-connected current is only 0.03 percent, and compared with the traditional double-Buck inverter adopting a unipolar SPWM (sinusoidal pulse width modulation) strategy, the direct current component is also greatly reduced.
In summary, the double buck photovoltaic grid-connected inverter (circuit structure of DPGCI) capable of adopting the frequency doubling SPWM modulation strategy proposed by the present invention can draw the following conclusions:
(1) The double-Buck grid-connected inverter circuit adopting the bipolar frequency multiplication SPWM modulation strategy can greatly improve the quality of grid-connected electric energy, and the THD is reduced by nearly 85 percent; and the grid-connected power quality is improved, the size and the cost of the filter inductor are reduced, and the power density of the system is improved.
(2) The DPGCI isolates the direct current side and the alternating current side of the inverter, so that the direct current component of the grid-connected current is greatly reduced, and the quality of the grid-connected electric energy is further improved.

Claims (2)

1. The utility model provides a two step-down full-bridge grid-connected inverter based on doubling of frequency modulation which characterized in that: comprising a power switch tube S5Said power switch tube S5Drain electrode of and DC voltage UdcThe positive electrodes are connected, and the power switch tube S5Respectively with the power switch tube S1Drain electrode of (2), diode D2Negative electrode of (1), power switch tube S3And diode D4The negative electrodes are connected; the power switch tube S6Source and U ofdcThe negative pole is connected with the power switch tube S6Respectively with the power switch tube S2Source electrode of (2), diode D1positive electrode of (2), power switch tube S4Source and diode D3The positive electrodes of the two electrodes are connected; the power switch tube S1With the source of the diode as a node A and respectively connected with a diode D1Negative electrode and inductor LAOne end of the two ends are connected; the power switch tube S1Respectively with the switch tube S5Source and diode D2Connecting the negative electrodes; the diode D2With the positive pole of the switch tube S as the node B2Drain electrode and inductor L ofBOne end of the two ends are connected; the power switch tube S3With the source as node D and respectively connected with diode D3Negative electrode, inductor LBanother terminal of (1) and an inductance LDOne end of the two ends are connected; the inductance LDThe other end of the first switch is used as an output end G which is grounded; the diode D4As node C and respectively with S4Drain electrode of (1), inductor LAAnother terminal of (1) and an inductance LCone end of the two ends are connected; the inductance LAInductor LBInductor LCAnd an inductance LDAre all filter inductors, and inductor LA，LB，LCAnd LDSatisfy LA+LC＝LB+LD，LC＝LD。
2. The double-buck full-bridge grid-connected inverter based on frequency multiplication modulation according to claim 1, characterized in that: the power switch tube S1Power switch tube S2Power switch tube S3Power switch tube S4Power switch tube S5And a power switch tube S6Are all metal oxide semiconductor field effect transistors.
CN201810668373.4A 2018-06-26 2018-06-26 Double-buck full-bridge grid-connected inverter based on frequency multiplication modulation Expired - Fee Related CN108736758B (en)

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Publication number Priority date Publication date Assignee Title
CN102223101A (en) * 2011-06-21 2011-10-19 盐城工学院 Control method for dual-bucking full-bridge grid-connected inverter
CN107342700A (en) * 2017-08-18 2017-11-10 西南石油大学 A kind of new double step-down combining inverter for eliminating common mode leakage current

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* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN102223101A (en) * 2011-06-21 2011-10-19 盐城工学院 Control method for dual-bucking full-bridge grid-connected inverter
CN107342700A (en) * 2017-08-18 2017-11-10 西南石油大学 A kind of new double step-down combining inverter for eliminating common mode leakage current

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