CN101873124A - Adaptive Threshold Pulse Amplification and Shaping Circuit - Google Patents
Adaptive Threshold Pulse Amplification and Shaping Circuit Download PDFInfo
- Publication number
- CN101873124A CN101873124A CN 201010179713 CN201010179713A CN101873124A CN 101873124 A CN101873124 A CN 101873124A CN 201010179713 CN201010179713 CN 201010179713 CN 201010179713 A CN201010179713 A CN 201010179713A CN 101873124 A CN101873124 A CN 101873124A
- Authority
- CN
- China
- Prior art keywords
- resistor
- circuit
- pulse
- output
- operational amplifier
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Granted
Links
- 238000007493 shaping process Methods 0.000 title claims abstract description 37
- 230000003044 adaptive effect Effects 0.000 title claims abstract description 19
- 230000003321 amplification Effects 0.000 title claims abstract description 12
- 238000003199 nucleic acid amplification method Methods 0.000 title claims abstract description 12
- 238000000605 extraction Methods 0.000 claims abstract description 13
- 239000003990 capacitor Substances 0.000 claims description 9
- 238000005259 measurement Methods 0.000 abstract description 4
- 230000000052 comparative effect Effects 0.000 description 10
- 238000001514 detection method Methods 0.000 description 10
- 230000001681 protective effect Effects 0.000 description 9
- 239000003381 stabilizer Substances 0.000 description 8
- 230000006978 adaptation Effects 0.000 description 7
- 230000001105 regulatory effect Effects 0.000 description 7
- 238000010586 diagram Methods 0.000 description 6
- 230000000694 effects Effects 0.000 description 5
- 239000000284 extract Substances 0.000 description 5
- 238000000034 method Methods 0.000 description 3
- 238000003672 processing method Methods 0.000 description 2
- 230000015572 biosynthetic process Effects 0.000 description 1
- 230000008878 coupling Effects 0.000 description 1
- 238000010168 coupling process Methods 0.000 description 1
- 238000005859 coupling reaction Methods 0.000 description 1
- 238000005516 engineering process Methods 0.000 description 1
- 230000001788 irregular Effects 0.000 description 1
- 210000001503 joint Anatomy 0.000 description 1
- 230000000630 rising effect Effects 0.000 description 1
- 238000000926 separation method Methods 0.000 description 1
- 239000011800 void material Substances 0.000 description 1
Images
Landscapes
- Amplifiers (AREA)
Abstract
本发明提供的是一种自适应阈值脉冲放大整形电路。它是由求和放大器及其保护电路、直流电平提取电路、基准电平自适应调节电路和脉冲比较整形电路构成。本发明可以去除脉冲包络直流漂移的影响，减小因脉冲幅度所造成的脉宽测量误差，降低噪声干扰的影响，进而降低虚警及漏报概率。
The invention provides an adaptive threshold pulse amplification and shaping circuit. It is composed of a summing amplifier and its protection circuit, a DC level extraction circuit, a reference level adaptive adjustment circuit and a pulse comparison shaping circuit. The invention can remove the influence of the pulse envelope DC drift, reduce the pulse width measurement error caused by the pulse amplitude, reduce the influence of noise interference, and further reduce the false alarm and false alarm probability.
Description
Technical field
The present invention relates to a kind of circuit, the signal that particularly relating to achieve a butt joint receives amplifies the circuit of shaping.
Background technology
The radiofrequency signal that receiver receives is the output video pulse signal after the envelope detector detection, owing to the reasons such as inconsistency of impulse disturbances, thermal noise, receive path may make the serious distortion of pulse envelope (changes in amplitude and time delay expansion), the pulse signal of this moment just can not directly be used as the measurement of pulse parameter, and must be through certain processing.Conventional processing method is: at first envelope signal is coupled to next stage by ac-coupled device, make porch precipitous by the one-level voltage ratio then, usually the reference voltage of comparator is made as E/2 (E is the pulse envelope amplitude of coupling output), and relatively the pulse signal after carries out parameter measurement and tracking by just giving next stage behind the pulse shaper again.
Such processing method exists several problems.At first, reconnaissance receiver is usually operated in the complex electromagnetic environments, and when stream of pulses density was big, ac-coupled device can not be finished the extraction of signal pulse, and for example two pulsion phases can be coupled to a pulse when nearer, causes pulse missing and handles mistake.Secondly, because the radiofrequency signal that receiver receives has DC bias through behind the video detection, this DC level is with temperature, time drift, and because the inconsistency of receive path, the signal DC bias is also inconsistent after each passage detection, causes pulse amplitude to differ greatly, simultaneously because The noise, if directly select for use a certain reference level to make comparisons, the pulsewidth that measures thus will produce than mistake and delay, even causes serious false-alarm and fail to report.Reasonably handle input pulse and suitable thresholding is set and not only can reduce false-alarm and miss probability, can also reduce the pulse width measure error that causes because of amplitude, and then improve speed and the reliability that back end signal is handled.
Summary of the invention
The invention reside in provides a kind of high-precision self-adaptive threshold pulse amplified shaping circuit that is applied to radar receiver.
The object of the present invention is achieved like this:
Self-adaptive threshold pulse amplified shaping circuit of the present invention; it is characterized in that: it is by summing amplifier and protective circuit thereof; DC level is extracted circuit; reference level self adaptation regulating circuit and pulse ratio constitute than shaping circuit; the input of circuit is extracted in the output of summing amplifier and protective circuit thereof as DC level; output with summing amplifier and protective circuit thereof is connected to the anode of pulse ratio than the shaping circuit comparator again; the output that DC level is extracted circuit is connected to reference level self adaptation regulating circuit; what reference level self adaptation regulating circuit was obtained is connected to the negative terminal of pulse ratio than the shaping circuit comparator with value; pulse ratio is connected to inverter than the output of shaping circuit comparator, is finally exported after the process two-stage is anti-phase.
Self-adaptive threshold pulse amplified shaping circuit of the present invention can also comprise:
1; described summing amplifier and protective circuit thereof comprise amplifier; resistance; triode and voltage-stabiliser tube; three groups of signals are respectively through second resistance; be input to the in-phase end of first amplifier behind the 3rd resistance and the 4th resistance; the 6th resistance is connected to the in-phase end of first amplifier; first resistance links to each other with the 5th resistance and constitutes the negative feedback links of first amplifier; the first amplifier end of oppisite phase feeds back to the first amplifier output node by the 5th resistance; the 7th resistance; the 8th resistance is connected respectively to first triode; the emitter of second triode; the tenth resistance; the 11 resistance connects respectively and obtains the 3rd triode; the emitter of the 4th triode; and first triode links to each other with the base stage of second triode; the 3rd triode links to each other with the base stage of the 4th triode, inserts first voltage-stabiliser tube at the first amplifier output node.
2, described DC level is extracted circuit and is comprised resistance, electric capacity and diode, the first amplifier output node is connected to the junction of first voltage-stabiliser tube and the 13 resistance, the junction of first voltage-stabiliser tube and the 13 resistance is connected to the junction of the 12 resistance and the 13 resistance after by the 13 resistance, the junction of the 12 resistance and the 13 resistance is capacitively coupled to ground by first, the junction of the 12 resistance and the 13 resistance feeds back to junction, the 12 resistance and second diode formation discharge loop of first voltage-stabiliser tube and the 13 resistance by the 12 resistance and second diode.
3, described reference level self adaptation regulating circuit comprises adjustable output voltage benchmark that is made of digital regulation resistance and the adder that is made of amplifier, the DC level of first electric capacity directly connects first input end, the adjusting output voltage of digital regulation resistance is connected to terminal second, first input end and second input terminal are input to the in-phase end of second amplifier respectively by the 16 resistance and the 17 resistance, second amplifier and the 14 resistance～the 18 resistance constitutes adder.
4, described pulse ratio adopts high-speed comparator than shaping circuit, the junction of the 12 resistance and the 16 resistance is connected to the negative terminal of comparator, the first amplifier output node is connected to the anode of comparator, and the two-stage of the output of comparator by U5 finally exported after oppositely.
Advantage of the present invention is: can remove the influence of pulse envelope dc shift, reduce the pulse width measure error that causes because of pulse amplitude, reduce the influence of noise jamming, and then reduce false-alarm and miss probability.
Description of drawings
Fig. 1 is the video pulse envelope schematic diagram after the ideally radio frequency of the present invention detection;
Fig. 2 uses the fixed level reference voltage schematic diagram of device as a comparison for the present invention;
Fig. 3 is the use adaptive threshold of the present invention reference voltage schematic diagram of device as a comparison;
Fig. 4 is the standard digital pulse schematic diagram after use adaptive threshold of the present invention compares shaping;
Fig. 5 is a self-adaptive threshold pulse amplified shaping circuit schematic diagram of the present invention.
Embodiment
For example the present invention is done description in more detail below in conjunction with accompanying drawing:
In conjunction with Fig. 1～5, Fig. 1 is the video pulse envelope that obtains after the ideally radio frequency detection.By envelope signal 1. as can be seen, differ greatly in the DC level of three pulse envelopes in the long time periods, the pulse of this moment just can not be discerned by digital device, and must by compare shaping afterwards could with the digital device interface.If the reference voltage of comparator uses fixedly comparative level, as the fixedly comparative level among Fig. 2 2. shown in, then be easy to cause the erroneous judgement of pulse, and pulse width measure brought very big influence.Figure 3 shows that and use the adaptive threshold reference voltage of device as a comparison, 3. comparative level exports Δ E addition by the DC level and the adjustable voltage benchmark of pulse envelope, the pulse that not only can reduce to bring because of dc shift is judged by accident, and regulates the influence that suitable Δ E can reduce noise jamming.Fig. 4 amplifies the standard digital pulse signal that obtains after the shaping for using the adaptive threshold pulse.
Self-adaptive threshold pulse amplified shaping circuit of the present invention is made of than shaping circuit summing amplifier and protective circuit, DC level extraction circuit, reference level self adaptation regulating circuit and pulse ratio.
The self-adaptive threshold pulse amplified shaping circuit of the present invention amplification of at first the pulse envelope signal after each passage detection being sued for peace, here do not adopt traditional ac-coupled device mode, this is because the pulsewidth scope of radar signal is 0.05uS～500uS usually, repetition scope 10Hz～100KHz, and amplifier is compared with ac-coupled device and is had better low frequency characteristic and amplification.Simultaneously, use summing circuit can effectively utilize the detection result of each passage, reach the effect that suppresses with frequency and relevant interference.Use adaptive threshold mode relatively in the reference voltage end of next stage comparator, can overcome dc shift that receiver front end and amplifier bring measuring the influence that pulsewidth causes.Damage in order to prevent amplifier out overcurrent or shorted to earth, add current-limiting circuit at the power end of amplifier and limit output current.Insert the amplitude limiter of being made up of voltage-stabiliser tube at amplifier out, prevent that the output overvoltage from damaging output stage, the while plays a protective role to the input of next stage comparator again.Pulse envelope after the amplification remains irregular, need relatively make its edge precipitous by comparator.According to the minimum error probability criterion, comparative level should be E/2 (E is the pulse envelope amplitude of amplifier output), if comparative level is a steady state value, then may cause failing to judge of some pulse, or, cause the pulse width measuring error bigger than normal because of the integrating effect of circuit makes pulse width distortion.At input signal dc shift problem, the present invention proposes a kind of adaptive threshold level manner of comparison, extract the DC level E1 that circuit extraction goes out envelope signal by one group of DC level, add the adjustable output reference voltage Δ E that digital regulation resistance constitutes, constitute the reference voltage of comparator jointly.Still can not directly be used for carrying out pulse parameter from the pulse signal of comparator output and measure, need it is become the digital signal level of standard by pulse shaper, then could with other digital device interfaces.
Fig. 5 is the schematic diagram of self-adaptive threshold pulse amplified shaping circuit.Self-adaptive threshold pulse amplified shaping circuit is made of four parts, is respectively summing amplifier and protective circuit thereof, DC level extraction circuit, reference level self adaptation regulating circuit and pulse ratio than shaping circuit.Be elaborated with regard to each several part circuit structure, principle and function below.
Referring to Fig. 5, first's summing amplifier of shaping circuit is the three input homophase add circuits that are made of amplifier U1, three tunnel detection output signals are connected respectively to three inputs of adder, the output of itself and value is as the input of second portion DC level extraction circuit after suing for peace, also to be connected to simultaneously the anode of the 4th part comparator U4, as a comparison the comparative voltage of device.The second portion circuit from the input with value signal extract DC component and output to third part.Use amplifier U3 to make up an in-phase adder in third part, the input of its in-phase end is respectively the DC component of second portion extraction and the output of this part digital regulation resistance U2, its addition be connected to the negative terminal of the 4th part comparator U4, the reference voltage of device as a comparison with value.The output of the 4th part comparator is connected to inverter U5, is finally exported Uo after the process two-stage is anti-phase.
First's summing amplifier and protective circuit thereof (part that frame of broken lines I chooses among Fig. 5) are made of amplifier U1, resistance R 1 ~ R11, triode Q1 ~ Q4 and voltage-stabiliser tube D1.Result after each receive path detection is carried out handling after the summation operation again, can effectively suppress with frequency and relevant interference.The present invention adopts triple channel to receive, and 1. signal Ui1, the Ui2 after its triple channel detection, Ui3 sue for peace through in-phase end ("+") node that is input to amplifier U1 behind resistance R 2, R3, the R4 respectively, and resistance R 6 plays the effect of balance adjustment.Short, the empty disconnected principle of void according to amplifier, 1. voltage is identical with the in-phase end node for amplifier end of oppisite phase ("-") node voltage 2., and resistance R 1 and R5 constitute the negative feedback links of amplifier U1, and 3. 2. node feed back to the amplifier output node by R5.According to the basic form of homophase add circuit can get after Ui1, Ui2, Ui3 amplify through summation output as a result Uo can be expressed as
Wherein, R
p=R
2//R
3//R
4//R
6, R
n=R
1//R
5
Work as R
p=R
nThe time,
Select suitable resistance value, make
Then
U
o＝k(U
i1+U
i2+U
i3)
Thereby the purpose that reaches summation and amplify.For the amplifier protective circuit, resistance R 7, R8 are connected respectively to the emitter of PNP triode Q1, Q2, and R10, R11 connect the emitter that obtains NPN triode Q3, Q4 respectively, and these four resistance mainly are to play metering function.And Q1 and Q2; Q3 links to each other with the Q4 base stage, when Q1 ~ Q4 is operated in the amplification region, and Q1 and Q2; Q3 and Q4 form mirror current source.Q2 and Q4 provide bigger base current.Q1, Q3 are operated in the saturation region during circuit operate as normal, power supply+V ,-V is equivalent to directly insert amplifier.When output current increases; impel current source current also to increase; as Q1, when the Q2 collector current equates; Q1 ~ Q4 enters the amplification region; be in the current source operating state; the electric current that flows through Q1, Q3 collector electrode is invariable, thereby limited the further increase of output current, plays the effect of guard amplifier.In addition, 3. insert voltage-stabiliser tube D1, play the effect of output violent change at the output node of summing amplifier U1.
The second portion DC level is extracted circuit (part that frame of broken lines II chooses among Fig. 5), and by resistance R 12 ~ R13, capacitor C 1 and diode D2 form.The input node that 3. output node of first's summing amplifier is directly connected to second portion 4., 5. 5. the input node 4. output node by being connected to second portion behind the adjustable resistance R13 and be coupled to ground by capacitor C 1.In fact R13 and C1 have constituted low-pass filter circuit, can extract the DC level of input envelope signal.And 5. node feeds back to the input of second portion by resistance R 12 and diode D2, and in fact R12 and D2 constitute discharge loop.If the bottom level of a certain pulse envelope is E0, top level is E1, and when rising edge of a pulse arrived, diode D2 ended, capacitor C 1 charging, and the instantaneous voltage that can calculate on the capacitor C 1 according to the total regression state equation is:
Increasing R13 makes the charging voltage on the C1 become slow.When arrival of pulse envelope trailing edge and near VC-VD (VD is a diode turn-on voltage), capacitor C 1 begins discharge.Because R12 and diode resistance rd are less, the voltage on the electric capacity has dropped to the bottom of signal soon, thus when the bottom of signal when drifting about, the voltage on the electric capacity can followed timely and changed.The voltage that takes out on the capacitor C 1 is exactly required direct current comparative level.
Third part reference level self adaptation regulating circuit (part that frame of broken lines III chooses among Fig. 5), by digital regulation resistance U2, amplifier U3 and resistance R 14 ~ R18 constitute.6. the second portion DC level extracts input terminal that DC level that circuit extraction goes out directly connects third part, 7. the adjusting output voltage of digital regulation resistance U2 is connected to terminal, then 6. and 7. be input to the in-phase end of amplifier U3 respectively by resistance R 16 and R17.In fact, amplifier U3 and resistance R 14 ~ R18 have constituted adder, and this is identical with the summing amplifier principle mentioned in the first, just repeats no more here.Tell about the realization principle of this part below.DC level extract direct current comparative level that circuit takes out can't be directly the reference voltage of device as a comparison, because according to the minimum error probability criterion, comparative level should be E/2, therefore also being required to be relatively to hold provides a reference voltage source, does not have the measurement of pulse duration as reference level with a certain median of pulse amplitude.Adopt digital regulation resistance U2 to produce reference voltage among the present invention, this reference voltage has the characteristics of control able to programme.If it is low excessively that this magnitude of voltage is established, just may introduce the more noise pulse, not only increased the burden that back end signal is handled, also may cause alarmed falsely probability to increase; Otherwise, too high if this magnitude of voltage is established, can omit pulse again, and then cause miss probability to rise.Therefore, this reference voltage can not use a fixed value, and should adjust according to signal environment and real-time the going of separation results, and this is an adaptive process.The DC level of the pulse envelope of this reference voltage and extraction is by the comparative voltage of device U4 as a comparison after adder addition.The adder here is the homophase add circuit that is made of amplifier U3 and resistance R 14 ~ R18.What adder was exported will compare the reference voltage of comparator in the shaping circuit as the 4th partial pulse with voltage.
The 4th partial pulse is shaping circuit (part that frame of broken lines IV chooses among Fig. 5) relatively, is made up of comparator U4 and inverter U5.8. the output of third part adder be connected to the negative terminal of comparator U4, and 3. the output of first be connected to the anode of comparator U4, and 9. the output of comparator oppositely arrive final output in the back by the two-stage of U5.Comparator U4 selects for use high-speed comparator can handle the signal of little pulsewidth, can reduce simultaneously to postpone.Comparator output earth pulse signal still can not directly be used for carrying out pulse parameter and measure, need it is become the digital signal level of standard by pulse shaper, then could with other digital device interfaces.The chip U5 that is used for the shaping pulse function among the present invention adopts 7414 to realize, this chip comprises hex inverter, owing to used Schmidt trigger at input, therefore to rise time of input signal and fall time without limits, and improved the anti-noise ability of input.Here only use two inverter cascades to constitute pulse shaper.
Claims (5)
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN2010101797130A CN101873124B (en) | 2010-05-24 | 2010-05-24 | Self-adaptive threshold pulse amplified shaping circuit |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN2010101797130A CN101873124B (en) | 2010-05-24 | 2010-05-24 | Self-adaptive threshold pulse amplified shaping circuit |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN101873124A true CN101873124A (en) | 2010-10-27 |
| CN101873124B CN101873124B (en) | 2012-03-14 |
Family
ID=42997821
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN2010101797130A Expired - Fee Related CN101873124B (en) | 2010-05-24 | 2010-05-24 | Self-adaptive threshold pulse amplified shaping circuit |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN101873124B (en) |
Cited By (9)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN102522966A (en) * | 2011-12-30 | 2012-06-27 | 武汉电信器件有限公司 | Programmable nanosecond pulse signal generator |
| CN103368534A (en) * | 2012-04-09 | 2013-10-23 | 北京大基康明医疗设备有限公司 | Threshold circuit |
| CN104502688A (en) * | 2015-01-04 | 2015-04-08 | 上海交通大学 | DC (direct current) variable low-frequency envelope digital detector |
| CN105067833A (en) * | 2015-08-28 | 2015-11-18 | 无锡伊佩克科技有限公司 | Automobile engine rotating speed detection apparatus based on power controller |
| CN105181990A (en) * | 2015-08-28 | 2015-12-23 | 无锡伊佩克科技有限公司 | Automobile engine rotating speed detection device |
| CN105606632A (en) * | 2015-08-31 | 2016-05-25 | 无锡伊佩克科技有限公司 | Water content detection and control system based on shaping amplification circuit |
| CN105718835A (en) * | 2016-01-14 | 2016-06-29 | 大唐微电子技术有限公司 | Digital shaping circuit |
| CN108449073A (en) * | 2018-06-05 | 2018-08-24 | 北方电子研究院安徽有限公司 | The multichannel amplification and rectification circuit of wide power voltage range low crosstalk |
| CN109936293A (en) * | 2019-02-28 | 2019-06-25 | 西安微电子技术研究所 | A kind of level shifting circuit and the transformation output DC/DC inverter power supply module based on it |
Citations (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US4410763A (en) * | 1981-06-09 | 1983-10-18 | Northern Telecom Limited | Speech detector |
| CN1440137A (en) * | 2003-02-24 | 2003-09-03 | 陶成 | Suppression pulse interference device via power line communication systems |
| US6980786B1 (en) * | 2001-01-16 | 2005-12-27 | Sequoia Communications Corp. | Adaptive receiver system that adjusts to the level of interfering signals |
-
2010
- 2010-05-24 CN CN2010101797130A patent/CN101873124B/en not_active Expired - Fee Related
Patent Citations (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US4410763A (en) * | 1981-06-09 | 1983-10-18 | Northern Telecom Limited | Speech detector |
| US6980786B1 (en) * | 2001-01-16 | 2005-12-27 | Sequoia Communications Corp. | Adaptive receiver system that adjusts to the level of interfering signals |
| CN1440137A (en) * | 2003-02-24 | 2003-09-03 | 陶成 | Suppression pulse interference device via power line communication systems |
Cited By (12)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN102522966A (en) * | 2011-12-30 | 2012-06-27 | 武汉电信器件有限公司 | Programmable nanosecond pulse signal generator |
| CN103368534A (en) * | 2012-04-09 | 2013-10-23 | 北京大基康明医疗设备有限公司 | Threshold circuit |
| CN104502688A (en) * | 2015-01-04 | 2015-04-08 | 上海交通大学 | DC (direct current) variable low-frequency envelope digital detector |
| CN104502688B (en) * | 2015-01-04 | 2017-04-19 | 上海交通大学 | DC (direct current) variable low-frequency envelope digital detector |
| CN105067833A (en) * | 2015-08-28 | 2015-11-18 | 无锡伊佩克科技有限公司 | Automobile engine rotating speed detection apparatus based on power controller |
| CN105181990A (en) * | 2015-08-28 | 2015-12-23 | 无锡伊佩克科技有限公司 | Automobile engine rotating speed detection device |
| CN105606632A (en) * | 2015-08-31 | 2016-05-25 | 无锡伊佩克科技有限公司 | Water content detection and control system based on shaping amplification circuit |
| CN105718835A (en) * | 2016-01-14 | 2016-06-29 | 大唐微电子技术有限公司 | Digital shaping circuit |
| CN105718835B (en) * | 2016-01-14 | 2018-12-28 | 大唐微电子技术有限公司 | A kind of number shaping circuit |
| CN108449073A (en) * | 2018-06-05 | 2018-08-24 | 北方电子研究院安徽有限公司 | The multichannel amplification and rectification circuit of wide power voltage range low crosstalk |
| CN108449073B (en) * | 2018-06-05 | 2023-07-07 | 安徽北方微电子研究院集团有限公司 | Multi-channel amplifying and shaping circuit with wide power supply voltage range and low crosstalk |
| CN109936293A (en) * | 2019-02-28 | 2019-06-25 | 西安微电子技术研究所 | A kind of level shifting circuit and the transformation output DC/DC inverter power supply module based on it |
Also Published As
| Publication number | Publication date |
|---|---|
| CN101873124B (en) | 2012-03-14 |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| CN101873124A (en) | Adaptive Threshold Pulse Amplification and Shaping Circuit | |
| WO2012102300A1 (en) | Optical signal detection circuit and optical receiver | |
| CN206293885U (en) | A kind of output overcurrent protection circuit of digital power | |
| CN101949988B (en) | Detection device of level-type signal disconnection fault | |
| CN203787935U (en) | Over-current protection circuit based on high-side current detection | |
| EP2728748B1 (en) | Automatic gain adjusting circuit | |
| CN106888006B (en) | Signal peak value detection device | |
| CN104242254B (en) | A kind of high-power IGBT temperature sampling protection circuit | |
| CN202757983U (en) | Current detection circuit and USB interface circuit | |
| CN206041466U (en) | Switching power supply circuit with over-temperature protection | |
| EP1884785B1 (en) | A device for comparing the peak value of at least one voltage signal with a reference voltage | |
| CN203276080U (en) | Single-proton detector bias voltage generating circuit based on avalanche photodiode | |
| CN114812317B (en) | Digital detonator communication demodulation interface circuit, signal processing system and method | |
| CN212321723U (en) | Aviation radar fault detection circuit | |
| CN100410636C (en) | A circuit module for APD single photon detection | |
| CN110277900B (en) | IGBT driving peak value detection protection circuit | |
| CN204333903U (en) | An overvoltage protection circuit | |
| JP2013255056A (en) | Optical signal detection circuit | |
| CN207396767U (en) | Infrared tube detection device and system | |
| CN211014474U (en) | Three-phase bias current detection circuit | |
| CN208537614U (en) | Current detection means | |
| CN204258275U (en) | A kind of Switching Power Supply protection circuit against input over-voltage | |
| CN104810782B (en) | Power circuit and electronic products based on resettable fuse | |
| CN209326786U (en) | A Low Noise Laser Receiver | |
| CN109217101B (en) | Laser current driving circuit with maximum current protection and driving method |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| C06 | Publication | ||
| PB01 | Publication | ||
| C10 | Entry into substantive examination | ||
| SE01 | Entry into force of request for substantive examination | ||
| C53 | Correction of patent for invention or patent application | ||
| CB03 | Change of inventor or designer information |
Inventor after: Gao Lipeng Inventor after: Zhao Zhongkai Inventor after: Lin Yun Inventor after: Li Xiang Inventor before: Gao Lipeng Inventor before: Zhao Zhongkai Inventor before: Lin Yun Inventor before: Li Xiang |
|
| C14 | Grant of patent or utility model | ||
| GR01 | Patent grant | ||
| CF01 | Termination of patent right due to non-payment of annual fee |
Granted publication date: 20120314 Termination date: 20170524 |
|
| CF01 | Termination of patent right due to non-payment of annual fee |