CN101053172A - Multiple-input multiple output system and method - Google Patents

Abstract

A multiple-input multiple-output (MIMO) system can transmit on multiple antennas simultaneously and receive on multiple antennas simultaneously. Unfortunately, because a legacy 802.11a/g device is not able to decode multiple data streams, such a legacy device may ''stomp'' on a MIMO packet by transmitting before the transmission of the MIMO packet is complete. Therefore, MIMO systems and methods are provided herein to allow legacy devices to decode the length of a MIMO packet and to restrain from transmitting during that period. These MIMO systems and methods are optimized for efficient transmission of MIMO packets.

Description

Multi-input multi-output system and method

Related application

The application requires the priority of No. the 60/517th, 445, the U.S. Provisional Patent Application that is entitled as " Method For Multiple Input MultipleOutput Systems (method of multi-input multi-output system) " submitted on November 4th, 2003.

Background of invention

Invention field

The present invention relates to multiple-input and multiple-output (MIMO) system and method in the wireless communications environment, and in one embodiment, relate to the MIMO method and system of being convenient to realize backward compatibility with legacy equipment.

Description of related art

The wireless lan (wlan) design of communication system is based on standard family described in the IEEE 802.11.For example, the 802.11a standard provides in the frequency range of 5GHz and is up to 54Mbps, and the 802.11g standard also provides up to 54Mbps, but in the frequency range of 2.4GHz.802.11a/g standard is all used OFDM (OFDM) encoding scheme.

Especially, the 802.11a/g regulation and stipulation only has a data flow to be sent out or to receive at any given time.For example, Fig. 1 illustrates simplified system 100, and it comprises reflector 101 that single output can be provided at any given time and the receiver 102 that can handle single input at any given time.Thus, system 100 is characterized as being single-input single-output system.

For solving decline (wherein the object in the environment can reflect the wireless signal of being launched) and other situation that multipath, especially multipath cause, wireless system can adopt various technology.A kind of this type of technology is a switched diversity, and wherein reflector and/or receiver optionally switch between many antennas.For example, Fig. 2 illustrates simplified system 200, and wherein reflector 101 can be selected to send signal (using switch 203) from antenna 201A or antenna 201B, and receiver 102 can select to handle the signal (using switch 204) from antenna 202A or antenna 202B.Thus, system 200 is characterized as being the switch diversity antenna configuration.

Fig. 3 illustrates multiple-input and multiple-output (MIMO) system 300 of simplification, and it can be launched on many antennas simultaneously, and receives simultaneously on many antennas.Particularly, reflector 301 can transmit from antenna 302A (using transmitter chain 303A) with from antenna 302B (using transmitter chain 303B) simultaneously.Similarly, receiver 304 can be simultaneously from antenna 305A (using receiver chain 306A) with from antenna 305B (using receiver chain 306B) received signal.

Note that the MIMIO system of a few types is arranged.For example, MIMO-AG is meant and 802.11a and the compatible mimo system of 802.11g.Otherwise MIMO-SM is meant the mimo system of tool spatial multiplexing.Below employed abbreviation " MIMO " be meant MIMO-SM.

Depend on specific implementation, but the use of many antennas or expanded scope maybe can improve the data transfer rate of given range.For example, Fig. 4 illustrates the intermediate value data transfer rate of various antenna configurations on relative distance.Waveform 401 expression single antenna configurations; Waveform 402 expression switch diversity antenna configurations; And waveform 403 expression MIMO antenna configurations.Especially, any relative distance between 2 and 4, the intermediate value data transfer rate of MIMO antenna configurations is apparently higher than the intermediate value data transfer rate of single antenna configuration or switch diversity antenna configuration.For example, in the high-end relative distance 3 of the typical home space 404 of expression, the intermediate value data transfer rate (50Mbps) of MIMO antenna configurations is apparently higher than single antenna configuration (18Mbps) or or even the intermediate value data transfer rate of switch diversity antenna configuration (33Mbps).

Mimo system also can advantageously reduce signal to noise ratio (snr) poor on the different frequency groove.For example, Fig. 5 illustrates the SNR of various antennas on each frequency slots, that is, and and the SNR 501 of first antenna (waveform is represented by dotted line), the SNR 502 of second antenna (waveform is illustrated by the broken lines), and first and second antennas use the SNR 503 of (waveform is represented by solid line) simultaneously.Note SNR 501 and 502 all significant changes on frequency slots 0-60.On the contrary, SNR 503 uses the mimo system of first and second antennas difference of the SNR on the different frequency groove can be minimized (promptly in the time of represented, trap on channel is by the non-trap compensation in the one other channel), allow thus this type of SNR in receiver chain and/or the transmitter chain is carried out more effective compensation.

In mimo system 300 (Fig. 3), receiver 304 uses many chains (that is, chain 306A and 306B) to receive by a plurality of data flow (for example, grouping) of reflector 301 emissions and with they decodings.Unfortunately because traditional 802.11a/g equipment can not be to the decoding of a plurality of data flow, so such legacy equipment may be because of launching before finishing in the emission of MIMO grouping " overlapping " in the MIMO grouping.

Therefore, produced allowing legacy equipment, and forbidden the mimo system launched at this section time durations and the demand of method the decoding of MIMO block length.Further produced demand to the high efficiency method of emission MIMO grouping.

Summary of the invention

Multiple-input and multiple-output (MIMO) system can launch on many antennas simultaneously, and receives simultaneously on many antennas.Unfortunately because traditional 802.11a/g equipment can not be to the decoding of a plurality of data flow, so such legacy equipment may be because of launching before finishing in the emission of MIMO grouping " overlapping " in the MIMO grouping.Therefore, provide the permission legacy equipment herein, and forbidden the mimo system and the method for launching at this section time durations to MIMO block length decoding.And these mimo systems and method are optimized at the efficient transmission of MIMO grouping.

The time-division training mode of MIMO grouping for example, is provided.In this pattern, first antenna can be launched short code unit, first long symbols, is traditional signal element then.Second antenna can be launched second long symbols after the classical signal transmission of symbols.First and second antennas code element (being associated) that can after second long symbols emission, transmit in fact simultaneously with the MIMO data.

The another kind of pattern of MIMO grouping is provided.In this pattern, can be by first antenna and second antenna emission short code unit.This short code unit can split between one group short predetermined groove.Especially, first antenna can be associated with first group short groove, and second antenna is associated with second group short groove.Can after the emission of second short code unit, send long symbols in fact simultaneously by first and second antennas.This long symbols can be associated with first group leader's groove and second group leader's groove.Especially, first antenna can use first group leader's groove to launch before using second group leader's groove.On the contrary, second antenna can use second group leader's groove to launch before using first group leader's groove.The signal element that is associated with multiple input multiple output data can be launched in fact simultaneously by first and second antennas.

In one embodiment, first group short groove can comprise-24 ,-16 ,-8,4,12,20, and second group short groove can comprise-20 ,-12 ,-4,8,16,24.In another embodiment, first group short groove can comprise-24 ,-16 ,-8,8,16,24, and second group short groove can comprise-20 ,-12 ,-4,4,12,20.

In one embodiment, first group leader's groove can comprise-26 ,-24 ... ,-2,1,3 ... 25, and second group leader's groove can comprise-25 ,-23 ...-1,2,4 ... 26.In another embodiment, first group leader's groove can comprise-26 ,-24 ... ,-2,2,4 ... 26, and second group leader's groove can comprise-25 ,-23 ...-1,1,3 ... 25.

In one embodiment, at least two kinds of split modes that this pattern also can be included as short groove calculate the value of peak-to-average force ratio (PAR), and use the split mode with minimum PAR value.In another embodiment, at least two kinds of split modes that this pattern also can be included as elongated slot calculate the value of peak-to-average force ratio (PAR), and use the split mode with optimized PAR value.

First and second groups short grooves can use different frequency displacements.For example, if this pattern is to use one in every N groove, then frequency displacement pattern can comprise 1 to as many as N-1 groove.

In one embodiment, first antenna can use one group of antenna to realize.In this case, it is heavy to use restore one's right on the groove of first group of antenna, has alleviated the beam shaping effect thus.Restore one's right heavily comprises at least one in the phase shift or the phase width of cloth, and wherein alleviates the beam shaping effect and just caused the emission of omnidirectional in fact.

In having an embodiment of traditional headers, what this pattern also can be included in emission after the traditional headers is used to indicate the code symbols of launching the MIMO grouping.This code symbols can be indicated the data flow of some emissions at least.In one embodiment, this code symbols can comprise the signal element that is associated with the MIMO data.These signal elements can comprise the pilot tone that is reversed, and the pilot tone that wherein is reversed is different with the conventional code element that should appear at this position.

A kind of method of emission MIMO grouping in the legacy equipment environment is provided.In the method, one group in classical signal code element bit that keeps can be made as predetermined value, indicate thus and launch MIMO signal.In another approach, one group of bit in the classical signal code element can be indicated the information that is associated with the MIMO grouping.In one embodiment, this group bit can comprise a plurality of lowest bit of the length field of classical signal code element.The information that is associated with the MIMO grouping can be indicated the number of the data streams that is associated with this MIMO grouping.In another approach, can carry out ' mould ' computing, to indicate the information (for example, the number of stream) that is associated with the MIMO grouping to one group of bit in the classical signal code element.

A kind of method of phase change of a plurality of reception data symbols of following the tracks of and proofreading and correct the MIMO signal is provided.In the method, a plurality of pilot tone grooves can be inserted in each data symbols.In one embodiment, can increase phase shift by on a plurality of pilot tone grooves, using a kind of pattern.For example, can on a plurality of pilot tone grooves, rotate the pattern of (for example, circularly) phase shift.In one embodiment, can be with four pilot tone grooves with [1 1 1-1] * p _lForm insert in each data symbols, wherein [1 1 1-1] is the pattern on these four pilot tone grooves, and p _lBe the pilot tone polarity of code element l.

Another kind of tracking also is provided and has proofreaied and correct the method for phase change of a plurality of reception data symbols of MIMO signal.In the method, on the long any interval of M data code element, provide the orthogonal modes on each data flow.Provide orthogonal modes can meet following formula:

$\frac{1}{M}\underset{l=k}{\overset{k+M-1}{\mathrm{\Σ}}}{q}_m\left(l\right)q_n^{*}\left(l\right)={\mathrm{\δ}}_{\mathrm{mn}},$

Wherein M represents the number of data streams, and m represents stream, and k represents the beginning index of M orthogonal data code element, and l represents the index of MIMO code element, and δ _MnEqual 1 for m=n, equal 0 for m ≠ n.For M data streams, the modulating mode that then flows m is $q_m\left(l\right)={\mathrm{<figure-callout\; id="2"\; label="e\; j"\; filenames="A20048003561400432.png,A20048003561400531.png"\; state="\{\{state\}\}">e</figure-callout>}}^j,$ 1≤m≤M and l 〉=0 wherein.

Provide a kind of and on several streams, carried out the method that joint pilot is followed the tracks of.In the method, can estimate received signal in each pilot tone groove based on channel estimation and known pilot pattern.The received signal that receiver n goes up in pilot tone K is expressed from the next

$y_{n,k}=\underset{m}{\mathrm{\&Sigma;}}{H}_{n,m,k}{e}^{\mathrm{j\&theta;}}\&CenterDot;s_{m,k}+n_{n,k}$

S wherein _{M, k}Be the pilot frequency code element of stream m, θ is the common phase skew, H _{N, m, k}Be channel response, and n _{N, k}Be noise,

Wherein the common phase skew is expressed from the next

$\mathrm{\&theta;}=\mathrm{angle}(\underset{n,k}{\mathrm{\&Sigma;}}{y}_{n,k}\&CenterDot;{\left(\underset{m}{\mathrm{\&Sigma;}}{\hat{H}}_{n,m,k}{s}_{m,k}\right)}^{*})$

Wherein

It is the channel estimation.

Provide a kind of each emission chain has been carried out the method that pilot tone is followed the tracks of.In the method, can be to pilot tone groove using MIMO detection algorithm to detect pilot tone

Wherein ${\hat{s}}_{m,k}\&ap;s_{m,k}\&CenterDot;e^{j{\mathrm{\&theta;}}_t\left(m\right)},$ θ wherein _t(m) be the phase deviation of stream m.Can average to the phase difference of decoding between pilot tone and the desirable pilot tone on each pilot tone groove of each data flow, to generate phase estimation ${\widehat{\mathrm{\&theta;}}}_t\left(m\right)=\mathrm{angle}(\underset{k}{\mathrm{\&Sigma;}}{\hat{s}}_{m,k}\&CenterDot;s_{m,k}^{*}).$

Provide a kind of each transmit has been carried out the method that pilot tone is followed the tracks of.The method can comprise with orthogonal modes comes the modulated pilots polarity sequence, is every transmit evaluation phase separately thus.If the number of data streams is M, then flow m modulating mode can by $q_m\left(l\right)={\mathrm{<figure-callout\; id="2"\; label="e\; j"\; filenames="A20048003561400432.png,A20048003561400531.png"\; state="\{\{state\}\}">e</figure-callout>}}^j$ Expression, 1≤m≤M wherein, l 〉=0th wherein, the index of MIMO code element.This method also can comprise by averaging on a plurality of pilot tone grooves estimates the phase deviation of the stream m on the reception antenna n, and this skew is expressed from the next

${\mathrm{\&theta;}}_{n,m}=\mathrm{angle}\left(\underset{k}{\mathrm{\&Sigma;}}{v}_{n,m,k}\right)=\mathrm{angle}(\underset{k}{\mathrm{\&Sigma;}}\underset{l}{\mathrm{\&Sigma;}}{y}_{n,k}\left(l\right)\&CenterDot;r_{m,k}^{*}\left(l\right)\&CenterDot;H_{n,m,k}^{*}).$

Provide a kind of source data bit that splits to constitute the method for MIMO signal.In the method, can add bit with initialization and termination encoder to the source data bit, create modified source data bit thus.Modified source data bit can be offered encoder, create the source data bit of having encoded thus.The source data bit of having encoded can be split as N data flow then.

Provide another kind of fractionation source data bit to constitute the method for MIMO signal.In the method, the source data bit can be split as N data flow.Can add bit with initialization and N encoder of termination to this N data flow, create N modified data flow thus.This method also can comprise the sum of selecting bit, so that when splitting on the code element of each stream in this N data flow, the code element number in each data flow is equal in fact.

Provide another to split the source data bit to constitute the method for MIMO signal.In the method, can add bit with initialization and termination encoder to the source data bit, create modified source data bit thus.Modified source data bit can be offered encoder, create the source data bit of having encoded thus.The source data bit of having encoded can be offered perforator, create source data bit thus through perforation.Then, the source data bit through perforation can be split as N data flow.

A kind of method of using the classical signal code element to indicate the length of MIMO grouping is provided.This classical signal code element can comprise data rate field and length field.But the length of MIMO grouping may be longer than what use length field to represent.In this case, this method can comprise the length of using length field and data rate field to represent the MIMO grouping.For example, can in data rate field, provide pseudo-data rate value, and the pseudo-length value can be provided in length field.In one embodiment, pseudo-data rate value can be minimum traditional data rate, and the pseudo-length value can be the actual conventional lengths of expression emission duration.In another embodiment, the MIMO signal element of MIMO grouping comprises relative block length.

A kind of pattern of MIMO grouping is provided.This pattern can comprise traditional headers and MIMO header.Traditional headers can comprise a plurality of short code unit, is used for determining the automatic gain control of the reception of traditional headers.Relative with it, the MIMO header can comprise more than second short code unit, for use in the automatic gain control of the reception of MIMO header.

The another kind of pattern of MIMO grouping is provided.This pattern can comprise the first short code unit by many antenna emissions.Especially, can between one group short predetermined groove, split this first short code unit, wherein the subclass of each root in these many antennas with these short grooves can be associated.This first short code unit can be used for automatic gain control is carried out in MIMO grouping (comprising the MIMO grouping of this first short code unit).

This pattern also can comprise first long symbols of being launched in fact simultaneously by these many antennas.Especially, this first long symbols can be associated with each group leader's groove, wherein every antenna uses the elongated slot group of different order to launch.First long symbols can be used for mimo channel estimation (this MIMO grouping also comprises this first long symbols).

In one embodiment, these many antennas comprise first and second antennas.In this case, first and second antennas can be launched the first short code unit after the emission of classical signal code element.First antenna can be associated with first group short groove, and second antenna is associated with second group short groove.First and second antennas can be launched first long symbols in fact simultaneously.Especially, first long symbols can be associated with first group leader's groove and second group leader's groove, wherein first antenna used first group leader's groove to launch before using second group leader's groove, and second antenna used second group leader's groove to launch before using first group leader's groove.

This pattern also can comprise the signal element that the MIMO that launches in fact simultaneously with first and second antennas is associated after first short code unit and first long symbols.This pattern also can comprise the second short code unit, second long symbols and classical signal code element.The second short code unit can be used for the automatic gain control of traditional headers.Traditional headers can comprise the second short code unit, second long symbols and classical signal code element.Especially, traditional headers was launched before the MIMO header.

Another pattern of MIMO grouping is provided.This pattern also can comprise traditional headers and MIMO header.Traditional headers can comprise more than first long symbols that is used to carry out the estimation of legacy equipment channel.The MIMO header can comprise more than second long symbols that is used to carry out the estimation of MIMO device channel.

The another kind of pattern of multiple-input and multiple-output (MIMO) grouping is provided.This pattern can comprise first long symbols by many antenna emissions.This first long symbols can be launched in fact simultaneously by these many antennas.Especially, this first long symbols can be associated with the array elongated slot, wherein every antenna uses these elongated slot groups of different order to launch.This first long symbols can be used for the MIMO grouping mimo channel estimation of (comprising the MIMO grouping of this first long symbols).

This pattern also can comprise the first short code unit.This first short code unit also can be by these many antenna emissions.Especially, can split this first short code unit between one group short predetermined groove, wherein each root in these many antennas is associated with a subclass of these short grooves.The first short code unit can be used for the MIMO grouping automatic gain control of (comprising the MIMO grouping of this first short code unit).

In one embodiment, these many antennas can comprise first and second antennas.This first and second antenna can be launched the first short code unit after the emission of classical signal code element.First antenna can be associated with first group short groove, and second antenna is associated with second group short groove.First and second antennas can be launched first long symbols in fact simultaneously.First long symbols can be associated with first group leader's groove and second group leader's groove.Especially, first antenna can use first group leader's groove to launch before using second group leader's groove.Relative with it, second antenna can use second group leader's groove to launch before using first group leader's groove.

This pattern also can comprise the signal element that is associated with the MIMO that is launched in fact simultaneously by first and second antennas after first short code unit and first long symbols.

Providing a kind of decodes so that carry out the MIMO method for transmitting to a plurality of streams of coded data.In the method, for decoding, compare with data bit from bad groove, can carry out heavier weighting to the data bit of the groove of regarding for oneself.For example, the groove weight can be directly proportional with the square root of signal to noise ratio (snr) or SNR.

The weighting meeting influences the Viterbi branch metric calculation.In one embodiment, this method also can comprise the influence of determining error propagation based on the formula of the effective noise item of following calculating second and the 3rd stream:

${\widetilde{\mathrm{\&sigma;}}}_2^2={\mathrm{\&sigma;}}_2^2+{\left|{\mathrm{<figure-callout\; id="2"\; label="w"\; filenames="A20048003561400432.png,A20048003561400531.png"\; state="\{\{state\}\}">w</figure-callout>}}_2^{*}{\mathrm{<figure-callout\; id="1"\; label="h"\; filenames="A20048003561400431.png,A20048003561400531.png"\; state="\{\{state\}\}">h</figure-callout>}}_1\right|}^2\&CenterDot;{\mathrm{\&sigma;}}_1^2$

${\widetilde{\mathrm{\&sigma;}}}_3^2={\mathrm{\&sigma;}}_3^2+{\left|{\mathrm{<figure-callout\; id="3"\; label="w"\; filenames="A20048003561400441.png,A20048003561400531.png"\; state="\{\{state\}\}">w</figure-callout>}}_3^{*}{\mathrm{<figure-callout\; id="2"\; label="h"\; filenames="A20048003561400432.png,A20048003561400531.png"\; state="\{\{state\}\}">h</figure-callout>}}_2\right|}^2\&CenterDot;{\mathrm{\&sigma;}}_2^2+{\left|{\mathrm{<figure-callout\; id="3"\; label="w"\; filenames="A20048003561400441.png,A20048003561400531.png"\; state="\{\{state\}\}">w</figure-callout>}}_3^{*}{\mathrm{<figure-callout\; id="1"\; label="h"\; filenames="A20048003561400431.png,A20048003561400531.png"\; state="\{\{state\}\}">h</figure-callout>}}_1\right|}^2\&CenterDot;{\mathrm{\&sigma;}}_1^2$

Wherein, σ _m ²Be original noise item, w _mBe the zeroing vector, h _mBe channel, and

It is the effective noise item of m data flow.

A kind of method of revising the channel correction of many receiver chains is provided.In the method, can receive the channel estimation of many receiver chains.Can calculate the gain adjustment value of these many receiver chains based on intrinsic noise level (noise floor) and automatic gain control value.Then, these gain adjustment value can be applied to this many receiver chains.

A kind of method of using phase estimation for mimo system is provided.In the method, can use single associating phase estimation from a plurality of data flow, be applicable to the phasing of all data flow with calculating.In one embodiment, these a plurality of data flow comprise all data flow.

Provide a kind of for each emission/reception to the method for phase estimation is provided.In the method, can estimate each first phase deviation θ of channel matrix H from pilot tone _{N, m}(1≤m≤M, 1≤n≤N), and phase deviation is converted to θ _t(m) (1≤m≤M) and θ _r(n) (1≤n≤N).In channel matrix H,

Wherein, 1 _NBe all to be that 1 N takes advantage of 1 vector, I _NBe that size is the unit matrix of N, θ _r=[θ _r(1) θ _r(2) ... θ _r(N)] ^TBe the phase vectors at N receiver place, and θ _m=[θ _{1, m}θ _{2, m}θ _{N, m}] ^TIt is the phase vectors of the m row of matrix H.

A kind of optimization MIMO signal method for transmitting is provided.In the method, can use receiver to visit quality of channel from the grouping of the transmitter receipt of MIMO signal by expection.At this moment, can send grouping (for example, CTS grouping or ACK grouping) to reflector from the receiver of expection, this grouping comprises the feedback information that is used to optimize emission.This feedback information can obtain from a plurality of data flow of previous emission in fact simultaneously.For example, feedback information can comprise (1) channel estimation, or the detection pilot tone EVM of (2) pilot tone of proofreading and correct from channel and known clean channel calculation gained.

In one embodiment, feedback information can comprise the data transfer rate that will be used by reflector.In another embodiment, feedback information can comprise the designator of minimum data rates, maximum data rate, higher data and/or the lower data rate that will be used by reflector.

A kind of method for transmitting of optimizing emission MIMO signal is provided.In the method, can use MIMO grouping to visit channel quality, this MIMO grouping is to be received by the reflector of the MIMO signal receiver from expection.Can come definite emission data based on this MIMO grouping through optimizing.

A kind of method of determining the receiver selection of MIMO signal in diversity aerial system is provided.At least one receiver chain can be connected to many reception antennas.In the method,, can select to have the reception antenna of peak signal for every receiver chain.

A kind of method of determining the receiver selection of MIMO signal in diversity aerial system also is provided.In the method, can determine the combination that reception antenna is possible, wherein at least one receiver chain can be connected to many reception antennas.Can be each combination calculation signal to noise ratio (snr).Can select to have the combination of minimum SNR then.

Also provide a kind of selection to split the method for sequence.In the method, can be a plurality of sequences that split and calculate peak-to-average force ratio (PAR).Can select to have the fractionation sequence of optimum PAR then.

The advantage of these mimo systems and method is described referring now to the following drawings.

The accompanying drawing summary

Fig. 1 illustrates a kind of simplified system that comprises the single output of single input antenna configurations.

Fig. 2 illustrates a kind of simplified system that comprises the switch diversity antenna configuration.

Fig. 3 illustrates a kind of multiple-input and multiple-output (MIMO) system of simplification, and it can be launched on many antennas simultaneously, and can receive simultaneously on many antennas.

Fig. 4 illustrates the intermediate value data transfer rate of various antenna configurations on relative distance.

Fig. 5 illustrates the SNR of various antennas on each frequency slots.

Fig. 6 illustrates a kind of exemplary time-division training mode that comprises the MIMO grouping of traditional headers.

Fig. 7 A illustrates a kind of weak point that split and long symbols of comprising so that improve the exemplary patterns of the MIMO grouping of receiver gain controlling.

Fig. 7 B illustrates a kind of exemplary weak point that has split and the long symbols of three data flow.

Fig. 7 C illustrates and can be configured to indicate MIMO to divide into groups in the classical signal code element and one group of bit of the number of data streams.

Fig. 8 illustrates a kind of exemplary shared encoder system that is used for two spatial flows.

Fig. 9 illustrates the another kind of exemplary shared encoder system that is used for two spatial flows.

Figure 10 illustrates a kind of exemplary independent encoder system that is used for two spatial flows.

Figure 11 illustrates an a kind of part of exemplary receiver of the channel correction of revising many receiver chains.

Figure 12 illustrates the data transfer rate of several emitter/receiver antenna configurations on relative distance.

Figure 13 illustrates various turbo and the data transfer rate of non-turbo antenna configurations on relative distance.

Accompanying drawing describes in detail

Traditional headers and code element split

According to an embodiment,, just can prevent that legacy equipment " overlapping " is at (that is, launch in the MIMO grouping launching before finishing) on the MIMO signal by being received in the backward compatibility preamble before the MIMO grouping.Can advantageously allow legacy equipment to carry out the decoding of MIMO block length with this backward compatibility preamble of IEEE 802.11a/g system compatible, and forbid launching at this section time durations.In addition, whether this preamble can be indicated appended grouping is the MIMO grouping, and if it be the MIMO grouping, then can indicate the number of the data flow that just is being launched.

Fig. 6 illustrates a kind of exemplary time-division training mode 600 of the MIMO grouping that comprises this preamble.Particularly, the preamble 612 that is also referred to as traditional headers herein can comprise 802.11a/g short code unit, long symbols and the signal element of one or more standards.Notice that although following citation to these code elements is a plural form, these citations can be represented the code element of plural number or odd number.

In one embodiment, can be respectively from two (for example, first and second) antenna emission space streams 610 and 611.In other embodiments, can many antenna emission space from the beam shaping antenna configurations flow 610.Thus, spatial flow 610 can be characterized as being by one group of antenna emission.For simplicity, spatial flow 610 is described as by the emission of first antenna, and spatial flow 611 is described as being launched by second antenna.

In traditional headers 612, can use short code unit 601 to carry out rough ppm estimation and timing.Can use from the long symbols 602 of first antenna emission and estimate from the channel of first antenna.Especially, in one embodiment, signal element 603 can advantageously comprise the length information of MIMO grouping, prevents that thus legacy equipment from overlapping in the MIMO grouping.Except being from second antenna emission, other long symbols 604 identical with long symbols 602 can be used to estimate the channel from second antenna.Signal element 605A and 605B can comprise respectively about the modulation of the MIMO part of spatial flow 610 and 611 and the information (wherein MIMO partly is those parts after traditional headers 612) of length.

Fig. 7 A illustrates the another kind of exemplary patterns 700 of the MIMO grouping that comprises traditional headers 612.Mode 7 00 can advantageously split short and long symbols, so that improve receiver gain controlling (that is, even the transmission path dissmilarity also can be guaranteed continuous received power).In mode 7 00, can after traditional headers 612, insert additional short code 704A of unit and 704B, allow receiver to carry out time stage gain adjustment thus.

For obtaining constant received power, the training symbol of launching from these two (that is, first and second) antennas should be incoherent.This irrelevant can the realization by in frequency domain, splitting short code unit and long symbols.In other words, the 704A of short code unit uses half in short code unit 601 employed each grooves, and the 704B of short code unit use in these grooves second half (thus, 704A+704B=601).Similarly, long symbols 705A uses half in long symbols 602 employed each grooves, and long symbols 705B use in these grooves second half (thus, 705A+705B=602).In one embodiment, every antenna can use in the two halves of these grooves any one to launch in the different time.

Because on a transmit antennas, only use the groove of half, so for the short code unit and the long symbols that have split, the power of each groove should double.Especially, from the short code unit that has split, it is constant that received power will keep.Therefore, it will be effective having split that gain during the short code unit is provided with these data symbols.At the receiver place, can extract out the estimation of the channel of half groove in certain time, and two halves are all available after with its combination and smoothly.

Fractionation can realize in every way.For example, in one embodiment, long symbols 705A can use groove-26 ,-24 ... ,-2,1,3 ... 25, and long symbols 705B can use groove-25 ,-23 ...-1,2,4 ... 26.In another embodiment, long symbols 705A can use groove-26 ,-24 ... ,-2,2,4 ... 26, and long symbols 705B can use groove-25 ,-23 ...-1,1,3 ... 25.Note, if the peak-to-average force ratio of long symbols 602 (PAR) is 3.18dB, and the data in each groove remain unchanged after splitting, then first groove uses embodiment respectively long symbols 705A and 705B to be produced the PAR of 5.84dB and 6.04dB, and second groove uses embodiment respectively long symbols 705A and 705B to be produced the PAR of 5.58dB and 5.85dB.

Especially, weak point that has split and long symbols can be generalized to any a plurality of data flow.For example, as shown in Fig. 7 B,, then these grooves should be split as three staggered and average at interval on all grooves groups, A, B and C if three streams are arranged.Thus, for the short code unit that has split, first antenna can be launched the 414A of short code unit (using groove A), and second antenna can be launched the 414B of short code unit (using groove B), and third antenna can be launched the 414C of short code unit (using groove C).

For the long symbols that has split, first antenna can sequentially be launched long symbols 415A, 415B and 415C (using groove A, B and C respectively), second antenna can sequentially be launched long symbols 415B, 415C and 415A (using groove B, C and A respectively), and third antenna can sequentially be launched long symbols 415C, 415A and 415B (using groove C, A and B respectively).This rotary mode allows all grooves are carried out the channel estimation, and always guarantees the orthogonality in the frequency domain.The exemplary long sequence of the stream of two 20MHz can be L _-26:26={ 1 1-1 11 1-1-1-1-1 111 1-1 1-1 1-1-1 11 1-1 11 0-1 1 1-1-1 1-1-1 1-1-1 1-1-1 111 1-11 11111 1}, wherein long symbols 705A uses the groove [26:2:-2 2:2:26] of PAR as 2.73dB, and long symbols 705B uses the groove [25:2:-1 1:2:25] of PAR as 2.67dB.

The exemplary sequence of the stream of three 20MHz can be L _-26:26={ 1-1 1111 1-1-1-1 1-1-1-1-1-1 111111 1-1-1 10 1-1-1-1 1-1 1-1 1-1 1 1-1 1-1-1 1 1-1 1 1-1 1-1-11}, wherein the first single-tone group is that PAR is 3.37dB [26:3:-2 2:3:26], the second single-tone group is that PAR is 3.10dB [25:3:-1 3:3:24], is 3.10dB [24:3:-3 1:3:25] and the 3rd single-tone group is PAR.The exemplary sequence of the stream of four 20MHz can be L _-26:26={ 1111 1-1-1-1 1-1 11 1-1 1 1-1 1-1-1-1 11 1-1 101 1-1 1-1-1 1-1-1-1-1 1-1-1-1 111 1-1 1 1-1 11 1}, wherein the first single-tone group is that PAR is 3.05dB [26:4:-2 3:4:23], the second single-tone group is that PAR is 3.05dB [25:4:-1 4:4:24], the 3rd single-tone group is that PAR is 3.11dB [24:4:-4 1:4:25], is 3.11dB [23:4:-3 2:4:26] and the 4th single-tone group is PAR.

The exemplary long sequence of the stream of a 40MHz can be:

L _-58:58＝{-1?1?1?1?1?-1?1?1?-1?-1?-1?-1?1?1?1?1?1?-1?1?1?-1?1?-1?1?1?-1?-1?1?1?-1?-1?1?1-1?-1?-1?-1?-1?1?-1?1?1?-1?-1?-1?1?-1?-1?1?-1?-1?1?1?-1?1?1?1?0?0?0?-1?-1?-1?-1?-1?-1?-1?-1-1?-1?-1?1?1?1?-1?1?-1?1?1?-1?-1?1?-1?-1?1?-1?1?-1?1?-1?-1?-1?-1?1?1?-1?1?-1?-1?-1?1?-1?1-1?1?-1?1?1?-1?1?-1?-1?1?-1?1?1?1}

The exemplary long sequence of the stream of two 40MHz can be:

L _-58:58＝{-1?1?1?1?1?-1?1?1?-1?-1?-1?-1?1?1?-1?1?1?-1?1?1?-1?1?-1?1?1?-1?-1?1?1?-1?-1?1?1-1?-1?-1?1?-1?1?-1?1?1?1?-1?-1?1?-1?-1?-1?-1?-1?-1?1?-1?1?-1?1?0?0?0?-1?-1?-1?-1?-1?-1?-1-1?-1?-1?-1?1?1?1?-1?1?-1?1?1?-1?-1?1?-1?1?1?-1?1?-1?1?-1?-1?-1?-1?1?1?-1?1?-1?-1?-1?-1?-11?-1?1?1?1?1?-1?1?1?-1?1?-1?1?1?1}

Wherein, the first single-tone group is [58:2:-2 2:2:58], and the second single-tone group is [57:2:-3 3:2:57].

The exemplary long sequence of the stream of three 40MHz can be:

L _-58:58＝{-1?-1?-1?-1?-1?-1?1?1?1?-1?-1?-1?-1?-1?-1?1?1?1?-1?-1?-1?-1?-1?-1?1?1?1?1?1?1?1?11?-1?-1?-1?-1?-1?-1?1?1?1?1?1?1?-1?-1?-1?-1?-1?-1?-1?-1?-1?-1?-1?-1?0?0?0?-1?-1?-1?-1?-1?-1-1?-1?-1?-1?-1?-1?1?1?1?-1?-1?-1?1?1?1?1?1?1?1?1?1?-1?-1?-1?-1?-1?-1?-1?-1?-1?-1?-1?-1?1?11?1?1?1?1?1?1?1?1?1?1?1?1?-1?-1?-1}

Wherein, the first single-tone group is [58:3:-4 2:3:56], and the second single-tone group is [57:3:-3 3:3:57], and the 3rd single-tone group is [56:3:-2 4:3:58].

The exemplary long sequence of the stream of four 40MHz can be:

L _-58:58＝{-1?1?-1?-1?-1?1?1?-1?1?1?1?-1?1?1?1?1?-1?-1?-1?-1?1?-1?-1?-1?1?-1?1-?1?1?-1?-1?-1-1?1?1?-1?-1?-1?1?1?1?1?-1?1?-1?-1?1?-1?1?1?1?1?1?-1?-1?-1?1?0?0?0?-1?1?1?-1?-1?-1?-1?-1?11?1?-1?1?1?-1?-1?-1?1?-1?1?-1?-1?-1?1?-1?1?-1?-1?1?1?1?1?1?1?1?-1?-1?-1?-1?1?1?-1?1?1?1?-11?1?-1?-1?1?-1?1?-1?-1?1?1}

Wherein, the first single-tone group is [58:4:-2 5:4:57], and the second single-tone group is [57:4:-5 2:4:58], and the 3rd single-tone group is [56:4:-4 3:4:55], and the 4th single-tone group is [55:4:-3 4:4:56].Note,, can carry out the random search of data pattern for reducing PAR.

Can split short code unit similarly, recognize simultaneously in per 4 grooves and only use one.For example, in one embodiment, the 704A of short code unit can use groove-24 ,-16 ,-8,4,12,20, and the 704B of short code unit can use groove-20 ,-12 ,-4,8,16,24.In another embodiment, the 704A of short code unit can use groove-24 ,-16 ,-8.8,16,24, and the 704B of short code unit can use groove-20 ,-12 ,-4,4,12,20.If the PAR of short code unit 601 is 2.09dB, then first groove uses embodiment that short code 704A of unit and 704B are produced the PAR of 4.67dB, and second groove uses embodiment that the 704A of short code unit is produced the PAR of 4.32dB, the 704B of short code unit is produced the PAR of 2.79dB.Note, use the exhaustive search of embodiment to produce the minimum PAR of 4.26dB first groove.It is that { 704A of short code unit of 1-1 1-1-1-1} produces the minimum PAR of 1.68dB, and be { the minimum PAR of the first 704B generation 2.79 of the short code of 1-1-1-1-1 1} to polarity to polarity that second groove is used the similar exhaustive search of embodiment.

Note,, only use a few groove for each short code unit that has split.Therefore, when channel is a frequency selectivity, and supposition the short code unit, the long symbols that has split and the signal element that have split is when having identical transmitting power, and in the short code unit that has split, mean receiving power may differ widely.This difference power can cause the problem of receiver gain controlling.Therefore, in one embodiment, can use 24 grooves, guarantee that thus there is more groove in each short code unit that has split short code unit.In another embodiment, in all data flow, can use the frequency displacement short code unit of 12 grooves, but each data flow can be used different frequency displacements, that is, move 1,2 or 3 groove from original short code unit.The continuity from frequency displacement short code unit to long symbols that has split and subsequent received power has been guaranteed in this frequency displacement.But be noted that in this scheme the number of supported data streams is no more than four.In addition, the cycle of frequency displacement short code unit is longer than the cycle of traditional short code unit, the modification that this may require frequency offset estimation to realize.

As mentioned above, can be from one group of antenna emission traditional headers.Comprise in this group and in the situation of many antennas the beam shaping effect may take place.Be to realize theaomni-directional transmission, can the subdivision amount of each frequency slots of every antenna be weighted.For example, can on each groove on other antenna, use the phase shift (for example, the phase shift of phase place oblique ascension or any kind) and/or the phase width of cloth, so that different grooves stands different beam shapings.A kind of example technique of creating the phase place oblique ascension comprises the known cyclic delay diversity of technical staff (CDD) of wireless technical field.

An example of the phase width of cloth can be to use the odd bin on an even bin on the antenna and another root antenna.In another example of the phase width of cloth, can use all positive frequency grooves to an antenna, and can use all negative frequency grooves another root antenna.Thus, generally speaking, can use irrelevantly the component of each frequency slots to be weighted and create theaomni-directional transmission with two antennas.

A kind of mechanism of MIMO grouping and legacy packets being distinguished ground mark should also can receive traditional 802.11a/g grouping because can receive the receiver of MIMO grouping, so can be provided.In addition, if grouping is the MIMO grouping, then receiver also needs to know the number of data streams.In an embodiment shown in Fig. 7 C, first group of bit in the classical signal code element 603 can be indicated the MIMO grouping, and second group of bit in the classical signal code element 603 can be indicated the number of data streams.What for example, the reservation bit R of signal element 603 can be made as that " 1 " launching with indication is MIMO grouping.In addition, can use the lowest bit of predetermined number in the length field 721 of signal element 603 to indicate the number of data streams.Thus, if used two lowest bit, then the length value in the length field 721 will be rounded to the 3rd lowest bit.

Notice that after the MIMO receiver was to 603 decodings of classical signal code element, it can check reservation bit R.If this bit is " 0 ", then this grouping is a legacy packets, and the length value in the length field 721 is the validity score group length by byte.But if reservation bit is " 1 ", then this grouping is MIMO grouping, and latter two bit of length field is the number of data streams.In a kind of situation in back, the length of grouping is accurate in 2 bytes.Especially, traditional receiver only uses length value to calculate it should to forbid time of launching.Therefore, for legacy equipment, the value in the length field 721 need not very accurate.Advantageously, as mentioned above, the true length of each data flow can be included in the MIMO signal element (for example, 706A and the 706B among Fig. 7 A).Therefore, in fact the MIMO receiver can ignore the value that is stored in the length field 721.

In another embodiment, can use ' mould ' computing to represent the number of MIMO stream.Particularly, if the data word joint number of grouping is L, the data word joint number of every code element is B, and service and telegram end byte number be C, and then required code element number is

Wherein The expression round-up is to immediate integer.The number of tentation data stream is M, and M≤B.In this case, modified length is

$\tilde{L}=B\&CenterDot;(N_{\mathrm{sym}}-1)-C+M$

Notice that the code element number of being calculated gained by legacy equipment remains N _Sym:

MIMO equipment can calculate the number of stream according to following formula:

$\hat{M}=(\tilde{L}+C)\mathrm{mod}B=M$

If M=B, then

To be 0.In this case, will take place $\hat{M}=B$ Mapping.Notice that can use this identical technology and represent to remove out of Memory the number that flows, wherein the information that will represent is encoded as above M.

In yet another embodiment, can after classical signal code element 603, insert code symbols 722 with indication MIMO grouping (and stay use it for anything else reservation bit).Code symbols 722 can comprise and have the pilot tone that is reversed the MIMO signal element (with respect to the conventional code element that should appear at this position) of (that is ,+/-).For example, code symbols 722 can comprise with BPSK modulation with strengthen robustness through revising signal element 706A ' and 706B '.In this embodiment, the MIMO receiver can determine that the grouping of importing into is MIMO grouping or legacy packets based on the phase place of the pilot tone of code symbols 722.If it is the MIMO grouping, then can extracts the number of data streams, and detect the remainder of grouping in the mode that meets MIMO.Otherwise, this grouping is divided into groups to handle as traditional 802.11g.

Pilot tone

Pilot tone is inserted in the 802.11a/g system so that carry out frequency shift (FS) and phase noise tracking.Use in the multiple wireless mimo system at reflector and receiver place, different transmit and receive chain and may stand common or incoherent phase noise.According to an aspect of the present invention, can be advantageously for federation chain, for every emission chain or for each emission/reception to the pilot tone tracking scheme is provided.

Because frequency shift (FS) and phase noise between reflector and the receiver, the phase place that receives data symbols may be different during the emission of grouping.For following the tracks of and phase calibration changes, in 802.11a/g, with four pilot tone grooves with [1 1 1-1] * p _lForm insert in each OFDM code element, wherein [1 1 1-1] is the pattern on each pilot tone groove, and p _lBe the pilot tone polarity of code element l.For MIMO OFDM code element, 4 bit modes and pilot tone polarity sequence all can be generalized to a plurality of spatial flows.

In one embodiment, in all data streams, repeat the pilot frequency format identical with 802.11a/g.For example, if the pilot tone polarity sequence of 802.11a/g code element is p ₀, p ₁, p ₂, p ₃, p ₄..., then can use following pilot tone polarity, the emission stream that wherein different line displays is different to the MIMO code element:

p ₀?p ₁?p ₂?p ₃?p ₄?…

p ₀?p ₁?p ₂?p ₃?p ₄?…

p ₀?p ₁?p ₂?p ₃?p ₄?…

Because pilot tone polarity is identical on different spatial flows, so, then will in the pilot tone groove, form fixing beam shaping pattern if also on each stream, repeat this 4 bit pilot frequency mode.For guaranteeing that bad groove can not remain in zero-bit all the time, can increase phase shift, and code element ground of a code element is in these 4 groove cocycle rotations.For example:

Code element 1 code element 2 code elements 3 code elements 4

Antenna 1[1 11 1] [1 11 1] [1 11 1] [1 11 1]

Antenna 2[1 j-1-j] [j-1-j 1] [1-j, 1 j] [j 1 j-1]

Pilot tone on second antenna (antenna 2) in first code element (code element 1), have 0,90,180 and 270 the degree phase shifts, and be recycled to anticlockwise as subsequent symbol.Note, in last example, used the initial pilot frequency mode [1 11 1] of 4 pilot tone grooves, but this scheme can be applied to any initial pilot frequency mode and the pilot tone groove more than 4.Thus, generally speaking, can on any frequency spectrum, pilot tone be separated to carry out estimation.

Can carry out pilot tone in a different manner follows the tracks of.For example, be public (allow thus to carry out joint pilot follow the tracks of) if phase noise transmits and receives on the chain at all, then every reception chain can be estimated received signal in each pilot tone groove based on channel estimation and known pilot pattern.The complex conjugate of this estimation can be multiply by actual reception pilot signal then.Can be with the result combinations on each pilot tone groove and each chain.The phase place of final result is exactly the phase deviation of being asked thus.In mathematical formulae, the received signal that receiver n goes up in pilot tone groove k is expressed from the next:

$y_{n,k}=\underset{m}{\mathrm{\&Sigma;}}{H}_{n,m,k}{e}^{\mathrm{j\&theta;}}\&CenterDot;s_{m,k}+n_{n,\mathrm{<figure-callout\; id="1"\; label="k\; Formula"\; filenames="A20048003561400431.png,A20048003561400531.png"\; state="\{\{state\}\}">k</figure-callout>}}$ Formula 1

S wherein _{M, k}Be the pilot frequency code element of stream m, θ is the common phase skew, H _{N, m, k}Be channel response, and n _{N, k}It is noise.The common phase skew is expressed from the next:

$\mathrm{\&theta;}=\mathrm{angle}(\underset{n,k}{\mathrm{\&Sigma;}}{y}_{n,k}\&CenterDot;{\left(\underset{m}{\mathrm{\&Sigma;}}{\hat{H}}_{n,m,k}{s}_{m,k}\right)}^{*})$ Formula 2

Wherein It is the channel of estimation.

Relative with it, if on different emission chains, there is independent phase noise (the pilot tone tracking of every emission chain is necessitated), then at first the MIMO detection algorithm can be applied to the pilot tone groove to detect pilot tone

Because ${\hat{s}}_{m,k}\&ap;s_{m,k}\&CenterDot;e^{j{\mathrm{\&theta;}}_t\left(\mathrm{mm}\right)},$ θ wherein _t(m) be the phase deviation of stream m, thus can average to the phase difference of decoding between pilot tone and the desirable pilot tone on each pilot tone groove of each data flow, with the generation phase estimation,

${\widehat{\mathrm{\&theta;}}}_t\left(m\right)=\mathrm{angle}(\underset{k}{\mathrm{\&Sigma;}}{\hat{s}}_{m,k}\&CenterDot;s_{m,k}^{*})$ Formula 3

If phase noise is incoherent (the right pilot tone of each send-receive is followed the tracks of to necessitate) on transmitting chain and reception chain, then the available orthogonal pattern is come the modulated pilots polarity sequence, so that can be separately that each send-receive is to evaluation phase.For example, if the number of data streams is M, then flow m modulating mode can by $q_m\left(l\right)={\mathrm{<figure-callout\; id="2"\; label="e\; j"\; filenames="A20048003561400432.png,A20048003561400531.png"\; state="\{\{state\}\}">e</figure-callout>}}^j$ Expression, 1≤m≤M wherein, l 〉=0th wherein, the index of MIMO code element.For example, the exemplary modulated pilot tone polarity sequence of three emission streams can be:

p ₀ p ₁ p ₂ p ₃ p ₄ …

p ₀ p ₁e ^j2π/3 p ₂e ^-j2π/3?p ₃ p ₄e ^j2π/e …

p ₀ p ₁e ^-j2π/3?p ₂e ^j2π/3 p ₃ p ₄e ^-j2π/e?…

Note, $\frac{1}{M}\underset{l=k}{\overset{k+M-1}{\mathrm{\&Sigma;}}}{q}_m\left(l\right)q_n^{*}\left(l\right)={\mathrm{\&delta;}}_{m,n},$ Wherein

That is, on the long any interval of M code element, the pattern on each data flow is a quadrature, and wherein k represents the beginning index of M orthogonal data code element.In this case, tackling all stream uses same 4 bit pilot frequency modes to keep orthogonality.

In one embodiment, last (M-1) the individual code element that receives on every antenna can be kept in the buffering area.After this, when on every antenna, receiving new code element, the complex conjugate of the pilot tone of this M code element be multiply by these code elements and summation,

Y wherein _{N, k}(l) be that chain n goes up the received signal in the groove k of l code element, and r _{M, k}(l) be the pilot frequency code element in the groove k of l code element among the stream m.Item r _{M, k}(l) comprise groove pilot frequency mode, original pilots polarity and quadrature modulation.To all send-receives among all pilot tone groove k to (m n) carries out this calculating.The complex conjugate of result and channel estimation can be multiplied each other then, produce the pilot tone through Orthogonal Composite and channel correction thus, it can be expressed from the next:

$v_{n,m,k}=\underset{l}{\mathrm{\&Sigma;}}{y}_{n,k}\left(l\right)\&CenterDot;r_{m,k}^{*}\left(l\right)\&CenterDot;H_{n,m,k}^{*}$ Formula 4

Estimate the phase deviation of stream m on reception antenna n then by averaging on each pilot tone groove, it is expressed from the next:

${\mathrm{\&theta;}}_{n,m}=\mathrm{angle}\left(\underset{k}{\mathrm{\&Sigma;}}{v}_{n,m,k}\right)=\mathrm{angle}(\underset{k}{\mathrm{\&Sigma;}}\underset{l}{\mathrm{\&Sigma;}}{y}_{n,k}\left(l\right)\&CenterDot;r_{m,k}^{*}\left(l\right)\&CenterDot;H_{n,m,k}^{*})$ Formula 5

For preceding (M-1) individual MIMO code element, can use pilot tone tracking associating or every emission chain, because history is long not enough.In addition, can use any orthogonal modes q that meets the following conditions _m(l) (wherein m and l definition is as above) comes the modulated pilots polarity sequence:

$\frac{1}{M}\underset{l=k}{\overset{k+M-1}{\mathrm{\&Sigma;}}}{q}_m\left(l\right)q_n^{*}\left(l\right)={\mathrm{\&delta;}}_{m,n},$ Wherein

Wherein m, n, l, k and M definition are as above.For example, the modulated pilot tone polarity sequence of three of last example emission streams will be:

p ₀q ₁(0)?p ₁q ₁(1)?p ₂q ₁(2)?p ₃q ₁(3)?p ₄q ₁(4)?…

p ₀q ₂(0)?p ₁q ₂(1)?p ₂q ₂(2)?p ₃q ₂(3)?p ₄q ₂(4)?…

p ₀q ₃(0)?p ₁q ₃(1)?p ₂q ₃(2)?p ₃q ₃(3)?p ₄q ₃(4)?…

Notice that the succession of 802.11a/g pilot tone polarity sequence is for the sake of simplicity purely, and can be abandoned together,, establishes p that is _l=1.Third and fourth embodiment is drawn in this setting.In the 3rd embodiment, the pilot tone polarity sequence all is 1, and is represented as following sequence:

1?1?1?1?1?…

1?1?1?1?1?…

1?1?1?1?1?…

Similar with first embodiment, should comprise the beam shaping effect of circulation rotation phase shift on the pilot tone groove to avoid fixing.Can carry out the pilot tone of joint pilot tracking or every emission chain follows the tracks of.

In the 4th embodiment, pilot frequency sequence only is q _m(l), it can be represented by following sequence:

q ₁(0)?q ₁(1)?q ₁(2)?q ₁(3)?q ₁(4)?…

q ₂(0)?q ₂(1)?q ₂(2)?q ₂(3)?q ₂(4)?…

q ₃(0)?q ₃(1)?q ₃(2)?q ₃(3)?q ₃(4)?…

In this case, can be to the same pilot frequency mode on all each grooves of stream use.Can carry out the right pilot tone of each send-receive follows the tracks of.

Data flow splits

For structure MIMO signal element, the source data bit suitably need be split as a plurality of data flow.In 802.11a/g, the use encoding rate is 1/2,2/3 and 3/4 convolution code, and four kinds of modulation schemes (that is, BPSK, QPSK, 16QAM and 64QAM) are provided.Encoding rate and modulation scheme are determined the bit number in each OFDM code element.For realizing optimum MIMO performance, tackle different data flow and allow different modulation and encoding rate.Therefore, for different data flow, the bit number in each MIMO signal element can be different.

Typical encoding block comprises encoder and perforator, the two all be known in the WLAN technical field (for example, perforator is described in the 17.3.5.6 joint at IEEE 802.11a).According to an aspect of the present invention, can pass through to use identical encoder and different perforators, or by using identical perforator and different encoders to construct different sign indicating numbers.If use identical encoder, then split and to finish before the encoder or before perforator.On the other hand, if use different encoders, then split and before encoder, to finish.Fractionation before perforator is referred to herein as " sharing " encoder, and the fractionation before encoder is referred to herein as " separately " encoder.Notice that in 802.11a/g, encoding rate is that 2/3 and 3/4 sign indicating number all is to be that 1/2 convolution code perforation gets from encoding rate.Therefore, can realize sharing encoder or independent encoder.

Can insert additional bit before or after the source data bit comes initialization and stops encoder.For example, in 802.11a/g, can before the source data bit, add 16 service bits, and after the source data bit, add 6 tail bits.Therefore, in the situation of independent encoder, can be the bit that each encoder inserts these interpolations.

Fig. 8 illustrates a kind of exemplary shared encoder system 800 that is used for two spatial flows.In system 800, source data bit 801 can be offered piece 802, piece 802 adds above-mentioned service/tail bits.Encoder 803 receives modified bit, and generates n1+n2 bit.Splitter 804 receives n1+n2 bit, and generates two spatial flows, they so that be provided for perforator 805A and 805B respectively.

In one embodiment, for every n1+n2 bit after the encoder 803, first spatial flow is obtained preceding n1 bit, and second spatial flow is obtained n2 the bit in back.A kind of exemplary chunk sizes is n _i=N _Cbps(i) (N wherein _CbpsBe the perforation number of coded bits of each code element before), thus code element is split one by one.Another kind of exemplary chunk sizes is n _i=N _Cbps(i)/gcd (N _Cbps(1), N _Cbps(2)) (wherein gcd () expression greatest common divisor) reduced thus to split the size of chunk when keeping adequate rate, thereby shortened processing delay.

In this embodiment, the length field in the MIMO signal element is set as by the true length of the grouping of byte.R14 field in the MIMO signal element is set as other data transfer rate.R14 field in the classical signal code element can be set as the data transfer rate of first data flow, or always is made as lowest data rate.As describing in detail more, can handle the length field in the classical signal code element, so that consistent with the actual duration of grouping by the code element number of legacy equipment calculating gained following.

Fig. 9 illustrates the another kind of exemplary shared coded system 900 that is used for two spatial flows.In system 900, source data bit 901 can be offered piece 902, piece 902 adds service/tail bits.Encoder 903 receives modified bit, and generates n1+n2 bit.Perforator receives this n1+n2 bit, and generates output code with predetermined data rate.Splitter 905 receives this n1+n2 bit with predetermined data rate, and generates two spatial flows, that is, and and n1 bit and n2 bit.Equally, for every n1+n2 bit after the encoder 903, first spatial flow is obtained preceding n1 bit, and second spatial flow is obtained n2 the bit in back.

Figure 10 illustrates a kind of exemplary independent encoder system 1000 that is used for two spatial flows.In system 1000, can be with source data byte 1001, promptly N1+N2 offers splitter 1002, and splitter 1002 generates two spatial flows (first spatial flow is obtained preceding N1 byte, and second spatial flow is obtained N2 the byte in back).Piece 1003A and 1003B receive this N1 and N2 byte respectively, and add service/tail bits to them.Encoder 904A and 904B receive modified byte, to modified byte code, and the output that they have been encoded are offered perforator 905A and 905B respectively.

Notice that in independent encoder system, the minimum data unit is by byte, because the length field in the signal element is by byte.Therefore, in this case, each stream can be at the service bit that begins to locate to add 2 bytes, and adds 6 tail bits (～1 byte) in end.Notice that N1 can be the data word joint number of every code element, or this byte number is divided by the greatest common divisor of every symbol data total amount of byte.The byte number of every code element all is an integer for all data transfer rates except that 9Mbps, and in the situation of 9Mbps, each code element comprises 4.5 bytes.Therefore, in this case, for the data flow of using 9Mbps, chunk sizes can replace between 4 bytes and 5 bytes.

For example, supposing has two spatial flows (stream 1 and stream 2), and the data word joint number of every code element is respectively 27 (54Mbps) and 4.5 (9Mbps).Originally, can 2 of each emissions in stream 1 and stream 2 serve byte.Then, preceding 25 (27-2) data bytes can be transmitted into stream 1, following 2 (4-2) data bytes are transmitted into stream 2, following again 27 bytes are transmitted into stream 1, and following again 5 bytes are transmitted into stream 2, and the rest may be inferred.

Before carrying out actual fractionation, need the value of the length field of MIMO signal element.Above-mentioned direct order splits and causes complicated a little length computation.Below be a kind of simple length computation, can realize this calculating splitting to make an amendment slightly.At first, calculate required code element sum:

Formula 6

Wherein L is the sum of uncoded word joint in the grouping, and M is the number of data flow, and B (i) is every code element uncoded word joint number of stream i.

The expression round-up is to immediate integer.If K the data flow of using 9Mbps arranged, and N _SymBe odd number, then recomputate:

Formula 7

Thus, the byte number in first data flow is Wherein

The expression round down is to immediate integer, and the byte number in second stream is The rest may be inferred.Can use byte counter to each stream.In case reach the byte limit of stream, can in order splits, skip this stream.Notice that formula 6 and 7 all is applicable to general encoder and perforator, the data flow of general number and the service/tail bits of general number.Notice that system 900 only has a length, so formula 6 and 7 is not suitable for this system.

In the 802.11a/g grouping, the length field in the signal element is 12 bit long, and this is corresponding to the largest packet size of 4095 bytes.In mimo system, for keeping high Payload efficient, need be greater than the grouping of 4K byte.Therefore, represent that definite block length may need the more bits that can comprise than in the individual signals code element.

According to an embodiment, can in the classical signal code element, use pseudo-data transfer rate and pseudo-length to indicate and to occupy data transfer rate and the length of identical launch time with the MIMO grouping.(for example can use minimum legal traditional data rate, for 802.11a/g is 6Mbps), to allow grouping to have the longest duration (with 4096 byte=5.46 of 6Mbps data transfer rate emission millisecond, perhaps for the longest effective 802.11 block lengths, with 2304 bytes of 6Mbps data transfer rate emission=3.07ms).

In one embodiment, for MIMO signal element, can use relative block length to replace absolute growth to limit required bit number.Relative length is that the total amount of byte that can be launched in the grouping with same symbol number deducts the byte number of actual transmission, or is approximately the byte number of being filled.As mentioned above, total amount of byte can use code element number (determining from the classical signal code element) and data transfer rate (being coded in the MIMO signal element) in the grouping to calculate.

For shared encoder, determine single relative length, and only in the MIMO of first stream signal element, launch this relative length.Length field in other data flow can be stayed and use it for anything else.For independent encoder, can be each data-flow computation relative length, and launch these relative lengths separately.Perhaps, can be the single relative length of all data-flow computation, and this relative length of emission (that is, individual other relative length can draw from total relative length of any byte allocation scheme of reaching an agreement between reflector and the receiver) in first data flow only.

AGC and channel estimation

Get back to Fig. 7 A, can use traditional short code unit 601 to carry out coarse frequency estimation, rough timing estimate and automatic gain control (AGC).Can use traditional long symbols 602 to carry out fine frequency estimation, meticulous timing estimate and channel estimation.Classical signal code element 603 can comprise and prevents that legacy equipment from overlapping information required in the MIMO grouping, and the signature of MIMO grouping and the data flow number of being launched.The automatic gain control that the MIMO that can use the first 704A/B of the short code that has split to divide into groups selects, and carry out antenna diversity and select (if suitable).Can use the long symbols 705A/B that has split to carry out the mimo channel estimation.MIMO signal element 706A/B can comprise the length and the modulation intelligence of data streams.

Because traditional headers 612 can be from an antenna emission, and MIMO header (comprising short code unit 704A/B, long symbols 705A/B and signal element 706A/B) is from many antennas emissions, so the received power on every reception antenna may change between traditional headers and MIMO header to some extent.In this case, the short code unit that has split can be designed to be convenient to AGC and adjust gain setting, so that the big young pathbreaker of the input of ADC is suitably adjusted.Notice that AGC can receive chain to all and use the single status machine, but every reception chain can come its corresponding received signal is applied different gains according to the size of signal.

If necessary, then use the unit of fractionation short code that receives from many antennas, jointly carry out other timing recovery and frequency offset estimation.This joint operation can be carried out by making up these a plurality of received signals.This joint operation also can comprise the selection optimum signal, and uses this optimum signal to carry out timing and recover and offset estimation.

In one embodiment, can traditional headers 612 be transmitted into the receiver of expection from optimal antenna.This expression is for the system with M spatial flow, and the flash-up from traditional headers to the MIMO header is no more than 10*log10 (M).For unexpected receiver, flash-up may be higher, but remain 10*log10 (M) by the balanced growth of dB.Therefore, only need meticulous gain to change.

The length that splits lasting 2M the OFDM code element of long symbols that is proposed, wherein M is the number of spatial flow.For to the estimation of each spatial flow calculating channel, can in frequency domain, extract the groove that each flows employed correspondence by the FFT from this 2M OFDM code element, they are averaged and merge.Can apply smoothing filter to reduce estimation error to domain channel response.For bigger M, the phase change on 2M OFDM code element may be very big.In one embodiment, can take FFT, average and level and smooth before, use the fine frequency estimation that obtains from traditional headers, in time domain, proofread and correct the phase place of each OFDM code element.Can use during the long code element of 2M other measurement to phase change (because inaccuracy and phase noise of fine frequency estimation), before level and smooth correctly with they alignment.

The detection of MIMO signal

Can use several different technology to detect the MIMO signal.Two kinds of known technology are MMSE-LE and MMSE-DFE detection scheme.Can use least mean-square error (MMSE) linear equalization (LE) or decision feedback equalization (DFE) algorithm to separate and detect a plurality of data flow.For note for simplicity, only consider a subcarrier in the following description, wherein will repeat identical process to each subcarrier.

Suppose to have M transmit antennas and N root reception antenna.If it is x that frequency domain transmits, channel is H, and noise is n, and received signal is y, and wherein x is that M takes advantage of 1, and y and n are that N takes advantage of 1, and H is that N takes advantage of M, then:

y＝Hx+n E(nn ^*)＝σ ²I _N

Can illustrate, with E ‖ W ^*Y-x ‖ ²Minimized MMSE solution W is:

W ^*＝(H ^*H+σ ²I _M) ^-1H ^* R _e＝σ ²(H ^*H+σ ²I _M) ^-1

R wherein _eIt is the error variance matrix of gained.In the MMSE-IE algorithm, W ^*Strictness is as above calculated, and is applied in y to detect all data flow concurrently.

The MMSE-DFE detection algorithm uses two steps (1) and (2) to carry out continuous cancellation.In step (1), can calculate the zeroing vector.Calculate the zeroing vector and then can comprise three step (a) and (b) and (c).In step (a), can calculate R _eDiagonal element and find smallest element.Smallest element is corresponding to the transmitting antenna with optimum signal quality.In step (b), can calculate W ^*Corresponding row.This will be the zeroing vector of selected transmitting antenna.In step (c), can detect the respective column among the H, and M is successively decreased 1.But repeating step (a) and (b) and (c) until M=0.

In step 2, can detect a plurality of data flow.Step 2 and then can comprise four steps (d), (e), (f) and (g).In step (d), y can be multiply by the zeroing vector of optimum transmit antenna, generate the original judgement of optimum transmit antenna thus.In step (e), the respective column of H can be multiply by this original judgement, and deduct the result of gained from y.In step (f), can be to suboptimum transmitting antenna repeating step (d) and (e), all decoded until all antennas.In step (g) (can choose wantonly), the feedback channel estimation that can use data judging to carry out to be judged guidance is upgraded.

Notice that original judgement can be hard decision or soft decision, wherein hard decision only is the constellation point of the receiving symbol of the most close channel correction, and soft decision is the weighted sum (weight is directly proportional with the likelihood of each constellation) of the constellation point of some possibility maximums.

The weighting of Viterbi groove

In one embodiment, after the receiver place detects convolution encoded data stream, can use Viterbi decoder to come to its decoding.For the channel of frequency selective fading, the reliability of signal in the different frequency groove may be different.Therefore, in the Viterbi peak measure is calculated, can give more weight to the data bit of the groove of regarding for oneself, and to giving less weight from the data bit of bad groove.In one embodiment, optimum groove weight can be directly proportional with SNR (signal to noise ratio).

In the 802.11a/g that only launches a data flow, be under the situation of additive white Gaussian noise on each groove at the supposition noise, SNR can square approaching by channel magnitude.But in the system of reality, because channel estimation error, phase noise and quantizing noise, the growth of SNR is slower than the growth of channel magnitude usually.Therefore, in one embodiment, can use channel magnitude to carry out the groove weighting.

In mimo system, under the situation of certain Carrier To Noise Power Density of supposition, can calculate the detection SNR of each data streams.Similarly, can use two kinds of diverse ways to determine the weighting of Viterbi groove.In first embodiment, Viterbi groove weight is directly proportional with detection SNR.In a second embodiment, Viterbi groove weight is directly proportional with the square root that detects SNR.

For MMSE-DFE, the influence from the detection SNR of MMSE formula calculating gained does not comprise error propagation causes the excellent detection of the mistake SNR to the data flow that detects after a while thus.This excellent excessively detection SNR can reduce the performance of decoder, and this is that people are undesirable.

For improving the performance of decoder, the influence of error propagation can be included in and carry out SNR calculating in the noise item.Below be the example of calculating the effective noise item of the second and the 3rd data flow:

${\widetilde{\mathrm{\&sigma;}}}_2^2={\mathrm{\&sigma;}}_2^2+{\left|{\mathrm{<figure-callout\; id="2"\; label="w"\; filenames="A20048003561400432.png,A20048003561400531.png"\; state="\{\{state\}\}">w</figure-callout>}}_2^{*}{\mathrm{<figure-callout\; id="1"\; label="h"\; filenames="A20048003561400431.png,A20048003561400531.png"\; state="\{\{state\}\}">h</figure-callout>}}_1\right|}^2\&CenterDot;{\mathrm{\&sigma;}}_1^2$

${\widetilde{\mathrm{\&sigma;}}}_3^2={\mathrm{\&sigma;}}_3^2+{\left|{\mathrm{<figure-callout\; id="3"\; label="w"\; filenames="A20048003561400441.png,A20048003561400531.png"\; state="\{\{state\}\}">w</figure-callout>}}_3^{*}{\mathrm{<figure-callout\; id="2"\; label="h"\; filenames="A20048003561400432.png,A20048003561400531.png"\; state="\{\{state\}\}">h</figure-callout>}}_2\right|}^2\&CenterDot;{\mathrm{\&sigma;}}_2^2+{\left|{\mathrm{<figure-callout\; id="3"\; label="w"\; filenames="A20048003561400441.png,A20048003561400531.png"\; state="\{\{state\}\}">w</figure-callout>}}_3^{*}{\mathrm{<figure-callout\; id="1"\; label="h"\; filenames="A20048003561400431.png,A20048003561400531.png"\; state="\{\{state\}\}">h</figure-callout>}}_1\right|}^2\&CenterDot;{\mathrm{\&sigma;}}_1^2$

Wherein, σ _m ²Be original noise item, w _mBe the zeroing vector, h _mBe channel, and

It is the effective noise item of m data flow.

Compensation to different intrinsic noise level

More than the derivation of MMSE detector is based on noise power identical this supposition on each component of y.Because have different intrinsic noise level and/or gain to be provided with in the receiver chain, so this supposition generally is not true in the system of reality.Therefore, can followingly will revise this formula with stating.

y＝Hx+n，

After AGC, received signal becomes

σ wherein _n ²Be the intrinsic noise level, and g _nIt is respectively the amplitude gain on the n root reception antenna.

Be the channel estimation, because channel just estimation after AGC.

In order to use the MMSE solution, noise variance should be scaled to identical value.For this reason, make K=min _n(g _nσ _n), and the definition scaled matrix

Channel through convergent-divergent is $H_{\mathrm{eq}}=\mathrm{\&Pi;}\&CenterDot;\tilde{H},$ And the noise variance of gained is ${\mathrm{\&sigma;}}_{\mathrm{<figure-callout\; id="2"\; label="eq"\; filenames="A20048003561400432.png,A20048003561400531.png"\; state="\{\{state\}\}">eq</figure-callout>}}^2={\mathrm{<figure-callout\; id="2"\; label="K"\; filenames="A20048003561400432.png,A20048003561400531.png"\; state="\{\{state\}\}">K</figure-callout>}}^2,$ It is constant on all reception antennas.At this moment, can use H _EqAnd σ _Eq ²Calculate zeroing vector W _Eq ^*

Reply $y_{\mathrm{eq}}=\mathrm{\&Pi;}\&CenterDot;\tilde{y}$ Apply W _Eq ^*As being each code element convergent-divergent

Substitute preferred calculating ${\tilde{W}}^{*}=W_{\mathrm{eq}}^{*}\&CenterDot;\mathrm{\&Pi;}$ Once, and directly right

Apply

For MMSE-DFE, use With

Carry out continuous cancellation.Do not need to carry out any convergent-divergent.

Figure 11 illustrates the part of the receiver 1100 that a kind of channel of revising many receiver chains proofreaies and correct.In receiver 1100, variable gain amplifier 1101 receives wireless signal (comprising the channel information that is associated) from antenna, and their output through amplifying is offered channel inverse block 1102 handles.Automatic gain control (AGC) piece 1103 can be variable gain amplifier 1101 and generates the AGC controlling value.Channel inverse block 1102 can receive these AGC controlling values and intrinsic noise level (also being generated by AGC piece 1103) to calculate suitable channel correction.This channel correction can be offered AGC 1103 to adjust the AGC controlling value.

Compensation to phase error

Because in the channel between reflector and the receiver phase noise, residual frequency offset are arranged, the phase error of inducting and/or Doppler change, so the phase place of efficient channel matrix H can slowly change on whole group.For to these effect modelings, efficient channel can be written as Λ _rH Λ _t, wherein ${\mathrm{\&Lambda;}}_r=\mathrm{diag}\left(\left[\begin{array}{cccc}{e}^{j{\mathrm{\&theta;}}_r\left(1\right)}& e^{j{\mathrm{\&theta;}}_r\left(2\right)}& \&CenterDot;\&CenterDot;\&CenterDot;& e^{j{\mathrm{\&theta;}}_r\left(N\right)}\end{array}\right]\right),$ And ${\mathrm{\&Lambda;}}_t=\mathrm{diag}\left(\left[\begin{array}{cccc}{e}^{j{\mathrm{\&theta;}}_t\left(1\right)}& e^{j{\mathrm{\&theta;}}_t\left(2\right)}& \&CenterDot;\&CenterDot;\&CenterDot;& e^{j{\mathrm{\&theta;}}_t\left(N\right)}\end{array}\right]\right)$ Catch the phase change at N root reception antenna and M transmit antennas place respectively.Corresponding balanced matrix is Λ _t ^*W ^*Λ _r ^*But when the phase estimation time spent, this matrix can be modified at an easy rate.

As mentioned above, can use the different pilot schemes that allows pilot tone that unite, every emission chain or that every send-receive is right to follow the tracks of.Follow the tracks of for joint pilot, only transmit and receive chain estimation common phase skew, i.e. a Λ for all _tAnd Λ _rContracting goes out is scalar e ^{J θ}Modification to balanced matrix only is to multiply by scalar e ^{-j θ}

Pilot tone for every emission chain is followed the tracks of, and can estimate phase estimation, i.e. a Λ of each data streams _tAnd Λ _rContracting goes out is a Λ _tTherefore, balanced matrix can be revised as Λ _t ^*W ^*If necessary, can launch on the chain at each phase estimation is averaged obtaining a common phase, and it is used as scalar.Mean value can obtain from the mean value of angle, $\mathrm{\&theta;}=\frac{1}{M}\underset{M}{\mathrm{\&Sigma;}}{\mathrm{\&theta;}}_t\left(m\right),$ Maybe can obtain from the angle of mean value (equivalently and), $\mathrm{\&theta;}=\mathrm{angle}\left(\underset{m}{\mathrm{\&Sigma;}}{e}^{j{\mathrm{\&theta;}}_t\left(m\right)}\right).$

Follow the tracks of for the pilot tone that every send-receive is right, at first derive pilot tone (seeing formula 4) through Orthogonal Composite and phasing.In first embodiment, can be from each first phase deviation θ of these pilot tone estimation channel matrix H _{N, m}(1≤m≤M, 1≤n≤N), and phase deviation is converted to θ _t(m) (1≤m≤M) and θ _t(n) (1≤n≤N).

Note following mapping relations:

Wherein, 1 _NBe all to be that 1 N takes advantage of 1 vector, I _NBe that size is the unit matrix of N, θ _r=[θ _r(1) θ _r(2) ... θ _r(N)] ^TBe the phase vectors at N receiver place, and θ _m=[θ _{1, m}θ _{2, m}θ _{N, m}] ^TIt is the phase vectors of the m row of matrix H.Pseudo-counter-rotating is the least square (LS) of the phase place at reflector and receiver place, and it only depends on the number that transmits and receives antenna, therefore can be calculated by off-line ground.

Can solve two problems of implementation at this.At first, should not allow Θ ₂In code element of code element of angle ground 2 π that reel because at Θ ₂In the variation of 2 π do not cause Θ ₁In the variation of 2 π.For with Θ ₂Launch, be by adding or deduct 2 π with the Θ between current code element and the last code element ₂In variation adjust to (π, π) within, and it is added to previous Θ ₂On.

The second, if Θ ₂In some angles are insecure (for example, the weak component in the matrix channel), then separating also to be unsettled.Separate is according to Θ when the structure cost function ₂In the reliability of component to these component weightings, and find the solution the LS problem of weighting, that is, with ‖ Г (A Θ ₁-Θ ₂) ‖ ²=‖ Г A Θ ₁-Г Θ ₂‖ ²Minimize, rather than with ‖ A Θ ₁-Θ ₂‖ ²Minimize, wherein Г is the diagonal matrix of band weighted factor.Separate thus and become:

Θ ₁＝pinv(ГA)·ГΘ ₂

The higher component of reply reliability carries out heavier weighting, and the lower component of reliability is carried out lighter weighting.An amplitude that tolerance is channel component of reliability.Weight can be by maximum normalization, and if necessary, for the sake of simplicity, weight can be quantified as discrete grade.

If necessary, can be on each reception antenna to all send-receive antennas right evaluation phase skew average, obtaining phase estimation of every transmit antennas, ${\mathrm{\&theta;}}_t\left(m\right)=\frac{1}{N}\underset{n}{\mathrm{\&Sigma;}}{\mathrm{\&theta;}}_{n,m},$ Or transmit and receive on the chain at all and to average, obtaining a public phase estimation, $\mathrm{\&theta;}=\frac{1}{\mathrm{MN}}\underset{n,m}{\mathrm{\&Sigma;}}{\mathrm{\&theta;}}_{n,m}.$

In a second embodiment, θ _tAnd θ _rCan be from pilot tone v through Orthogonal Composite and channel correction _{N, m, k}The combination of (seeing formula 4) is derived.On each pilot tone groove and the reception antenna and angle be the skew of every transmit antennas, ${\mathrm{\&theta;}}_t\left(m\right)=\mathrm{angle}\left(\underset{n,k}{\mathrm{\&Sigma;}}{v}_{n,m,k}\right).$ On each transmitting antenna and angle be the skew of every reception antenna, ${\mathrm{\&theta;}}_r\left(n\right)=\mathrm{angle}\left(\underset{m,k}{\mathrm{\&Sigma;}}{v}_{n,m,k}\right).$ Calculate all transmit and receive on the antenna and angle $\mathrm{\&theta;}=\mathrm{angle}\left(\underset{n,m,k}{\mathrm{\&Sigma;}}{v}_{n,m,k}\right),$ And from emission skew and receive that skew all deducts this angle half to eliminate deviation, θ _t(m)=θ _t(m)-θ/2, and θ _r(m)=θ _r(m)-θ/2.

If necessary, only calculate and use the skew of every emission chain, ${\mathrm{\&theta;}}_t\left(m\right)=\mathrm{angle}\left(\underset{n,k}{\mathrm{\&Sigma;}}{v}_{n,m,k}\right).$ Perhaps, only calculate and use all common phase that transmit and receive on the chain and be offset, $\mathrm{\&theta;}=\mathrm{angle}\left(\underset{n,m,k}{\mathrm{\&Sigma;}}{v}_{n,m,k}\right).$

Proofread and correct for continuous residual frequency offset, use all to transmit and receive common phase skew θ on the chain, be offset, and suppressed the fluctuation that produces owing to phase noise because it captures the common phase that produces owing to residual frequency offset.

Closed loop transmit is optimized

If the MIMO reflector just can be optimized launch scenario known to mimo channel is had, comprise the number of the data flow that will launch, each is flowed employed data transfer rate, each is flowed employed subcarrier, the selection of transmitting antenna, the transmitting power of every antenna, or the like.These optimization and improvements the robustness and the throughput of mimo system.

Get back to Fig. 3, in first embodiment, the quality of receiver 304 accessible channels, and give reflector 301 with this feedback information.This information or can be the form (for example, channel estimation or detect pilot tone EVM) of channel information, or can be the form of recommending launch scenario.Notice that can calculate detection pilot tone EVM from pilot tone and known clean pilot tone that channel is proofreaied and correct, it can be that signal quality is well measured thus.Can use two different groupings to beam back channel information: CTS grouping in the standard RTS/CTS exchange and ACK grouping.

In a second embodiment, reflector 301 can use from the grouping of receiver 304 receptions and estimate channel.Supposed the reciprocity of this scheme, wherein for up link and down link, identical antenna has all been used on both sides.Therefore, reflector 301 can be determined the optimum transmit scheme based on the channel of estimation gained.

Note, in the channel of high spatial dimension, can support more data flow, and in the channel of end dimension, can support less data flow.The dimension that spendable optimal data stream number is based on the mimo channel estimation is determined.For the system that does not have the emission diversity, from all available transmission antennas, select the transmitting antenna with optimum channel of same number.

For the system that transmit diversity is arranged, can carry out suitable phase shift to each data flow, and launch these data flow to constitute the wave beam (being called transmit beam-forming (TxBF)) that merges from many antennas simultaneously.Can use the U.S. Patent application of submitting on October 8th, 2003 the 10/682nd that is entitled as " Apparatus and Method of Multiple Antenna TransmitterBeamforming of High Data Rate...Signals (High Data Rate ... the apparatus and method of many antenna emitters beam shaping of signal) ", No. 381, and the U.S. Patent application the 10/682nd that is entitled as " Apparatus and Method of Multiple Antenna Receiver Combining of Higj DataRate Wideband Signals (apparatus and method of the multiple antenna receiver combination of High Data Rate broadband signal) " of submission on October 8th, 2003, technology described in No. 787 is carried out the BF process of each data flow, and the content of these two patent applications is contained in this by reference.

Generally speaking, different data flow be carried out beam shaping towards reception antenna and receive SNR to improve.This technology is particularly useful for the access point in the system that very heavy downlink traffic amount is arranged.Can be by launching the following distinct data streams of 1 above M, and use remaining antenna to come redundant ground to launching code, and will launch towards the direction wave beam shaping of expection transmit beam-forming and High Data Rate MIMO are made up.

In Discrete Multitone (DMT) technology, the power of each subcarrier and modulation type can be determined based on the channel estimation.Compare with the subcarrier that bad signal quality is arranged, have the subcarrier of good signal quality to use more power and higher modulation levels.

Receiver is selected diversity

Because the constraint of cost and power consumption, the quantity of the receiver chain that the MIMO receiver can have is normally limited.On the contrary, the cost of RF antenna is much lower.Therefore, have reception antenna, and dynamically to select the optimum reception antenna be desirable more than receiver chain.This ability of Dynamic Selection reception antenna has been brought diversity gain, and has improved the robustness of system.Be to reduce complexity and handoff loss, in one embodiment, the RF antenna is divided into group with the quantity same number of receiver chain.Each antenna sets is connected to its corresponding receiver chain by switch.

In first embodiment, can use quick antenna diversity.In quick antenna diversity, every receiver chain can be sampled to the signal strength signal intensity on the RF antenna that it connected rapidly, and selects to have the antenna of peak signal.

In a second embodiment, selection criterion is based on and detects SNR.Can carry out the channel estimation to all RF antennas.For each possible combination of reception antenna, can calculate all data streams and detect SNR.Then can be on all possible combination of antennas more minimum SNR.Can select to provide that group antenna of maximum minimum SNR.

The data transfer rate self adaptation

The data transfer rate self adaptation of mimo system is more difficult than the data transfer rate self adaptation of traditional 802.11a/g system.Particularly, need implicit feedback (utilizing reciprocity) or explicit feedback (using explicit message) to visit quality of channel from every transmit antennas.

This feedback can have different detail grades.In the most rough grade, it all is correct can using single affirmation to indicate all data in all streams.This in addition can make all streams are had the scheme of the same data rate difficulty that becomes because be difficult to determine that the number of the emission stream that can support and which are optimum emission stream.

Next feedback levels is indivedual affirmations of each data flow.This affirmation technology can allow the independent rate self adaptation adjustment on each stream, although determine that the optimum transmitting antenna and the number of the data flow of being supported may be difficult.

In another feedback levels, the receiver of expection can be carried out the channel estimation to importing grouping into during channel is estimated preamble and/or grouped data part.These estimations can be determined indivedual SNR that each frequency/transmitting antenna is right, maybe this information fusion can be become reflector be used for adjusting its speed in batch every day line value.Middle solution is only to determine and the SNR of a class frequency groove of report reduction (such as the frequency slots of pilot tone frequency etc.).

In one embodiment, the receiver of expection can receive the definite optimum data rate that should use based on it, and sends these data transfer rates to reflector in ACK.Reflector is decoded to ACK, the retrieve data rate, and these data transfer rates are applied to mail to this user's next one grouping.This information can comprise the data rate information of each stream, or individual data rate and can support the tabulation of the transmitting antenna of this data transfer rate, or individual data rate and can support the number of the transmitting antenna of this data transfer rate.

In another embodiment, reflector is from the special MIMO ACK that receiver the sent being seen channel of receiver of estimating expection of expection.For guaranteeing reciprocity, all antennas that the receiver of expection will use it to be used for receiving send this ACK.This ACK only comprises traditional preamble and MIMO preamble, and does not comprise any data symbols.Reflector upgrades at needs can ask this special ACK when the data transfer rate self adaptation is adjusted parameter, or can use this ACK always.(notice that the statistics that can use lost packets is as the supplementary means of slowly adjusting data transfer rate.)

The data transfer rate adjustment information if particularly adopt the form of one or one group explicit data transfer rate, must be passed in time or wears out with the emission of failure, to allow data transfer rate because the channel condition that changes is producing decline to some extent under the situation of repeatedly failure.

Polymerization, many verifications and and part A CK

The MIMO header has increased packet overhead widely.On the other hand, be the information of emission same word joint number, the MIMO grouping needs the data symbols of much less usually.Therefore, the gross efficiency of MIMO grouping is more much lower than the efficient of the legacy packets of identical size.

In one embodiment, for keeping the benefit of the High Data Rate that MIMO data transmission system provided, will only surpass the grouping of certain minimum threshold with MIMO form emission size.Can use packet aggregation to increase the size of grouping, wherein several less packets are polymerized to big " a surpassing " grouping.

In 802.11a/g, the afterbody of grouping add CRC check and, and it is passed to physical layer.CRC in the output of receiver MAC inspection Viterbi decoder makes mistakes, to determine whether this grouping is correctly received.In the mimo system of High Data Rate, the data word joint number in the grouping is much bigger usually, thereby can raise the efficiency as previously mentioned.The error probability of these long groupings is higher usually, and the cost of therefore launching these groupings again is also higher.

For overcoming this problem, can use a kind of in two kinds of methods in each MIMO grouping, comprise a plurality of verifications and.Use first method, for each prepolymerized grouping specify each verification and.Use second method, the superpacket of back polymerization can be divided into isometric part, and be each part calculation check with, and be inserted into after this part.

At receiver place (and after decoder), can be that each grouping/part is checked verification and to determine whether correctly to receive this grouping/partly (for example, use the acknowledgement bit vector).If have at least a grouping/part correctly to be received, then receiver can send part ACK to reflector, to represent which grouping/part is correctly received.Reflector only needs the grouping/part of retry failure then.For reducing the complexity of MAC, MAC can be chosen under any sub situation of dividing into groups to make mistakes and launch all son groupings again.Notice that MAC still can be speed and adjusts purpose and use each bit in the acknowledgement bit vector.

Although be described in detail with reference to the attached drawings illustrative examples herein, should be appreciated that the present invention is not limited to those accurate embodiment.Be not intended to make that they become limit yet or limit the invention to disclosed precise forms.Equally, many modifications and changes schemes will be obvious to those skilled in the art.

For example, Figure 12 is the chart 1200 that the data transfer rate of several emitter/receiver antenna configurations on relative distance is shown.In chart 1200, line 1201 expression 3 antenna emitters and 3 antenna receivers configurations (3 * 3), line 1202 expressions 2 * 3 configurations, and line 1203 expressions 2 * 2 configurations.Notice that selected antenna configurations can be trading off between peak-data rates and the robustness.Thus, in one embodiment, can select based on economic consideration by 2 * 3 represented configurations of line 1202.

Note, can add " turbo " pattern to MIMO-SM and MIMO-AG.This turbo pattern is meant wideer channel width, it is at the U.S. Patent application the 10/367th of being entitled as of submitting on February 14th, 2003 " Receiving and TransmittingSignals Having Multiple Modulation Types Using Sequencing Interpolator (use the sequencing interpolater to receive and launch the signal with multiple modulation type) ", No. 527, and the U.S. Patent application 10/XXX that is entitled as " Multi-Channel Binding In Data Transmission (multi-channel binding in the data transmission) " of submission on November 6th, 2003, describe in XXX number, the content of these two applications all is contained in this by reference.Generally speaking, the turbo pattern can realize by (1) dual timing or (2) channel joint (that is, the 20MHz channel of two routines and the gap that also has between them being used together).The dual timing generation subcarricr structure identical with general mode, but that each subcarrier is a twice is wide.Channel engages the width of keeping each subcarrier, but increases the number of subcarrier.The concrete example that channel engages is, use from-58 to-2 and+114 single-tones of 2 to+58, wherein do not use three single-tones (1,0,1) near DC.

Notice that all embodiment of above-mentioned mimo system are applicable to the turbo pattern.

Figure 13 is the chart 1300 that various turbo and the data transfer rate of non-turbo antenna configurations on relative distance are shown.As shown in chart 1300, turbo MIMO-SM provides the data transfer rate up to 216Mbps.But the in fact comparable MIMO-SM height of turbo MIMO-AG is less than 60Mbps.

Thus, be intended to make scope of the present invention to define by appended claims and equivalence techniques scheme thereof.

Claims (88)

1. one kind is used for the time-division training mode that multiple-input and multiple-output divides into groups, and described pattern comprises:

Short code unit by the emission of first antenna;

After the emission of described short code unit by first long symbols of described first antenna emission;

The classical signal code element of after the emission of described first long symbols, launching by described first antenna;

Second long symbols of after the emission of described classical signal code element, launching by second antenna; And

The signal element that is associated with the multiple input multiple output data of after the emission of described second long symbols, launching in fact simultaneously by described first antenna and described second antenna.

2. one kind is used for the pattern that multiple-input and multiple-output divides into groups, and described pattern comprises:

By the short code unit of first antenna and second antenna emission, described short code unit is split between one group short predetermined groove, and wherein said first antenna is associated with first group short groove, and described second antenna is associated with second group short groove;

The long symbols of after the emission of the described second short code unit, launching in fact simultaneously by described first antenna and described second antenna, described long symbols is associated with first group leader's groove and second group leader's groove, wherein said first antenna used described first group leader's groove to launch before using described second group leader's groove, and wherein said second antenna used described second group leader's groove to launch before using described first group leader's groove; And

The signal element that is associated with the multiple input multiple output data of launching in fact simultaneously by described first antenna and described second antenna.

3. pattern as claimed in claim 2 is characterized in that,

Described first group short groove comprises-24 ,-16 ,-8,4,12,20, and

Described second group short groove comprises-20 ,-12 ,-4,8,16,24.

4. pattern as claimed in claim 2 is characterized in that,

Described first group short groove comprises-24 ,-16 ,-8,8,16,24, and

Described second group short groove comprises-20 ,-12 ,-4,4,12,20.

5. pattern as claimed in claim 2 is characterized in that,

Described first group leader's groove comprises-26 ,-24 ... ,-2,1,3 ... 25, and

Described second group leader's groove comprises-25 ,-23 ...-1,2,4 ... 26.

6. pattern as claimed in claim 2 is characterized in that,

Described first group leader's groove comprises-26 ,-24 ... ,-2,2,4 ... 26, and

Described second group leader's groove comprises-25 ,-23 ...-1,1,3 ... 25.

7. pattern as claimed in claim 2 is characterized in that, at least two kinds of split modes that also are included as described short groove calculate the value of peak-to-average force ratio (PAR), and use the split mode with minimum PAR value.

8. pattern as claimed in claim 2 is characterized in that, at least two kinds of split modes that also are included as described elongated slot calculate the value of peak-to-average force ratio (PAR), and use the split mode with optimum PAR value.

9. pattern as claimed in claim 2 is characterized in that, 24 grooves of described short code unit's use.

10. pattern as claimed in claim 2 is characterized in that, described first group short groove uses different frequency displacements with described second group short groove.

11. pattern as claimed in claim 10 is characterized in that, if described pattern is to use 1 in every N groove, then frequency displacement pattern can comprise 1 to maximum N-1 groove.

12. pattern as claimed in claim 2 is characterized in that, 12 grooves of described short code unit's use.

13. pattern as claimed in claim 2 is characterized in that, also comprises traditional headers before described short code unit and long symbols, described traditional headers comprises:

Traditional short code unit by the emission of described first antenna;

After the emission of described traditional short code unit by traditional long symbols of described first antenna emission; And

The classical signal code element of after the emission of described traditional long symbols, launching by described first antenna.

14. pattern as claimed in claim 13 is characterized in that, described first antenna is to use one group of antenna to realize.

15. pattern as claimed in claim 14 is characterized in that, it is heavy to apply restore one's right on the groove of described first group of antenna, alleviates the beam shaping effect thus.

16. pattern as claimed in claim 15 is characterized in that, described restore one's right heavily comprises at least one in the phase shift or the phase width of cloth, and wherein, alleviates the beam shaping effect and produce the emission of omnidirectional in fact.

17. pattern as claimed in claim 13 is characterized in that, also is included in the code symbols of emission after the described traditional headers, being used to indicate what launching is the multiple-input and multiple-output grouping.

18. pattern as claimed in claim 17 is characterized in that, described code symbols is indicated the number of data streams at least.

19. pattern as claimed in claim 17 is characterized in that, described code symbols comprises the described signal element that is associated with multiple-input and multiple-output (MIMO) data.

20. pattern as claimed in claim 19 is characterized in that, described code symbols comprises the pilot tone of upset, and the pilot tone of wherein said upset is different with the single-tone of the conventional code element that should occur in this position.

21. a method that sends the multiple-input and multiple-output grouping in the environment of legacy equipment, described method comprises:

The one group of bit that keeps in the classical signal code element is set to predetermined value, and what indication was being launched thus is MIMO signal.

22. a method that sends multiple-input and multiple-output (MIMO) grouping in the environment of legacy equipment, described method comprises:

Use one group of bit in the classical signal code element to indicate the information that is associated with described MIMO grouping.

23. method as claimed in claim 22 is characterized in that, described one group of bit comprises a plurality of significant bits of the length field of described classical signal code element.

24. method as claimed in claim 22 is characterized in that, described information comprises the number of the stream that is associated with described MIMO grouping.

25. a method that sends multiple-input and multiple-output (MIMO) grouping in the environment of legacy equipment, described method comprises:

One group of bit in the classical signal code element is carried out ' mould ' computing, to indicate the information that is associated with described MIMO grouping.

26. method as claimed in claim 25 is characterized in that, described information comprises the number of stream.

27. the method for the phase change of a plurality of reception data symbols of following the tracks of and proofreading and correct MIMO signal, described method comprises:

A plurality of pilot tone grooves are inserted in each data symbols.

28. method as claimed in claim 27 is characterized in that, is included in also that the use pattern increases phase shift on described a plurality of pilot tone groove.

29. method as claimed in claim 28 is characterized in that, also is included in the pattern of the described phase shift of rotation on described a plurality of pilot tone groove.

30. method as claimed in claim 29 is characterized in that, rotation is included in the described pattern of described a plurality of pilot tone groove cocycles ground rotation.

31. method as claimed in claim 28 is characterized in that, with four pilot tone grooves with [1 1 1-1] * p _lForm be inserted in each data symbols, wherein [1 1 1-1] is the pattern on described four pilot tone grooves, and p _lBe the pilot tone polarity of code element l.

32. the method for the phase change of a plurality of reception data symbols of following the tracks of and proofreading and correct multiple-input and multiple-output (MIMO) signal, described method comprises:

On the long any interval of M data code element, provide the orthogonal modes on each data flow.

33. method as claimed in claim 32 is characterized in that, provides orthogonal modes to meet following formula:

$\frac{1}{M}\underset{l=k}{\overset{k+M-1}{\mathrm{\&Sigma;}}}{q}_m\left(l\right)q_n^{*}\left(l\right)={\mathrm{\&delta;}}_{\mathrm{mn}}$

Wherein M represents the number of data streams, and m represents stream, and k represents the beginning index of M orthogonal data code element, and l represents the index of MIMO code element, and δ _MnEqual 1 for m=n, or equal 0 for m ≠ n.

34. method as claimed in claim 33 is characterized in that, for M data streams, the modulating mode that then flows m is $q_m\left(l\right)=e^{j\frac{2\mathrm{\&pi;}}{M}(m-1)l},$ 1≤m≤M and l 〉=0 wherein.

35. one kind is carried out the method that joint pilot is followed the tracks of on each stream, described method comprises:

Estimate received signal in each pilot tone groove based on channel estimation and known pilot pattern,

Wherein the last received signal in pilot tone groove K of receiver n is expressed from the next:

$y_{n,k}=\underset{m}{\mathrm{\&Sigma;}}{H}_{n,m,k}{e}^{\mathrm{j\&theta;}}\&CenterDot;s_{m,k}+n_{n,k}$

Wherein, s _{M, k}Be the pilot frequency code element of stream m, θ is the common phase skew, H _{N, m, k}Be channel response, and n _{N, k}Be noise,

Wherein, the common phase skew is expressed from the next:

$\mathrm{\&theta;}=\mathrm{angle}(\underset{n,k}{\mathrm{\&Sigma;}}{y}_{n,k}\&CenterDot;{\left(\underset{m}{\mathrm{\&Sigma;}}{\hat{H}}_{n,m,k}{s}_{m,k}\right)}^{*})$

Wherein

It is the channel estimation.

36. the method that every emission chain is carried out the pilot tone tracking, described method comprises:

To pilot tone groove using MIMO detection algorithm to detect pilot tone

Wherein ${\hat{s}}_{m,k}\&ap;s_{m,k}\&CenterDot;e^{j{\mathrm{\&theta;}}_t\left(m\right)},$ θ wherein _t(m) be the phase deviation of stream m; And

The phase difference of decoding between pilot tone and the desirable pilot tone on each pilot tone groove of each data flow is averaged, to generate phase estimation ${\widehat{\mathrm{\&theta;}}}_t\left(m\right)=\mathrm{angle}(\underset{k}{\mathrm{\&Sigma;}}{\hat{s}}_{m,k}\&CenterDot;s_{m,k}^{*}).$

37. the method that every transmit is carried out the pilot tone tracking, described method comprises:

Coming the modulated pilots polarity sequence with orthogonal modes, is every independent evaluation phase of transmit thus,

Wherein, if the number of data streams is M, then flow m modulating mode can by $q_m\left(l\right)=e^{j\frac{2\mathrm{\&pi;}}{M}(m-1)l}$ Expression, 1≤m≤M wherein, l 〉=0th wherein, the index of described MIMO code element.

38. method as claimed in claim 37 is characterized in that, also comprises by averaging on a plurality of pilot tone grooves estimating the phase deviation of the stream m on the reception antenna n, described skew is expressed from the next

${\mathrm{\&theta;}}_{n,m}=\mathrm{angle}\left(\underset{k}{\mathrm{\&Sigma;}}{v}_{n,m,k}\right)=\mathrm{angle}(\underset{k}{\mathrm{\&Sigma;}}\underset{l}{\mathrm{\&Sigma;}}{y}_{n,k}\left(l\right)\&CenterDot;r_{m,k}^{*}\left(l\right)\&CenterDot;H_{n,m,k}^{*}).$

39. one kind splits the source data bit to constitute the method for MIMO signal, described method comprises:

Add bit with initialization and termination encoder to the source data bit, create modified source data bit thus;

Described modified source data bit is offered described encoder, create the source data bit of having encoded thus;

Described source data bit of having encoded is split as M data flow.

40. one kind splits the source data bit to constitute the method for MIMO signal, described method comprises:

Described source data bit is split as M data flow; And

Add bit with initialization and M encoder of termination to described M data flow, create M modified data flow thus.

41. method as claimed in claim 40 is characterized in that, also comprises the sum of selecting bit, so that when splitting on the code element of each stream in a described M data flow, the code element number in each data flow is equal in fact.

42. one kind splits the source data bit to constitute the method for MIMO signal, described method comprises:

Add bit with initialization and termination encoder to the source data bit, create modified source data bit thus;

Described modified source data bit is offered described encoder, create the source data bit of having encoded thus;

Described source data bit of having encoded is offered perforator, create source data bit thus through perforation; And

Described source data bit through perforation is split as N data flow.

43. method of using the classical signal code element to indicate the length of multiple-input and multiple-output (MIMO) grouping, described classical signal code element comprises data rate field and length field, the length of described MIMO grouping is longer than the length of using described length field to represent, and described method comprises:

Use described data rate field and described length field to represent the length of described MIMO grouping.

44. method as claimed in claim 43 is characterized in that, uses described data rate field and described length field to comprise, pseudo-data rate value is provided in described data rate field, and the pseudo-length value is provided in described length field.

45. method as claimed in claim 44 is characterized in that, described pseudo-data rate value is minimum traditional data rate, and described pseudo-length value is the actual conventional lengths of expression emission duration.

46. method as claimed in claim 43 is characterized in that, the MIMO signal element of described MIMO grouping comprises relative block length.

47. a pattern that is used for multiple-input and multiple-output (MIMO) grouping, described pattern comprises:

Traditional headers comprises more than first short code unit, is used for the automatic gain control of the reception of definite described traditional headers; And

The MIMO header comprises more than second short code unit, is used to help the automatic gain control to the reception of described MIMO header.

48. a pattern that is used for multiple-input and multiple-output (MIMO) grouping, described pattern comprises:

By the first short code unit of many antenna emissions, the described first short code unit is split between one group short predetermined groove, and each root in the wherein said many antennas is associated with a subclass of described short groove,

Wherein, the described first short code unit is used to carry out the automatic gain control of MIMO grouping, and described MIMO grouping comprises the described first short code unit.

49. pattern as claimed in claim 48 is characterized in that, described MIMO grouping also comprises first long symbols, and described pattern also comprises:

By described many antennas described first long symbols of synchronized transmissions in fact, described first long symbols is associated with some group leader's grooves, and wherein every antenna uses some group leader's grooves of different order to launch,

Wherein, described first long symbols is used to carry out the mimo channel estimation.

50. pattern as claimed in claim 49 is characterized in that,

Described many antennas comprise first antenna and second antenna,

By the emission of described first antenna and described second antenna, described first antenna is associated with first group short groove after the emission of described classical signal code element in the described first short code unit, and described second antenna is associated with second group short groove,

Described first long symbols is launched in fact simultaneously by described first antenna and described second antenna, described first long symbols is associated with first group leader's groove and second group leader's groove, wherein said first antenna used described first group leader's groove to launch before using described second group leader's groove, and wherein said second antenna used described second group leader's groove to launch before using described first group leader's groove.

51. pattern as claimed in claim 49 is characterized in that, also comprises:

The signal element that is associated with MIMO of after described first short code unit and described first long symbols, launching in fact simultaneously by described first antenna and described second antenna.

52. pattern as claimed in claim 49 is characterized in that, also comprises:

The second short code unit;

Second long symbols;

The classical signal code element,

The wherein said second short code unit is used to carry out the automatic gain control of traditional headers, wherein said traditional headers comprises the described second short code unit, described second long symbols and described classical signal code element, and wherein said traditional headers was launched before described MIMO header.

53. a pattern that is used for multiple-input and multiple-output (MIMO) grouping, described pattern comprises:

Traditional headers comprises more than first long symbols, is used to carry out the channel estimation of legacy equipment; And

The MIMO header comprises more than second long symbols, is used to carry out the channel estimation of MIMO equipment.

54. a pattern that is used for multiple-input and multiple-output (MIMO) grouping, described pattern comprises:

By first long symbols of many antenna emissions, described first long symbols is launched in fact simultaneously by described many antennas, and described first long symbols is associated with some group leader's grooves, and wherein every antenna uses some group leader's grooves of different order to launch,

Wherein, described first long symbols is used to carry out the mimo channel estimation of MIMO grouping, and described MIMO grouping comprises described first long symbols.

55. pattern as claimed in claim 54 is characterized in that, the long sequence of the stream of 2 20MHz is

L _-26:26={ 1 1-1 11 1-1-1-1-1 111 1-1 1-1 1-1-1 11 1-1 11 0-1 1 1-1-1 1-1-11-1-1 1-1-1 111 1-1 111111 1}, wherein the first single-tone group is [26:2:-2 2:2:26] 73dB, and the second single-tone group is [25:2:-1 1:2:25].

56. pattern as claimed in claim 54 is characterized in that, the long sequence of the stream of 3 20MHz is

L _-26:26={ 1-1 1111 1-1-1-1 1-1-1-1-1-1 111111 1-1-1 10 1-1-1-1 1-1 1-11-1 1 1-1 1-1-1 1 1-1 1 1-1 1-1-1 1}, wherein the first single-tone group is [26:3:-2 2:3:26], the second single-tone group is [25:3:-1 3:3:24], and the 3rd single-tone group is [24:3:-3 1:3:25].

57. pattern as claimed in claim 54 is characterized in that, the long sequence of the stream of 4 20MHz is

L _-26:26={ 1111 1-1-1-1 1-1 11 1-1 1 1-1 1-1-1-1 11 1-1 1011 20:-1 1-1-1 1-1-1-1-1 1-1-1-1 111 1-1 1 1-1 11 1}, wherein the first single-tone group is [26:4:-2 3:4:23], the second single-tone group is [25:4:-1 4:4:24], the 3rd single-tone group is [24:4:-4 1:4:25], and the 4th single-tone group is [23:4:-3 2:4:26].

58. pattern as claimed in claim 54 is characterized in that, the exemplary long sequence of the stream of a 40MHz is

L _-58，+58＝{-1?1?1?1?1?-1?1?1?-1?-1?-1?-1?1?1?1?1?1?-1?1?1?-1?1?-1?1?1?-1?-1?1?1?-1?-1?1?1-1?-1?-1?-1?-1?1?-1?1?1?-1?-1?-1?1?-1?-1?1?-1?-1?1?1?-1?1?1?1?0?0?0?-1?-1?-1?-1?-1?-1?-1?-1-1?-1?-1?1?1?1?-1?1?-1?1?1?-1?-1?1?-1?-1?1?-1?1?-1?1?-1?-1?-1?-1?1?1?-1?1?-1?-1?-1?1?-1?1-1?1-?1?1?1?-1?1?-1?-1?1?-1?1?1?1}

59. pattern as claimed in claim 54 is characterized in that, the exemplary long sequence of the stream of two 40MHz is

L _-58，+58＝{-1?1?1?1?1?-1?1?1?-1?-1?-1?-1?1?1?-1?1?1?-1?1?1?-1?1?-1?1?1?-1?-1?1?1?-1?-1?1?1-1?-1?-1?1?-1?1?-1?1?1?1?-1?-1?1?-1?-1?-1?-1?-1?-1?1?-1?1?-1?1?0?0?0?-1?-1?-1?-1?-1?-1?-1-1?-1?-1?-1?1?1?1?-1?1?-1?1?1?-1?-1?1?-1?1?1?-1?1?-1?1?-1?-1?-1?-1?1?1?-1?1?-1?-1?-1?-1?-11?-1?1?1?1?1?-1?1?1?-1?1?-1?1?1?1}

Wherein, the first single-tone group is [58:2:-2 2:2:58], and the second single-tone group is [57:2:-3 3:2:57].

60. pattern as claimed in claim 54 is characterized in that, the exemplary long sequence of the stream of three 40MHz is

L _-58，+58＝{-1?-1?-1?-1?-1?-1?1?1?1?-1?-1?-1?-1?-1?-1?1?1?1?-1?-1?-1?-1?-1?-1?1?1?1?1?1?1?11?1?-1?-1?-1?-1?-1?-1?1?1?1?1?1?1?-1?-1?-1?-1?-1?-1?-1?-1?-1?-1?-1?-1?0?0?0?-1?-1?-1?-1?-1-1?-1?-1?-1?-1?-1?-1?1?1?1?-1?-1?-1?1?1?1?1?1?1?1?1?1?-1?-1?-1?-1?-1?-1?-1?-1?-1?-1?-1?-1?11?1?1?1?1?1?1?1?1?1?1?1?1?1?-1?-1?-1}

Wherein, the first single-tone group is [58:3:-4 2:3:56], and the second single-tone group is [57:3:-3 3:3:57], and the 3rd single-tone group is [56:3:-2 4:3:58].

61. pattern as claimed in claim 54 is characterized in that, the exemplary long sequence of the stream of four 40MHz is

L _-58，+58＝{-1?1?-1?-1?-1?1?1?-1?1?1?1?-1?1?1?1?1?-1?-1?-1?-1?1?-1?-1?-1?1?-1?1?-1?1?-1?-1-1?-1?1?1?-1?-1?-1?1?1?1?1?-1?1?-1?-1?1?-1?1?1?1?1?1?-1?-1?-1?1?0?0?0?-1?1?1?-1?-1?-1?-1-1?1?1?1?-1?1?1?-1?-1?-1?1?-1?1?-1?-1?-1?1?-1?1?-1?-1?1?1?1?1?1?1?1?-1?-1?-1?-1?1?1?-1?1?11?-1?1?1?-1?-1?1?-1?1?-1?-1?1?1}

Wherein, the first single-tone group is [58:4:-2 5:4:57], and the second single-tone group is [57:4:-5 2:4:58], and the 3rd single-tone group is [56:4:-4 3:4:55], and the 4th single-tone group is [55:4:-3 4:4:56].

62. pattern as claimed in claim 54 is characterized in that, described MIMO grouping also comprises the first short code unit, and described pattern also comprises:

By the described first short code unit of described many antennas emission, the described first short code unit is split between one group short predetermined groove, and each root in the wherein said many antennas is associated with a subclass of described short groove,

Wherein, the described first short code unit is used to carry out the automatic gain control of described MIMO grouping, and described MIMO grouping comprises the described first short code unit.

63. pattern as claimed in claim 62 is characterized in that,

Described many antennas comprise first antenna and second antenna,

After the emission of described classical signal code element, the described first short code unit is by described first antenna and the emission of described second antenna, and described first antenna is associated with first group short groove, and described second antenna is associated with second group short groove;

Described first long symbols is launched in fact simultaneously by described first antenna and described second antenna, described first long symbols is associated with first group leader's groove and second group leader's groove, wherein said first antenna used described first group leader's groove to launch before using described second group leader's groove, and wherein said second antenna used second group leader's groove to launch before using described first group leader's groove.

64. as the described pattern of claim 63, it is characterized in that, also comprise:

The signal element that is associated with MIMO of after described first short code unit and described first long symbols, launching in fact simultaneously by described first antenna and described second antenna.

65. the method to a plurality of coded stream decodings of multiple-input and multiple-output (MIMO) emission, described method comprises:

For decoding, the data bit of the groove of regarding for oneself is compared from the heavier weighting of the data bit of bad groove.

66., it is characterized in that described groove weight and signal to noise ratio (snr) are proportional as the described method of claim 65.

67., it is characterized in that described groove weight is directly proportional with the square root of signal to noise ratio (snr) as the described method of claim 65.

68., it is characterized in that weighting influences the Viterbi branch metric calculation as the described method of claim 67.

69., it is characterized in that described groove weight is directly proportional with signal to noise ratio (snr) as the described method of claim 68.

70., it is characterized in that the square root of described groove weight and signal to noise ratio (snr) is proportional as the described method of claim 68.

71. as the described method of claim 65, it is characterized in that, also comprise the influence of determining error propagation based on the formula of the effective noise item of following calculating second and the 3rd stream:

${\widetilde{\mathrm{\&sigma;}}}_2^2={\mathrm{\&sigma;}}_2^2+{\left|w_2^{*}{h}_1\right|}^2\&CenterDot;{\mathrm{\&sigma;}}_1^2$

${\widetilde{\mathrm{\&sigma;}}}_3^2={\mathrm{\&sigma;}}_3^2+{\left|w_3^{*}{h}_2\right|}^2\&CenterDot;{\widetilde{\mathrm{\&sigma;}}}_2^2+{\left|w_3^{*}{h}_1\right|}^2\&CenterDot;{\mathrm{\&sigma;}}_1^2$

Wherein, σ _m ²Be original noise item, w _mBe the zeroing vector, h _mBe channel, and

It is the effective noise item of m data flow.

72. a method of revising the channel correction of many receiver chains, described method comprises:

Receive the channel estimation of described many receiver chains;

Calculate the gain adjustment value of described many receiver chains based on noise level and automatic gain control value; And

Described gain adjustment value is put on described many receiver chains.

73. one kind is the method that multiple-input and multiple-output (MIMO) system uses phase estimation, described method comprises:

Use single associating phase estimation from a plurality of data flow, be applicable to the phasing of all data flow with calculating.

74., it is characterized in that described a plurality of data flow comprise all data flow as the described method of claim 73.

75. one kind for each emission/reception to the method for phase estimation is provided, described method comprises:

Each first phase deviation θ from pilot tone estimation channel matrix H _{N, m}(1≤m≤M, 1≤n≤N), and described phase deviation is converted to θ _t(m) (1≤m≤M) and θ _r(n) (1≤n≤N).

76. as the described method of claim 75, it is characterized in that,

Wherein, 1 _NBe all to be that 1 N takes advantage of 1 (N-by-1) vector, I _NBe that size is the unit matrix of N, θ _r=[θ _r(1) θ _r(2) ... θ _r(N)] ^TBe the phase vectors at N receiver place, and θ _m=[θ _{1, m}θ _{2, m}θ _{N, m}] ^TIt is the phase vectors of the m row of matrix H.

77. a method for transmitting of optimizing multiple-input and multiple-output (MIMO) signal, described method comprises:

Use visits quality of channel by the receiver of expection from the grouping of the transmitter receipt of described MIMO signal; And

Divide into groups to described reflector emission from the receiver of described expection, described grouping comprises the feedback information that is used to optimize emission, and described feedback information can obtain from a plurality of data flow of previous emission in fact simultaneously.

78., it is characterized in that described grouping comprises the CTS grouping as the described method of claim 77.

79., it is characterized in that described grouping comprises the ACK grouping as the described method of claim 77.

80., it is characterized in that described feedback information comprises in following two as the described method of claim 77, (1) channel estimation, and the detection pilot tone EVM of (2) pilot tone of proofreading and correct from channel and known clean channel calculation gained.

81., it is characterized in that described feedback information comprises will be by the data transfer rate of described reflector use as the described method of claim 77.

82., it is characterized in that described feedback information can comprise at least one the designator in minimum data rates, maximum data rate, higher data and the lower data rate that will be used by described reflector as the described method of claim 77.

83. a method for transmitting of optimizing emission multiple-input and multiple-output (MIMO) signal, described method comprises:

Use visits channel quality by the reflector of described MIMO signal from the MIMO grouping that the receiver of expecting receives; And

Come definite emission information based on described MIMO grouping through optimizing.

84. a method of determining the receiver selection of multiple-input and multiple-output (MIMO) signal in diversity aerial system, wherein at least one receiver chain can be connected to many reception antennas, and described method comprises:

For every receiver chain, select to have the reception antenna of peak signal.

85. a method of determining the receiver selection of multiple-input and multiple-output (MIMO) signal in diversity aerial system, wherein at least one receiver chain can be connected to many reception antennas, and described method comprises:

Determine the combination that reception antenna is possible;

Be each combination calculation signal to noise ratio (snr); And

Selection has the combination of minimum SNR.

86. a selection has split the method for sequence, comprising:

For a plurality of sequences that split are calculated peak-to-average force ratio (PAR); And

Selection has the fractionation sequence of optimum PAR.

87., it is characterized in that the described optimum PAR of short code unit is by calculating the minimum PAR that described a plurality of each PAR that has split in the sequence provides as the described method of claim 86.

88., it is characterized in that the described optimum PAR of long symbols is the relatively low PAR that provides by each the PAR that calculates in described a plurality of at random one group that has split in the sequence as the described method of claim 86.

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