CN100337392C - DC/DC converter having voltage clamping circuit - Google Patents
DC/DC converter having voltage clamping circuit Download PDFInfo
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- CN100337392C CN100337392C CNB2003101244325A CN200310124432A CN100337392C CN 100337392 C CN100337392 C CN 100337392C CN B2003101244325 A CNB2003101244325 A CN B2003101244325A CN 200310124432 A CN200310124432 A CN 200310124432A CN 100337392 C CN100337392 C CN 100337392C
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Abstract
The present invention relates to a DC/DC converter having a voltage clamping circuit. In the prior art, a DC/DC converter with a secondary side clamping circuit has severe voltage oscillation problems, and larger forward and reverse recovery current can pass through a primary side clamping circuit, which can cause the problems of heat radiation, clamping circuit loss, etc. A tap inductor or an intercoupling inductor set is arranged on a DC/AC converter with the primary side clamping circuit by the present invention, which enables the voltage oscillation of an output diode to be reduced. The forward current and the reverse recovery current passing through the clamping circuit are also reduced so as to reduce the loss of the clamping circuit.
Description
Technical field
The present invention is relevant for soft switch DC/DC converter, particularly relevant for the DC to DC converter with voltage clamp circuit.
Background technology
The change type power supply unit of a standard utilizes pulse-width modulation (Pulse WidthModulation, PWM) adjust the size of input power, required to supply suitable load, pulse wave width modulation device control its switch (utilizing Power MOSFET to reach usually) is cut into a string voltage pulse with DC input voitage, utilize transformer and fast diode that it is changed into level and smooth direct voltage output subsequently, this output voltage compares with a reference voltage (this voltage is the standard voltage value that power supply unit should be exported) immediately, the voltage difference that is produced is feedback to the controller of pulse wave width modulation, utilizes this error voltage signal to change the size of pulse bandwidth.For example: when output voltage was too high, pulse bandwidth can reduce, and then reduced the power supply supply, made output voltage return back to normal output valve.So, by changing the ON time that pulse bandwidth comes the power controlling switch, with the VD that accurately obtains wanting.
And bad switching is the main cause that causes the converter power loss.When non-vanishing, then their understand absorbed power to voltage with electric current during changeover module is being opened (turn on) or closed the transition of (turn off).When the switching frequency increase, transition takes place more frequent, and makes the average power loss of assembly increase.High switching frequency is that we want, because can reduce the size of filter assembly and transformer, thereby can reduce the size and the weight of transducer.In controlled resonant converter (ResonantConverter), switch switches when occurring in voltage and being zero with electric current, so can avoid the while transition of voltage and electric current and can eliminate switch cost.
The advantages of resonance converter and pulse wave width modulation technology is got up to form the control method of soft switch (SoftSwitching) pulse wave width modulation, the advantage that integrates controlled resonant converter and pulse wave width modulation, both can realize the soft switch of power switch, make power supply under high frequency, realize efficient operation, and and then reduce the passive block size and improve power density (Power density), this also be present electric and electronic technical field developing direction one.In DC to DC converter, suitable active of the research of phase shifting full bridge soft switch circuit, it is one of the DC power supply desirable topology (Topology) that realizes high frequencyization, especially in, in the powerful application.
Fig. 1 is a typical phase whole-bridging circuit, and L1 is the resonant inductance of transformer outside.The energy that utilization is stored among this resonant inductance L1 discharges and recharges the output parasitic capacitance of lagging leg MOS transistor Q3 and Q4, can realize the zero voltage switch of MOS transistor.Simultaneously, because the existence of resonant inductance L1, be reflected to elementary load current and the reverse recovery current resonant inductance L1 that can flow through, just can limit output diode D3 and the D4 current changing rate di/dt when the change of current, thereby reduce the reverse recovery current (Reverse Recovery Current) and the circuit of diode electromagnetic interference (Electromagnetic Interference, EMI).
But this outside resonant inductance also can bring negative effect.Because generally speaking, in order to enlarge soft-switching range, the inductance value of the resonant inductance L1 that this is outside can be bigger than the leakage inductance of isolating transformer T.Therefore, if do not have the clamp circuit RCD (zone that frame of broken lines impaled among Fig. 1 on transformer T shown in Figure 1 secondary, resistance R c, capacitor C c, diode D1 have been comprised), then in the time of output diode D3 or the reverse recovery of D4, reverse recovery current in the diode can be reflected into primary coil and flow to resonant inductance L1, and reverse recovery energy major part is transferred among the resonant inductance L1.Suddenly block when reverse current arrives maximum owing to be in the diode that oppositely returns to form, resonance will take place in the parasitic capacitance of resonant inductance L1 and this diode, causes the phenomenon of the magnitude of voltage generation voltage oscillation that the C that shows in Fig. 1 order.Fig. 2 has clearly illustrated the measured voltage oscillation of C point experimentally.The voltage oscillation that C is ordered can be reflected to the secondary of isolating transformer, therefore also can produce voltage oscillation on diode D3 that oppositely recovers or the D4, as shown in Figure 3.
Reduce the clamp circuit that this voltage oscillation method commonly used is to use loss-type.Clamp circuit RCD circuit in Fig. 1 frame of broken lines is exactly a kind of typical loss-type clamp circuit.When having used clamp circuit RCD secondary in transformer T shown in Figure 1, just can reduce the voltage resonance between the parasitic capacitance of resonant inductance L1 and diode D3 or D4.Fig. 4 promptly be to use clamp circuit RCD after secondary diode D3 or the voltage waveform of D4.Compared to Fig. 3, can see that the due to voltage spikes on diode D3 or the D4 has reduced greatly, but the existence of some parasitic oscillation is still arranged.Therefore, the clamper effect that in this way reaches voltage also is not very desirable.
In United States Patent (USP) numbering 5198969, then be the mode that has adopted elementary clamper in 1992 by phase whole-bridging circuits that the people proposed such as Red1, as shown in Figure 5.Though this clamper mode has been improved the problem of aforesaid voltage oscillation, but produce the problem that some can't be ignored simultaneously.Subject matter is that the forward current that flows through among clamp diode D1 and the D2 is bigger, cause clamp diode D1 and D2 heating more serious, even cause some problems in the heat radiation, and in clamp diode D1 and D2, there is the bigger reverse recovery current of work, can on clamp diode D1 and D2, causes very big loss like this.
Summary of the invention
In the foregoing invention background, the primary side clamp circuit has serious voltage concussion problem in the prior art, and the primary side clamp circuit can flow through bigger forward and reverse recovery current and cause problems such as heat radiation, clamp circuit loss.Main purpose of the present invention is to provide one near desirable clamp circuit, makes the due to voltage spikes of output diode enough little.
Another purpose of the present invention makes the forward current of the clamp circuit of flowing through and reverse recovery current littler, makes the loss ratio of the clamp circuit that is caused less.
According to the above purpose, the invention provides a kind of DC to DC converter output voltage clamper method.The method is utilized a DC-DC converter, and changing an input voltage is an output voltage; Connect a clamp circuit then to DC-DC converter, in order to the output voltage clamper and connect an inductive bank to DC-DC converter and clamp circuit, inductive bank comprises one first inductance and one second inductance that connects and intercouple with series system, one end of first inductance is connected to DC-DC converter, and an end of second inductance is connected to clamp circuit.So, when the rectifier change of current of DC-DC converter, one reverse recovery current of one rectifier diode of rectification circuit will be reflected into the primary side of a transformer of DC-DC converter, form an induced current flow through first inductance of inductive bank and a primary coil of transformer, when rectifier diode took place to end, induced current diminished and flows through inductive bank and clamp circuit then.So, the due to voltage spikes of output diode is enough little, and the forward current of the clamp circuit of flowing through and reverse recovery current are littler, make the loss ratio of the clamp circuit that is caused less.
Moreover the present invention also discloses a kind of phase whole-bridging circuit with clamp circuit, comprises:
One first series connection commutation circuit comprises one first changeover module and one second changeover module, and this first changeover module and this second changeover module are connected to a direct-current input power supplying with series system;
One second series connection commutation circuit comprises one the 3rd changeover module and one the 4th changeover module, and the 3rd changeover module and the 4th changeover module are connected to this direct-current input power supplying with series system;
One clamp circuit includes one first clamp diode and one second clamp diode, and this first clamp diode and this second clamp diode connect this direct-current input power supplying with series system;
One inductive bank comprises one first inductance and one second inductance that connect and intercouple with series system, and an end of this first inductance connects the contact of connecting of the 3rd changeover module and the 4th changeover module, and an end of this second inductance is coupled to this clamp circuit;
One transformer, include a primary coil and a level coil, one first end of this primary coil connects a string interface of this first changeover module and this second changeover module, and one second end of this primary coil connects a string interface of this first inductance and this second inductance; And
One output rectification circuit comprises a rectifier, a filter capacitor and a filter inductance and connects this secondary coil;
Wherein, when this rectifier change of current, the primary side that one reverse recovery current of one rectifier diode of this rectifier will be reflected into this transformer forms an induced current flow through this first inductance and this primary coil, when this rectifier diode took place to end, this induced current diminished and flows through this inductive bank and this clamp circuit then.
Wherein above-mentioned inductive bank is a tap inductance.
Wherein this of above-mentioned inductive bank first inductance coil is thick than this second inductance coil.
The wherein above-mentioned second inductance coil number and the ratio of this first inductance coil number are less than or equal to the ratio of a leakage inductance with the inductance value of this first inductance coil of this transformer.
Wherein above-mentioned output rectification circuit more comprises one and diminishes clamp circuit.
The wherein above-mentioned clamp circuit that diminishes comprises a resistance, an electric capacity at least.
The wherein above-mentioned clamp circuit that diminishes comprises a resistance, an electric capacity and a diode at least.
Wherein above-mentioned inductive bank also comprises one the 3rd inductance, and one first end of the 3rd inductance connects a string interface of this first inductance and this second inductance, and one second end of the 3rd inductance is coupled to this clamp circuit.
And a kind of three level shifting circuits with clamp circuit are also disclosed, comprise:
One series connection electric capacity comprises one first electric capacity, one second electric capacity, and is connected to a direct-current input power supplying;
One circuit, comprise one first changeover module, one second changeover module, one the 3rd changeover module and one the 4th changeover module, this first changeover module, this second changeover module, the 3rd changeover module and the 4th changeover module are connected to this direct-current input power supplying in regular turn;
One capacitance component, one first end points of this capacitance component is connected to a string interface of this first changeover module and this second changeover module, and one second end points of this capacitance component is connected to a string interface of the 3rd changeover module and the 4th changeover module;
One diode series circuit, comprise one first diode and one second diode, one first end points of this diode series circuit connects this first end points of this capacitance component, one second end points of this diode series circuit connects this second end points of this capacitance component, and a series connection tie point of this first diode and this second diode is connected to a series connection tie point of this first electric capacity and this second electric capacity;
One clamp circuit comprises one first clamp diode and one second clamp diode of series connection, and one first end points of this clamp circuit connects this first end points of this capacitance component, and one second end points of this clamp circuit connects this second end points of this capacitance component;
One inductive bank comprises one first inductance and one second inductance that connect and intercouple with series system, and an end of this first inductance connects the contact of connecting of this second changeover module and the 3rd changeover module, and an end of this second inductance is coupled to this clamp circuit;
One transformer, include a primary coil and a level coil, one first end of this primary coil connects this first diode of this diode series circuit and this contact of connecting of this second diode, and one second end of this primary coil connects a string interface of this first inductance and this second inductance; And
One output rectification circuit comprises a rectifier, a filter capacitor and a filter inductance and connects this secondary coil;
Wherein, when this rectifier change of current, the primary side that one reverse recovery current of one rectifier diode of this rectifier will be reflected into this transformer forms an induced current flow through this first inductance and this primary coil, when this rectifier diode took place to end, this induced current diminished and flows through this inductive bank and this clamp circuit then.
Therefore, have serious voltage concussion problem, and the primary side clamp circuit can flow through bigger forward and reverse current and cause problems such as heat radiation, clamp circuit loss compared to the primary side clamp circuit of prior art.The present invention can reduce the voltage concussion of diode, and reduces forward and the reverse recovery current that the primary side clamp circuit can flow through, and makes the loss ratio of the clamp circuit that is caused less.
Description of drawings
Fig. 1 is the schematic diagram of the phase whole-bridging circuit of the secondary clamper mode of available technology adopting;
Fig. 2 is the circuit of survey map 1 when not having clamp circuit RCD, the resulting voltage waveform of C point;
Fig. 3 is the circuit of survey map 1 when not having clamp circuit RCD, the resulting voltage waveform of rectifier diode;
Fig. 4 is the circuit of survey map 1 when clamp circuit RCD is arranged, the resulting voltage waveform of rectifier diode;
Fig. 5 is the phase whole-bridging circuit schematic diagram of the elementary clamper mode of available technology adopting;
Fig. 6 is the elementary clamper mode phase whole-bridging circuit schematic diagram of a preferred embodiment of the present invention;
Fig. 7 is the resulting voltage waveforms of survey map 6 preferred embodiment circuit C points of the present invention;
Fig. 8 is the resulting voltage waveforms of survey map 6 preferred embodiment circuit rectifier diodes of the present invention;
Fig. 9 the present invention is applied to the schematic diagram of another preferred embodiment in three level DC/DC converting circuit;
Figure 10 is the schematic diagram that the present invention utilizes another preferred embodiment of coupling inductance;
Figure 11 the present invention utilizes coupling inductance to be applied to the schematic diagram of another preferred embodiment in three level DC/DC converting circuit;
Figure 12 has the schematic diagram that secondary side has clamp circuit RC;
Figure 13 has the schematic diagram that secondary side has clamp circuit RCD; And
Figure 14 has the schematic diagram that secondary side has clamp circuit RC2D.
Embodiment
Some embodiments of the present invention can be described in detail as follows.Yet except describing in detail, the present invention can also be widely implements at other embodiment, and scope of the present invention do not limited, and is as the criterion with the claim of application.
Moreover for clearer description being provided and being more readily understood the present invention, graphic interior each several part is not drawn according to its relative size, and some size is compared with other scale dependent and exaggerated; Incoherent detail section is not drawn fully yet, in the hope of graphic succinct.
Fig. 6 is a preferred embodiment that applies the present invention to phase whole-bridging circuit.Circuit in the frame of broken lines among the figure has constituted component elements of the present invention: be made up of an inductance L with tap and two clamp diode D1 and D2.The operation principle of this circuit will be done detailed explanation below.
Among Fig. 6, the input of phase whole-bridging circuit is a direct voltage source Vin, in the application of reality in, the power factor corrector of prime (Power Factor Correction, output PFC) normally.Full-bridge circuit itself is elementary 4 switching transistors (normally MOSFET) Q1, Q2, Q3 and Q4, the action that transistor Q1 and Q2 can alternately open repeatedly, close, and after transistor Q1 opened or closes, transistor Q4 can open or close with work; Similarly, after transistor Q2 opened or closes, Q3 also can open or close with work.Secondary have 2 rectifier diode D3 and a D4, in order to the voltage Vo of rectification output end, and the inductance L f of LC filter and capacitor C f, in order to the filtering voltage noise.
Tap inductance L among the present invention is the emphasis assembly, comprises inductance L 11 and inductance L 12 two parts.And the number of turn of inductance L 11 and inductance L 12 is respectively n11 and n12.In the practical application, the inductance L 11 and the coupling between the L12 at tap inductance L tap two ends must be good as far as possible.When secondary rectifier diode D3 and D4 the change of current did not take place, inductance L 11 flow through whole primary electric currents, so the coiling of L11 must can be carried whole primary currents.And 12 of inductance L are when the secondary rectifier diode D3 and the D4 change of current, flow through to be reflected to elementary reverse recovery current, therefore only need thinner coiling.
As can be seen from Figure 6, when rectifier diode D4 takes place oppositely to recover, transistor Q2 and Q3 conducting, the electric current that carries among the rectifier diode D3 has comprised the reverse recovery current of load current and rectifier diode D4.Flow through rectifier diode D3 is reflected to primary side via transformer T primary current in the inductance L 11.Therefore, primary current equally also comprises two parts: be reflected to elementary load current and the reverse recovery current that is reflected to elementary rectifier diode D4.Then, when rectifier diode D4 blocked suddenly, the part of the reaction reverse recovery current that flows through in the inductance L 11 can form circulation through clamp diode D1 and transistor Q3 by inductance L 12.According to the ampere-turn equilibrium principle, the electric current that flows through clamp diode D1 is i
RrN
11/ N (n
11+ n
12), wherein irr is the reverse recovery current of rectifier diode D4, N is a transformer primary and secondary turn ratio.Because transistor Q3 and clamp diode D1 are conducting, so the current potential that B point and D are ordered is Vin, and the voltage difference at tap inductance L two ends just is clamped to zero.Under the very good situation of the coupling of inductance L 11 and L12, the current potential that C is ordered can be very near Vin, even is clamped on the Vin equally.And this moment, transistor Q2 also was conducting, so the current potential that A order is zero potential, thereby made the voltage difference that the A point is ordered to C can be clamped at-Vin, and the conversion by isolating transformer T concerns that secondary voltage just is clamped at-Vin/N.
When similarly the change of current and clamp process also occur in rectifier diode D3 and oppositely recover, Q1 and Q4 conducting, the electric current that carries among the D4 this moment has comprised the reverse recovery current of load current and rectifier diode D3.Flow through rectifier diode D4 is reflected to primary side via transformer T primary current in the inductance L 11.Same, this electric current also comprises two parts, is reflected to elementary load current and rectifier diode D3 is reflected to elementary reverse recovery current.When rectifier diode D3 blocked suddenly, the part of the reflection reverse recovery current that flows through in the inductance L 11 can form circulation through transistor Q4 and clamp diode D2 by inductance L 12.According to the ampere-turn equilibrium principle, the electric current that flows through clamp diode D2 is i
RrN
11/ N (n
11+ n
12), wherein irr is the reverse recovery current of D3.This moment, the current potential of B point and D was zero owing to transistor Q4 and the equal conducting of clamp diode D2, so the voltage difference at tap inductance L two ends is clamped to zero.Under the good situation of inductance L 11 and L12 coupling, the current potential that C order is clamped at zero, and transistor Q1 conducting at this moment, the current potential that A is ordered is Vin, thereby make the voltage difference that the A point is ordered to C be clamped at Vin, by the conversion relation of isolating transformer T, secondary voltage also is clamped at Vin/N.
Obviously, utilize clamp circuit of the present invention, can make the electric current that flows through clamp diode D1 and D2 via inductance L 12 have only the n that flows through the clamp diode electric current among Fig. 5
11/ (n
11+ n
12) doubly.Therefore, circuit of the present invention has littler clamp diode forward current and reverse recovery current, and the clamper loss that is caused also will be littler.And for the change of current time that makes circuit of the present invention unlikely oversize and cause the loss of work period rate (duty cycle), the relational expression below needing to satisfy:
Wherein, Lk is the leakage inductance value of transformer T, and L11 is the inductance value of inductance L 11, and n11 and n12 are respectively the number of turn of inductance L 11 and inductance L 12.
According to above-mentioned analysis, under the situation of the various changes of current, the current potential that C is ordered will be clamped between 0 to Vin.The shown measured voltage oscillation of C point of Fig. 7 has been verified this point.Because elementary another node A of the isolating transformer T voltage of ordering also is between the 0-Vin, thus the elementary voltage of transformer T be clamped at-Vin is between the Vin.Be reflected to secondaryly, secondary voltage also is clamped at-and Vin/N is between the Vin/N.Because secondary voltage is by clamper, so the voltage on secondary commutation diode D3 and the D4 is also correspondingly by clamper.Fig. 8 has shown the voltage waveform that has adopted the rectifier diode after this clamper method.But, also have very little voltage overshoot (voltageovershoot) on output diode D3 and the D4 because there is smaller leakage inductance in isolating transformer T inside.
At clamper method of the present invention, also there are the very little voltage overshoot of energy in rectifier diode D3 and D4 voltage, can adopt the various secondary method of clamping that diminish, for example: the RCD shown in Fig. 1 diminishes clamp circuit, perhaps the RCD that diminishes clamp circuit, Figure 13 as the RC of Figure 12 RC2D that diminishes clamp circuit or Figure 14 diminishes clamp circuit (Figure 12, Figure 13 and Figure 14 only draws secondary side and do not draw primary edge, in the hope of graphic succinct), can further reduce the voltage overshoot of secondary commutation diode D3 and D4.This elementary tap inductance clamp will be included in the patent of the present invention in conjunction with the method for secondary low damage clamp combination.
Fig. 9 is that the present invention is applied to another preferred embodiment in three level (tri-level) the DC circuit.The cross-pressure of capacitor C 1 and C2 is 0.5Vin, so the current potential that A is ordered is 0.5Vin.And the cross-pressure of capacitor C 3 also is 0.5Vin, thus the C voltage of ordering via clamp diode D1 and D2 clamper between 0 to Vin (for example: when Vin just very+400V, and negative pole is-400V, then A point current potential is 0V, C point current potential is-400V is between+400).Therefore the elementary voltage of transformer T is clamped between 0 to Vin.Be reflected to secondaryly, secondary voltage also is clamped between 0 to Vin/N.In the same manner, can adopt the various secondary voltage overshoots that method of clamping reduces secondary commutation diode D5 and D6 that diminish.
Figure 10 and Figure 11 are that the circuit according to Fig. 6 and Fig. 9 changes and forms, and are applied to two preferred embodiments in addition of phase-shifting full-bridge and three level DC/DC transfer circuit respectively.Mainly be that the tap inductance L is replaced with coupling inductance L1, L2 and L3.If inductance L 1, L2 and the L3 number of turn are respectively n1, n2 and n3,, can learn between the number of turn and must satisfy following formula according to first formula:
Wherein, Lk is the leakage inductance value of transformer T, and L1 is the inductance value of inductance L 1.
And the number of turn of inductance L 2 and L3 does not limit and need to equate, and preferable situation to be n2 equate that with n3 clamp diode forward current and reverse recovery current that clamp diode D1 and D2 like this are met with just can equate.Moreover, because only when the secondary rectifier diode D5 and the D6 change of current, flowing through, inductance L 2 and L3 be reflected to elementary reverse recovery current, therefore only need thinner coiling.In the same manner, Figure 10 and circuit shown in Figure 11 also can adopt the various secondary voltage overshoots that method of clamping reduces secondary commutation diode D5 and D6 that diminish.
Moreover the present invention utilizes the tap inductance or the inductance that intercouples to reduce clamp diode forward current and reverse recovery current, also can be applicable to have the various DC-DC converters of primary side clamp circuit with the circuit structure that reduces the clamper loss.
Comprehensively the above the invention provides a kind of DC-DC converter output voltage clamper method.The method is utilized a DC-DC converter, and changing an input voltage is an output voltage; Connect a clamp circuit then to DC-DC converter, in order to the output voltage clamper and connect an inductive bank to DC-DC converter and clamp circuit, inductive bank comprises one first inductance and one second inductance that connects and intercouple with series system, one end of first inductance is connected to DC-DC converter, and an end of second inductance is connected to clamp circuit.So, when the rectifier change of current of DC-DC converter, one reverse recovery current of one rectifier diode of rectification circuit will be reflected into the primary side of a transformer of DC-DC converter, form an induced current flow through first inductance of inductive bank and a primary coil of transformer, when rectifier diode took place to end, induced current diminished and flows through inductive bank and clamp circuit then.So, the due to voltage spikes of output diode is enough little, and the forward current of the clamp circuit of flowing through and reverse recovery current are littler, make the loss ratio of the clamp circuit that is caused less.
Moreover the present invention has also disclosed a kind of phase whole-bridging circuit with clamp circuit, comprises one first series connection commutation circuit, one second series connection commutation circuit, a clamp circuit, an inductive bank, a transformer and an output rectification circuit; And also disclosed a kind of three level shifting circuits with clamp circuit, comprise a series connection condenser network, and switch circuit, one the 3rd electric capacity, a diode series circuit, a clamp circuit, an inductive bank, a transformer and an output rectification circuit.When the rectifier change of current of output rectification circuit, one reverse recovery current of one rectifier diode of rectification circuit will be reflected into the primary side of transformer, form an induced current flow through one first inductance of inductive bank and a primary coil of transformer, when rectifier diode took place to end, induced current diminished and flows through inductive bank and clamp circuit then.So, the due to voltage spikes of output diode is enough little, and the forward current of the clamp circuit of flowing through and reverse recovery current are littler, make the loss ratio of the clamp circuit that is caused less.
Therefore, have serious voltage concussion problem, and the primary side clamp circuit can flow through bigger forward and reverse current and cause problems such as heat radiation, clamp circuit loss compared to the primary side clamp circuit of prior art.The present invention can reduce the voltage concussion of diode, and reduces forward and the reverse current that the primary side clamp circuit can flow through, and makes the loss ratio of the clamp circuit that is caused less.
The above is preferred embodiment of the present invention only, is not in order to limit claim of the present invention; All other changes for the equivalence of being finished under the disclosed spirit of disengaging or modifies, and all should be included in claim.
Claims (10)
1. phase whole-bridging circuit with clamp circuit comprises:
One first series connection commutation circuit comprises one first changeover module and one second changeover module, and this first changeover module and this second changeover module are connected to a direct-current input power supplying with series system;
One second series connection commutation circuit comprises one the 3rd changeover module and one the 4th changeover module, and the 3rd changeover module and the 4th changeover module are connected to this direct-current input power supplying with series system;
One clamp circuit includes one first clamp diode and one second clamp diode, and this first clamp diode and this second clamp diode connect this direct-current input power supplying with series system;
One inductive bank comprises one first inductance and one second inductance that connect and intercouple with series system, and an end of this first inductance connects the contact of connecting of the 3rd changeover module and the 4th changeover module, and an end of this second inductance is coupled to this clamp circuit;
One transformer, include a primary coil and a level coil, one first end of this primary coil connects a string interface of this first changeover module and this second changeover module, and one second end of this primary coil connects a string interface of this first inductance and this second inductance; And
One output rectification circuit comprises a rectifier, a filter capacitor and a filter inductance and connects this secondary coil;
Wherein, when this rectifier change of current, the primary side that one reverse recovery current of one rectifier diode of this rectifier will be reflected into this transformer forms an induced current flow through this first inductance and this primary coil, when this rectifier diode took place to end, this induced current diminished and flows through this inductive bank and this clamp circuit then.
2. the phase whole-bridging circuit with clamp circuit as claimed in claim 1 is characterized in that, wherein above-mentioned inductive bank is a tap inductance.
3. the phase whole-bridging circuit with clamp circuit as claimed in claim 1 is characterized in that, wherein this of above-mentioned inductive bank first inductance coil is thicker than this second inductance coil.
4. the phase whole-bridging circuit with clamp circuit as claimed in claim 1 is characterized in that, the wherein above-mentioned second inductance coil number and the ratio of this first inductance coil number are less than or equal to the ratio of a leakage inductance with the inductance value of this first inductance coil of this transformer.
5. the phase whole-bridging circuit with clamp circuit as claimed in claim 1 is characterized in that, wherein above-mentioned output rectification circuit more comprises one and diminishes clamp circuit.
6. the phase whole-bridging circuit with clamp circuit as claimed in claim 5 is characterized in that, the wherein above-mentioned clamp circuit that diminishes comprises a resistance, an electric capacity at least.
7. the phase whole-bridging circuit with clamp circuit as claimed in claim 5 is characterized in that, the wherein above-mentioned clamp circuit that diminishes comprises a resistance, an electric capacity and a diode at least.
8. the phase whole-bridging circuit with clamp circuit as claimed in claim 1, it is characterized in that, wherein above-mentioned inductive bank also comprises one the 3rd inductance, one first end of the 3rd inductance connects a string interface of this first inductance and this second inductance, and one second end of the 3rd inductance is coupled to this clamp circuit.
9. three level shifting circuits with clamp circuit comprise:
One series connection electric capacity comprises one first electric capacity, one second electric capacity, and is connected to a direct-current input power supplying;
One circuit, comprise one first changeover module, one second changeover module, one the 3rd changeover module and one the 4th changeover module, this first changeover module, this second changeover module, the 3rd changeover module and the 4th changeover module are connected to this direct-current input power supplying in regular turn;
One capacitance component, one first end points of this capacitance component is connected to a string interface of this first changeover module and this second changeover module, and one second end points of this capacitance component is connected to a string interface of the 3rd changeover module and the 4th changeover module;
One diode series circuit, comprise one first diode and one second diode, one first end points of this diode series circuit connects this first end points of this capacitance component, one second end points of this diode series circuit connects this second end points of this capacitance component, and a series connection tie point of this first diode and this second diode is connected to a series connection tie point of this first electric capacity and this second electric capacity;
One clamp circuit comprises one first clamp diode and one second clamp diode of series connection, and one first end points of this clamp circuit connects this first end points of this capacitance component, and one second end points of this clamp circuit connects this second end points of this capacitance component;
One inductive bank comprises one first inductance and one second inductance that connect and intercouple with series system, and an end of this first inductance connects the contact of connecting of this second changeover module and the 3rd changeover module, and an end of this second inductance is coupled to this clamp circuit;
One transformer, include a primary coil and a level coil, one first end of this primary coil connects this first diode of this diode series circuit and this contact of connecting of this second diode, and one second end of this primary coil connects a string interface of this first inductance and this second inductance; And
One output rectification circuit comprises a rectifier, a filter capacitor and a filter inductance and connects this secondary coil;
Wherein, when this rectifier change of current, the primary side that one reverse recovery current of one rectifier diode of this rectifier will be reflected into this transformer forms an induced current flow through this first inductance and this primary coil, when this rectifier diode took place to end, this induced current diminished and flows through this inductive bank and this clamp circuit then.
10. DC-DC converter output voltage clamper method comprises:
Utilize a DC-DC converter, changing an input voltage is an output voltage;
Connect a clamp circuit to this DC-DC converter, in order to this output voltage clamper; And
Connect an inductive bank to this DC-DC converter and this clamp circuit, this inductive bank comprises one first inductance and one second inductance that connects and intercouple with series system, one end of this first inductance is connected to this DC-DC converter, one end of this second inductance is connected to this clamp circuit, and the tie point of this first inductance and this second inductance is connected to a primary coil of a transformer of this DC-DC converter;
Wherein, when the rectifier change of current of this DC-DC converter, the primary side that one reverse recovery current of one rectifier diode of this rectifier will be reflected into a transformer of this DC-DC converter forms an induced current flow through this first inductance of this inductive bank and a primary coil of this transformer, when this rectifier diode took place to end, this induced current diminished and flows through this inductive bank and this clamp circuit then.
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| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CNB2003101244325A CN100337392C (en) | 2003-12-26 | 2003-12-26 | DC/DC converter having voltage clamping circuit |
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| CNB2003101244325A CN100337392C (en) | 2003-12-26 | 2003-12-26 | DC/DC converter having voltage clamping circuit |
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| CN1635695A CN1635695A (en) | 2005-07-06 |
| CN100337392C true CN100337392C (en) | 2007-09-12 |
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Cited By (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US9847707B2 (en) | 2015-08-20 | 2017-12-19 | Delta Electronics, Inc. | Converter |
| TWI669892B (en) * | 2018-03-20 | 2019-08-21 | 力智電子股份有限公司 | Dc-dc converting controller and operating method thereof |
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| Publication number | Priority date | Publication date | Assignee | Title |
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| FI120123B (en) * | 2007-08-24 | 2009-06-30 | Abb Oy | Method and apparatus for stabilizing intermediate circuit voltage in a frequency converter |
| MX2011000429A (en) | 2008-07-30 | 2011-02-23 | Toshiba Mitsubishi Elec Inc | Power conversion device. |
| CN103339844A (en) * | 2011-02-04 | 2013-10-02 | 三菱电机株式会社 | Dc-dc converter |
| CN109286311A (en) * | 2017-07-19 | 2019-01-29 | 中国电力科学研究院 | A kind of tap coupler inductance type non-isolation type direct-current booster converter and modulator approach |
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| Publication number | Priority date | Publication date | Assignee | Title |
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| US9847707B2 (en) | 2015-08-20 | 2017-12-19 | Delta Electronics, Inc. | Converter |
| TWI669892B (en) * | 2018-03-20 | 2019-08-21 | 力智電子股份有限公司 | Dc-dc converting controller and operating method thereof |
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| Publication number | Publication date |
|---|---|
| CN1635695A (en) | 2005-07-06 |
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