CN111193398A - Isolated bidirectional DCDC converter and current bidirectional control method - Google Patents
Isolated bidirectional DCDC converter and current bidirectional control method Download PDFInfo
- Publication number
- CN111193398A CN111193398A CN202010106345.0A CN202010106345A CN111193398A CN 111193398 A CN111193398 A CN 111193398A CN 202010106345 A CN202010106345 A CN 202010106345A CN 111193398 A CN111193398 A CN 111193398A
- Authority
- CN
- China
- Prior art keywords
- circuit
- phase
- switching
- inverter circuit
- resonant
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Withdrawn
Links
Images
Classifications
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/3353—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having at least two simultaneously operating switches on the input side, e.g. "double forward" or "double (switched) flyback" converter
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
Abstract
The invention relates to an isolated bidirectional DCDC converter, which comprises: the inverter comprises two inverter circuits formed by connecting at least three bridge arms in parallel, wherein each bridge arm is formed by connecting at least two switching tubes in series; the resonant circuit is formed by at least three groups of resonant capacitors and resonant inductors which are connected in series and at least three excitation inductors on the inverter circuit on any side of the at least three-phase transformer; and the at least three-phase transformer is used for converting pulse current provided by the at least three-phase transformer into direct current voltage providing energy for the circuit at the output side and outputting the direct current voltage. The three-phase full-bridge bidirectional conversion can be realized on the premise of ensuring the reduction of ripple current, and the redundancy of the system can be reduced.
Description
Technical Field
The invention belongs to the technical field of power equipment, and particularly relates to an isolated bidirectional DCDC converter and a current bidirectional control method.
Background
The DC-DC converter is an electric device for converting DC into another fixed or adjustable DC, and specifically, the DC output from an input end is converted into AC, and then the AC is converted into DC for output after the voltage is changed by a transformer, or the AC is converted into high-voltage DC for output by a voltage doubling rectifying circuit.
A common converter is realized by a single-phase full-bridge LLC resonant circuit, the current of the input end and the current of the output end of the input end of the common converter are close to sine waves, the current added on a filter capacitor is that the output alternating current subtracts the direct current output by the converter, and then, the ripple current effective value of the output filter capacitor is extremely large, so that the required filter capacitor is correspondingly large.
Based on the above problems of the single-phase full-bridge LLC resonant converter, an easily conceivable way is to solve the technical defects of the single-phase full-bridge LLC resonant converter by using a three-phase full-bridge LLC resonant circuit. For example, the invention patent application with application publication number CN101841244A specifically discloses a low output loss LLC resonant converter, which adopts at least 3 inductors and at least 3 rectifier tubes on the secondary side of a transformer for hybrid rectification, which can significantly reduce the loss of an output rectification circuit, and by setting a lag angle between the primary side bridge arms, the secondary side output current ripple after superposition becomes significantly smaller, effectively solving the problem of large output capacitance ripple.
However, in the three-phase full-bridge LLC resonant circuit in the prior art, due to the existence of the excitation current, the current output by the LLC resonant circuit is not a perfect sinusoidal current, which results in mutual influence among multiple resonant currents, and the secondary diode realizes current-doubling rectification, which makes the structure of the LLC resonant circuit more complex. Above all, the three-phase full-bridge LLC resonant circuit has difficulty in realizing bidirectional conversion or bidirectional output, and the energy transfer can only be directionally transferred from one side of the circuit to the other side of the circuit, thus causing considerable limitation to the applicability of the converter.
In another prior art, the aforementioned technical defects are solved by connecting single-phase full-bridge LLC converters in parallel. Fig. 1 is a schematic diagram showing a circuit configuration of another converter in the prior art, and referring to fig. 1, in the prior art, a unidirectional full-bridge LLC converter is connected in parallel, so that bidirectional energy transmission can be realized, however, at least 24 switching devices are required in the primary and secondary stages, and a driving circuit for each switching device makes a system become abnormally complex, which naturally also brings about a sharp increase in configuration cost, and is also disadvantageous to miniaturization of the system and improvement of system reliability.
In view of the above, the prior art should be improved to solve the above technical problems.
Disclosure of Invention
The invention aims to overcome the defects of the prior art and provide an isolated bidirectional DCDC converter and a current bidirectional control method which can realize three-phase full-bridge bidirectional conversion and reduce the system redundancy on the premise of ensuring the reduction of ripple current so as to ensure that the system is applied in a composite high-power occasion.
In order to solve the above technical problem, an isolated bidirectional DCDC converter according to the present invention includes: the bridge comprises two inverter circuits formed by connecting at least three bridge arms in parallel, wherein each bridge arm is formed by connecting at least two switching tubes in series; the resonant circuit is formed by at least three groups of resonant capacitors and resonant inductors which are connected in series and at least three excitation inductors on the inverter circuit on any side of the at least three-phase transformer; and the at least three-phase transformer is connected with the two inverter circuits and the resonant circuit, when energy is transmitted to the other side from any side of the two inverter circuits, the inverter circuit serving as an input side inverts the direct-current voltage into square wave or step wave voltage, the inverter circuit serving as an output side forms a rectification circuit, and pulse current provided by the at least three-phase transformer is converted into direct-current voltage providing energy for the circuit on the output side to be output.
Preferably, each inverter circuit is connected in parallel with a decoupling circuit, and the decoupling circuit is formed by connecting at least two decoupling capacitors in series.
Further preferably, when the inverter circuit on any side is used as an output side, the switching tubes in the bridge arms on the inverter circuit on any side adopt the same frequency, wherein when the inverter circuit on any side is used as an output side, the switching tubes on each bridge arm are respectively defined as a first switching tube and a second switching tube according to a current direction, a source electrode of the first switching tube is connected with a drain electrode of the second switching tube, phase angles of the second switching tube and the first switching tube in each bridge arm are different by 180 degrees, and hysteresis is formed between the bridge arms according to a preset angle.
Further preferably, in the resonant circuit, the excitation inductor is an external inductor connected in parallel to one side of the N-phase transformer, and the resonant inductor is an external inductor or a leakage inductor of the N-phase transformer, where the excitation inductor is connected in parallel to one side of the N-phase transformer and then connected in series with the resonant inductor and the resonant capacitor to form a branch of the resonant circuit.
Still further preferably, an N-leg of {1, 2, 3 … N-1, N } and an N-phase transformer of {1, 2, 3 … N-1, N } are defined, and for an m-th phase resonant circuit of the N-phase transformer, one end of the m-th phase resonant circuit is connected to a leg midpoint of the m-th leg of the side inverter circuit, and the other end is connected to a midpoint of a decoupling circuit of the side inverter circuit, in one side of the N-phase transformer; in the other side edge of the N-phase transformer, one end of the m-th phase resonance circuit is connected with the middle point of the bridge arm of the (N +1-m) -th bridge arm of the inverter circuit at the side, and the other end of the m-th phase resonance circuit is connected with the middle point of the decoupling circuit of the inverter circuit at the side.
Still preferably, the switch tube is connected with a diode in inverse parallel.
Still preferably, the switch tube is a mosfet.
Correspondingly, the invention also provides a bidirectional control method of the DCDC current based on the isolated bidirectional DCDC converter, which comprises the following steps: step S1 of configuring the lag angle between the bridge arms and the phase angle difference of the switching tubes; step S2 of switching on and off time sequence of the switch tube when the configuration energy is transmitted from the inverter circuit on any side to the other side; step S3, configuring the converter to switch the energy transfer direction and/or transferring energy between two inverter circuits of the converter.
Preferably, in step S2, in the on-off sequence of the switching tubes, if the driving signals of the switching tubes on any one of the arms are two complementary driving signals, the switching tubes are connected to one of the arms.
Due to the adoption of the technical scheme, compared with the prior art, the invention has the following advantages:
1. by arranging the two symmetrical inverter circuits, when energy is transmitted from one side of the two inverter circuits to the other side, the two inverter circuits can be respectively used as an input side or an output side, so that the modulation and rectification functions are respectively realized, the on-off of a switching tube on a three-bridge arm used as the input side is controlled, so that the current output by a resonance tank on the input side is close to a sine wave, the sine currents with the three phases different by 120 degrees are equivalent to a direct current, and the ripple current on a filter capacitor is remarkably reduced in the process;
2. because the ripple current on the filter capacitor is reduced, the technical scheme can realize three-phase full-bridge bidirectional conversion on the premise of ensuring that the ripple current is reduced so as to ensure that the system is applied in a composite high-power occasion, namely, two inverter circuits are respectively used as an input side and an output side, and the alternation of the inverter circuits is realized by controlling the channels of the switching tubes on the bridge arms according to a certain period, so that the three-phase full-bridge bidirectional conversion is realized on the basis of the prior art, and energy can be transmitted on two sides of the three-phase full bridge and/or the switching of the energy transmission direction is realized;
3. when energy is transmitted between the two inverter circuits, the switch tubes in the half-bridge LLC on one side are in a soft-switching state, and most of the switch tubes in the half-bridge LLC on the other side work in the soft-switching state, so that the conversion efficiency in the energy transmission process is obviously improved;
4. the full-bridge rectification mode is adopted to replace the mode of realizing current-doubling rectification through a diode and a corresponding inductor in the prior art, so that the redundancy of the system is obviously reduced, the currents of the resonant tanks in the three-phase resonant circuit are independent, and the mutual influence of the currents of the resonant tanks is avoided;
5. compared with the mode of connecting a single-phase full-bridge LLC resonant converter in parallel, the number of the switching devices is reduced from 24 to 12, the cost of an equipment system is reduced, the overall size of the equipment is reduced, and the overall operation stability of the equipment is improved by reducing components;
6. by setting a lag angle for a switching tube between each bridge arm of the inverter circuit, the superposed output current ripple is obviously reduced, the problem of large output capacitance ripple is effectively solved, the technical limit that the bidirectional DCDC converter is suitable for high-power conversion occasions is solved, and the application range of equipment is expanded;
7. decoupling capacitors are respectively arranged on the two inverter circuits, and when any inverter circuit is used as an output side circuit, the decoupling capacitors filter the interference of output signals, prevent the interference signals from returning to a power supply and avoid mutual coupling interference.
Drawings
Fig. 1 is a schematic diagram showing a circuit configuration of a converter in the prior art;
FIG. 2 is a diagram illustrating the circuit structure of a preferred embodiment of the present invention;
FIG. 3 is a schematic diagram showing an equivalent circuit configuration at time t1 of the first half cycle of the bidirectional conversion in the preferred embodiment shown in FIG. 1;
FIG. 4 is a schematic diagram showing an equivalent circuit configuration at time t2 of the first half cycle of the bidirectional conversion in the preferred embodiment shown in FIG. 1;
FIG. 5 is a schematic diagram showing an equivalent circuit configuration at time t3 of the first half cycle of the bidirectional conversion in the preferred embodiment shown in FIG. 1;
FIG. 6 is a schematic diagram showing an equivalent circuit configuration at time t4 of the first half cycle of the bidirectional conversion in the preferred embodiment shown in FIG. 1;
FIG. 7 is a schematic diagram showing an equivalent circuit configuration at time t5 of the first half cycle of the bidirectional conversion in the preferred embodiment shown in FIG. 1;
FIG. 8 is a schematic diagram showing an equivalent circuit configuration at time t6 of the first half cycle of the bidirectional conversion in the preferred embodiment shown in FIG. 1;
FIG. 9 is a diagram illustrating an equivalent circuit structure at time t7 of the second half cycle of the bidirectional conversion in the preferred embodiment shown in FIG. 1;
FIG. 10 is a diagram illustrating an equivalent circuit structure at time t8 of the second half cycle of the bidirectional conversion in the preferred embodiment shown in FIG. 1;
FIG. 11 is a diagram illustrating an equivalent circuit structure at time t9 of the second half cycle of the bidirectional conversion in the preferred embodiment shown in FIG. 1;
FIG. 12 is a diagram illustrating an equivalent circuit structure at time t10 of the second half cycle of the bidirectional conversion in the preferred embodiment shown in FIG. 1;
FIG. 13 is a diagram illustrating an equivalent circuit structure at time t11 of the second half cycle of the bi-directional conversion in the preferred embodiment shown in FIG. 1;
FIG. 14 is a diagram illustrating an equivalent circuit structure at time t12 of the second half cycle of the bidirectional conversion in the preferred embodiment shown in FIG. 1;
fig. 15 is a schematic diagram illustrating a circuit configuration of an isolated bidirectional DCDC converter according to another preferred embodiment of the present invention;
FIG. 16 is a flow chart illustrating the flow of the current bi-directional control method of the present invention;
wherein: 10. an inverter circuit; 11. a switching tube; 12. a decoupling capacitor; 20. a resonant circuit; 21. a resonant capacitor; 22. a resonant inductor; 23. and (4) exciting the inductor.
Detailed Description
An embodiment of an isolated bidirectional DCDC converter according to the present invention will be described with reference to the accompanying drawings. Those of ordinary skill in the art will recognize that the described embodiments can be modified in various different ways, without departing from the spirit and scope of the present invention. Accordingly, the drawings and description are illustrative in nature and not intended to limit the scope of the claims. Furthermore, in the present description, the drawings are not to scale and like reference numerals refer to like parts.
It should be noted that, in the embodiments of the present invention, the expressions "first" and "second" are used to distinguish two entities with the same name but different names or different parameters, and it is understood that "first" and "second" are merely for convenience of description and should not be construed as limitations of the embodiments of the present invention, and the descriptions thereof in the following embodiments are omitted.
The invention relates to an isolated bidirectional DCDC converter, which comprises two symmetrically arranged inverter circuits formed by connecting at least three bridge arms in parallel, wherein each bridge arm is formed by connecting at least two switching tubes in series, a resonant circuit formed by connecting at least three groups of resonant capacitors and resonant inductors in series and at least three excitation inductors on the inverter circuits on any side of at least a three-phase transformer is arranged between the inverter circuits on two sides, and the at least three-phase transformer comprises at least three windings and is connected with the two inverter circuits and the resonant circuit.
As described above, the resonant circuit is composed of a plurality of branches including the excitation inductor, the resonant capacitor, and the resonant inductor, in the resonant circuit, the excitation inductor is an external inductor connected in parallel with one side of the N-phase transformer, the resonant inductor is an external inductor or a leakage inductor of the N-phase transformer, and each branch of the resonant circuit is composed of the excitation inductor connected in parallel with one side of the N-phase transformer and then connected in series with the resonant inductor and the resonant capacitor. Then, in the embodiment of the present invention, an N-leg including {1, 2, 3 … N-1, N } and an N-phase transformer including {1, 2, 3 … N-1, N } may be defined, and for the m-th phase resonant circuit of the N-phase transformer, for one side of the N-phase transformer, one end of the m-th phase resonant circuit is connected to the leg midpoint of the m-th leg of the side inverter circuit, and the other end is connected to the midpoint of the decoupling circuit of the side inverter circuit; meanwhile, in the other side edge of the N-phase transformer, one end of the m-th phase resonance circuit is connected with the middle point of the bridge arm of the (N +1-m) -th bridge arm of the inverter circuit on the side, and the other end of the m-th phase resonance circuit is connected with the middle point of the decoupling circuit of the inverter circuit on the side.
The switch tube may be configured as a soft switch with an antiparallel diode, or a MOS device with a parasitic diode, such as a mosfet, for example, but the embodiment of the invention is not limited thereto.
In actual work, when energy is transmitted from any one side of the two inverter circuits to the other side, the inverter circuit on the input side inverts the input direct-current voltage into a square wave or step wave voltage, the square wave or step wave voltage is transformed by the three-phase transformer to form pulse current, and the pulse current is converted into direct-current voltage which provides energy for the circuit on the output side as the inverter current on the output side to be output. In order to avoid coupling interference, each inverter circuit is connected with a decoupling circuit in parallel, and each decoupling circuit is connected with two decoupling capacitors in series.
When any one side of the inverter circuit serves as an output side, the switching tubes on the inverter circuit adopt the same frequency, the switching tubes on each bridge arm are respectively defined as a first switching tube and a second switching tube according to the current direction, the source electrode of the first switching tube is connected with the drain electrode of the second switching tube, the phase angles of the second switching tube and the first switching tube in each bridge arm are different by 180 degrees, a preset hysteresis angle is formed between the bridge arms, the preset hysteresis angle should be 360 degrees/N, wherein N is the number of the bridge arms, and for example, when three bridge arms are included, the hysteresis angle between the three bridge arms can be set to be 360 degrees/3, namely 120 degrees. When the isolated bidirectional DCDC converter works, energy can be bidirectionally input from one side and output from the other side, namely, direct current voltage input from any one side is inverted into square wave or step wave voltage, pulse current is formed after the square wave or step wave voltage passes through a transformer, and then the pulse current is rectified into direct current voltage which provides energy for a circuit on the output side by an inverter circuit on the other side and is output.
The bidirectional control realized in the invention can change the direction of current transmission, namely the direction of energy transmission, so as to realize the switching of the working mode of the converter; or the direction of current and energy transmission can be changed to realize the transfer of energy between two inverter circuits of the converter. In order to realize the switching of the energy transmission direction or the repeated transmission of energy between two sides, the invention is realized by controlling the on-off time sequence of the switch tube.
The operation of the isolated bidirectional DCDC converter according to the present invention is described below with reference to the following embodiments.
Example one
Fig. 1 is a schematic diagram showing a circuit configuration of a preferred embodiment of the present invention. As shown in fig. 1, the isolated bidirectional DCDC converter in this embodiment of the present invention includes inverter circuits 10 symmetrically disposed on both sides, each inverter circuit 10 includes three bridge arms, each bridge arm is formed by connecting two switch tubes 11 in series, so that the two inverter circuits 10 include 12 switch tubes 11 (S7, S8, S9, S10, S11, S12, S13, S14, S15, S16, S17, and S18), each inverter circuit 10 is provided with a decoupling circuit connected in parallel to the bridge arm, and each decoupling circuit includes two decoupling capacitors 12, which are C3, C4, C8, and C9; the left inverter circuit 10 is connected with a resonance circuit 20, and the resonance circuit 20 is formed by three groups of resonance capacitors 21(C5, C6 and C7) and resonance inductors 22(L4, L6 and L8) which are connected in series and then are connected with three excitation inductors 23(L5, L7 and L9) of the left inverter circuit 10; and a three-phase transformer 24 including three windings (T1, T2, T3) and connected to the inverter circuit 10 and the resonance circuit.
For the two switching tubes 11 included in each bridge arm, the two switching tubes 11 are defined as a first switching tube and a second switching tube from top to bottom according to the current direction, the source of the first switching tube is connected with the drain of the second switching tube, for example, in this embodiment, the source of the switching tube S7 in the first bridge arm is connected with the drain of S8, the drain of S7 is connected with the drain of the switching tube S9 in the second bridge arm, the source of S9 is connected with the drain of the switching tube S10, the source of S8 is connected with the source of S10, the drain of S9 is connected with the drain of the switching tube S11 in the third bridge arm, the source of S10 is connected with the source of the switching tube S12 in the third bridge arm, and the drain of S11 and the source of S12 are respectively connected with the decoupling capacitor 12. In the inverter circuit on the other side, the switching tubes on the respective bridge arms are also correspondingly connected, that is, the source of the switching tube S17 on the first bridge arm is connected with the drain of S18, the drain of S17 is connected with the drain of the switching tube S15 on the second bridge arm, the source of S15 is connected with the drain of S16, the source of S18 is connected with the source of S16, the drain of S15 is connected with the drain of the switching tube S13 on the third bridge arm, the source of S16 is connected with the source of the switching tube S14 on the third bridge arm, and the drain of S13 and the source of S14 are respectively connected with the decoupling capacitor 12.
In this embodiment, for any side inverter circuit, according to the direction from the input/output end to the resonant circuit, a three-bridge three-phase converter is defined to sequentially include a first phase resonant circuit, a second phase resonant circuit, and a third phase resonant circuit, referring to fig. 1, for the left side of the three-phase transformer, one end of the first phase resonant circuit is connected to the middle point of the first bridge arm of the side inverter circuit, and the other end is connected to the middle point of the decoupling circuit of the side inverter circuit; meanwhile, in the other side of the three-phase transformer, one end of the first-phase resonance circuit is connected with the middle point of the bridge arm of the third bridge arm of the side inverter circuit, and the other end of the first-phase resonance circuit is connected with the middle point of the decoupling circuit of the side inverter circuit; one end of the second phase resonance circuit is connected with the middle point of the bridge arm of the second bridge arm of the side inverter circuit, and the other end of the second phase resonance circuit is connected with the middle point of the decoupling circuit of the side inverter circuit; meanwhile, in the other side of the three-phase transformer, one end of a second phase resonance circuit is connected with the middle point of a bridge arm of a second bridge arm of the side inverter circuit, and the other end of the second phase resonance circuit is connected with the middle point of a decoupling circuit of the side inverter circuit; one end of the third phase resonant circuit is connected with the middle point of the bridge arm of the third bridge arm of the side inverter circuit, and the other end of the third phase resonant circuit is connected with the middle point of the decoupling circuit of the side inverter circuit; meanwhile, in the other side edge of the three-phase transformer, one end of a third phase resonance circuit is connected with the middle point of the bridge arm of the first bridge arm of the side inverter circuit, and the other end of the third phase resonance circuit is connected with the middle point of the decoupling circuit of the side inverter circuit.
Setting the first half cycle of the bidirectional conversion, and transmitting energy from the left inverter circuit 10 to the right inverter circuit 10, wherein the left inverter circuit 10 serves as an input side and the right inverter circuit 10 serves as an output side; in the latter half cycle of the bidirectional conversion, energy is transmitted from the right inverter circuit 10 to the left inverter circuit 10, and at this time, the right inverter circuit 10 serves as an input side and the left inverter circuit 10 serves as an output side. In the first half cycle of the bidirectional conversion, the frequencies of the switching tubes 11 in the arms of the left inverter circuit are set to be the same, and the lags between the arms of the left inverter circuit are set to be 120 degrees, that is, at this time, the lag angle between the arm formed by the switching tubes S7 and S8 and the arm formed by the switching tubes S9 and S10 is 120 degrees, the lag angle between the arm formed by the switching tubes S11 and S12 and the arm formed by the switching tubes S9 and S10 is 120 degrees, and the lag angle between the arm formed by the switching tubes S7 and S8 and the arm formed by the switching tubes S11 and S12 is 120 degrees. The driving signals of the first switching tube and the second switching tube on each bridge arm are two complementary driving signals, that is, at any moment, the first switching tube and the second switching tube are selected to be turned on, and the phase angles between the first switching tube and the second switching tube are different by 180 degrees.
The working process of the first embodiment is as follows:
in this embodiment, taking a complete sequence including 12 valid sequences as an example, fig. 2 to 13 illustrate the complete process of implementing bidirectional conversion in a preferred embodiment, including 12 moments from t1 to t12, i.e., the working process of the first embodiment, which can be divided into 12 valid working sequences, and in particular, the working process can be a process including 12 valid sequences and circulating according to the sequences, i.e., implementing the transfer of energy between two inverter circuits 10; the process may also include the first six times (i.e., time t1 to time t 6) or the last six times (i.e., time t7 to time t 12) of the complete process, and the process is cycled, that is, the directional transmission of energy from the inverter circuit 10 on one side to the inverter circuit 10 on the other side is realized.
Referring to fig. 2, at time T1, the switching timing is S7, S10, S11 is turned on, when the current passes through two resonant circuits consisting of S7, L4, L5, T1, C5, S11, L8, T3, L9, and C7 from the positive electrode, a part of the current passes through C3 and C4 for decoupling, and another part of the current passes through the resonant circuit consisting of C6, L7, T2, L6, and S10 to the negative electrode, the current passing through L6 increases in reverse direction, the current passing through L7 increases in reverse direction, and at this time, the energy is transferred to the secondary side through T1, T2, and T3, i.e., the inverter circuit on the other side, when the switching tubes S13, S14, S15, S16, S17, and S18 on the inverter circuit on the side are turned on, and the energy and the rectified side C8 and C9 filters the rectified side;
referring to fig. 3, at time T2, the switching sequence is S7, S10, S12 is turned on, at this time, the current passes through the resonant circuit composed of S7, L4, L5, T1, C5 from the positive electrode, then a part of the current passes through C3, C4 for decoupling, another part of the current passes through the resonant circuit composed of C6, L7, T2, L6, S10 and C7, L9, T3, L8, S12 to the negative electrode, the current passing through resonant inductors L6 and L8 starts to act, the direction of the current passing through excitation inductor L7 increases, the current passing through excitation inductor L9 increases in the forward direction, the energy passes through T1, T2, T3 to the secondary side, i.e., the inverter circuit on the other side, at this time, the switching tubes S3, S3 and C3 on the inverter circuit on the side, and the rectifier filter the rectified line;
referring to fig. 4, at time T3, the switching sequence is S7, S9, S12 is turned on, at this time, after the current passes through two resonant circuits consisting of S7, L4, L5, T1, C5 and S9, L6, T2, L7, C6 from the positive electrode, a part of the current passes through C3, C4 for decoupling, and another part of the current passes through a resonant circuit consisting of C7, L9, T3, L8, S12 for the negative electrode, the energy is transferred to the secondary side through T1, T2, T3, i.e. the other side inverter circuit, at this time, the switching tubes S13, S14, S15, S16, S17, S18 on the side inverter circuit are turned on, and the energy is rectified and filtered by capacitors C8, C64 and then output to the 9 side;
referring to fig. 5, at time T4, the switching sequence is S8, S9, S12, at this time, after the current passes through the resonant circuit composed of S9, L6, L7, T2, C6 from the positive electrode, a part of the current passes through C3, C4 for decoupling, and another part of the current passes through the resonant circuit composed of C5, L5, T1, L4, S8 and C7, L9, T3, L8, S12 for negative electrode, at this time, the energy is transmitted to the secondary side through T1, T2, T3, i.e. the inverter circuit on the other side, at this time, the switching tubes S13, S14, S15, S16, S17, S18 on the inverter circuit on the other side are turned on, and the energy is rectified and filtered by the capacitors C8, C9 and then output to the side;
referring to fig. 6, at time T5, the switching timing is S8, S9, S11, when the current passes through two resonant circuits consisting of S11, L8, L9, T3, C7, S9, L6, T2, L7, and C6 from the positive electrode, a part of the current passes through C3 and C4 for decoupling, and another part of the current passes through the resonant circuit consisting of C5, L5, T1, L4, and S8 to the negative electrode, at this time, the energy is transferred to the secondary side through T1, T2, and T3, i.e., the inverter circuit on the other side, at this time, the switching tubes S13, S14, S15, S16, S17, and S18 on the inverter circuit on the other side are turned on, and the energy is rectified and filtered by capacitors C8 and C9 and then output to the side;
referring to fig. 7, at time T6, the switching sequence is S8, S10, S11 is turned on, at this time, after the current passes through the resonant network composed of S11, L8, L9, T3, C7 from the positive electrode, a part of the current passes through C3, C4 for decoupling, and another part of the current passes through the resonant circuit composed of S5, L5, T1, L4, S8, C6, L7, T2, L6, S10 for negative electrode, at this time, the energy is transferred to the secondary side through T1, T2, T3, i.e., the other-side inverter circuit, at this time, the switching tubes S13, S14, S15, S16, S17, S18 on the side inverter circuit are turned on, and the energy is rectified and filtered by capacitors C8, C64 and then output to the 9 side;
after the first half cycle is finished, when the current direction needs to be turned, the second half cycle is continued. At this time, the switching tubes 11(S13 to S18) of the right inverter circuit 10 maintain the same operating frequency, and at this time, the hysteresis angle between the arm formed by the switching tubes S13 and S14 and the arm formed by the switching tubes S15 and S16 is 120 degrees, the hysteresis angle between the arm formed by the switching tubes S17 and S18 and the arm formed by the switching tubes S15 and S16 is 120 degrees, and the hysteresis angle between the arm formed by the switching tubes S17 and S18 and the arm formed by the switching tubes S13 and S14 is 120 degrees. Correspondingly, for the first switch tube and the second switch tube on each bridge arm, the drive signals of the first switch tube and the second switch tube are also set to be two complementary drive signals, that is, at any moment, the first switch tube and the second switch tube are selected to be turned on, and the phase angles between the first switch tube and the second switch tube are different by 180 degrees.
Referring to fig. 8, at time T7, the switching timing is S13, S16, S17 is turned on, at this time, after the current flows from the positive electrode through S13, T1, S17, T3, respectively, a part of the current is decoupled through C8, C9, and another part of the current flows through S16, T2 to the negative electrode, at this time, the energy is transferred to the secondary side through T1, T2, T3, i.e., the other side inverter circuit, at this time, the switching tubes S7, S8, S9, S10, S11, S12 on the side inverter circuit are turned on, and the energy and the capacitor C2 are rectified and filtered and then output to the side;
referring to fig. 9, at time T8, the switching timing is S13, S16, S18 is turned on, at this time, after the current flows from the positive electrode through S13 and T1, respectively, a part of the current is decoupled through C8 and C9, and another part of the current flows through S16, T2, S18, and T3, respectively, to the negative electrode, at this time, the energy is transferred to the secondary side through T1, T2, and T3, that is, the inverter circuit on the other side, at this time, the switching tubes S7, S8, S9, S10, S11, and S12 on the inverter circuit on the side are turned on, and the energy and the capacitor C2 are rectified and filtered and then output to the side;
referring to fig. 10, at time T9, the switching timing is S13, S15, S18 is turned on, at this time, after the current flows from the positive electrode through S13, T1, S15, and T2, respectively, a part of the current is decoupled through C8 and C9, and another part of the current flows through S18 and T3 to the negative electrode, at this time, the energy is transferred to the secondary side through T1, T2, and T3, i.e., the other side inverter circuit, at this time, the switching tubes S7, S8, S9, S10, S11, and S12 on the side inverter circuit are turned on, and the energy and the capacitor C2 are rectified and filtered to be output to the side;
referring to fig. 11, at time T10, the switching timing is S14, S15, and S18 are turned on, at this time, after the current respectively flows through S15 and T2 from the positive electrode, a part of the current is decoupled through C8 and C9, and another part of the current respectively flows through S14, T1, S18, and T3 to the negative electrode, at this time, the energy is transferred to the secondary side through T1, T2, and T3, i.e., the other side inverter circuit, at this time, the switching tubes S7, S8, S9, S10, S11, and S12 on the side inverter circuit are turned on, and the energy and the capacitor C2 are rectified and filtered and then output to the side;
referring to fig. 12, at time T11, the switching timing is S14, S15, S17 is turned on, at this time, after the current flows from the positive electrode through S17, T3, S15, and T2, respectively, a part of the current is decoupled through C8 and C9, and another part of the current flows through S14 and T1 to the negative electrode, at this time, the energy is transferred to the secondary side through T1, T2, and T3, i.e., the other side inverter circuit, at this time, the switching tubes S7, S8, S9, S10, S11, and S12 on the side inverter circuit are turned on, and the energy and the capacitor C2 are rectified and filtered to be output to the side;
referring to fig. 13, at time T12, the switching timings S14, S16, and S17 are turned on, and at this time, after the current flows from the positive electrode through S17 and T3, respectively, a part of the current is decoupled through C8 and C9, and another part of the current flows through S14, T1, S16, and T2, respectively, to the negative electrode, and at this time, the energy is transferred to the secondary side through T1, T2, and T3, that is, the inverter circuit on the other side, at this time, the switching tubes S7, S8, S9, S10, S11, and S12 on the inverter circuit on the one side are turned on, and the energy and the capacitor C2 are rectified and filtered and then output to the.
Example two
Fig. 14 is a schematic diagram illustrating a circuit configuration of an isolated bidirectional DCDC converter according to another preferred embodiment of the present invention. Referring to fig. 14, in this embodiment of the present invention, the isolated bidirectional DCDC converter is a four-leg four-phase LLC resonant converter. The difference from the first embodiment is that the inverter circuits on both sides of the four-phase transformer are formed by connecting four arms in parallel, the lag angle between the arms is changed from 120 degrees of the three arms to 90 degrees, that is, the energy is transmitted from the left inverter circuit 10 to the right inverter circuit 10 in the first half cycle of the bidirectional conversion, and then the left inverter circuit 10 is used as the input side and the right inverter circuit 10 is used as the output side; in the latter half cycle of the bidirectional conversion, energy is transmitted from the right inverter circuit 10 to the left inverter circuit 10, and at this time, the right inverter circuit 10 serves as an input side and the left inverter circuit 10 serves as an output side. In the first half cycle of the bidirectional conversion, the frequencies of the switching tubes 11 in the arms of the left inverter circuit are set to be the same, and the lags between the arms of the left inverter circuit are set to be 90 degrees, that is, at this time, the lag angle between the arm formed by the switching tubes S7 and S8 and the arm formed by the switching tubes S9 and S10 is 90 degrees, the lag angle between the arm formed by the switching tubes S11 and S12 and the arm formed by the switching tubes S9 and S10 is 90 degrees, the lag angle between the arm formed by the switching tubes S13 and S14 and the arm formed by the switching tubes S11 and S12 is 90 degrees, and the lag angle between the arm formed by the switching tubes S7 and S8 and the arm formed by the switching tubes S13 and S14 is 90 degrees. For the two switching tubes 11 included in each bridge arm, the two switching tubes 11 are defined as a first switching tube and a second switching tube from top to bottom according to the current direction, the source electrode of the first switching tube is connected with the drain electrode of the second switching tube, and then the driving signals for the first switching tube and the second switching tube on each bridge arm are two complementary driving signals, that is, at any moment, the first switching tube and the second switching tube are selectively turned on, and the phase angles between the first switching tube and the second switching tube are different by 180 degrees. The rule of the second half cycle is consistent with the change rule in the first embodiment, and details are not repeated here.
The two inverter circuits 10 include 16 switching tubes 11 (S7, S8, S9, S10, S11, S12, S13, S14, S15, S16, S17, S18, S19, S20, S21, and S22, respectively), each inverter circuit 10 is provided with a decoupling circuit connected in parallel with a bridge arm, and each decoupling circuit includes two decoupling capacitors 12, namely C3, C4, C9, and C10; the left inverter circuit 10 is connected with a resonance circuit 20, and the resonance circuit 20 is formed by three groups of resonance capacitors 21(C5, C6, C7 and C8) and resonance inductors 22(L4, L6, L8 and L10) which are connected in series and then are connected with three excitation inductors 23(L5, L7, L9 and L11) of the left inverter circuit 10; and a four-phase transformer 24 including three windings (T1, T2, T3, T4) and connected to the inverter circuit 10 and the resonance circuit.
The operation process of the second embodiment is similar to that of the first embodiment, but should include (2^4) × 2, i.e. 32 valid timings, and is not described herein again.
Correspondingly, the invention also provides a current bidirectional control method of various preferred embodiments of the invention including the first embodiment and the second embodiment. Fig. 15 is a flowchart showing a flow of a current bidirectional control method according to the present invention, and referring to fig. 15, the method according to this embodiment includes a step S1 of configuring a hysteresis angle between bridge arms and a phase angle difference of a switching tube; step S2 of switching on and off time sequence of the switch tube when the configuration energy is transmitted from the inverter circuit on any side to the other side; step S3, configuring the converter to switch the energy transfer direction and/or transferring energy between two inverter circuits of the converter. In step S2, in the on-off sequence of the switching tubes, if the driving signals of the switching tubes on any one of the bridge arms are two complementary driving signals, the switching tube is connected to one of the bridge arms.
Compared with the prior art, the invention has the following beneficial technical effects due to the adoption of the technical scheme:
1. by arranging the two symmetrical inverter circuits, when energy is transmitted from one side of the two inverter circuits to the other side, the two inverter circuits can be respectively used as an input side or an output side, so that the modulation and rectification functions are respectively realized, the on-off of a switching tube on a three-bridge arm used as the input side is controlled, so that the current output by a resonance tank on the input side is close to a sine wave, the sine currents with the three phases different by 120 degrees are equivalent to a direct current, and the ripple current on a filter capacitor is remarkably reduced in the process;
2. because the ripple current on the filter capacitor is reduced, the technical scheme can realize three-phase full-bridge bidirectional conversion on the premise of ensuring that the ripple current is reduced so as to ensure that the system is applied in a composite high-power occasion, namely, two inverter circuits are respectively used as an input side and an output side, and the alternation of the inverter circuits is realized by controlling the channels of the switching tubes on the bridge arms according to a certain period, so that the three-phase full-bridge bidirectional conversion is realized on the basis of the prior art, and energy can be transmitted on two sides of the three-phase full bridge and/or the switching of the energy transmission direction is realized;
3. when energy is transmitted between the two inverter circuits, the switch tubes in the half-bridge LLC on one side are in a soft-switching state, and most of the switch tubes in the half-bridge LLC on the other side work in the soft-switching state, so that the conversion efficiency in the energy transmission process is obviously improved;
4. the full-bridge rectification mode is adopted to replace the mode of realizing current-doubling rectification through a diode and a corresponding inductor in the prior art, so that the redundancy of the system is obviously reduced, the currents of the resonant tanks in the three-phase resonant circuit are independent, and the mutual influence of the currents of the resonant tanks is avoided;
5. compared with the mode of connecting a single-phase full-bridge LLC resonant converter in parallel, the number of the switching devices is reduced from 24 to 12, the cost of an equipment system is reduced, the overall size of the equipment is reduced, and the overall operation stability of the equipment is improved by reducing components;
6. by setting a lag angle for a switching tube between each bridge arm of the inverter circuit, the superposed output current ripple is obviously reduced, the problem of large output capacitance ripple is effectively solved, the technical limit that the bidirectional DCDC converter is suitable for high-power conversion occasions is solved, and the application range of equipment is expanded;
7. decoupling capacitors are respectively arranged on the two inverter circuits, and when any inverter circuit is used as an output side circuit, the decoupling capacitors filter the interference of output signals, prevent the interference signals from returning to a power supply and avoid mutual coupling interference.
The present invention has been described in detail, and the embodiments are only used for understanding the method and the core idea of the present invention, and the purpose of the present invention is to enable those skilled in the art to understand the content of the present invention and to implement the present invention, and not to limit the protection scope of the present invention. All equivalent changes and modifications made according to the spirit of the present invention should be covered within the protection scope of the present invention.
Claims (9)
1. An isolated bidirectional DCDC converter, comprising:
the bridge comprises two inverter circuits formed by connecting at least three bridge arms in parallel, wherein each bridge arm is formed by connecting at least two switching tubes in series;
the resonant circuit is formed by at least three groups of resonant capacitors and resonant inductors which are connected in series and at least three excitation inductors on the inverter circuit on any side of the at least three-phase transformer;
at least three-phase transformer with at least three windings connected with the two inverter circuits and the resonant circuit,
when energy is transmitted to the other side from any one side of the two inverter circuits, the inverter circuit serving as an input side inverts the direct-current voltage into a square wave or step wave voltage, the inverter circuit serving as an output side forms a rectification circuit, and the pulse current provided by the at least three-phase transformer is converted into the direct-current voltage providing energy for the circuit on the output side to be output.
2. The isolated bidirectional DCDC converter according to claim 1, wherein each of the inverter circuits is connected in parallel with a decoupling circuit, and the decoupling circuit is formed by connecting at least two decoupling capacitors in series.
3. The isolated bidirectional DCDC converter according to claim 2, wherein when the inverter circuit on any side is used as an output side, the switching tubes in the bridge arms thereon use the same frequency, wherein,
when the inverter circuit on any side serves as an output side, the switching tubes on each bridge arm are respectively defined as a first switching tube and a second switching tube according to the current direction, the source electrode of the first switching tube is connected with the drain electrode of the second switching tube, the phase angles of the second switching tube and the first switching tube in each bridge arm are different by 180 degrees, and hysteresis is formed between the bridge arms according to a preset angle.
4. The isolated bidirectional DCDC converter according to claim 3, wherein in the resonant circuit, the excitation inductor is an external inductor connected in parallel with one side of the N-phase transformer, and the resonant inductor is an external inductor or a leakage inductor of the N-phase transformer, wherein,
the excitation inductor is connected with one side of the N-phase transformer in parallel and then connected with the resonance inductor and the resonance capacitor in series to form a branch circuit of the resonance circuit.
5. The isolated bidirectional DCDC converter of claim 4, wherein N-phase transformers comprising N legs of {1, 2, 3 … N-1, N } and {1, 2, 3 … N-1, N } are defined, and for the m-th phase resonant circuit of the N-phase transformers, wherein,
in one side edge of the N-phase transformer, one end of the mth phase resonant circuit is connected with the middle point of the bridge arm of the mth bridge arm of the inverter circuit on the side, and the other end of the mth phase resonant circuit is connected with the middle point of the decoupling circuit of the inverter circuit on the side;
in the other side edge of the N-phase transformer, one end of the m-th phase resonance circuit is connected with the middle point of the bridge arm of the (N +1-m) -th bridge arm of the inverter circuit at the side, and the other end of the m-th phase resonance circuit is connected with the middle point of the decoupling circuit of the inverter circuit at the side.
6. The isolated bidirectional DCDC converter of any one of claims 1 to 5, wherein said switching tubes are connected in anti-parallel with diodes.
7. The isolated bidirectional DCDC converter of any one of claims 1 to 5, wherein said switching transistor is a metal oxide semiconductor field effect transistor.
8. A bidirectional DCDC current control method based on the isolated bidirectional DCDC converter of claims 1-7, characterized in that said method comprises:
step S1 of configuring the lag angle between the bridge arms and the phase angle difference of the switching tubes;
step S2 of switching on and off time sequence of the switch tube when the configuration energy is transmitted from the inverter circuit on any side to the other side;
step S3, configuring the converter to switch the energy transfer direction and/or transferring energy between two inverter circuits of the converter.
9. The bidirectional DCDC current control method according to claim 8, wherein in the step S2, in the on-off timing sequence of the switching tubes, the driving signals of the switching tubes on any one of the arms are two complementary driving signals, and the switching tubes are alternatively connected for any one of the arms.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN202010106345.0A CN111193398A (en) | 2020-02-21 | 2020-02-21 | Isolated bidirectional DCDC converter and current bidirectional control method |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN202010106345.0A CN111193398A (en) | 2020-02-21 | 2020-02-21 | Isolated bidirectional DCDC converter and current bidirectional control method |
Publications (1)
| Publication Number | Publication Date |
|---|---|
| CN111193398A true CN111193398A (en) | 2020-05-22 |
Family
ID=70710166
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN202010106345.0A Withdrawn CN111193398A (en) | 2020-02-21 | 2020-02-21 | Isolated bidirectional DCDC converter and current bidirectional control method |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN111193398A (en) |
Cited By (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN112564497A (en) * | 2020-12-02 | 2021-03-26 | 阳光电源股份有限公司 | Three-phase LLC resonant DC converter |
| CN113067479A (en) * | 2021-03-25 | 2021-07-02 | 国文电气股份有限公司 | Charging module DC/DC topological circuit |
| CN116260344A (en) * | 2023-05-15 | 2023-06-13 | 西安图为电气技术有限公司 | Multiphase resonant circuit and power supply device |
Citations (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| EP1708350A2 (en) * | 2005-03-30 | 2006-10-04 | E2V Technologies (UK) Limited | AC-DC Converters |
| CN202759382U (en) * | 2012-08-10 | 2013-02-27 | 江苏嘉茵泰电气科技有限公司 | Heavy-current high-frequency isolated DC-DC converter |
| CN107294392A (en) * | 2017-08-11 | 2017-10-24 | 何晓东 | A kind of bidirectional DC/DC converter |
| CN110289766A (en) * | 2019-06-21 | 2019-09-27 | 南京工程学院 | A kind of two-way three-phase LLC resonant converter |
| CN110401352A (en) * | 2019-07-12 | 2019-11-01 | 国创新能源汽车能源与信息创新中心(江苏)有限公司 | A kind of two-way resonance converter |
-
2020
- 2020-02-21 CN CN202010106345.0A patent/CN111193398A/en not_active Withdrawn
Patent Citations (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| EP1708350A2 (en) * | 2005-03-30 | 2006-10-04 | E2V Technologies (UK) Limited | AC-DC Converters |
| CN202759382U (en) * | 2012-08-10 | 2013-02-27 | 江苏嘉茵泰电气科技有限公司 | Heavy-current high-frequency isolated DC-DC converter |
| CN107294392A (en) * | 2017-08-11 | 2017-10-24 | 何晓东 | A kind of bidirectional DC/DC converter |
| CN110289766A (en) * | 2019-06-21 | 2019-09-27 | 南京工程学院 | A kind of two-way three-phase LLC resonant converter |
| CN110401352A (en) * | 2019-07-12 | 2019-11-01 | 国创新能源汽车能源与信息创新中心(江苏)有限公司 | A kind of two-way resonance converter |
Non-Patent Citations (1)
| Title |
|---|
| ARIEF NOOR RAHMAN,ET AL,: "Bidirectional Three-Phase LLC Resonant Converter", 《2018 IEEE TRANSPORTATION ELECTRIFICATION CONFERENCE AND EXPO, ASIA-PACIFIC 》 * |
Cited By (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN112564497A (en) * | 2020-12-02 | 2021-03-26 | 阳光电源股份有限公司 | Three-phase LLC resonant DC converter |
| CN113067479A (en) * | 2021-03-25 | 2021-07-02 | 国文电气股份有限公司 | Charging module DC/DC topological circuit |
| CN116260344A (en) * | 2023-05-15 | 2023-06-13 | 西安图为电气技术有限公司 | Multiphase resonant circuit and power supply device |
| CN116260344B (en) * | 2023-05-15 | 2024-03-08 | 西安图为电气技术有限公司 | Multiphase resonant circuit and power supply device |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| US10958180B2 (en) | DC-DC converter for wide input voltage | |
| WO2021237503A1 (en) | Three-phase cllc bidirectional direct current transformer and control method therefor | |
| US8559193B2 (en) | Zero-voltage-switching scheme for high-frequency converter | |
| US9520792B2 (en) | Staggered parallel three-level DC/DC converter and AC/DC converter | |
| EP3337024B1 (en) | Bidirectional resonant conversion circuit and converter | |
| EP2722979A1 (en) | Switch mode converter including auxiliary commutation circuit for achieving zero current switching | |
| CN108988676B (en) | Single-stage isolated bidirectional AC-DC converter | |
| CN103595287A (en) | Method for controlling double-direction power flow high-frequency isolated active clamping inverter | |
| EP3734824B1 (en) | Method for controlling a power conversion circuit and related power conversion circuit | |
| CN109921653B (en) | Single-phase power electronic transformer topological structure and control method thereof | |
| EP2537241A1 (en) | Dc-dc converter circuit for high input-to-output voltage conversion | |
| CN111193398A (en) | Isolated bidirectional DCDC converter and current bidirectional control method | |
| CN114301301A (en) | Wide-range resonant soft-switching bidirectional direct-current converter and control method thereof | |
| CN217087777U (en) | Wide-range resonant soft-switching bidirectional direct-current converter | |
| CN101521460B (en) | Multi-channel output direct current-direct-current converter | |
| US7142439B2 (en) | Zero-voltage-switching single-switched resonant DC link with minimized conduction loss | |
| CN101465605B (en) | Flexible DC-DC converter with wide input range and variable topological | |
| CN112202351A (en) | Single-stage isolated three-phase AC/DC rectifier of wide-range soft switch | |
| WO2020134313A1 (en) | Full-bridge circuit and full-bridge converter | |
| CN103856061A (en) | Full-range soft switching method of input-series output-paralleled phase-shifted full-bridge convertor | |
| CN1127796C (en) | Two-way DC-DC converter | |
| CN212677095U (en) | Three-port bidirectional power converter | |
| CN115912920A (en) | Control method and control circuit of bidirectional resonant DC converter | |
| CN201378796Y (en) | Multiplexed output DC-DC convertor | |
| CN210958160U (en) | Soft switching circuit |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| PB01 | Publication | ||
| PB01 | Publication | ||
| SE01 | Entry into force of request for substantive examination | ||
| SE01 | Entry into force of request for substantive examination | ||
| WW01 | Invention patent application withdrawn after publication | ||
| WW01 | Invention patent application withdrawn after publication |
Application publication date: 20200522 |