CN1379540A - Intensified full-bridge phase-shift soft switch method and converter - Google Patents
Intensified full-bridge phase-shift soft switch method and converter Download PDFInfo
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- CN1379540A CN1379540A CN02121903A CN02121903A CN1379540A CN 1379540 A CN1379540 A CN 1379540A CN 02121903 A CN02121903 A CN 02121903A CN 02121903 A CN02121903 A CN 02121903A CN 1379540 A CN1379540 A CN 1379540A
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- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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Abstract
This invention relates a reinforcement full bridge phase-shift soft-switch method and a converter used in power source or power system, including a full bridge phase-shift circuit made up from switch tubes and a primary side end inductor L1 serial-connected to the transformer. It is characterized by the said full bridge phase-shift circuit connecting to the voltage resonant network which enables delayed switch tubes to have the complete zero voltage when turned-on, and to suppress the peak voltage of output commutation diode. The voltage resonant network comprises connecting points parallel-connected to the transformer primaryside, inductory L1 connecting point, capacitor C1 at both ends of input voltage, diode D1 and capacitor C2 and diode D2 to form voltage resonance via inductor L1 serial-connected to the transformer primary side.
Description
[technical field]
The present invention relates to be used for the transform method and the equipment of power supply or similarly electric power system, relate in particular to a kind of intensified full-bridge phase-shift soft switch method and converter.
[background technology]
The full-bridge phase-shift soft switch technology can realize that the no-voltage of switching tube is open-minded, obtained extensive use in the high-power applications scope, its basic topology as shown in Figure 1, four switching tube Q1, Q2, Q3 and Q4 drive near 50% duty ratio among Fig. 1, wherein switching tube Q1 and Q2 complementary drive, switching tube Q3 and Q4 complementary drive; The driving of switching tube Q4 postpones certain angle with respect to switching tube Q1, assumed initial state is switching tube Q1, the Q4 conducting, then energy is delivered to time limit from former limit, suppose output rectifying tube DR1 conducting, if this moment, switching tube Q1 turn-offed, then primary current is to the junction capacitance charging of switching tube Q1, simultaneously the junction capacitance of switching tube Q2 is discharged, when switching tube Q1 junction capacitance voltage was Vin, switching tube Q2 junction capacitance voltage was zero, the inverse parallel body diode conducting of switching tube Q2, because the conducting of switching tube Q2 inverse parallel body diode, open switching tube Q2 this moment is that no-voltage is open-minded; This moment, primary current passed through the body diode of switching tube Q2, inductance L 1, switching tube Q4 afterflow; On-off switching tube Q4 behind the certain hour, then the electric current in the inductance L 1 is to the junction capacitance charging of switching tube Q4, junction capacitance discharge to switching tube Q3, when switching tube Q4 both end voltage is Vin, the body diode conducting of switching tube Q3, open switching tube Q3 this moment is that no-voltage is open-minded, in like manner can analyze switching tube Q1, and Q4 can both realize that no-voltage is open-minded; But for switching tube Q1, Q2 and Q3, the Q4 process is different, mainly is switching tube Q1, the energy that the opening process of Q2 is taken junction capacitance away is that inductance L 1 adds that inductance L 2 reflexes to the energy on former limit, take switching tube Q3 away, the energy of Q4 is the energy in the inductance L 1, claims that generally switching tube Q1, Q2 are advance pipe, this part is leading arm, switching tube Q3, Q4 are the pipe that lags behind, and this part is a lagging leg, and the no-voltage of hysteresis pipe is opened and had difficulties under underloading; After switching tube Q3 opened, there was the voltage input on the former limit of transformer, because junction capacitance and the reverse recovery characteristic thereof of output rectifying tube DR1 will cause the vibration of output rectifying tube DR1 both end voltage.
By last analysis as can be known, full-bridge phase shifting still has following problem:
1. the energy of taking the lagging leg junction capacitance away is less, and it is open-minded possibly can't to reach no-voltage like this when underloading, thereby the underloading loss is bigger.
2. output rectifying tube commutation course causes the both end voltage vibration, increases diode losses and voltage stress.
For overcoming the above problems, at present, the employing auxiliary network that has, as shown in Figure 2, its principle is when switching tube Q3 or Q4 open, auxiliary capacitor and inductance resonance, its inverse parallel diode current flow when the electric capacity both end voltage is zero, electric current is approximate constant in the auxiliary induction, when switching tube Q3 or Q4 shutoff, in the resonant inductance in electric current and the inductance L 1 electric current take the energy of switching tube Q3 and Q4 junction capacitance together away, the voltage oscillation of the output rectifying tube commutation process of this method still exists.
[summary of the invention]
The object of the present invention is to provide high intensified full-bridge phase-shift soft switch method of a kind of stable working and efficient and converter.
The technical solution adopted in the present invention is: realize that by the full-bridge phase shifting circuit that switching tube constitutes the no-voltage of switching tube is open-minded, it is characterized in that: primary side end and Input voltage terminal at transformer insert the voltage resonance network, when finishing, the capacitor charge and discharge of voltage resonance network carries out the change of current, at this moment, voltage is zero on the electric capacity in the voltage resonance network, another capacitance voltage is an input voltage, with the conducting of electric capacity diode connected in parallel, thereby transformer original edge voltage clamper in input voltage, is suppressed due to voltage spikes on the output rectifying tube.
In the intensified full-bridge phase-shift soft switch converter, constitute the full-bridge phase shifting circuit by switching tube, the inductance L 1 that comprises the primary side end that is serially connected with transformer, it is characterized in that: described full-bridge phase shifting circuit inserts and is connected to the primary side end of transformer and the voltage resonance network of Input voltage terminal, this voltage resonance network makes the hysteresis switching tube realize that complete no-voltage is open-minded, and suppresses the peak voltage of output rectifying tube DR1, DR2; The voltage resonance network comprises the primary side end that is connected to transformer respectively and capacitor C 1 and diode D1 and the capacitor C 2 and the diode D2 at inductance L 1 tie point M and input voltage two ends.
Principle of the present invention and beneficial effect are: in the present invention, finish when the electric capacity of voltage resonance network and to carry out the change of current when discharging and recharging, this moment wherein on the electric capacity voltage be zero, another capacitance voltage is an input voltage, thereby with the conducting of electric capacity diode connected in parallel will-with transformer original edge voltage clamper in input voltage, suppress output rectifying tube DR1, the last due to voltage spikes of DR2, adopt after this voltage resonance network, at diode D1, in the D2 commutation process, when a rectifying tube turn-offs, though there is reverse recovery current, but because diode D1, the clamping action of D2, output rectifying tube DR1, DR2 commutation course oscillatory occurences will disappear, and make to export rectifying tube DR1, the DR2 stable working, there is not due to voltage spikes, raises the efficiency; Select suitable auxiliary capacitor C1 and C2 and resonant inductance L1 simultaneously, the no-voltage that can obtain lagging leg in whole loading range is open-minded, improvement during particularly to the higher and underloading of switching frequency clearly, contrast adopts the technology of auxiliary network not need extra auxiliary induction, has further simplified circuit; Adopt booster diode can the due to voltage spikes of rectifying tube be suppressed to some extent separately, as shown in Figure 3, adopt booster diode D1, D2, in output rectifying tube commutation process, original edge voltage is clamped on input voltage, alleviate the vibration at rectifying tube two ends, when output rectifying tube commutation process, because the reverse recovery characteristic of output rectifying tube, cause transformer time limit electric current current reflection to former limit, the effect of former limit inductance, electric current can not be suddenlyd change, so booster diode D1, the D2 conducting, with transformer original edge voltage clamper at input voltage value Vin, making does not have the spike appearance on the output rectifying tube, be illustrated in figure 4 as the electric current sequential of transformer original edge voltage and booster diode in the scheme of this independent employing booster diode, Fig. 5 then is the electric current sequential of the original edge voltage of the corresponding transformer of the present invention and booster diode, clearly, the present invention and the independent scheme of booster diode that adopts are different on principle, the present invention is the booster diode stable working not only, the due to voltage spikes that has suppressed rectifying tube, and, the improvement of the present invention during to the higher and underloading of switching frequency clearly, this be this independent employing booster diode scheme can not compare; In the present invention, the voltage resonance network adopts the former limit that is connected to transformer and capacitor C 1 and diode D1 and the capacitor C 2 and the diode D2 at inductance L 1 tie point M and input voltage two ends simply, and structure is also comparatively simple.
In a word, the present invention is simple in structure, can suppress due to voltage spikes effectively, raises the efficiency, and the no-voltage that can obtain in whole loading range is open-minded.
[description of drawings]
Fig. 1 is the full-bridge phase-shift soft switch circuit theory diagrams;
Fig. 2 is prior art scheme one circuit diagram;
Fig. 3 is prior art scheme two circuit diagrams;
Fig. 4 is the original edge voltage of transformer in the prior art scheme two and the electric current sequential schematic diagram of booster diode;
Fig. 5 is the original edge voltage of transformer of the present invention and the electric current sequential schematic diagram of booster diode;
Fig. 6 is a circuit diagram of the present invention;
Fig. 7 is stage 1 a circuit equivalent schematic diagram;
Fig. 8 is stages 2 circuit equivalent schematic diagrames;
Fig. 9 is stages 3 circuit equivalent schematic diagrames;
Figure 10 is stages 4 circuit equivalent schematic diagrames;
Figure 11 is stages 5 circuit equivalent schematic diagrames;
Figure 12 is stages 6 circuit equivalent schematic diagrames;
Figure 13 is stages 7 circuit equivalent schematic diagrames;
Figure 14 is stages 8 circuit equivalent schematic diagrames;
Figure 15 is stages 9 circuit equivalent schematic diagrames;
Figure 16 is stages 10 circuit equivalent schematic diagrames;
Figure 17 is stages 11 circuit equivalent schematic diagrames;
Figure 18 is stages 12 circuit equivalent schematic diagrames;
Figure 19 is main devices electrical characteristics sequential schematic diagram in the circuit of the present invention;
Figure 20 is the voltage and current actual waveform figure of output rectifying tube;
Switching tube Q2, switching tube Q4, voltage resonance network mid point M and transformer primary current actual waveform figure when Figure 21 is unloaded;
Figure 22 is used for the application schematic diagram of three level for the voltage resonance network.
[embodiment]
With embodiment the present invention is described in further detail with reference to the accompanying drawings below:
According to Fig. 6, switching tube Q1, Q2, Q3 and Q4 constitute basic full-bridge phase shifting circuit, the inductance L 1 that also comprises the primary side end that is serially connected with transformer, the full-bridge phase shifting circuit inserts the voltage resonance network, this voltage resonance network comprises former limit and the tie point M of inductance L 1 and the capacitor C 1 and the diode D1 at input voltage two ends that is connected to transformer respectively, and capacitor C 2 and diode D2, form voltage resonance by the inductance L 1 that is serially connected with the former limit of transformer, this design can realize that the no-voltage under the underloading condition is open-minded, and in the commutation process because auxiliary capacitor C1, C2 and diode D1, the effect of D2, can suppress output rectifying tube DR1, the voltage oscillation of DR2 is raised the efficiency.
When finishing, the capacitor charge and discharge of voltage resonance network carries out the change of current, this moment wherein on the electric capacity voltage be zero, another capacitance voltage is an input voltage, conducting with the electric capacity diode connected in parallel, thereby with transformer original edge voltage clamper in input voltage, the appearance of restriction output rectifying tube DR1, the last due to voltage spikes of DR2 is illustrated in figure 5 as the original edge voltage of transformer of the present invention and the electric current sequential schematic diagram of diode D1.
For the present invention, the course of work of entire circuit can be divided into 12 stages, the equivalent electric circuit such as the Fig. 7 to Figure 18 in each stage, the course of work in each stage of detailed description below.
Stage 1 (t0-t1): output rectifying tube DR2 turn-offs, diode D2 conducting, from former limit to inferior limit transmission of power, as shown in Figure 7, switching tube Q1 and Q4 conducting, diode D2 conducting, rectifying tube DR1 conducting, electric current flows through switching tube Q1, transformer, resonant inductance L1, switching tube Q4, transformer energy is delivered to output, because electric current is greater than the transformer primary current among the resonant inductance L1, have electric current to flow through among the diode D2, this moment main devices electrical characteristics sequential as shown in figure 19, in Figure 19: waveform a1 is the waveform of switching tube Q1 driving voltage;
Waveform a2 is the waveform of switching tube Q2 driving voltage;
Waveform a3 is the waveform of switching tube Q3 driving voltage;
Waveform a4 is the waveform of switching tube Q4 driving voltage;
Waveform a5 is leading arm mid-point voltage waveform;
Waveform a6 is a lagging leg mid-point voltage waveform;
Waveform a7 is a voltage resonance network mid-point voltage waveform;
Waveform a8 is the transformer input voltage waveform;
Waveform a9 is the transformer imput current waveform;
Waveform a10 is the inductive current waveform;
Waveform a11 is a transformer time limit output voltage waveforms;
Waveform a12 is a rectifying tube DR1 current waveform;
Waveform a13 is a rectifying tube DR2 current waveform.
Stage 2 (t1-t2): switching tube Q1 turn-offs, leading arm junction capacitance discharges and recharges, and as shown in Figure 8, switching tube Q1 turn-offs constantly at t1, transformer primary current switching tube Q1 junction capacitance Cq1 charging, the Cq2 discharge, output still is rectifying tube DR1 conducting, this moment, the inductance to leading arm charging resonance comprised the value of time limit inductive feedback to former limit, transformer leakage inductance, resonant inductance L1, diode D2 still keeps conducting simultaneously, and main devices electrical characteristics sequential is as shown in figure 19 at this moment.
Stage 3 (t2-t3): switching tube Q2 no-voltage conducting, output rectifying tube DR1 afterflow conducting, as shown in Figure 9, at t2 constantly, capacitor C q1 voltage equals Vin, Cq2 voltage is zero, the body diode nature conducting of switching tube Q2, the former limit of transformer this moment input voltage is zero, at this moment, still not conducting of output rectifying tube DR2, transformer primary current are converted inferior limit by output rectifying tube DR1 afterflow.In the time of switching tube Q2 body diode conducting, opening switching tube Q2 constantly at t3, will to obtain no-voltage open-minded, because electric current is greater than former primary electric current among the resonant inductance L1, diode D2 still keeps conducting.In this process, because still for inferior limit provides energy, primary current constantly reduces, main devices electrical characteristics sequential as shown in figure 19 at this moment.
Stage 4 (t4-t5): switching tube Q4 turn-offs, the lagging leg junction capacitance discharges and recharges, as shown in figure 10, and at t4 moment on-off switching tube Q4, lagging leg brachium pontis electric capacity and resonance inductance L 1 resonance, capacitor C q4 voltage will rise, and capacitor C q3 voltage reduces, and equal Vin up to t5 moment capacitor C q4 voltage, this moment, capacitor C q3 voltage equalled zero, this moment, the resonant inductance electric current was still not reverse, so the conducting of switching tube Q3 body diode, and main devices electrical characteristics sequential as shown in figure 19 at this moment.
Stage 5 (t5-t6): switching tube Q3 no-voltage is open-minded, inductance L 1 current attenuation is to former limit leakage inductance electric current, as shown in figure 11, opening switching tube Q3 constantly at t6 is that no-voltage is open-minded, comprising the body diode conducting, diode D2 conducting, when therefore electric current arrives the former limit of transformer leakage inductance electric current with linear attenuation in the inductance L 1, diode D2 will turn-off naturally, before this, voltage on capacitor C 1 and the C2 is respectively Vin and zero, and inferior limit still is output rectifying tube DR1 afterflow conducting, and main devices electrical characteristics sequential as shown in figure 19 at this moment.
Stage 6 (t6-t7): capacitor C 1, C2 and inductance L 1, transformer leakage inductance resonance, as shown in figure 12, because former limit leakage inductance electric current is arrived in the resonant inductance current attenuation, diode D2 turn-offs, this moment rectifying tube DR1 and DR2 conducting simultaneously, transformer input voltage pincers be zero, but this moment leakage inductance still in action; Therefore, capacitor C 1, C2 will with inductance L 1 and leakage inductance resonance, capacitor C 1 voltage reduces, and capacitor C 2 voltages rise, because the transformer primary current changes, current reversal also constantly increases, convert and pay the limit and make that electric current constantly reduces among the output rectifying tube DR1, electric current constantly increases among the output rectifying tube DR2, this moment main devices electrical characteristics sequential as shown in figure 19.
Stage 7 (t7-t8): diode D1 conducting, output rectifying tube DR1 turn-offs, from former limit to inferior limit transmission of power, as shown in figure 13, in t7 diode D1 nature conducting constantly, primary current flows through switching tube Q3, inductance L 1, to output, diode D1 also keeps conducting simultaneously with power transfer for transformer, switching tube Q2; Meanwhile export rectifying tube DR1 and constantly be reduced to zero, electric current constantly increases among the output rectifying tube DR2, and DR1 turn-offs up to the output rectifying tube, and output rectifying tube DR2 flows through whole electric currents, and energy is delivered to time limit from former limit.In the moment of exporting rectifying tube DR1 shutoff, though there is reverse recovery current, because diode D1 clamps the transformer original edge voltage at Vin, oscillatory occurences will disappear when therefore exporting rectifying tube DR1 shutoff, and main devices electrical characteristics sequential as shown in figure 19 at this moment.
Stage 8 (t8-t9): as shown in figure 14, switching tube Q2 turn-offs, and leading arm junction capacitance discharges and recharges, and main devices electrical characteristics sequential as shown in figure 19 at this moment.
Stage 9 (t9-t10): as shown in figure 15, switching tube Q1 no-voltage is open-minded, output rectifying tube DR2 afterflow conducting, and main devices electrical characteristics sequential is as shown in figure 19 at this moment.
Stage 10 (t10-t11): as shown in figure 16, switching tube Q3 turn-offs, and the lagging leg junction capacitance discharges and recharges, and main devices electrical characteristics sequential as shown in figure 19 at this moment.
Stage 11 (t11-t12): as shown in figure 17, switching tube Q4 no-voltage is open-minded, and the auxiliary induction current attenuation is to zero, and main devices electrical characteristics sequential as shown in figure 19 at this moment.
Stage 12: begin again a new cycle this moment, as shown in figure 18, capacitor C 1, C2 and auxiliary induction, transformer leakage inductance resonance, main devices electrical characteristics sequential is as shown in figure 19 at this moment.
The process in above stage 8 to stage 12 is similar to stage 2 to the stage 6 respectively, and only the commutation process of another brachium pontis repeats no more here.
By above analysis as can be known, when discharging and recharging, the electric capacity of voltage resonance network begins the change of current, wherein voltage is zero on the electric capacity, another capacitance voltage is an input voltage, with electric capacity diode connected in parallel D1, the conducting restriction output rectifying tube DR1 of D2, the appearance of the last due to voltage spikes of DR2, when a rectifying tube turn-offs, though there is reverse recovery current, but because diode D1, the clamping action of D2, output rectifying tube DR1, DR2 commutation course oscillatory occurences will disappear, and make to export rectifying tube DR1, there is not due to voltage spikes in the DR2 stable working, raise the efficiency, as shown in figure 20, the top among Figure 20 is rectifying tube DR1, the waveform that the DR2 alternating voltage is superimposed as does not obviously produce due to voltage spikes, bottom among Figure 20 is rectifying tube DR1, the waveform that the DR2 electric current alternately is superimposed as has reflected rectifying tube DR1, the DR2 stable working; Switching tube Q2, switching tube Q4, voltage resonance network mid point M and transformer primary current actual waveform figure during again referring to Figure 21 zero load, show that the present invention is under no-load condition, still can realize zero voltage switch, it is open-minded to illustrate that the present invention can obtain in whole loading range the no-voltage of leading arm and lagging leg when the higher and underloading of switching frequency.
Because there are duality relation to a great extent in three level and full-bridge phase shifting, therefore the present invention can be generalized in three level easily, can realize that equally the diode voltage spike suppresses and enhancing underloading change of current effect, as shown in figure 22, its operation principle is consistent with process with last surface analysis, need give unnecessary details hurriedly at this.
Claims (3)
1. intensified full-bridge phase-shift soft switch method, realize that by the full-bridge phase shifting circuit that switching tube constitutes the no-voltage of switching tube is open-minded, it is characterized in that: primary side end and Input voltage terminal at transformer insert the voltage resonance network, when finishing, the capacitor charge and discharge of voltage resonance network carries out the change of current, at this moment, voltage is zero on the electric capacity in the voltage resonance network, another capacitance voltage is an input voltage, with the conducting of electric capacity diode connected in parallel, thereby transformer original edge voltage clamper in input voltage, is suppressed due to voltage spikes on the output rectifying tube.
2. an application rights requires the intensified full-bridge phase-shift soft switch converter of 1 described full-bridge phase-shift soft switch method, constitute the full-bridge phase shifting circuit by switching tube, the inductance L 1 that comprises the primary side end that is serially connected with transformer, it is characterized in that: described full-bridge phase shifting circuit inserts and is connected to the primary side end of transformer and the voltage resonance network of Input voltage terminal, this voltage resonance network makes the hysteresis switching tube realize that complete no-voltage is open-minded, and suppresses the peak voltage of output rectifying tube (DR1), (DR2).
3. intensified full-bridge phase-shift soft switch converter according to claim 2 is characterized in that: described voltage resonance network comprises primary side end and the tie point (M) of inductance (L1) and electric capacity (C1) and diode (D1) and the electric capacity (C2) and the diode (D2) at input voltage two ends that is connected to transformer respectively.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CNB021219036A CN1193490C (en) | 2002-05-27 | 2002-05-27 | Intensified full-bridge phase-shift soft switch method and converter |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CNB021219036A CN1193490C (en) | 2002-05-27 | 2002-05-27 | Intensified full-bridge phase-shift soft switch method and converter |
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| CN1379540A true CN1379540A (en) | 2002-11-13 |
| CN1193490C CN1193490C (en) | 2005-03-16 |
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| CNB021219036A Expired - Lifetime CN1193490C (en) | 2002-05-27 | 2002-05-27 | Intensified full-bridge phase-shift soft switch method and converter |
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Cited By (7)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN100337392C (en) * | 2003-12-26 | 2007-09-12 | 台达电子工业股份有限公司 | DC/DC converter having voltage clamping circuit |
| CN100446398C (en) * | 2005-11-22 | 2008-12-24 | 福建龙净环保股份有限公司 | Resonance switch driving controlling and protecting circuit |
| CN1943100B (en) * | 2004-04-21 | 2010-09-22 | 三菱电机株式会社 | Power supply device |
| CN104935172A (en) * | 2015-06-09 | 2015-09-23 | 南京邮电大学 | Three-level soft switch forward-flyback DC/DC converter circuit topology structure |
| CN105140908A (en) * | 2015-09-29 | 2015-12-09 | 中国科学院电工研究所 | Zero-voltage soft-switching control method for photovoltaic high-voltage DC transmission system |
| EP2348626A3 (en) * | 2005-07-29 | 2017-04-19 | TDK Corporation | Switching power supply with surge voltage suppression |
| CN113014111A (en) * | 2021-03-23 | 2021-06-22 | 苏州茹浩电动科技有限公司 | Novel phase-shifted full-bridge topological structure process |
Families Citing this family (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101170278B (en) * | 2007-09-18 | 2010-06-16 | 艾默生网络能源有限公司 | A bridge soft shutdown circuit |
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2002
- 2002-05-27 CN CNB021219036A patent/CN1193490C/en not_active Expired - Lifetime
Cited By (8)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN100337392C (en) * | 2003-12-26 | 2007-09-12 | 台达电子工业股份有限公司 | DC/DC converter having voltage clamping circuit |
| CN1943100B (en) * | 2004-04-21 | 2010-09-22 | 三菱电机株式会社 | Power supply device |
| EP2348626A3 (en) * | 2005-07-29 | 2017-04-19 | TDK Corporation | Switching power supply with surge voltage suppression |
| CN100446398C (en) * | 2005-11-22 | 2008-12-24 | 福建龙净环保股份有限公司 | Resonance switch driving controlling and protecting circuit |
| CN104935172A (en) * | 2015-06-09 | 2015-09-23 | 南京邮电大学 | Three-level soft switch forward-flyback DC/DC converter circuit topology structure |
| CN104935172B (en) * | 2015-06-09 | 2018-07-24 | 南京邮电大学 | The straight translation circuit topological structure of three-level soft switch Forward- flyback |
| CN105140908A (en) * | 2015-09-29 | 2015-12-09 | 中国科学院电工研究所 | Zero-voltage soft-switching control method for photovoltaic high-voltage DC transmission system |
| CN113014111A (en) * | 2021-03-23 | 2021-06-22 | 苏州茹浩电动科技有限公司 | Novel phase-shifted full-bridge topological structure process |
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| Publication number | Publication date |
|---|---|
| CN1193490C (en) | 2005-03-16 |
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Address after: 518057 Nanshan District science and Technology Industrial Park, Guangdong, Shenzhen Branch Road, No. Patentee after: Vitamin Technology Co., Ltd. Address before: 518057 Nanshan District science and Technology Industrial Park, Guangdong, Shenzhen Branch Road, No. Patentee before: Aimosheng Network Energy Source Co., Ltd. |
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