WO2024257408A1 - 交流直流変換装置、回転機駆動装置及び冷凍サイクル適用機器 - Google Patents

交流直流変換装置、回転機駆動装置及び冷凍サイクル適用機器 Download PDF

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Publication number
WO2024257408A1
WO2024257408A1 PCT/JP2024/006339 JP2024006339W WO2024257408A1 WO 2024257408 A1 WO2024257408 A1 WO 2024257408A1 JP 2024006339 W JP2024006339 W JP 2024006339W WO 2024257408 A1 WO2024257408 A1 WO 2024257408A1
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WIPO (PCT)
Prior art keywords
power supply
voltage
current
phase
rectifier circuit
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Ceased
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PCT/JP2024/006339
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English (en)
French (fr)
Japanese (ja)
Inventor
謙吾 河内
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Mitsubishi Electric Corp
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Mitsubishi Electric Corp
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Application filed by Mitsubishi Electric Corp filed Critical Mitsubishi Electric Corp
Priority to JP2024560626A priority Critical patent/JP7603907B1/ja
Priority to DE112024002491.2T priority patent/DE112024002491T5/de
Priority to CN202480035975.XA priority patent/CN121285944A/zh
Publication of WO2024257408A1 publication Critical patent/WO2024257408A1/ja
Anticipated expiration legal-status Critical
Ceased legal-status Critical Current

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of AC power input into DC power output; Conversion of DC power input into AC power output
    • H02M7/02—Conversion of AC power input into DC power output without possibility of reversal
    • H02M7/04—Conversion of AC power input into DC power output without possibility of reversal by static converters
    • H02M7/12—Conversion of AC power input into DC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of AC power input into DC power output; Conversion of DC power input into AC power output
    • H02M7/42—Conversion of DC power input into AC power output without possibility of reversal
    • H02M7/44—Conversion of DC power input into AC power output without possibility of reversal by static converters
    • H02M7/48—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode

Definitions

  • This disclosure relates to an AC/DC converter that converts AC power into desired DC power, as well as a rotating machine drive device and a refrigeration cycle application device that are equipped with the AC/DC converter.
  • a power factor correction circuit When obtaining DC voltage from an AC power source, it is common to use a power factor correction circuit.
  • a power factor correction circuit has the functions of controlling the bus voltage at a constant level and controlling the power supply current so as to comply with harmonic standards.
  • a power factor correction circuit and one of its control methods is a method in which switching is performed at least once per half cycle of the power supply voltage, which is the voltage of the AC power supply, and has the characteristic of being able to control the bus voltage to be lower than the peak value of the power supply voltage.
  • the operating circuit switches from a boost chopper to a capacitor-input type diode rectifier, which creates the problem of distorting the power supply current.
  • Patent Document 1 determines whether the combination of reactor capacity and switching timing complies with harmonic standards by repeating the design for each load power.
  • Patent Document 1 is a method for checking whether or not compliance with harmonic standards can be achieved through repeated trials, which poses the problem that the number of trials increases exponentially as the number of pulses increases.
  • the present disclosure has been made in consideration of the above, and aims to shorten the time required for design by obtaining an AC/DC conversion device that can comply with harmonic standards without relying on trial-and-error adjustments.
  • the AC/DC conversion device includes a rectifier circuit, a capacitor, a reactor, a current detection unit, and a control unit.
  • the rectifier circuit has at least one switching element and rectifies the power supply voltage applied from the AC power supply.
  • the capacitor is connected to the DC bus and smoothes the output voltage of the rectifier circuit.
  • the reactor is arranged closer to the AC power supply than the capacitor.
  • the current detection unit detects the power supply current flowing between the AC power supply and the rectifier circuit. When generating a switching signal for controlling the switching element arranged closer to the AC power supply than the capacitor, the control unit generates the switching signal so as to change the phase of the power supply current.
  • the AC-DC converter disclosed herein can comply with harmonic standards without relying on trial-and-error adjustments, which has the effect of shortening the time required for design.
  • FIG. 1 is a block diagram showing a configuration example of a rotary machine driving device according to a first embodiment; A circuit diagram showing a configuration example of an AC-DC converter according to a first embodiment.
  • FIG. 1 is a block diagram showing a configuration example of a control unit according to a first embodiment;
  • FIG. 1 is a block diagram showing an example of the configuration of a sine wave signal generator provided in a control unit according to a first embodiment;
  • FIG. 3 is a diagram showing an example of operating waveforms when the AC-DC converter shown in FIG. 2 is operated in a passive mode.
  • FIG. 3 is a diagram showing an example of operating waveforms when the AC-DC converter shown in FIG. 2 is operated with a fundamental wave power factor of 1;
  • FIG. 3 is a diagram showing an example of operational waveforms when phase shift control is performed on the AC-DC converter shown in FIG. 2 .
  • FIG. 13 is a diagram showing a configuration example of a refrigeration cycle application device according to a second embodiment;
  • Embodiment 1. 1 is a block diagram showing a configuration example of a rotating machine driving device 8 according to embodiment 1.
  • the rotating machine driving device 8 is connected to an AC power source 1 and a load 4 including a motor 41.
  • the rotating machine driving device 8 includes an AC/DC converter 2 and a DC/AC converter 3.
  • the load 4 is a compressor or a fan
  • the motor 41 is a compressor motor or a fan motor.
  • FIG. 2 is a circuit diagram showing an example of the configuration of the AC-DC converter 2 according to the first embodiment.
  • the AC-DC converter 2 according to the first embodiment mainly comprises a control unit 6, a rectifier circuit 20, a reactor 212, and a capacitor 216.
  • the AC-DC converter 2 also comprises a current detector 211 and voltage detectors 217a and 217b as means for detecting voltage or current.
  • the voltage detector 217b when the voltage detectors 217a and 217b are to be distinguished from each other without reference numbers, the voltage detector 217b will be referred to as the "first voltage detector” and the voltage detector 217a will be referred to as the "second voltage detector.”
  • the rectifier circuit 20 includes single-phase diode bridge cells 213a and 213b in which four diodes are bridge-connected, and a switching element 215 connected in parallel to both ends of the single-phase diode bridge cell 213b.
  • the single-phase diode bridge cells 213a and 213b are connected in parallel to each other with the AC power source 1.
  • the rectifier circuit 20 as shown in FIG. 2 is called a "simple switching circuit.”
  • the single-phase diode bridge cell 213b and the switching element 215 constitute a switching cell 225.
  • the switching element 215 performs a switching operation at least once per half cycle of the power source voltage.
  • the capacitor 216 is connected between the DC bus 9a and the DC bus 9b.
  • the reactor 212 is disposed closer to the AC power source than the capacitor 216.
  • the rectifier circuit 20 receives the power source voltage applied from the AC power source 1 via the reactor 212, and rectifies the received power source voltage.
  • the capacitor 216 smoothes the output voltage of the rectifier circuit 20.
  • the voltage detection unit 217b detects the bus voltage, which is the voltage of the DC bus to which the capacitor is connected.
  • the voltage detection unit 217a detects the power supply voltage.
  • the current detection unit 211 detects the power supply current flowing between the AC power supply 1 and the rectifier circuit 20.
  • the control unit 6 receives the detection values of the voltage detection units 217a, 217b and the current detection unit 211. Based on each detection value, the control unit 6 generates a switching signal for controlling the on/off of the switching element 215.
  • An example of the switching element 215 is an IGBT (Insulated Gate Bipolar Transistor) as shown in the figure, but is not limited to an IGBT. Any element capable of switching operation may be used as the switching element 215.
  • Another example of the switching element 215 is a MOSFET (Metal-Oxide-Semiconductor Field-Effect Transistor).
  • the AC-DC converter 2 shown in FIG. 2 is configured as a closed loop using the detection values of the voltage detectors 217a, 217b and the current detector 211, but may be configured as an open loop using target values, estimated values, etc. If the AC-DC converter 2 is configured as an open loop, it is also possible to control the switching element 215 without using the detection values of the voltage detectors 217a, 217b and the current detector 211.
  • FIG. 3 is a block diagram showing an example of the configuration of the control unit 6 according to the first embodiment.
  • the control unit 6 includes a subtractor 611, a voltage controller 612, a multiplier 613, a subtractor 614, a current controller 615, a switching signal generator 616, and a sine wave signal generator 617.
  • the subtractor 611 generates a voltage deviation, which is the difference between the first voltage command value and the bus voltage detection value detected by the voltage detection unit 217b.
  • the first voltage command value is a command value for the bus voltage.
  • the voltage controller 612 generates a first current command value using the voltage deviation output from the subtractor 611.
  • the voltage controller 612 can be configured, for example, as a PI (Proportional Integral) controller.
  • the transfer function G AVR(s) can be expressed by the following equation (1).
  • AVR in the transfer function G AVR(s) is an abbreviation for "Automatic Voltage Regulator.”
  • K pAVR is a proportional gain
  • K iAVR is an integral gain
  • s is a Laplace operator.
  • the proportional gain K pAVR and the integral gain K iAVR can be determined arbitrarily. Note that the proportional gain K pAVR may be set to zero to configure an I controller, or the integral gain K iAVR may be set to zero to configure a P controller.
  • the sine wave signal generator 617 generates a sine wave signal as a vibration signal based on the first voltage command value and the detected value of the power supply voltage.
  • the multiplier 613 multiplies the first current command value by the sine wave signal.
  • the sine wave signal is a sine wave synchronized with the phase of the power supply voltage.
  • the output of the multiplier 613 is input to the subtractor 614 as a second current command value.
  • the subtractor 614 generates a current deviation that is the difference between the second current command value and the detected value of the power supply current detected by the current detection unit 211.
  • the current controller 615 generates a second voltage command value using the current deviation output from the subtractor 614.
  • the current controller 615 can be configured, for example, by a PI controller.
  • the switching signal generator 616 generates a switching signal using the second voltage command value.
  • the transfer function G ACR(s) can be expressed by the following equation (2).
  • ACR in the transfer function G ACR(s) is an abbreviation for "Automatic Current Regulator.”
  • K pACR is a proportional gain
  • K iACR is an integral gain
  • s is a Laplace operator.
  • the proportional gain K pACR and the integral gain K iACR can be determined arbitrarily. Note that the proportional gain K pACR may be set to zero to configure an I controller, or the integral gain K iACR may be set to zero to configure a P controller.
  • FIG. 4 is a block diagram showing an example of the configuration of a sine wave signal generator 617 provided in the control unit 6 according to the first embodiment.
  • the sine wave signal generator 617 outputs a sine wave synchronized with the phase and frequency of the power supply voltage.
  • the sine wave signal generator 617 includes a PLL (Phase Locked Loop) calculator 6171, a subtractor 6172, a sine wave calculator 6173, and a phase shift amount calculator 6174.
  • PLL Phase Locked Loop
  • PLL calculator 6171 generates and outputs a sine wave phase synchronized with the phase and frequency of the power supply voltage.
  • Phase shift amount calculator 6174 calculates the phase shift amount based on the detected value of the power supply voltage and a first voltage command value which is the command value of the bus voltage.
  • Subtractor 6172 calculates the difference between the output of PLL calculator 6171 and the output of phase shift amount calculator 6174.
  • Sine wave calculator 6173 calculates a sine wave signal using the difference output from subtractor 6172.
  • FIG. 5 is a diagram showing an example of operating waveforms when the AC-DC converter 2 shown in FIG. 2 is operated passively. Passive operation refers to operation in passive mode. Passive mode is a mode in which the rectifier circuit 20 operates without switching the switching element 215.
  • Passive mode is a mode in which the rectifier circuit 20 operates without switching the switching element 215.
  • the waveform of the absolute value of the power supply voltage is shown in dashed lines, and the waveform of the bus voltage is shown in solid lines.
  • the waveform of the power supply current is shown in dashed lines, and the waveform of the fundamental wave component of the power supply current is shown in solid lines.
  • the power supply current shown in the lower part is the detected waveform of the power supply current detected by the current detection unit 211.
  • the current start phase ⁇ which is the phase at which this current starts to flow, is the intersection point where the power supply voltage rises and becomes equal to the bus voltage, and can be calculated using the following formula (3).
  • Vdc is the bus voltage
  • vs is the effective value of the power supply voltage.
  • the power supply current continues to increase until the power supply voltage and the bus voltage cross again, and this intersection point is the peak value of the power supply current.
  • the current peak phase ⁇ which is the phase of the peak value of the power supply current, can be expressed by the following formula (4) when the peak value of the power supply voltage is used as the reference.
  • the fundamental component of the power supply current has a waveform with a phase lag relative to the power supply voltage, as shown in Figure 5. Due to this characteristic during passive operation, if you try to make the fundamental power factor 1 when the bus voltage is below the peak value of the power supply voltage, it will lead to low-order harmonics being superimposed on the power supply current. The reason for this is as follows. First, if you try to make the fundamental power factor 1 during passive operation, it becomes necessary to perform switching multiple times after the zero crossing of the power supply voltage. On the other hand, this switching control will distort the power supply current. Therefore, if you try to make the fundamental power factor 1 when the bus voltage is below the peak value of the power supply voltage, the power supply current will be distorted and low-order harmonics will be superimposed on the power supply current.
  • the fundamental power factor when the bus voltage is equal to or less than the peak value of the power supply voltage, the fundamental power factor is not set to 1, but the phase of the sine wave signal that oscillates the first current command value is controlled to be synchronized with the fundamental phase of the power supply current during passive operation. In this way, the current distortion caused by the fundamental wave control of the power supply current can be reduced, making it possible to suppress harmonic components that may be contained in the power supply current when the bus voltage is equal to or less than the peak value of the power supply voltage.
  • the lower part of Figure 5 shows the phase shift amount ⁇ .
  • the phase shift amount ⁇ is the phase of the peak value of the power supply current based on the peak value of the power supply voltage.
  • the upper part of Figure 5 shows the current peak phase ⁇ described above.
  • the current peak phase ⁇ is the phase of the peak value of the power supply current during passive operation.
  • Both the phase shift amount ⁇ and the current peak phase ⁇ are based on the peak value of the power supply voltage. Also, as shown in Figure 5, the two are close to each other and have similar values.
  • phase shift amount ⁇ is considered to be approximately equal to the current peak phase ⁇ , and is defined by the following equation (5).
  • the phase shift amount calculator 6174 outputs the phase shift amount ⁇ generated based on the above equation (5) to the subtractor 6172. If the sine wave phase output from the PLL calculator 6171 is represented as ⁇ vs , then " ⁇ vs - ⁇ " is input to the sine wave calculator 6173. Therefore, the sine wave calculator 6173 outputs a sine wave signal f expressed by the following equation (6).
  • the sine wave signal f is a signal that excites the first current command value, and shifting the phase of the sine wave signal f also shifts the phase of the power supply current. In this paper, this control is appropriately referred to as "phase shift control.”
  • FIG. 6 is a diagram showing an example of operating waveforms when the AC-DC converter 2 shown in FIG. 2 is operated with a fundamental power factor of 1.
  • the waveform of the absolute value of the power supply voltage is shown by a dashed line
  • the waveform of the bus voltage is shown by a solid line.
  • the waveform of the power supply current is shown by a solid line
  • the waveform of the fundamental wave component of the power supply current is shown by a dashed line.
  • the switching control for the switching element 215 is concentrated in the period after the power supply voltage passes the zero crossing point and before the absolute value of the power supply voltage reaches its peak value.
  • the fundamental wave power factor of the power supply current is set to 1 without using phase shift control, the switching control for the switching element 215 is concentrated in a certain period, and as a result, the power supply current becomes distorted.
  • FIG. 7 is a diagram showing an example of operating waveforms when phase shift control is performed on the AC-DC converter 2 shown in FIG. 2.
  • the waveform of the absolute value of the power supply voltage is shown by a dashed line
  • the waveform of the bus voltage is shown by a solid line.
  • the waveform of the power supply current is shown by a solid line.
  • the waveform in the lower part of Figure 7 it can be seen that although minute changes in current are visible, the waveform of the power supply current itself changes in agreement with the waveform of the fundamental wave of the power supply current. Therefore, by operating the AC-DC converter 2 using the phase shift control of this paper, the power supply current can be controlled to be sinusoidal. Therefore, by using the phase shift control of this paper, it is possible to operate the AC-DC converter 2 in a manner that complies with harmonic standards without relying on trial-and-error adjustments that are performed repeatedly to confirm whether or not compliance with harmonic standards is possible.
  • the AC-DC converter according to the first embodiment includes a rectifier circuit that rectifies the power supply voltage applied from the AC power supply, a capacitor that smoothes the output voltage of the rectifier circuit, a reactor that is disposed closer to the AC power supply side than the capacitor, and a current detection unit that detects the power supply current flowing between the AC power supply and the rectifier circuit.
  • the rectifier circuit has at least one switching element that is disposed closer to the AC power supply side than the capacitor. When generating a switching signal for controlling the switching element, the control unit generates the switching signal so as to change the phase of the power supply current. According to the AC-DC converter according to the first embodiment, it is possible to control the power supply current to a sinusoidal wave shape.
  • the AC-DC converter includes a current detection unit that detects the power supply current, and the control unit generates a switching signal to change the phase of the power supply current based on the fundamental wave of the power supply current detected when the switching element is turned off and the rectifier circuit is passively operated.
  • the control unit By controlling the switching element of the rectifier circuit using the switching signal generated in this manner, the power supply current can be controlled to a sinusoidal wave, so that even under operating conditions where the bus voltage is equal to or lower than the peak value of the absolute value of the power supply voltage, it is possible to comply with the harmonic standards while improving the input power factor.
  • a switching signal can be generated by changing the phase of the power supply current depending on the magnitude relationship between the bus voltage detection value by the first voltage detection unit and the power supply voltage detection value by the second voltage detection unit.
  • Embodiment 2 8 is a diagram showing a configuration example of a refrigeration cycle-applied device 900 according to embodiment 2.
  • the refrigeration cycle-applied device 900 according to embodiment 2 includes the rotating machine drive device 8 described in embodiment 1.
  • the refrigeration cycle-applied device 900 according to embodiment 2 can be applied to products including a refrigeration cycle, such as air conditioners, refrigerators, freezers, and heat pump water heaters.
  • the refrigeration cycle application device 900 includes a compressor 42 incorporating the motor 41 in the first embodiment, a four-way valve 902, an indoor heat exchanger 906, an expansion valve 908, and an outdoor heat exchanger 910 attached via refrigerant piping 912. Inside the compressor 42, there is provided a compression mechanism 904 that compresses the refrigerant, and a motor 41 that operates the compression mechanism 904.
  • the refrigeration cycle application device 900 can perform heating or cooling operation by switching the four-way valve 902.
  • the compression mechanism 904 is driven by a motor 41 that is variable speed controlled.
  • the refrigerant is pressurized by the compression mechanism 904 and sent out, and returns to the compression mechanism 904 through the four-way valve 902, the indoor heat exchanger 906, the expansion valve 908, the outdoor heat exchanger 910, and the four-way valve 902.
  • the refrigerant is pressurized by the compression mechanism 904 and sent out, and returns to the compression mechanism 904 through the four-way valve 902, the outdoor heat exchanger 910, the expansion valve 908, the indoor heat exchanger 906, and the four-way valve 902.
  • the indoor heat exchanger 906 acts as a condenser to release heat, and the outdoor heat exchanger 910 acts as an evaporator to absorb heat.
  • the outdoor heat exchanger 910 acts as a condenser to release heat, and the indoor heat exchanger 906 acts as an evaporator to absorb heat.
  • the expansion valve 908 reduces the pressure of the refrigerant and causes it to expand.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Rectifiers (AREA)
PCT/JP2024/006339 2023-06-12 2024-02-21 交流直流変換装置、回転機駆動装置及び冷凍サイクル適用機器 Ceased WO2024257408A1 (ja)

Priority Applications (3)

Application Number Priority Date Filing Date Title
JP2024560626A JP7603907B1 (ja) 2023-06-12 2024-02-21 交流直流変換装置、回転機駆動装置及び冷凍サイクル適用機器
DE112024002491.2T DE112024002491T5 (de) 2023-06-12 2024-02-21 Wechselstrom-Gleichstrom-Wandler, Rotationsmaschinenantrieb und Kühlkreislauf-Anwendungsgerät
CN202480035975.XA CN121285944A (zh) 2023-06-12 2024-02-21 交流直流变换装置、旋转机驱动装置以及冷冻循环应用设备

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JP2023-096271 2023-06-12
JP2023096271 2023-06-12

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WO2024257408A1 true WO2024257408A1 (ja) 2024-12-19

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CN (1) CN121285944A (https=)
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Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2000125545A (ja) * 1999-11-24 2000-04-28 Mitsubishi Electric Corp 直流電源装置および空気調和機
JP2007215385A (ja) * 2006-02-13 2007-08-23 Mitsubishi Electric Corp 直流電源装置
JP2009100558A (ja) * 2007-10-17 2009-05-07 Panasonic Corp モータ駆動用インバータ制御装置

Patent Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2000125545A (ja) * 1999-11-24 2000-04-28 Mitsubishi Electric Corp 直流電源装置および空気調和機
JP2007215385A (ja) * 2006-02-13 2007-08-23 Mitsubishi Electric Corp 直流電源装置
JP2009100558A (ja) * 2007-10-17 2009-05-07 Panasonic Corp モータ駆動用インバータ制御装置

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DE112024002491T5 (de) 2026-04-30
JP7603907B1 (ja) 2024-12-20
CN121285944A (zh) 2026-01-06

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