WO2023074420A1 - Procédé de transmission radio, dispositif de transmission radio, procédé de réception radio, dispositif de réception radio, et procédé de communication radio - Google Patents

Procédé de transmission radio, dispositif de transmission radio, procédé de réception radio, dispositif de réception radio, et procédé de communication radio Download PDF

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WO2023074420A1
WO2023074420A1 PCT/JP2022/038451 JP2022038451W WO2023074420A1 WO 2023074420 A1 WO2023074420 A1 WO 2023074420A1 JP 2022038451 W JP2022038451 W JP 2022038451W WO 2023074420 A1 WO2023074420 A1 WO 2023074420A1
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signal
radio
frequency
synchronization
chirp
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PCT/JP2022/038451
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English (en)
Japanese (ja)
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誠司 小林
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公立大学法人公立諏訪東京理科大学
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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/18—Phase-modulated carrier systems, i.e. using phase-shift keying
    • H04L27/22—Demodulator circuits; Receiver circuits
    • H04L27/227—Demodulator circuits; Receiver circuits using coherent demodulation
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L7/00—Arrangements for synchronising receiver with transmitter
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L7/00—Arrangements for synchronising receiver with transmitter
    • H04L7/04—Speed or phase control by synchronisation signals
    • H04L7/06—Speed or phase control by synchronisation signals the synchronisation signals differing from the information signals in amplitude, polarity or frequency or length
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02D—CLIMATE CHANGE MITIGATION TECHNOLOGIES IN INFORMATION AND COMMUNICATION TECHNOLOGIES [ICT], I.E. INFORMATION AND COMMUNICATION TECHNOLOGIES AIMING AT THE REDUCTION OF THEIR OWN ENERGY USE
    • Y02D30/00—Reducing energy consumption in communication networks
    • Y02D30/70—Reducing energy consumption in communication networks in wireless communication networks

Definitions

  • the present invention relates to a radio transmission method, a radio transmission device, a radio reception method, a radio reception device, and a radio communication method that achieve reliable synchronization even on a communication channel with noise or interference, and as a result, achieve stable radio transmission.
  • JP 2016-46618 A Japanese Patent No. 6821231
  • FIG. 1 is a diagram briefly explaining two types of conventionally used wireless transmission formats.
  • FIG. 1(A) is a general synchronization technique that adds a "preamble" to the beginning of a frame.
  • a preamble 10 is followed by a frame sync 11 indicating the beginning of a frame and data 12.
  • FIG. Of these, the preamble 10 and the frame sync 11 are synchronization signals.
  • the data 12 includes a header, an error correction code, an error detection code, etc., although they are not shown because they are complicated.
  • the synchronization method of FIG. 1A has a problem that the preambles are temporally concentrated.
  • Patent Document 1 Japanese Patent Application Publication No. 2016-46618 discloses a communication method in which synchronization signals 13 generated by pseudo-random numbers are evenly dispersed in frames as shown in FIG. 1(B).
  • Patent Document 2 discloses a wireless transmission method using "a narrowband synchronization signal that exists continuously over the entire frame period when viewed on the time axis".
  • narrowband synchronization signal detection can be processed by fast Fourier transform (FFT), so the paradox can be resolved and synchronization can be easily realized.
  • FFT fast Fourier transform
  • the present invention provides a wireless transmission method that enables time, phase and frequency offsets to be adjusted (that is, synchronization is possible) with a simple receiver configuration, and that synchronization is less likely to be disturbed by the effects of interference. , a radio transmission device, a radio reception method, a radio reception device, and a radio communication method.
  • a wireless transmission method of the present invention is a wireless transmission method characterized by using a plurality of chirp signals as a synchronization signal or a part of the synchronization signal, and wherein the plurality of chirp signals have different change rates.
  • a radio transmission apparatus (2) to which the present invention is applied comprises modulation means (20) for encoding and modulating information to be radio-transmitted, synchronization signal generation means (23) for generating a synchronization signal, the modulation signal and the synchronization signal.
  • Composite signal generating means (26) for generating a composite signal by combining signals
  • high frequency modulation means for generating a high frequency signal by superimposing a carrier signal on the composite signal.
  • the synchronization signal generating means (23) generates a cross-carrier signal by combining chirp signals with two different change rates ( ⁇ 1, ⁇ 2).
  • the received radio signal is dechirped by a first chirp rate ( ⁇ 1) to create a first dechirp signal (Q1) (33A), and the received radio signal is subjected to a second chirp rate.
  • a second dechirped signal (Q2) is created (33B) by applying dechirping processing by ( ⁇ 2), and the time of the received radio signal is calculated from the first dechirped signal (Q1) and the second dechirped signal (Q2).
  • a radio reception method characterized by detecting (34) a delay ( ⁇ ) and correcting (35) the time delay of the received radio signal.
  • a radio receiver (3) of the present invention comprises front-end means (30) for converting a received radio signal into an IQ signal, synchronization signal extraction means (32) for extracting a synchronization signal from the IQ signal, and In response, channel correction means (35) for correcting the time delay ( ⁇ ) and phase rotation of the IQ signal to create a corrected IQ signal, and decoding means (38) for decoding the corrected IQ signal are used to obtain received data.
  • the synchronization signal extracting means (32) includes first dechirping means (33A) for dechirping the IQ signal with a first chirp rate ( ⁇ 1) to obtain a first dechirping signal (Q1); second dechirping means (33B) for dechirping the signal with a second chirping rate ( ⁇ 2) to obtain a second dechirped signal (Q2);
  • the radio receiving apparatus is characterized by including synchronization signal processing means (34) for detecting the time delay (.delta.) of the received radio signal.
  • a modulated signal (mod(t)) is generated by encoding and modulating transmission information, and two complex function signals exp(j2p ⁇ 1 ⁇ t ⁇ t) and exp(j2p ⁇ 2 ⁇ t ⁇ t) are generated, and a carrier signal is superimposed on the modulation signal and the sync signal to generate a high-frequency signal (TX(t)). is generated and transmitted as radio waves, and the high-frequency signal is received to restore the transmission information, wherein the synchronization signal (Cr(t)) included in the high-frequency signal is used to generate the time on the wireless transmission path
  • a wireless communication method characterized by decoding and detecting the transmission information by detecting a delay ( ⁇ ) and correcting the time delay.
  • a radio transmission method, a radio transmission device, a radio reception method, a radio reception device, and a radio communication method are realized, in which synchronization signals are less disturbed by interference from other systems and can be transmitted more reliably. can.
  • a wireless communication device to which these are applied it is possible to realize stable communication.
  • transmission power is not allocated to useless signals such as preambles, and lower power consumption can be realized than before.
  • the radio receiving apparatus to which the radio receiving method according to the present invention is applied can efficiently realize synchronization signal processing, it is possible to operate the receiving apparatus with a simpler configuration and lower power consumption than before.
  • FIG. 2 is a diagram briefly explaining two types of conventionally used wireless transmission formats; 1 is a diagram illustrating the concept of the wireless communication format of the present invention; FIG. 1 is a block diagram of a wireless transmission device 2 of the present invention; FIG. 3 is a configuration diagram of a modulated pulse generation block 21 used in the radio transmission device 2; FIG. 3 is a configuration diagram of a down-chirp generation block 24A used in the radio transmission device 2; FIG. 3 is a diagram schematically showing each signal in the radio transmission device 2; FIG. FIG. 4 is a diagram schematically showing the spectrum of a radio transmission signal in the present invention; 1 is a block diagram of a radio receiver 3 of the present invention; FIG.
  • FIG. 3 is a configuration diagram of synchronization signal extraction means 32 used in the radio receiving apparatus 3.
  • FIG. 4 shows the spectrum and spectrogram of a transmitted radio wave in an experiment using the wireless transmission method of the present invention; It is an example of a constellation obtained by an experiment using the radio reception method of the present invention.
  • FIG. 10 is a diagram schematically showing the spectrum of a radio transmission signal in the second embodiment;
  • FIG. 12 is a diagram showing the concept of a wireless communication format in the third embodiment;
  • FIG. It is a block diagram of the wireless transmission device 2 of the third embodiment.
  • FIG. 12 is a diagram showing the concept of a wireless communication format in the fourth embodiment;
  • FIG. FIG. 12 is a diagram showing the concept of a wireless communication format in the fifth embodiment;
  • FIG. 2 is a diagram showing the concept of the wireless communication format of the present invention.
  • the communication format of the present invention is shown with frequency on the vertical axis and time on the horizontal axis.
  • the data 12 includes an error correction code, authentication information, etc., but they are omitted in FIG. 2 for the sake of simplification.
  • the frequency bandwidth occupied by data 12 is denoted by Bw.
  • Bw the frequency bandwidth occupied by data 12 is denoted by Bw.
  • the symbol rate fb is 100ksps (Symbol Per Second)
  • the frequency bandwidth Bw is approximately 150kHz.
  • information transmitted as a frame consists of a frame sync 11 representing the start timing of the frame and data 12 .
  • the frame sync 11 modulation method is often the same as that of the data 12 .
  • the frequency bandwidth occupied by the frame sync 11 is also Bw.
  • the cross-carrier 14 is transmitted over substantially the entire time of the frame instead of the preamble.
  • the cross-carrier 14 is composed of a down-chirp signal 14A and an up-chirp signal 14B.
  • the down-chirp signal 14A is a signal whose starting frequency is the frequency +fs and whose frequency thereafter drops at a predetermined chirp rate ( ⁇ 1).
  • the up-chirp signal 14B has a frequency of -fs as a starting point, and thereafter increases at a predetermined chirp rate ( ⁇ 2).
  • the frame time T is 0.5 seconds
  • the chirp start frequency fs 75 kHz
  • ⁇ 1 -300 kHz/sec
  • ⁇ 2 +300 kHz/sec.
  • FIG. 3 is a block diagram of the radio transmission device 2 of the present invention.
  • FIG. 6 is a timing chart for schematically explaining the signals of the wireless transmission device 2.
  • the symbol clock frequency is 100 kHz when the symbol rate fb is 100 ksps.
  • the transmission data is modulated by the modulating means 20, added with the synchronizing signal (cross carrier 14) generated by the synchronizing signal generating means 23, amplified by the high frequency modulating means 27, and transmitted from the antenna 202 as radio waves TX(t). .
  • the transmission data "101101" is input to the modulated pulse generation block 21 and converted into one pulse (Mod Pulse) for each symbol.
  • Mod Pulse is a bipolar pulse train whose polarity changes according to transmission data.
  • the Mod Pulse is low-pass filtered by the low-pass filter 22 to become the modulated signal mod(t).
  • RRC Root Raised Cosine
  • a system controller (not shown) changes the Start Pulse (FIG. 6(E)) from “0" to "1" to instruct the start of data transmission, and at the same time, the cross-carrier signal Cr(t) is generated.
  • the cross-carrier signal Cr(t) is a signal obtained by synthesizing the down-chirp signal Ca(t) and the up-chirp signal Cb(t), as will be described later.
  • the synchronization signal generating means 23 is composed of a down-chirp ( ⁇ 1) generation block 24A and an up-chirp ( ⁇ 2) generation block 24B, which generate a down-chirp signal Ca(t) and an up-chirp signal Cb(t), respectively. These signals are added by the adder 25 to generate the cross-carrier signal Cr(t).
  • the cross-carrier signal Cr(t) becomes a real number and can be expressed by the cosine function (cosine) shown in Equation 3, which can be simplified.
  • the adder 26 adds the modulated signal mod(t) and the cross-carrier signal Cr(t) and supplies the result to the mixer 28 .
  • the cross-carrier signal Cr(t) becomes a real number and the imaginary part becomes unnecessary.
  • Adder 26 can also be omitted by feeding the signal into the Q axis of mixer 28 .
  • the modulated signal mod(t) and the cross-carrier signal Cr(t) are combined by the mixer 28, and the carrier (frequency fc) supplied from the local oscillator 29 is superimposed.
  • Carrier frequency fc can be, for example, 920 Mz.
  • the bandpass filter 200 removes unnecessary components contained in the signal from the mixer 28.
  • the output of the bandpass filter 200 is amplified by the linear amplifier 201 and transmitted in the air from the antenna 202 as radio waves TX(t).
  • FIG. 4 is a configuration diagram of the modulated pulse generation block 21 used in the radio transmission device 2. As shown in FIG. The configuration of the modulated pulse generation block 21 will be described with reference to FIG. Transmission data is input every symbol clock (syclk) and converted into a bipolar signal by the mapper 210 . That is, if the transmission data is "1", it is converted to "+1", and if the transmission data is "0", it is converted to "-1".
  • a rising edge detection circuit 211 generates a pulse at the rising edge of the symbol clock (syclk).
  • the rise detection circuit 211 is composed of a PLL circuit 213 , a D flip-flop 214 , a NOT gate 215 and an AND gate 216 .
  • the rising edge detection circuit 211 generates a rising edge pulse at the timing when the symbol clock (syclk) changes from logic "0" to logic "1".
  • the PLL circuit 213 generates a clock X16 obtained by multiplying the frequency of the symbol clock (syclk) by 16.
  • the symbol clock (syclk) is 100 kHz, so the clock X16 is a high-speed clock of 1.6 MHz.
  • the rising edge pulse is multiplied by the output of mapper 210 by multiplier 212 and output as one bipolar pulse (Mod Pulse) per symbol.
  • the Mod Pulse generated in this way is a bipolar impulse train whose polarity changes according to the transmission data, as shown in FIG. 6(C). Also, since Mod Pulse is synchronized with the rising edge of the symbol clock (syclk), it changes at the center of the time (Ts) during which one symbol is transmitted.
  • the synchronization signal generating means 23 is composed of a down-chirp generating means 24A, an up-chirp generating means 24B, and an adder 25.
  • FIG. 5 is a configuration diagram of the down chirp generating means 24A. Since the chirp rate of the up-chirp generating means 24B is different, the description thereof is omitted.
  • the counter 240 starts counting the clock X16.
  • the count value n which was "0" at the start of the frame, is a 20-bit integer that changes up to 800,000 at the end of the frame after 0.5 seconds.
  • the nonvolatile memory 241 receives a 20-bit address and outputs prewritten 8-bit data.
  • a non-volatile memory 241 for example, a semiconductor (AT27C080) manufactured by ATMEL can be used.
  • AT27C080 a semiconductor manufactured by ATMEL can be used.
  • the function mod() represents the remainder operation
  • ⁇ is the reciprocal of the clock X16 (0.625 ⁇ s).
  • the exponential function block 242 is composed of a non-volatile memory or the like, and outputs cos ⁇ 1 ( n) ⁇ as the real part and sin ⁇ 1 (n) ⁇ as the imaginary part for the phase ⁇ 1 (n) of the down-chirp signal. do.
  • the amplifier 243 multiplies the output of the exponential function block 232 by a predetermined constant ⁇ to output as a down-chirp signal Ca(t). If there is interference from other systems and the synchronization is disturbed, a large value can be adopted for ⁇ to improve the synchronization performance.
  • the down-chirp signal phase ⁇ 1 (n) generated in the manner described above gradually changes with the passage of time, and the degree of change is represented by a quadratic function.
  • the real part cos ⁇ 1 (n) ⁇ of the down chirp signal Ca(t) becomes a chirp signal whose frequency decreases with time as illustrated in FIG. 6(G).
  • the cross-carrier signal Cr(t) is generated as a synchronization signal simultaneously with the modulating signal mod(t). These are synthesized by the mixer 28, and the carrier (frequency fc) is superimposed by the high frequency modulation means 27 to produce the transmission signal TX(t) (see FIGS. 6(H) and 6(I)).
  • the transmission signal TX(t) can be represented by Equation 5 below.
  • ⁇ TX is the transmission frequency deviation that occurs in the radio transmission device 2 .
  • FIG. 7 is a diagram schematically showing the spectrum of the transmission signal TX(t).
  • the frame sync 11 and data 12 are BPSK modulated signals (mod(t)) having a flat frequency characteristic of approximately 150 kHz centered on the carrier frequency fc.
  • the cross-carrier signal Cr(t) is composed of up-chirp and down-chirp around the carrier frequency fc as illustrated in FIG.
  • FIG. 8 is a block diagram of the radio receiver 3 of the present invention.
  • the radio receiver 3 of the present invention comprises an antenna 301, a front end 30, a synchronization signal extraction means 32, a channel correction means 35 and a decoding means .
  • the received signal RX(t) received by the antenna 301 is expressed by the following equation 6,
  • ⁇ c(t) is the phase rotation that occurs in radio propagation, and in many cases, its frequency component changes gently on the order of several hertz.
  • ⁇ is the time delay that occurs in wireless communication
  • ⁇ TX is the frequency deviation that occurs in the wireless transmission device 2 .
  • the front end 30 is composed of an amplifier 302, a bandpass filter 303, a local oscillator 304, a mixer 305 and an AD converter 306.
  • a weak radio wave received by an antenna 301 is amplified by an amplifier 302, unnecessary frequency components are removed by a bandpass filter 303, carrier wave frequency (fc) components are removed by a mixer 305 and a local oscillator 304, and an AD converter 306 Convert to digital information (IQ signal).
  • sampling of the AD converter 306 is performed by the system clock (CLK), and the frequency of the system clock (CLK) is set sufficiently high, for example, 1.5MH.
  • a sampling interval ⁇ of the AD converter 306 is the reciprocal of the system clock (CLK).
  • ⁇ r is the sum of the frequency deviation ⁇ TX of the radio transmitter 2 and the frequency deviation ⁇ RX of the local oscillator 304 mounted on the radio receiver 3, and is the total frequency deviation of transmission and reception.
  • the IQ signal IQ B (n) has a total of three phase deviations, ie, the frequency shift ⁇ r and the gentle phase rotation ⁇ c. Putting these components together as ⁇ (n), Synchronization can be realized by obtaining and correcting the phase rotation ⁇ (n) and the time delay ⁇ in the above equation (7).
  • FIG. 9 shows the configuration of the synchronizing signal extracting means 32 which receives the IQ signal IQ B (n) and the system clock CLK as inputs, detects the transmission line characteristics ( ⁇ , ⁇ (n)), and outputs them.
  • the sync signal extraction means 32 extracts the down-chirp sync signal Q 1 (n) and the up-chirp sync signal Q 2 (n) by two dechirp circuits 33A and 33B.
  • the synchronization signal processing means 34 is configured to detect the transmission path characteristics (.delta., .phi.(n)).
  • the counter 79 When the synchronization signal extraction is started by a system controller (not shown), the counter 79 counts the system clock CLK and outputs the count value n.
  • the dechirping circuit 33A comprises a non-volatile memory 331A and a phase reverse rotation block 330A, performs chirp correction at a chirp rate ⁇ 1 on the IQ signal IQ B (n), and extracts the down chirp synchronization signal Q 1 (n).
  • a dechirping circuit 33B performs chirp correction at a chirping rate ⁇ 2 on the IQ signal IQ B (n) to extract an up-chirped synchronizing signal Q 2 (n).
  • phase ⁇ 3 (n) shown in the following equation 9 corresponding to the address (n) of the nonvolatile memory 331A
  • a down-chirp signal with an initial frequency fs and a chirp rate ⁇ 1 can be generated.
  • the phase ⁇ 4 (n) derived by the non-volatile memory 331B can be constructed in the same way, except that the chirp rate is changed to ⁇ 2 and the initial frequency to +fs. (See Equation 10 below.)
  • Phase derotation blocks 330A and 330B also comprised of non-volatile memory, perform chirp correction on the IQ signal IQ B (n) to produce a down-chirp sync signal Q 1 (n) as shown in Equations 11 and 12 below. Extract the up-chirp sync signal Q 2 (n).
  • FFT 70A and 70B perform Fourier transforms on the down-chirp sync signal Q 1 (n) and the up-chirp sync signal Q 2 (n) to obtain frequency responses.
  • Peak detection circuits 72A and 72B detect frequencies (fd, fu) at which the frequency response peaks.
  • Subtraction circuit 76 finds the difference between the two peak frequencies (fd, fu) and division circuit 73 divides by 2 ⁇ to find time delay ⁇ from equation 13 below.
  • the frequency deviation ⁇ r is removed, and the accurate time delay ⁇ can be obtained.
  • the delay circuit 36 shown in FIG. 8 can correct the time delay .delta.
  • the peak filters 71A and 71B are narrow band filters and extract spectral components around two peak frequencies (fd, fu).
  • Inverse Fourier transform circuits 74A and 74B inverse Fourier transform the signal components extracted by the peak filters 71A and 71B.
  • the arctangent calculators 75A and 75B detect the phase component ⁇ (n) of the transmission line characteristic by extracting the phase component from the output of the inverse Fourier transform circuit.
  • An adder circuit 77 adds the outputs of the two arctangent calculators 75A and 75B, and a divider circuit 78 divides the result by 2 to obtain the phase component ⁇ (n) of the transmission line characteristic with less noise after averaging processing. be able to.
  • the phase rotation correction circuit 36 reversely rotates the phase of the IQ signal IQ B (n) by - ⁇ (n), thereby correcting the frequency deviation and phase rotation occurring in the transmission path. is corrected and output as an IQ signal IQ C (n).
  • the synchronizing signal extracting means 32 extracts the down-chirp synchronizing signal Q 1 (n) and the up-chirp synchronizing signal Q 2 (n) by the two dechirp circuits 33A and 33B, and the synchronizing signal processing means 34
  • the channel characteristics ( ⁇ , ⁇ (n)) can be detected and output, and the transmission channel characteristics ( ⁇ , ⁇ (n)) thus obtained are used to generate the IQ signal IQ B (n). Synchronization can be achieved by correcting.
  • FIG. 10 shows an example of experimental results using the wireless transmission method of this system.
  • FIG. 10B is the result of spectrogram observation of the transmission signal TX(t).
  • the spectrogram is a method of creating a two-dimensional image with time on the vertical axis and frequency on the horizontal axis, and expressing the signal intensity by pixel brightness. From this spectrumgram, it was confirmed that the cross-carrier signal Cr(t) whose frequency changes over time is displayed like an "X" character centered on the carrier frequency.
  • FIG. 11 is a constellation observed in the radio receiver of the present invention. Due to the frequency deviation ( ⁇ TX , ⁇ Rx ) generated in each of the transmitter and receiver, and the phase rotation applied in the propagation path, the constellation of the IQ signal IQ B (n) before synchronization correction is swirling. rotating.
  • FIG. 11A On the other hand, the constellation of the IQ signal IQ C (n) subjected to the synchronizing signal processing of the present invention is in a decodable state as the rotation stops perfectly.
  • FIG. 11B Here the I axis is a BPSK modulated signal, so it is divided into two levels "+1, -1". A wide band is observed on the Q-axis as the cross-carrier signal Cr(t).
  • FIG. 12 is a diagram schematically showing the spectrum of a radio transmission signal in the second embodiment according to the invention.
  • FIG. 12A uses two different chir rates ( ⁇ 1, ⁇ 2) as the cross-carrier signal Cr(t) as in the first embodiment.
  • FIG. 12B different chirp rates ( ⁇ 3, ⁇ 4) are used as the cross-carrier signal Cr(t). These four chir plates ( ⁇ 1, ⁇ 2, ⁇ 3, ⁇ 4) are different from each other.
  • FIG. 13 is a diagram showing the concept of the wireless communication format in the third embodiment related to the present invention.
  • the down-chirp signal 14A and the up-chirp signal 14B are periodically turned on and off.
  • the turn-on time zones 14A and 14B are configured to be different from each other so that the down-chirp signal 14A and the up-chirp signal 14B do not interfere with each other. Therefore, interference between the down-chirp signal 14A and the up-chirp signal 14B can be prevented.
  • FIG. 14 is a block diagram of the wireless transmission device 2 that implements the method of FIG. 13 (the method of periodically turning on and off the down-chirp signal 14A and the up-chirp signal 14B).
  • an oscillator 231 generates a periodic signal
  • an inverting circuit 232 switches two analog switches 230A and 230B in opposite phases, whereby the down-chirp signal 14A and the up-chirp signal 14B are switched at timings that do not overlap each other.
  • a low-pass filter (LPF) 233 removes high frequency components generated at the switching timing.
  • LPF low-pass filter
  • the configuration of the radio receiving device 3 when periodically switching between the down-chirp signal 14A and the up-chirp signal 14B will be described.
  • the narrow band filters peak filters 71A and 71B mounted in the sync signal extracting means 32
  • the intermittently transmitted down-chirp signal 14A and up-chirp signal 14B can be smoothed.
  • synchronization can be achieved using the wireless receiving device 3 described in the first embodiment as it is.
  • FIG. 15 is a diagram showing the concept of the wireless communication format in the fourth embodiment.
  • FIG. 15 shows a fourth embodiment in which the wireless communication method described in the third embodiment is further developed.
  • a BPSK signal (frame sync 11 and data 12) is intermittently transmitted.
  • the down-chirp signal 14A and the up-chirp signal 14B are alternately switched and inserted as the cross-carrier signal.
  • FIG. 16 is a diagram showing the concept of the wireless communication format in the fifth embodiment.
  • FIG. 16 shows a fifth embodiment in which the radio communication method described in the first embodiment is further developed.
  • signals are created by adding cross-carrier signals 14A and 14B to BPSK signals (frame sync 11 and data 12), and chirp modulation is applied to these signals.
  • BPSK signals frame sync 11 and data 12
  • chirp modulation is applied to these signals.
  • the signal frequency band is widened from fc-fs to fc+fz, and it becomes possible to realize stable communication by reducing the influence of interference.
  • multiplexing can also be achieved by changing the two chirp rates ( ⁇ 5 and ⁇ 6) according to the system. It is also possible to intermittently cross-carrier signals and data signals as shown in the third and fourth embodiments.

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  • Engineering & Computer Science (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Signal Processing (AREA)
  • Digital Transmission Methods That Use Modulated Carrier Waves (AREA)
  • Synchronisation In Digital Transmission Systems (AREA)

Abstract

Un procédé de transmission radio selon la présente invention est caractérisé en ce qu'une pluralité de signaux chirp sont utilisés en tant que signaux de synchronisation ou certains des signaux de synchronisation et les taux de variation de la pluralité de signaux chirp sont différents.　Selon le procédé de transmission radio de la présente invention, des signaux de porteuse croisée obtenus par combinaison de signaux chirp présentant différents taux de variation sont transmis sans fil en tant que signaux de synchronisation, ce par quoi le retard temporel peut être détecté avec précision et un circuit simple peut être utilisé pour obtenir une synchronisation stable de communications radio.　En outre, selon le procédé de transmission radio de la présente invention, une structure simple de dispositif de réception peut être utilisée pour ajuster les décalages de temps, de phase et de fréquence (c'est-à-dire, pour réaliser une synchronisation) et en outre la synchronisation peut être rendue moins susceptible d'être perturbée par les interférences ou similaire.
PCT/JP2022/038451 2021-10-25 2022-10-14 Procédé de transmission radio, dispositif de transmission radio, procédé de réception radio, dispositif de réception radio, et procédé de communication radio WO2023074420A1 (fr)

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