WO2023005820A1

WO2023005820A1 - Antenna and electronic device

Info

Publication number: WO2023005820A1
Application number: PCT/CN2022/107262
Authority: WO
Inventors: 师传波; 王汉阳; 吴鹏飞; 侯猛
Original assignee: 华为技术有限公司
Priority date: 2021-07-27
Filing date: 2022-07-22
Publication date: 2023-02-02
Also published as: CN115693112A

Abstract

Provided in the present application are an antenna and an electronic device. The antenna comprises an annular radiation body and a switch circuit. The annular radiation body comprises a plurality of radiation units, wherein there is a gap between opposite ends of any two adjacent radiation units, and the plurality of radiation units comprise a main radiation unit. The main radiation unit is provided with a slit at the middle position, and the slit divides the main radiation unit into a first main radiation unit and a second main radiation unit, which are arranged end-to-end and are arranged in a manner of being spaced apart, wherein opposite ends of the first main radiation unit and the second main radiation unit perform feeding in an anti-symmetric feeding mode. The switch circuit is used for controlling an electrical connection state of a first radiation unit pair among the plurality of radiation units, wherein the first radiation unit pair comprises an adjacent first radiation unit and second radiation unit. By means of the present application, the switch circuit can be used to control the state between the radiation units, such that the antenna generates different radiation patterns, thereby improving the spatial coverage capability of the radiation direction of the antenna, and even realizing omnidirectional coverage of the radiation direction.

Description

Antennas and Electronics

This application claims the priority of a Chinese patent application with application number CN202110852952.6 and application title "antenna and electronic equipment" filed with the China Patent Office on July 27, 2021, the entire contents of which are incorporated herein by reference.

technical field

The present application relates to the field of antennas, in particular to an antenna and electronic equipment.

Background technique

With the miniaturization and multi-functionalization of terminal products, the requirements for antenna performance are getting higher and higher. Antennas often need to work in multiple states and modes. When the antenna is in different working modes, it will produce Different radiation patterns, for example, in some application scenarios, antennas are required to generate Broadside radiation patterns (that is, end-fire radiation patterns), and in some application scenarios, antennas are required to generate horizontal omnidirectional radiation patterns, so as to meet the needs of different wireless communication systems. need.

A single antenna in the prior art can usually only produce one radiation pattern, for example ["A MNG-TL Loop Antenna Array With Horizontally Polarized Omnidirectional Patterns" KunpengWei, Zhijun Zhang, Senior Member, IEEE, Zhenghe Feng, Fellow, IEEE , and Magdy F.Iskander, Life Fellow, IEEE] provided a horizontally polarized omnidirectional loop antenna based on an artificial negative magnetic permeability transmission line. Far-field radiation pattern, through array formation, the antenna can generate a horizontal omnidirectional radiation pattern, and the antenna gain is significantly improved.

However, the antenna in this document has the following defects. The antenna can only generate a horizontal omnidirectional radiation pattern, and the center point of the horizontal plane has a radiation "pits" (that is, points with very low radiation magnetic field strength), which cannot achieve full coverage of the radiation direction .

In order to solve the use requirements of antennas in different application scenarios, so that the radiation pattern of a single antenna is different from the antenna radiation pattern in the above literature, the literature ["Dual-linear Polarization Reconfigurable Broadband Omnidirectional Antenna", Angjie Li, Wen Jiang, Shui Gong] proposed A double-loop structure antenna, the double loops (large and small loops) are all non-slit structures, using a dipole feed network, and switching between different polarizations of 1*λ ring mode, large and small loop mixed modes through the feed network, For example, State1 (i.e. state 1) is the macrocyclic one-wavelength mode that excites Y polarization and the mixed mode of small and large rings that are Y-polarized, and State2 (i.e. state 2) is the macrocyclic one-wavelength mode that excites X polarization and The X-polarized small ring and large ring mixed mode can make the antenna work in different states and produce different radiation patterns.

However, the antenna in this document has the following defects. Although the radiation patterns generated by the antennas in the two antenna states are different and have certain complementarity, the realization of the state switching of the antenna requires the design of a complex feed switching network, and the two The antenna status can only switch the Broadside radiation pattern (that is, the end-fire radiation pattern), and cannot provide a horizontal omnidirectional radiation pattern.

It can be seen that the prior art has the problems of single radiation pattern and low spatial coverage of antenna radiation.

Contents of the invention

The purpose of the present application is to solve the problem in the prior art that the radiation pattern is single and the spatial coverage of antenna radiation is low. Therefore, this embodiment provides an antenna and an electronic device, which can control the electrical connection state between the radiation units of the antenna radiator through the switch circuit arranged between the radiation units, and then change the radiation pattern of the antenna, so as to Realize the switchability of multiple radiation patterns, thereby improving the spatial coverage capability of antenna radiation.

An embodiment of the present application provides an antenna, which includes a loop radiator, the loop radiator includes a plurality of radiation units, and there is a gap between the opposite ends of any two adjacent radiation units;

including a main radiating element in the plurality of radiating elements;

The main radiating unit is provided with a gap in the middle, and the slit divides the main radiating unit into a first main radiating unit and a second main radiating unit arranged end-to-end at intervals, and the first main radiating unit and the second main radiating unit are opposite to each other. The end adopts the mode of anti-symmetric feeding; the antenna also includes a switch circuit, and the switch circuit is used to control the electrical connection state of the first radiating unit pair in the plurality of radiating units, and the first radiating unit pair includes adjacent first radiating units and the second radiating unit, the gap between the first radiating unit and the second radiating unit is the first gap.

In this solution, through the switch circuit, the electrical connection state of the first radiating unit pair in the plurality of radiating units can be controlled, so that the antenna can generate different radiation patterns, and the antenna can generate complementary radiation patterns, in order to improve the radiation The spatial coverage capability of the direction lays the foundation.

In some possible embodiments, the switch circuit is used to control the electrical connection state of any two adjacent radiation units among the plurality of radiation units.

In some possible embodiments, among the opposite ends of the first main radiating unit and the second main radiating unit, one end is connected to the positive pole of the feed source, and the other end is connected to the negative pole of the feed source, so as to realize feeding through anti-symmetrical feeding. electricity.

In some possible embodiments, the shape of the annular radiator is circular or rectangular.

In some embodiments, the switch circuit includes a first sub-switch unit connected between the first radiating unit and the second radiating unit of the first radiating unit pair, the first sub-switching unit has a connected state and a disconnected state, in,

When the first sub-switch unit is in a connected state, the first radiating unit and the second radiating unit of the first radiating unit pair are electrically connected through the first sub-switching unit.

When the first sub-switch unit is in the off state, the first radiating unit and the second radiating unit of the first radiating unit pair are coupled through the first gap.

In some embodiments, the working frequency band of the antenna when the first sub-switch unit is in the disconnected state and the working frequency band of the antenna when the first sub-switch unit is in the connected state include the same working frequency band.

In some embodiments, the antenna further includes the first matching device, the first matching device is connected in series with the first sub-switch unit, and the first sub-switch unit and the first matching device are connected to the first radiation unit of the first radiation unit pair and between opposite ends of the second radiating element;

The first matching device is used to control: the working frequency band of the antenna when the first sub-switch unit is in the disconnected state, and: the working frequency band when the first sub-switch unit is in the connected state, including the same frequency band. This enables the antenna to maintain a stable and consistent operating frequency in various states (for example, when the first radiating unit is electrically connected to the second radiating unit or when the first radiating unit is not electrically connected to the second radiating unit).

In some embodiments, the switch circuit includes a plurality of sub-switch units, the plurality of radiating units includes a plurality of radiating unit pairs, each pair of radiating units includes two adjacent radiating units, and the plurality of sub-switching units and the plurality of radiating unit pairs One-to-one correspondence, each sub-switch unit in the plurality of sub-switch units is used to control the electrical connection state of two adjacent radiating units in a corresponding pair of radiating units.

In this solution, the electrical connection states of multiple radiating unit pairs can be controlled through a plurality of sub-switching units. At different times, the antenna can generate different radiation patterns. For example, when all the radiating elements and their adjacent radiating elements are in a state of electrical connection, the antenna can be understood as being able to form a traditional loop antenna to generate a Broadside radiation pattern (also known as That is, the end-fire radiation pattern), when all the radiating units and their adjacent radiating units are not electrically connected, the antenna can be understood as a coupling loop antenna at this time, and a horizontal omnidirectional radiation pattern is generated. It can be seen that this scheme can use Multiple sub-switch circuits help the antenna to generate complementary radiation patterns by controlling the electrical connection state between the radiation units, improve the spatial coverage capability of the antenna radiation direction, and even realize omnidirectional coverage in the radiation direction.

It should be noted that the multiple radiation unit pairs include the first radiation unit pair. The number of radiating units is the same as the number of radiating unit pairs, for example, 3 radiating units include 3 radiating unit pairs, and 4 radiating units include 4 radiating unit pairs.

The plurality of sub-switching units includes a first sub-switching unit. Further, the structure of other sub-switch units of the plurality of sub-switch units may be the same as that of the first sub-switch unit.

In some possible embodiments, the sub-switch units are switches and are disposed in corresponding gaps.

In some embodiments, the antenna includes multiple matching devices, the multiple matching devices correspond to the multiple sub-switch units one by one, each of the multiple matching devices is connected in series with a corresponding sub-switch unit, and each matching device The sub-switch unit connected in series with it is connected between two adjacent radiation units in the corresponding radiation unit pair.

It should be noted that the multiple matching devices include a first matching device. Further, the structure of other matching devices of the plurality of matching devices may be the same as that of the first matching device.

In some possible embodiments, the series-connected matching device and the sub-switch unit are arranged in corresponding gaps.

The matching device is used to control: the working frequency band of the antenna when each sub-switch unit is in a disconnected state, and: the working frequency band when each sub-switch unit is in a connected state, including the same frequency band. This enables the antenna to maintain a stable and consistent operating frequency in each state (for example, when each radiating element is electrically connected to an adjacent radiating element or when each radiating element is not electrically connected to an adjacent radiating element) .

In some possible embodiments, the resonant frequency of the antenna when each radiating element is not electrically connected to its adjacent radiating elements, and: the resonant frequency of the antenna when each radiating element is electrically connected to its adjacent radiating elements The resonant frequency is the same frequency or a similar frequency. In some possible embodiments, the matching device is an inductor.

In some embodiments, the antenna further includes a first coupling stub disposed corresponding to the first gap, and opposite ends of the first radiating element and the second radiating element of the first radiating element pair are coupled through the first coupling stub.

Among them, the first coupling stub can significantly enhance the coupling degree between the first radiating unit and the second radiating unit, especially when the first radiating unit and the second radiating unit are not electrically connected, the coupling between the first radiating unit and the second radiating unit can be enhanced. The degree of coupling between the two radiating units improves the radiation intensity of the radiating units.

In some embodiments, the first coupling stub is spaced from the annular radiator, and the length of the first coupling stub extending in the circumferential direction of the annular radiator exceeds the length of the first gap extending in the circumferential direction of the annular radiator. In this way, the coupling degree between the first radiating unit and the second radiating unit can be further improved.

In some embodiments, the first coupling stub is arranged at an interval from the annular radiator in the axial direction of the annular radiator, or the first coupling stub is located at an inner peripheral side or an outer peripheral side of the annular radiator and is arranged at intervals from the annular radiator.

In some embodiments, the antenna further includes a plurality of coupling stubs; the plurality of coupling stubs correspond to a plurality of radiation unit pairs, and each coupling stub in the plurality of coupling stubs corresponds to a corresponding radiation unit pair, each The opposite ends of two adjacent radiation units in the radiation unit pair are coupled through corresponding coupling stubs when the corresponding sub-switch unit is in an off state.

Among them, the coupling branch can significantly enhance the coupling degree between the corresponding adjacent pair of radiating units, especially when a pair of adjacent radiating units are in the disconnected state, it can enhance the coupling degree between two adjacent radiating units and improve The radiation intensity of the radiation unit, so that the radiation intensity of the radiator in each radiation direction in the horizontal plane is more uniform.

It should be noted that the multiple coupling stubs include the first coupling stub. Further, the structure of other coupling stubs of the plurality of coupling stubs may be the same as that of the first coupling stub. In some possible embodiments, the loop radiator is arranged on the antenna supporting board (such as a PCB board), so that the coupling degree between any adjacent two radiation units can be adjusted only by coupling stubs and the radiation unit itself, and The thickness of the antenna carrier board is decoupled (that is, it has nothing to do with the thickness of the antenna carrier board), thereby reducing the complexity of the design.

In some possible embodiments, among the plurality of coupling stubs, the lengths of the coupling stubs away from the main radiation unit along the circumferential direction of the annular radiator are respectively greater than the lengths of each other coupling stubs along the circumferential direction of the annular radiator , which can improve the unbalance of the coupling ring mode magnetic field, and then can excite the purer coupling ring mode, make the electromagnetic field and current distribution of the antenna more uniform, and make the antennas in different states (for example, all radiating elements are in the electrical connection state Or the radiating elements are in a non-electrically connected state) and the radiation patterns generated by them are more complementary.

In some embodiments, when all the sub-switch units are in the off state and the main radiation unit is feeding power, the ring radiator can generate a ring current flowing through all the radiation units;

When all the sub-switch units are connected and the main radiation unit is feeding power, the ring radiator can generate the first current and the second current;

Wherein, the first current flows through half of the annular radiator, the second current flows through the other half of the annular radiator, and the flow directions of the first current and the second current are opposite.

In some embodiments, the first main radiating unit and the second main radiating unit are symmetrical about the slot.

In some embodiments, the annular radiator adopts a centrosymmetric structure.

In some possible embodiments, the number of radiation units is 2 to 6.

In some embodiments, the number of radiation units is 3 or 4.

In some possible embodiments, if the number of the multiple radiation units is four, then: the multiple sub-switch units include a first sub-switch unit, a second sub-switch unit, a third sub-switch unit, and a fourth sub-switch unit; The first sub-switch unit, the second sub-switch unit, the third sub-switch unit and the fourth sub-switch unit are sequentially distributed along the circumferential direction of the annular radiator (in this embodiment, along the clockwise direction), and the first sub-switch unit Connected between the main radiation unit connected to the negative pole of the feed source and the radiation unit adjacent to the main radiation unit (that is, the main radiation unit connected to the negative pole of the feed source) among the first main radiation unit and the second main radiation unit Between the second sub-switching unit, the main radiation unit connected to the positive pole of the feed source and the main radiation unit connected to the positive pole of the feed source among the first main radiation unit and the second main radiation unit ) between adjacent radiating elements.

Specifically, the main radiation unit connected to the negative pole of the feed source among the first main radiation unit and the second main radiation unit is the first main radiation unit, and the first main radiation unit and the second main radiation unit are connected to the positive pole of the feed source The main radiating unit is the second main radiating unit. That is to say, the first sub-switch unit is connected between the radiation unit adjacent to the first main radiation unit and the first main radiation unit, and the first main radiation unit is also connected to the negative pole of the feed source; the second sub-switch unit is connected to Between the radiation unit adjacent to the second main radiation unit and the second main radiation unit, the second main radiation unit is also connected to the positive pole of the feed source.

When the two radiating units connected to the first sub-switch unit and the two radiating units connected to the third sub-switch unit are in an electrically connected state, and: the two radiating units connected to the second sub-switch unit, and the second sub-switch unit The two radiating units connected to the four sub-switching units are not electrically connected. At the same time, when the main radiating unit is connected to the feed source, the annular radiator can generate two flow directions from the fourth sub-switching unit to the second sub-switching unit. opposite current;

When the two radiation units connected to the first sub-switch unit and the two radiation units connected to the third sub-switch unit are not electrically connected, and: the two radiation units connected to the second sub-switch unit, and The two radiating units connected to the fourth sub-switching unit are both in an electrically connected state, and when the main radiating unit is connected to the feed source, the annular radiator can generate two flow directions from the first sub-switching unit to the third sub-switching unit respectively. opposite current.

In this solution, by controlling the switching between the connected state and the disconnected state of the four sub-switch units, a variety of different antenna states can be switched, up to 16 (2 ⁴ ) antenna states can be switched, for example, when the four sub-switches When the units are all disconnected, each radiating unit and its adjacent radiating units are not electrically connected. At this time, the antenna can be understood as a coupling loop antenna, which produces a horizontal omnidirectional radiation pattern. When all four sub-switch units are connected state, each radiating unit is electrically connected to its adjacent radiating unit, and the antenna at this time can be understood as a traditional loop antenna, which generates a Broadside radiation pattern (that is, an end-fire radiation pattern). When the first sub-switch unit and When the third sub-switch unit is in the connected state, and the second sub-switch unit and the fourth sub-switch unit are in the disconnected state, the antenna at this time can produce a Broadside radiation pattern (that is, an end-fire pattern) different from that of the above-mentioned traditional loop antenna. radiation pattern), when the second sub-switch unit and the fourth sub-switch unit are in the connected state, and the first sub-switch unit and the third sub-switch unit are in the disconnected state, the antenna at this time can generate Different Broadside radiation patterns (ie endfire radiation patterns).

It can be seen that the antenna provided by this solution can switch between the connected state and the disconnected state through the four sub-switch units, and switch between various antenna states, which further improves the spatial coverage of the antenna radiation.

An embodiment of the present application provides an electronic device, and the electronic device further includes the antenna provided in any one of the foregoing embodiments or any possible embodiment.

In some embodiments, the electronic device further includes an antisymmetric feed network, the antisymmetric feed network includes a first radio frequency microstrip line and a second radio frequency microstrip line, the opposite ends of the first main radiation unit and the second main radiation unit Among them, one end is connected to the positive pole of the feed source through the first radio frequency microstrip line, and the other end is connected to the negative pole of the feed source through the second radio frequency microstrip line, so that the first main radiation unit and the second main radiation unit are fed through antisymmetric way of feeding.

In some embodiments, the anti-symmetric feeding network further includes an adjustable capacitor connected between the feed source of the electronic device and the main radiation unit for adjusting the input impedance of the antenna.

In some embodiments, the electronic device further includes an antenna carrying plate, the antenna carrying plate has a first surface, and a second surface opposite to the first surface, and the loop radiator is disposed on the first surface of the antenna carrying plate;

When the antenna further includes a first coupling stub, the first coupling stub is disposed on the first surface or the second surface of the antenna bearing plate;

In some possible embodiments, the loop radiator of the antenna is pasted on the antenna bearing plate by laser direct forming process or integrated on the antenna bearing plate by etching process.

In some possible embodiments, the loop radiator of the antenna is an FPC board or a metal structure.

In some embodiments, the antenna carrying board is a PCB board or a dielectric board, and the electronic device is a router.

Description of drawings

Fig. 1, Fig. 2a, Fig. 2b are respectively the structural diagram of the antenna of the embodiment of the present application, the schematic diagram of the current flow in state 1 and the schematic diagram of the current flow in state 2, wherein the number of radiation units is 3, and the sub The switch unit and the matching device are arranged in the gap;

FIG. 3 is a schematic structural diagram of the antenna of the embodiment of the present application, wherein the number of radiation units is three, and the sub-switch unit and the matching device are arranged outside the gap;

FIG. 4 is a schematic structural diagram of an antenna and an antenna carrying board in an electronic device according to an embodiment of the present application;

Figures 5a to 5c are three-dimensional structural diagrams, front structural diagrams and rear structural schematic diagrams of the antenna and the antenna carrier board in the electronic device of the embodiment of the present application;

FIG. 6 is a schematic structural diagram of a router according to an embodiment of the present application;

Fig. 7 is the effect curve diagram of the comparison of the S parameters of the antenna obtained when the antenna of the embodiment of the present application is tested in state 1 and state 2 respectively;

Fig. 8 is an effect curve diagram comparing the radiation efficiency and system efficiency (i.e. efficiency) of the antenna obtained when the antenna of the embodiment of the present application is tested in state 1 and state 2 respectively;

Fig. 9a, Fig. 9b and Fig. 9c are respectively the antenna local current distribution diagram, the antenna local electric field distribution diagram, and the antenna local magnetic field distribution diagram obtained when the antenna of the embodiment of the present application performs the simulation effect test under state 1;

Fig. 10a, Fig. 10b, and Fig. 10c are the antenna local current distribution diagram, the antenna local electric field distribution diagram, and the antenna local magnetic field distribution diagram obtained when the antenna of the embodiment of the present application performs the simulation effect test in state 2, respectively;

Figure 11a and Figure 11b are three-dimensional diagrams of the antenna radiation direction obtained when the antenna of the embodiment of the present application is tested for simulation effects in state 1 and state 2, respectively;

Figures 12a to 12c are two-dimensional comparison diagrams of antenna radiation directions obtained when the antennas of the embodiments of the present application are tested for simulation effects in state 1 and state 2 respectively;

Figures 13a to 13c are the antenna polarization direction vector diagrams obtained when the antenna of the embodiment of the present application is tested for the simulation effect in state 1, wherein the spherical coordinate system is used for the simulation effect test;

Figures 13d to 13e are the angles Theta(θ) and Phi in the spherical coordinate system used when the antenna of the embodiment of the present application performs the simulation effect test under state 1.

schematic diagram;

Figures 14a to 14c are the antenna polarization direction vector diagrams obtained when the antenna of the embodiment of the present application is tested for the simulation effect in state 2, wherein the spherical coordinate system is used for the simulation effect test;

Figures 14d to 14e are the angles Theta(θ) and Phi in the spherical coordinate system used when the antenna of the embodiment of the present application is tested for the simulation effect in state 2.

schematic diagram;

Fig. 15 is a schematic structural diagram of the antenna of the embodiment of the present application, wherein the coupling branch is arranged on the inner peripheral side of the annular radiator, and the number of radiation units is three;

FIG. 16 is a schematic diagram of the front structure of the antenna and the antenna carrying board in the electronic device according to the embodiment of the present application;

FIG. 17 is an effect curve diagram of the comparison of S parameters obtained when the antenna of the embodiment of the present application is tested for simulation effects in state 1 and state 2 respectively;

Fig. 18 is an effect curve diagram comparing the radiation efficiency of the antenna and the system efficiency (ie, efficiency) obtained when the antenna of the embodiment of the present application is tested in state 1 and state 2 respectively;

Figure 19a, Figure 19b, and Figure 19c are the antenna local current distribution diagram, antenna local electric field distribution diagram, and antenna local magnetic field distribution diagram obtained when the antenna of the embodiment of the present application is tested for simulation effects in state 1, respectively;

Figure 20a, Figure 20b, and Figure 20c are the antenna local current distribution diagram, antenna local electric field distribution diagram, and antenna local magnetic field distribution diagram obtained when the antenna of the embodiment of the present application is tested for simulation effect in state 2, respectively;

Figure 21a and Figure 21b are three-dimensional diagrams of the antenna radiation direction obtained when the antenna of the embodiment of the present application is tested for simulation effects in state 1 and state 2, respectively;

Figures 22a to 22c are two-dimensional comparison diagrams of antenna radiation directions obtained when the antennas of the embodiments of the present application are tested for simulation effects in state 1 and state 2 respectively;

Figures 23a to 23c are the antenna polarization direction vector diagrams obtained when the antenna of the embodiment of the present application is tested for the simulation effect in state 1, wherein the spherical coordinate system is used for the simulation effect test;

Figures 24a to 24c are the antenna polarization direction vector diagrams obtained when the antenna of the embodiment of the present application is tested for the simulation effect in state 2, wherein the spherical coordinate system is used for the simulation effect test;

Figures 25a to 25e are schematic diagrams of the structure of the antenna of the embodiment of the present application, and schematic diagrams of the current flow of the antenna in state 1, state 2, state 3, and state 4, wherein the coupling branch is arranged below the annular radiator, and the radiation The number of units is 4;

FIG. 26 is a schematic structural diagram of an antenna and an antenna carrying board in an electronic device according to an embodiment of the present application;

Figures 27a to 27c are three-dimensional structural diagrams, front structural diagrams and rear structural schematic diagrams of the antenna and the antenna bearing plate in the electronic device of the embodiment of the present application;

Fig. 28 is an effect curve diagram of the comparison of S parameters obtained when the antenna of the embodiment of the present application is tested in state 1, state 2, state 3, and state 4 respectively;

Fig. 29 is an effect curve diagram comparing the radiation efficiency of the antenna and the system efficiency (i.e., efficiency) when the antenna of the embodiment of the present application is subjected to the simulation effect test under state 1, state 2, state 3, and state 4 respectively;

Figure 30a, Figure 30b, and Figure 30c are the antenna local current distribution diagram, the antenna local electric field distribution diagram, and the antenna local magnetic field distribution diagram obtained when the antenna of the embodiment of the present application is tested for the simulation effect in state 1, respectively;

Figure 31a, Figure 31b, and Figure 31c are the antenna local current distribution diagram, antenna local electric field distribution diagram, and antenna local magnetic field distribution diagram obtained when the antenna of the embodiment of the present application is tested for simulation effects in state 2, respectively;

Figure 32a, Figure 32b, and Figure 32c are the antenna local current distribution diagram, antenna local electric field distribution diagram, and antenna local magnetic field distribution diagram obtained when the antenna of the embodiment of the present application is tested for simulation effects in state 3, respectively;

Figure 33a, Figure 33b, and Figure 33c are the antenna local current distribution diagram, the antenna local electric field distribution diagram, and the antenna local magnetic field distribution diagram obtained when the antenna of the embodiment of the present application is tested for the simulation effect in state 4, respectively;

Fig. 34a, Fig. 34b, Fig. 34c, and Fig. 34d are the three-dimensional diagrams of the antenna radiation direction obtained when the antenna of the embodiment of the present application is tested for the simulation effect in state 1, state 2, state 3, and state 4, respectively;

Figures 35a to 35c are two-dimensional comparison diagrams of antenna radiation directions obtained when the antennas of the embodiments of the present application are tested for simulation effects in state 1 and state 2 respectively;

Figures 36a to 36c are the antenna polarization direction vector diagrams obtained during the simulation effect test of the antenna in the embodiment of the present application when it is in state 1, wherein the spherical coordinate system is used in the simulation effect test;

Figures 37a to 37c are the antenna polarization direction vector diagrams obtained during the simulation effect test of the antenna in the embodiment of the present application when it is in state 2, wherein the spherical coordinate system is used in the simulation effect test;

Figures 38a to 38c are the antenna polarization direction vector diagrams obtained during the simulation effect test of the antenna in the embodiment of the present application when it is in state 3, wherein the spherical coordinate system is used in the simulation effect test;

39a to 39c are the antenna polarization direction vector diagrams obtained during the simulation effect test of the antenna in state 4 according to the embodiment of the present application, wherein a spherical coordinate system is used in the simulation effect test.

Explanation of reference signs:

100: antenna;

110: main radiation unit; 111: first main radiation unit; 112: second main radiation unit; 113: gap; 120: radiation unit; 130: radiation unit; 141, 142, 143: gap; 151, 152, 153: sub-switch unit; 161, 162, 163: matching devices; 171, 172, 173: coupling stubs;

200: feed source;

300: electronic equipment; 310: antenna carrying board; 311: first surface; 312: second surface;

L1, L2, L3: inductance; S1, S2, S3: switch; α1, α2, α3: central angle;

100A: Antenna;

110A: main radiation unit; 111A: first main radiation unit; 112A: second main radiation unit; 113A: slot; 120A: radiation unit; 130A: radiation unit; 141A, 142A, 143A: gap; 171A, 172A, 173A: coupling branch;

200A: feed source;

300A: Electronic equipment; 310A: Antenna carrier board;

L1 _A , L2 _A , L3 _A : inductance; S1 _A , S2 _A , S3 _A : switch; α1 _A , α2 _A , α3 _A : central angle; W: width of coupling branch; D: distance;

100B: antenna;

110B: main radiation unit; 111B: first main radiation unit; 112B: second main radiation unit; 113B: gap; 120B: radiation unit; 130B: radiation unit; 140B: radiation unit; 141B, 142B, 143B, 144B: gap ;171B:, 172B, 173B, 174B: Coupling branches;

200B: feed source;

300B: electronic equipment; 310B: antenna carrier board; 311B: first surface; 312B: second surface; 321B: first microstrip line; 322B: second microstrip line;

L1 _B , L2 _B , L3 _B , L4 _B : inductance; S1 _B , S2 _B , S3 _B , S4 _B : switch; C: adjustable capacitor;

R1: inner diameter of annular radiator; R2: outer diameter of annular radiator; R3: outer diameter of antenna bearing plate; R4: inner diameter of coupling stub; R5: outer diameter of coupling stub; I ₀ : ring current; I ₁ : first current; I ₂ : the second current.

Detailed ways

The implementation of the present application will be described by specific specific examples below, and those skilled in the art can easily understand other advantages and effects of the present application from the content disclosed in this specification. Although the description of the present application will be presented in conjunction with some embodiments, this does not mean that the features of the application are limited to the embodiments. On the contrary, the purpose of introducing the application in conjunction with the embodiments is to cover other options or modifications that may be extended based on the claims of the application. The following description contains numerous specific details in order to provide an in-depth understanding of the present application. The application may also be practiced without these details. Furthermore, some specific details will be omitted from the description in order to avoid obscuring or obscuring the focus of the application. It should be noted that, in the case of no conflict, the embodiments in the present application and the features in the embodiments can be combined with each other.

It should be noted that in this specification, similar numerals and letters denote similar items in the following drawings, therefore, once an item is defined in one drawing, it does not need to be identified in subsequent drawings. for further definition and explanation.

In the description of this application, it should be noted that the terms "center", "upper", "lower", "left", "right", "vertical", "horizontal", "inner", "outer" etc. The indicated orientation or positional relationship is based on the orientation or positional relationship shown in the drawings, and is only for the convenience of describing the present application and simplifying the description, rather than indicating or implying that the referred device or element must have a specific orientation, use a specific orientation construction and operation, therefore should not be construed as limiting the application. In addition, the terms "first" and "second" are used for descriptive purposes only, and should not be understood as indicating or implying relative importance.

In the description of this application, it should be noted that unless otherwise specified and limited, the terms "installation", "connection", and "connection" should be understood in a broad sense, for example, it can be a fixed connection or a detachable connection. Connection, or integral connection; it may be mechanical connection; it may be direct connection or indirect connection through an intermediary, and it may be the internal communication of two elements. Those of ordinary skill in the art can understand the specific meanings of the above terms in this application in specific situations.

In the description of this application, it should be understood that "electrical connection" in this application can be understood as the physical contact and electrical conduction of components; PCB) copper foil or wires and other physical lines that can transmit electrical signals for connection. "Coupling" can be understood as the electrical conduction through indirect coupling. Among them, those skilled in the art can understand that the coupling phenomenon refers to the close relationship between the input and output of two or more circuit elements or electrical networks. The phenomenon of cooperation and mutual influence, and the transfer of energy from one side to the other through the interaction. In order to make the purpose, technical solution and advantages of the present application clearer, the implementation manner of the present application will be further described in detail below in conjunction with the accompanying drawings.

Please refer to FIG. 1 , which is a schematic structural diagram of an antenna according to an embodiment of the present application. As shown in FIG. 1 , an embodiment of the present application provides an antenna, which includes a loop radiator and a switch circuit. It should be noted that the shape of the annular radiator is not limited, and may be circular, elliptical, or rectangular. In this embodiment, the annular radiator is a circular shape with a centrally symmetrical structure.

Wherein, the annular radiator includes a plurality of radiation units, and there is a gap between opposite ends of any two radiation units. Among the multiple radiating units, one of the radiating units is the main radiating unit.

In this embodiment, the number of radiation units is three, specifically including the main radiation unit 110,

radiation units

120 and 130, and the main radiation unit 110, radiation unit 120, and radiation unit 130 are distributed in a ring to form the above-mentioned ring radiator. There is a gap 141 between the main radiation unit 110 and the radiation unit 120 , there is a gap 143 between the main radiation unit 110 and the radiation unit 130 , and there is a gap 142 between the radiation unit 120 and the radiation unit 130 .

Of course, those skilled in the art can understand that the number of radiating units is not limited, and can be 2, 4, 5, 6 or more, and the selection of the number can be selected according to the specific usage requirements of the antenna.

In addition, the main radiating unit 110 is provided with a slot 113 at the middle position, and the slit 113 divides the main radiating unit 110 into a first main radiating unit 111 and a second main radiating unit 112 arranged end-to-end and spaced apart. It should be noted that the middle position can be understood as including the midpoint of the geometric structure of the main radiation unit 110 , or the midpoint of the electrical length of the main radiation unit 110 , or an area within a certain range near the above midpoint. That is to say, the provision of the slit 113 at the middle position of the main radiation unit 110 can also be understood as: the slit 113 covers the midpoint of the main radiation unit. In this embodiment, the first main radiation unit 111 and the second main radiation unit 112 are symmetrical about the slot 113 .

It should be understood that the "symmetry" in this application is not a strict symmetry in the mathematical sense, and certain deviations are allowed.

Wherein, the main radiating unit 110 adopts an anti-symmetric feeding manner to feed power. For example, one of the opposite ends of the first main radiation unit 111 and the second main radiation unit 112 is connected to the anode of the feed source 200, and the other end of the second main radiation unit 112 and the first main radiation unit 111 is connected to the feed source. 200 negative. It should be noted that the signals output by the positive and negative poles of the feed source have the same amplitude and opposite phases, for example, the phase difference is 180°±10°.

Those skilled in the art should also understand that, when referring to one end of the radiating unit herein, the "end" is not limited to a certain end point of the radiating unit, but can also be a part of the radiating unit including the end point, For example, an area within 5 mm or an area of 2 mm within the end point of the radiating element.

Among them, the feed source 200 can be indirectly connected to the first main radiation unit 111 and the second main radiation unit 112 through a balun chip, and the single-channel signal of the feed source 200 can be converted into equal amplitude and 180° phase difference through the balun chip. The two-way signal to achieve anti-symmetrical feeding. It can also be connected to the main radiating unit 110 through a coaxial line, specifically, it can be connected to the second main radiating unit 112 through the outer conductor of the coaxial line, and connected to the first main radiating unit 111 through the inner conductor of the coaxial line. It may be connected to the first main radiation unit 111 through the outer conductor of the coaxial line, and connected to the second main radiation unit 112 through the inner conductor of the coaxial line. Of course, those skilled in the art can understand that, in other alternative implementation manners, other structures that satisfy anti-symmetric feeding are also possible.

Please refer to FIG. 1 , the switch circuit is used to control any adjacent radiating unit to switch between an electrically connected state and a non-electrically connected state, wherein any adjacent radiating unit can be, for example, the main radiating unit 110 and the radiating unit 120 in this embodiment, The main radiation unit 110 and the radiation unit 130 , and the radiation unit 120 and the radiation unit 130 .

When the switch circuit controls any of the above-mentioned radiating unit pairs (or two adjacent radiating units) to be electrically connected, the corresponding two radiating units (that is, the two radiating units controlled to be in the connected state) pass through the switching circuit electrical connection.

When the switch circuit controls any one of the radiating element pairs (or two adjacent radiating elements) to be in a non-electrically connected state, the corresponding two radiating elements (that is, the two radiating elements controlled to be in a non-electrically connected state) , can be coupled through the corresponding gap (that is, the gap between the two radiating elements controlled to be in the state of not being electrically connected). For example, when the switch circuit controls the main radiation unit 110 and the radiation unit 120 to be in the disconnected state, the main radiation unit 110 and the radiation unit 120 may be coupled through the gap 141.

Further, through the switch circuit, any two adjacent radiation units among the plurality of radiation units can be controlled to switch between an electrically connected state and a non-electrically connected state. Those skilled in the art can understand that, through the switch circuit, it is possible to control the electrical connection state between two adjacent radiating elements of a radiating element pair among the plurality of radiating elements, and also control The electrical connection status between the radiating elements. In the following, an example is used to control the electrical connection state between two adjacent radiation units of each radiation unit pair.

Further, as shown in FIG. 1 , the switch circuit includes a plurality of sub-switch units arranged in one-to-one correspondence with the gaps. Specifically, the switch circuit includes a sub-switch unit 151 corresponding to the gap 141 , a sub-switch unit 152 corresponding to the gap 142 , and a sub-switch unit 153 corresponding to the gap 143 . Each sub-switch unit is used to control two adjacent radiating units corresponding to a gap to switch between an electrically connected state and a non-electrically connected state.

For example, when the switch S1 is in the connected state, the main radiation unit 110 connected to the switch S1 and the radiation unit 120 are in an electrically connected state; when the switch S1 is in the disconnected state, the main radiation unit 110 connected to the switch S1 and the radiation unit 120 In the unconnected state, the main radiation unit 110 and the radiation unit 120 are coupled through the gap 141 or the coupling stub 171 mentioned later.

When the switch S2 or S3 is in the connected state and in the disconnected state, the situation is similar to that of the switch S1 , which will not be repeated here.

In the present application, through a plurality of sub-switch units, it is possible to control two adjacent radiation units of each radiation unit pair in the plurality of radiation units to switch between an electrically connected state and a non-electrically connected state. When the state (electrically connected state or not electrically connected state) is different, the antenna can produce different radiation patterns. A traditional loop antenna is formed to generate a Broadside radiation pattern (that is, an end-fire radiation pattern). When all radiating elements and adjacent radiating elements are not electrically connected, the antenna can be understood as a coupled loop antenna at this time, resulting in Horizontal omnidirectional radiation pattern, it can be seen that this application can use the switch circuit to control the state between the radiation units, which can help the antenna to generate a complementary radiation pattern, improve the spatial coverage of the antenna radiation direction, and even realize radiation omni-directional coverage.

Please refer to FIG. 2a and FIG. 2b. FIG. 2a is a schematic diagram of the current flow of the antenna of the embodiment of the present application in state 1, and FIG. 2b is a schematic diagram of the current flow of the antenna of the embodiment of the present application in state 2.

State 1 is: the main radiation unit 110 is connected to the feed source ₂₀₀ , and the switch S1, switch S2, and switch S3 are all in the off state. At this time, the ring radiator can generate a circular current I that flows through all the radiation units evenly and in the same direction. , in this embodiment, as shown in FIG. 2a, the loop current _I0 flows from the position connected to the positive pole of the feed source 200 through the entire loop radiator and then flows into the position connected to the negative pole of the feed source 200.

State 2 is: the main radiation unit 110 is connected to the feed source 200, and the switch S1, switch S2, and switch S3 are all in the connected state. When the antenna in state 2 excites the double wavelength mode, the feeding position of the ring radiator at this time (that is, the position where the feed source 200 is connected) is the strongest current point, the upper part of the annular radiator is centered on the feed position, and the current in the lower half of the annular radiator is symmetrically distributed with the current in the upper part, that is: annular radiation The body can generate a first current and a second current, the first current flows through half of the annular radiator, the second current flows through the other half of the annular radiator, and the flow directions of the first current and the second current are opposite. In this embodiment, as shown in FIG. 2 b , the first current I ₁ flows counterclockwise through the upper half of the annular radiator, and the second current I ₂ flows clockwise through the lower half of the annular radiator.

Further, as shown in FIG. 1 , the antenna 100 also includes matching devices corresponding to a plurality of sub-switch units, for example, the matching device 161 corresponding to the sub-switch unit 151 shown in FIG. 1 , and the sub-switch unit 152 The corresponding matching device 162 and the matching device 163 corresponding to the sub-switch unit 153, each matching device is connected in series with a corresponding sub-switch unit, and the sub-switch unit and the matching device connected in series are connected to the corresponding two adjacent radiation units between the opposite ends.

The matching device is used to control: the working frequency band of the antenna when each radiating unit is not electrically connected to its adjacent radiating unit, and: the working frequency band of the antenna when each radiating unit is electrically connected to its adjacent radiating unit , including the same frequency band. Or it can be understood as: the matching device can make the resonant frequency of the antenna in the above state 1 and state 2 be in the same frequency band. Specifically, the resonant frequencies of the antenna in state 1 and the antenna in state 2 may be the same or adjacent to each other.

It should be noted that, in the normal use of the antenna, the same frequency band should be understood as the working frequency band of the antenna. The antenna in this embodiment is a WiFi antenna, and the working frequency band of the antenna is the WiFi frequency band, for example, about 2.4 GHz to 2.5 GHz. Of course, those skilled in the art can understand that the working frequency of the antenna can be adjusted according to actual needs, such as 5 GHz, etc., which does not limit the protection scope of the present application.

In this embodiment, as shown in FIG. 1, the sub-switch unit is a switch, specifically, switch S1, switch S2, and switch S3, wherein the form of the switch is not limited, as long as it can control the corresponding two adjacent radiation units in the above-mentioned Switching between an electrically connected state and a non-electrically connected state does not depart from the scope of the present application.

The matching device is an inductor, for example, an inductor L1, an inductor L2, and an inductor L3. The inductor L1 is connected in series with the switch S1 in the gap 141 , the inductor L2 is connected in series with the switch S2 in the gap 142 , and the inductor L3 is connected in series with the switch S3 in the gap 143 . More specifically, taking the switch S1 and the inductor L1 as an example, one end of the switch S1 is connected to one end of the first main radiation unit 111 close to the gap 141, the other end of the switch S1 is connected to one end of the inductor L1, and the other end of the inductor L1 is connected to the radiation unit. 120 is close to the end of the gap 141. In other embodiments, the positions of the switch S1 and the inductor L1 can also be exchanged, as long as the switch and the inductor are connected in series between the corresponding two radiating elements and located in the corresponding gap, there will be no outside the scope of this application.

When the switch S1 is in the connected state, the main radiation unit 110 and the radiation unit 120 are in the connected state, and when the switch S1 is in the disconnected state, the main radiation unit 110 and the radiation unit 120 are in the disconnected state. The structures and principles of the switch S2 and the inductor L2, the switch S3 and the inductor L3 are similar, and will not be repeated here.

Further, as shown in FIG. 1 , the antenna may also include coupling stubs arranged one-to-one with the gaps, specifically as shown in the shaded part in FIG. 1 , including coupling stubs 171 corresponding to the gaps 141, and The coupling stub 172 corresponding to 142 and the coupling stub 173 corresponding to the gap 143, the opposite ends of any two adjacent radiation units can also be coupled through the corresponding coupling stub, specifically, for the coupling stub 171, when the main radiation unit 110 is connected to the feed source 200 , and the switch S1 between the main radiation unit 110 and the radiation unit 120 is in the off state, at this time, the main radiation unit 110 and the radiation unit 120 are coupled through the coupling branch 171 . As for the

coupling stubs

172 and 173 , their structure and principle are similar to those of the coupling stub 171 , and will not be repeated here.

Wherein, the shape of the coupling stub is not limited, and may be straight, arc, or other shapes. In this embodiment, the shape of the coupling stub is an arc extending along the circumferential direction of the annular radiator.

By setting the coupling branch, the coupling degree between the corresponding two adjacent radiation units can be significantly enhanced, especially when the two adjacent radiation units are in the disconnected state, the coupling degree between the two adjacent radiation units can be enhanced, The radiation intensity of the radiation unit is increased, so that the radiation intensity of the radiator in each radiation direction in the horizontal plane is more uniform.

Further, the coupling stubs are spaced apart from the annular radiator, and the two opposite ends of each coupling stub extend beyond the gap in the circumferential direction of the annular radiator. Taking the coupling stub 171 as an example, the two opposite ends of the coupling stub extend beyond the gap in the circumferential direction of the annular radiator. length, the coupling branch 171 can not only completely cover the gap 141 , but also cover a part of the main radiation unit 110 and a part of the radiation unit 120 . In this way, the coupling degree between any two adjacent radiating elements can be further improved. The structures of other coupling branches are similar and will not be repeated here.

In addition, in some schemes, when the annular radiator is a non-centrosymmetric structure, or the feeding port (that is, the slot 113) is not at the midpoint of the geometric structure of the radiation unit 110, the position of the coupling branch can also be adjusted, for example, multiple The two coupled stubs are adjusted to an asymmetric structure, and the radiation intensity is corrected.

Further, in this embodiment, along the axial direction of the annular radiator, each coupling branch is arranged on one side of the annular radiator. In other embodiments, different coupling branches can also be respectively arranged on two sides of the annular radiator. side.

Among them, along the direction perpendicular to the annular radiator, the more the overlapping part of the coupling branch and the adjacent radiation unit, the better the coupling degree between the corresponding radiation units, the coupling branch along the radial extension direction of the annular radiator The larger the length (or the width of the coupling branch), the better the coupling between the corresponding radiation units. Further, the shorter the distance between the coupling branch and the ring radiator along the direction perpendicular to the ring radiator , the better the coupling degree between the corresponding radiating elements.

In addition, it should be noted that the smaller the gap, the greater the coupling strength between the corresponding radiating elements. However, in the process of designing and processing the antenna, if the gap is designed too small, for example, less than 1mm, or less than 0.5mm , it will increase the processing difficulty of the annular radiator, and it is easy to produce large processing errors, which will have a large impact on the antenna. In this embodiment, the coupling through the corresponding coupling branches can not only ensure the radiation intensity between the radiation units , can also increase the allowable error of the antenna manufacturing process, and avoid the influence of the processing error of the gap on the antenna.

In the specific working process, when the switch S1, the switch S2, and the switch S3 are all in the off state, the radiation units are coupled through corresponding coupling branches, for example, the main radiation unit 110 and the radiation unit 120 are coupled through the coupling branch 171, The main radiation unit 110 and the radiation unit 130 are coupled through the coupling branch 173, and the radiation unit 120 and the radiation unit 130 are coupled through the coupling branch 172. At this time, the antenna is in the first state, that is, state 1, and the antenna in state 1 can be understood as A coupled loop antenna whose radiation pattern is a horizontal omnidirectional radiation pattern;

When the switch S1, the switch S2, and the switch S3 are all in the connected state, the main radiation unit 110 and the radiation unit 120, the main radiation unit 110 and the radiation unit 130, and the radiation unit 120 and the radiation unit 130 are all in an electrically connected state, and the antenna at this time In the second state, that is, state 2, the antenna in state 2 can be understood as a traditional loop antenna, and the radiation pattern generated by it is a Broadside radiation pattern (ie, an end-fire radiation pattern).

Please refer to Fig. 3, Fig. 3 is the structure diagram of the antenna of the embodiment of the present application, the structure of the antenna shown in Fig. 3 is basically the same as that of the antenna shown in Fig. L2 and inductor L3) and sub-switch units (such as switch S1, switch S2, and switch S3) are arranged outside the corresponding gaps. Specifically, taking inductor L1 and switch S1 as an example, one end of inductor L1 and switch S1 connected in series is connected to The main radiation unit 110 is near the gap 141 and located on the inner circumference of the ring radiator. The other end of the inductor L1 connected in series with the switch S1 is connected to the radiation unit 120 near the gap 141 and located on the inner circumference of the ring radiator. Of course, those skilled in the art can understand that the switch and inductor connected in series can be arranged on the inner peripheral side of the annular radiator or on the outer peripheral side of the annular radiator, which does not limit the protection scope of the present application. effect. It should be understood that the solutions in FIG. 3 and FIG. 1 can be combined, for example, some switches and inductors are arranged outside the corresponding gaps, and other switches and inductors are arranged inside the corresponding gaps.

Please refer to FIG. 4 to FIG. 5c. FIG. 4 is a schematic structural diagram of an antenna and an antenna carrying board in an electronic device according to an embodiment of the present application. Fig. 5a is a schematic perspective view of the three-dimensional structure of the antenna and the antenna carrying board in the electronic device according to the embodiment of the present application. Fig. 5b is a schematic diagram of the front structure of the antenna and the antenna carrying board in the electronic device according to the embodiment of the present application. FIG. 5c is a schematic diagram of the rear structure of the antenna and the antenna carrying board in the electronic device according to the embodiment of the present application.

As shown in FIG. 4 , the embodiment of the present application also provides an electronic device 300 , which includes an antenna carrying plate 310 and the antenna 100 involved in any of the above implementations, and the antenna 100 is disposed on the antenna carrying plate 310 . Specifically, as shown in Figures 5a to 5c, the antenna carrying plate 310 has a first surface 311, and a second surface 312 opposite to the first surface 311 (see Figure 5c), and the loop radiator is arranged on the antenna carrying plate 310 of the first surface 311 . Wherein the annular radiator of antenna 100 can adopt laser direct structuring process (LDS—Laser Direct Structuring) or FPC board to stick on the first surface 311, also can adopt etching process to be integrated on the first surface 311 of antenna carrier plate 310 It can also be a metal structure provided on the antenna supporting board 310 .

In this embodiment, as shown in FIG. 5 c , the coupling stub is disposed on the second surface 312 of the antenna supporting board 310 .

Specifically, the lengths of the coupling stubs 172 along the circumferential extension direction of the ring radiator are respectively greater than the lengths of the other coupling stubs (such as the coupling stub 171 and the coupling stub 173) along the circumferential extension direction of the ring radiator, which can improve the coupling ring mode The unbalanced magnetic field can then excite relatively pure coupled ring modes, making the electromagnetic field and current distribution of the antenna more uniform, and making antennas in different states (for example, all radiating elements are in an electrically connected state or between radiating elements are uniform) In the non-electrically connected state) the radiation patterns produced are more complementary.

More specifically, if an arc-shaped coupling branch is used, the angle formed by the coupling branch 172 along the circumferential extension direction of the annular radiator is 28°, and the angle formed by the coupling branch 171 along the circumferential extension direction of the annular radiator is 19°. The angle formed by 171 along the circumferential extension direction of the annular radiator is 19°. Of course, those skilled in the art can understand that, according to the actual working requirements of the antenna, the selection of the above angles can also be other angles.

Further, the antenna carrying board may be, for example, a PCB board or a dielectric board. If a dielectric board is used, the dielectric constant of the dielectric board is 2.65, and the thickness of the dielectric board is 1 mm.

In order to meet the design and use requirements of electronic equipment, this application provides a reference size matching parameter between the annular radiator and the antenna carrier plate. For example, the inner diameter R1 of the annular radiator can be 14mm, and the outer diameter R2 of the annular radiator can be The outer diameter of the antenna carrying plate 310 may be 22mm. Of course, those skilled in the art can understand that, in order to meet different usage and design requirements of electronic equipment, the above parameters can also be other values.

Further, please refer to FIG. 6, which is a schematic structural diagram of a router according to an embodiment of the present application. The electronic device involved in any of the foregoing implementation manners may be a router, and in other implementation manners, it may also be an electronic equipment such as a smart home or a smart watch.

The electronic equipment provided in this embodiment is simulated and analyzed by using the full-wave electromagnetic simulation software CST, and the effect curves shown in FIGS. 7 to 8 are obtained. Wherein, state 1 and state 2 described below can be understood with reference to the following: state 1 is a state in which all switches are in an off state, state 2 is a state in which all switches are in a connected state, and the antenna excitation loop antenna is twice wavelength mode.

The simulation effect of obtaining the graphs shown in Figures 7 to 8 is shown in Table 1 below (please understand in conjunction with Figure 1 and Figures 5a to 5b):

Table 1

参数parameter	数值value
环形辐射体的内径R1(mm)The inner diameter of the annular radiator R1 (mm)	1414
环形辐射体的外径R2(mm)The outer diameter of the annular radiator R2 (mm)	1818
天线承载板的外径R3(mm)The outer diameter of the antenna carrying plate R3 (mm)	22twenty two
间隙141的弧长所对应的圆心角α1(°)The central angle α1(°) corresponding to the arc length of the gap 141	1515
间隙142的弧长所对应的圆心角α2(°)The central angle α2 (°) corresponding to the arc length of the gap 142	1515
间隙143的弧长所对应的圆心角α2(°)The central angle α2 (°) corresponding to the arc length of the gap 143	1515
耦合枝节171沿环形辐射体周向延伸方向所呈角度(°)The angle formed by the coupling branch 171 along the circumferential extension direction of the annular radiator (°)	1919
耦合枝节172沿环形辐射体周向延伸方向所呈角度(°)The angle formed by the coupling branch 172 along the circumferential extension direction of the annular radiator (°)	2828

耦合枝节173沿环形辐射体周向延伸方向所呈角度(°)The angle formed by the coupling branch 173 along the circumferential extension direction of the annular radiator (°)	1919
电感L1的电感值(H)Inductance value of inductor L1 (H)	2.2e-92.2e-9
电感L2的电感值(H)Inductance value of inductor L2 (H)	2.2e-92.2e-9
电感L3的电感值(H)Inductance value of inductor L3 (H)	2.2e-92.2e-9
缝隙113沿环形辐射体周向延伸方向的长度L(mm)The length L (mm) of the slot 113 along the circumferential extension direction of the annular radiator	11
天线承载板的厚度(mm)The thickness of the antenna carrier board (mm)	11

Please refer to FIGS. 7 to 8. FIG. 7 is an effect curve diagram of the comparison of the S parameters of the antenna obtained when the antenna of the embodiment of the present application is tested in state 1 and state 2 respectively, and FIG. 8 is the effect curve of the embodiment of the present application An effect curve diagram of the comparison between the radiation efficiency of the antenna and the system efficiency (ie, efficiency) obtained when the antenna is tested in state 1 and state 2 respectively;

In FIG. 7 , the abscissa represents the frequency, the unit is GHz, and the ordinate represents the S11 amplitude value, the unit is dB. S11 is one of the S parameters. S11 represents the reflection coefficient. This parameter can represent the quality of the antenna’s emission efficiency. Specifically, the smaller the value of S11, the smaller the return loss of the antenna, and the smaller the energy reflected back by the antenna itself, that is, the energy that actually enters the antenna more and more.

It should be noted that in engineering, the S11 value of -6dB is generally used as the standard. When the S11 value of the antenna is less than -6dB, it can be considered that the antenna can work normally, or it can be considered that the transmission efficiency of the antenna is relatively good.

It can be seen from Figure 7 that in the frequency band of 2.4GHz to 2.5GHz, the S11 value of the antenna in state 1 is about -12dB to -10dB, which is less than -6dB, and the S11 value of the antenna in state 2 is about -9.2dB ~-8.9dB, which is also less than -6dB, and the resonant frequency of the antenna in state 1 and the antenna in state 2 is both 2.45GHz. Further, it can also be seen that in the working frequency range of 2.4GHz to 2.5GHz, The S11 parameter of the antenna in state 1 is better than the S11 parameter of the antenna in state 2.

In Figure 8, the abscissa represents the frequency, the unit is GHz, and the ordinate represents the radiation efficiency and system efficiency of the antenna. Among them, the radiation efficiency is a value to measure the radiation capability of the antenna, and the metal loss and dielectric loss are the influencing factors of the radiation efficiency. The system efficiency refers to the actual efficiency after the port matching of the antenna is considered, that is, the system efficiency of the antenna is the actual efficiency (ie, efficiency) of the antenna. Those skilled in the art can understand that the efficiency is generally represented by a percentage, and there is a corresponding conversion relationship between it and dB, and the closer the efficiency is to 0 dB, the better the efficiency of the antenna is.

It can be seen from Figure 8 that when the working frequency range is 2.4GHz to 2.5GHz, the radiation efficiency of the antenna in state 1 is -0.1dB to 0dB, the system efficiency is -0.7dB to -0.3dB, and the radiation efficiency of the antenna in state 2 is Radiation efficiency is -0.01dB ~ 0dB, system efficiency is -0.7dB ~ -0.6dB. It can be seen that when the working frequency range is 2.4GHz to 2.5GHz, the radiation efficiency of the antenna in state 2 is similar to that of the antenna in state 1, and the system efficiency of the antenna in state 1 is 0.3dB higher than that of the antenna in state 2.

Please refer to Figures 9a to 9c. Figures 9a, 9b and 9c are the antenna local current distribution diagram, antenna local electric field distribution diagram, and antenna local magnetic field obtained when the antenna of the embodiment of the present application is tested for simulation effects in state 1, respectively. Distribution.

In Fig. 9a, the arrow indicates the current direction on the loop radiator of the antenna. It can be seen from Fig. 9a that the antenna in state 1 can generate current from the positive pole position close to the feed source to the negative pole position close to the feed source. ring current. In Figure 9b, the darker the color, the stronger the electric field intensity. It can be seen from Figure 9b that the electric field intensity radiated by the radiating element near the feeding position is greater than that radiated by the radiating element far away from the feeding position . In Figure 9c, the darker the color, the stronger the strength of the magnetic field. It can be seen from FIG. 9c that, for the antenna in state 1, the intensity of the magnetic field radiated in all directions on the horizontal plane (that is, the plane parallel to the antenna bearing plate) is relatively uniform.

Please refer to Figures 10a to 10c. Figures 10a, 10b, and 10c are the antenna local current distribution diagram, antenna local electric field distribution diagram, and antenna local magnetic field obtained when the antenna of the embodiment of the present application is tested for simulation effects in state 2, respectively. Distribution.

In Fig. 10a, the arrow indicates the current direction on the antenna's annular radiator. It can be seen from Fig. 10a that the antenna in state 2 can generate the first current and the second current respectively flowing from the switch S1 to the switch S3, wherein , the first current flows through the upper half of the annular radiator, the second current flows through the lower half of the annular radiator, and the flow directions of the first current and the second current are opposite. In Figure 10b, the darker the color, the stronger the electric field strength. In this embodiment, the main radiation unit is on the upper part of the annular radiator. It can be seen from Fig. 10b that the electric field intensity of the left and right parts that are symmetrical about the centerline of the annular radiator (as shown by the dotted line in the figure) and far away from the centerline is relatively strong. , along the circumferential direction of the annular radiator, the electric field intensity is weaker near the centerline of the annular radiator. Wherein, the centerline of the above-mentioned annular radiator is the centerline passing through the midpoint of the slot 113 . In Figure 10c, the darker the color, the stronger the magnetic field intensity. It can be seen from Figure 10c that the antenna in state 2 has uneven magnetic field intensity radiated in all directions on the horizontal plane (that is, on a plane parallel to the antenna load plate). .

Please refer to Figures 11a to 11b. Figures 11a and 11b are three-dimensional diagrams of the antenna radiation direction obtained when the antenna of the embodiment of the present application is tested for simulation effects in state 1 and state 2 respectively. The operating frequency of the antenna is 2.45 GHz, where , the darker the color, the stronger the radiation intensity. It can be seen from Figure 11a that the antenna in state 1 produces stronger and more uniform radiation intensity on the horizontal plane (i.e., the XOY plane, the plane parallel to the antenna loading board), and the radiation intensity in the Z-axis direction (that is, the plane parallel to the antenna loading board) There are pits (that is, points with very low radiation intensity) on the vertical direction). It can be seen from FIG. 11b that the antenna in state 2 produces stronger radiation intensity in the direction of the Z axis, and weaker radiation intensity in the direction of the X axis.

Please refer to Figures 12a to 12c. Figures 12a to 12c are two-dimensional comparison diagrams of antenna radiation directions obtained when the antennas of the embodiments of the present application are tested for simulation effects in state 1 and state 2 respectively; wherein, Figure 12a is the XOZ plane Figure 12b is a two-dimensional comparison diagram of the radiation direction on the YOZ plane, and Figure 12c is a two-dimensional comparison diagram of the radiation direction on the XOY plane.

Please refer to Figure 12a, combined with Figure 11a and Figure 11b, the radiation intensity of the antenna in state 1 is stronger in the direction of the X axis, and the radiation intensity in the direction of the Z axis is weaker, and the radiation intensity of the antenna in state 2 is in the direction of the X axis The intensity of the radiation is weaker, and the radiation intensity in the Z-axis direction is stronger.

Please refer to FIG. 12b , combined with FIG. 11a and FIG. 11b , the radiation intensity of the antenna in state 1 is stronger in the direction of the Y axis, and the radiation intensity in the direction of the Z axis is weaker and less uniform. The radiation intensity of the antenna in state 2 is stronger and more uniform on the YOZ plane.

Please refer to FIG. 12c, and in combination with FIG. 11a and FIG. 11b, the radiation intensity of the antenna in state 1 on the XOY plane is relatively strong and uniform. The radiation intensity of the antenna in state 2 is weaker and less uniform on the X axis, and the radiation intensity on the Y axis is stronger but less uniform.

From the above comparative analysis, it can be seen that the antenna in state 1 can produce a horizontal omnidirectional radiation pattern, and the radiation intensity is relatively uniform. Broadside radiation pattern, and the radiation intensity on the Z axis is stronger. It can be seen that the application can make the antenna generate different and complementary radiation patterns in state 1 and state 2 respectively through the switch circuit, thereby improving the spatial coverage capability of the radiation direction of the antenna and laying the foundation for realizing the omnidirectional coverage of the radiation direction of the antenna.

Please refer to Figures 13a-13c, Figures 13a-13c are the antenna polarization direction vector diagrams obtained when the antenna of the embodiment of the present application is tested for simulation effects in state 1, wherein a spherical coordinate system is used for the simulation effect test. Among them, the darker the color, the stronger the electric field strength. The polarization of the antenna refers to the direction of the electric field intensity formed when the antenna radiates, and the direction of the electric field of the polarized electromagnetic wave is called the polarization direction.

Figure 13a is the omnidirectional vector diagram of the antenna polarization direction in state 1. It can be seen from Figure 13a that the pole is located in the direction of the Z axis, where the pole can be understood as the north pole in the spherical coordinate system, and Figure 13b is in state 1 The polarization component of the antenna on the angle Theta(θ) direction (the angle θ is located on the XOZ plane of the Cartesian coordinate system), that is to say, Figure 13b can characterize the polarization component of the antenna in state 1 on the XOZ plane , Figure 13c shows the antenna in state 1 at angle Phi

Direction (angle

The polarization component on the XOY plane of the Cartesian coordinate system), that is to say, Fig. 13c can characterize the polarization component of the antenna in state 1 on the XOY plane.

Among them, the angle Phi

It can also be understood as being located on a plane (that is, the XOY plane) perpendicular to the axis where the pole is located (here, the Z axis).

About Angle Theta(θ) and Angle Phi

Please refer to FIG. 14d and FIG. 14e , the following formulas can be used for conversion with the Cartesian coordinate system (x, y, z).

Among them, r can be understood as any point in the Cartesian coordinate system, and its distance to the origin of the Cartesian coordinate system is also represented by r.

It should be noted that since the current generated by the antenna of this embodiment is parallel to the horizontal plane (for details, it can be understood with reference to the above text and Fig. 9a and Fig. 10a), the antenna polarization mode of this embodiment is linear polarization, and the linear The polarization refers to the electromagnetic wave whose electric field vector has a fixed orientation in space. When the current direction of the radiation element of the antenna is parallel to the ground or perpendicular to the ground, the polarization of the antenna is linear polarization. It can be seen from Figure 13a and Figure 13c that the antenna in state 1 is at an angle

The polarization component in the direction (or it can be understood as the XOY plane) is basically consistent with the omnidirectional vector diagram of the antenna polarization direction. Therefore, the far-field principal component of the antenna electric field in state 1 is

The polarization components of the antenna are

(linear polarization). Since the direction of the magnetic field is perpendicular to the direction of the electric field, it can be concluded that the main component of the far field of the magnetic field is H _θ .

Please refer to Figs. 14a-14c. Figs. 14a-14c are the antenna polarization direction vector diagrams obtained when the antenna of the embodiment of the present application is tested for the simulation effect in state 2, wherein the spherical coordinate system is used for the simulation effect test.

Fig. 14a is an omnidirectional vector diagram of the antenna polarization direction in state 2. It can be seen from Fig. 14a that the pole is located in the X-axis direction. Figure 14b is the polarization component of the antenna in state 2 in the direction of angle Theta (θ) (the angle θ is located on the XOZ plane of the Cartesian coordinate system), and Figure 14c is the polarization component of the antenna in state 2 at angle Phi

Direction (angle

The polarization component on the YOZ plane of the Cartesian coordinate system).

It can be seen from Fig. 14a and Fig. 14c that the polarization component of the antenna in state 2 in the direction of angle Theta (θ) is basically consistent with the omnidirectional vector diagram of the antenna polarization direction. Therefore, the electric field far field of the antenna in state 2 is mainly The component is E _θ , and the polarization component of the antenna is E _θ (linear polarization). Since the direction of the magnetic field is perpendicular to the direction of the electric field, it can be concluded that the main component of the far field of the magnetic field is

Further, since the direction of the angle θ is consistent with the X axis, the polarization direction of the antenna is Ex linear polarization.

Among them, the angle Phi

It can also be understood as being located on a plane (ie, the YOZ plane) perpendicular to the axis where the pole is located (here, the X axis).

About Angle Theta(θ) and Angle Phi

Please refer to Figure 14d and Figure 14e, the following formulas can be used to convert with the Cartesian coordinate system (x, y, z):

Please refer to Fig. 15, Fig. 15 is a schematic structural diagram of the antenna of the embodiment of the present application, wherein the coupling branch is arranged on the inner peripheral side of the annular radiator, and the number of radiating units is three. The structure of the antenna 100A of the embodiment of the present application is basically the same as the structure of the antenna 100 provided by the embodiment of the present application, the difference is that the coupling stub (such as the coupling stub 171A, the coupling stub 172A, the coupling stub 173A) and the ring radiator (including the main radiation unit 110A, the radiation unit 120A and the radiation unit 130A) are arranged on the same plane and located on the inner or outer peripheral side of the annular radiator, or can be understood as: take the plane parallel to the axis of the annular radiator as the projection plane The projections of each coupling branch (for example, coupling branch 171A, coupling branch 172A, and coupling branch 173A) on the projection plane overlap at least partially with the projection of the annular radiator on the projection surface. Specifically, in this embodiment, the coupling branch is set at The inner peripheral side of the annular radiator.

Among them, along the direction parallel to the annular radiator, the more the overlapping part of the coupling branch and the adjacent radiation unit, the greater the coupling degree between the corresponding radiation units, the coupling branch along the radial extension direction of the annular radiator The greater the length (or it can be understood as the width of the coupling stub), the greater the coupling degree between the corresponding radiation units. Further, along the direction parallel to the ring radiator, the closer the distance between the coupling stub and the ring radiator is. The shorter the value, the greater the coupling degree between the corresponding radiating elements. In this embodiment, an exemplary size design selection is provided, as follows:

The inner diameter R1 of the annular radiator is 13mm, the outer diameter R2 of the annular radiator is 17mm, the inner diameter R4 of the coupling branch is 9mm, the outer diameter R5 of the coupling branch is 12mm, and the distance D from the outer peripheral edge of the coupling branch to the inner peripheral edge of the annular radiator is 1mm , the dimension W of the coupling stub along the radial direction of the annular radiator (or it can be understood as the width of the coupling stub) is 3mm.

In the specific working process, when the switch S1 _A , switch S2 _A , switch S2 _A , and switch S2 _A are all in the off state, the radiating units are coupled through the corresponding coupling branches, and the antenna at this time is in the first antenna state , that is, state 1, the antenna in state 1 can be understood as a coupled loop antenna, and the radiation pattern generated by it is a horizontal omnidirectional radiation pattern.

When the switch S1 _A , the switch S2 _A , and the switch S3 _A are all in the connected state, the main radiation unit 110A and the radiation unit 120A, the main radiation unit 110A and the radiation unit 130A, and the radiation unit 120A and the radiation unit 130A are all in an electrical connection state. The antenna at this time is in the second antenna state, that is, state 2. The antenna in state 2 can be understood as a traditional loop antenna, and the radiation pattern generated by it is a Broadside radiation pattern (ie, an end-fire radiation pattern).

Please refer to FIG. 16 . FIG. 16 is a schematic diagram of the front structure of the antenna and the antenna carrying board in the electronic device according to the embodiment of the present application.

As shown in FIG. 16 , the embodiment of the present application also provides an electronic device 300A, including an antenna carrying board 310A and the antenna 100A involved in each implementation manner of the above-mentioned embodiments, and the antenna 100A is disposed on the antenna carrying board 310A.

By setting the coupling branch on the inner or outer peripheral side of the annular radiator, when the annular radiator (such as the main radiation unit 110A, the radiation unit 120A, and the radiation unit 130A) is arranged on the antenna carrier board, any two radiation units The degree of coupling between them is only adjusted by the coupling branch and the radiation unit itself, and is decoupled from the thickness of the antenna carrier plate (that is, it has nothing to do with the thickness of the antenna carrier plate), thereby reducing the complexity of the design.

The electronic equipment provided in this embodiment is simulated and analyzed by using the full-wave electromagnetic simulation software CST, and the effect curves shown in FIGS. 17 to 18 are obtained. Wherein, state 1 and state 2 described below can be understood with reference to the following: state 1 is a state in which all switches are in an off state, state 2 is a state in which all switches are in a connected state, and the antenna excitation loop antenna is twice wavelength mode.

The simulation results obtained from the graphs shown in Figures 17 to 18 are shown in Table 2 below (please understand in conjunction with Figures 15 and 16):

Table 2

参数parameter	数值value
环形辐射体的内径R1(mm)The inner diameter of the annular radiator R1 (mm)	13mm13mm
环形辐射体的外径R2(mm)The outer diameter of the annular radiator R2 (mm)	17mm17mm

天线承载板的外径R3(mm)The outer diameter of the antenna carrying plate R3 (mm)	22mm22mm
耦合枝节内径R4(mm)Inner diameter of coupling branches R4(mm)	9mm9mm
耦合枝节外径R5(mm)Coupling stub outer diameter R5(mm)	12mm12mm
间隙141A的弧长所对应的圆心角α1 _A(°) The central angle α1 _A (°) corresponding to the arc length of the gap 141A	66
间隙142A的弧长所对应的圆心角α2 _A(°) The central angle α2 _A (°) corresponding to the arc length of the gap 142A	66
间隙143A的弧长所对应的圆心角α3 _A(°) The central angle α3 _A (°) corresponding to the arc length of the gap 143A	66
耦合枝节171A沿环形辐射体周向延伸方向所呈角度(°)The angle formed by the coupling branch 171A along the circumferential extension direction of the annular radiator (°)	9696
耦合枝节172A沿环形辐射体周向延伸方向所呈角度(°)The angle formed by the coupling branch 172A along the circumferential extension direction of the annular radiator (°)	9696
耦合枝节173A沿环形辐射体周向延伸方向所呈角度(°)The angle formed by the coupling branch 173A along the circumferential extension direction of the annular radiator (°)	9696
电感L1 _A的电感值(H) Inductance value of inductor L1 _A (H)	3.9e-93.9e-9
电感L2 _A的电感值(H) Inductance value of inductor L2 _A (H)	3.9e-93.9e-9
电感L3 _A的电感值(H) Inductance value of inductor L3 _A (H)	3.9e-93.9e-9
缝隙113A沿环形辐射体周向延伸方向的长度L(mm)The length L (mm) of the slot 113A along the circumferential extension direction of the annular radiator	11

Please refer to Figures 17 to 18. Figure 17 is an effect curve diagram of the comparison of the S parameters of the antenna obtained when the antenna of the embodiment of the application is tested in state 1 and state 2 respectively; Figure 18 is the effect curve of the embodiment of the application An effect curve diagram comparing the radiation efficiency of the antenna and the system efficiency (that is, efficiency) obtained when the antenna is subjected to the simulation effect test in state 1 and state 2 respectively.

It can be seen from Figure 17 that in the 2.4GHz to 2.5GHz frequency band, the S11 value of the antenna in state 1 is about -9.8dB to -8.9dB, and the S11 value of the antenna in state 2 is about -11dB to -9.91 dB, and the resonant frequencies of the antenna in state 1 and the antenna in state 2 are both 2.45GHz. It can also be seen that in the working frequency range of 2.4GHz to 2.5GHz, the S11 parameters of the antenna in state 2 are better than those in state 2. 1 for the S11 parameters of the antenna.

It can be seen from Figure 18 that when the working frequency range is 2.4GHz to 2.5GHz, the radiation efficiency of the antenna in state 1 is about -0.1dB to -0dB, the system efficiency is about -1dB to -0.8dB, and the antenna in state 2 The radiation efficiency of the antenna is about -0.1dB to -0.09dB, and the system efficiency is about -0.6dB to -0.5dB. It can be seen that when the working frequency range is 2.4GHz to 2.5GHz, the radiation efficiency of the antenna in state 2 is similar to that of the antenna in state 1, and the system efficiency of the antenna in state 2 is 0.4dB higher than that of the antenna in state 1.

Please refer to Figures 19a to 19c. Figures 19a, 19b and 19c are the antenna local current distribution diagram, antenna local electric field distribution diagram, and antenna local magnetic field obtained when the antenna of the embodiment of the present application is tested for simulation effects in state 1, respectively. Distribution.

It can be seen from Fig. 19a that the antenna in state 1 can generate a uniform and same-direction circular current flowing from a position close to the positive pole of the feed source to a position close to the negative pole of the feed source. It can be seen from Fig. 19b that the electric field intensity radiated by the radiating element close to the feeding position is larger than that radiated by the radiating element far away from the feeding position. It can be seen from FIG. 19c that, for the antenna in state 1, the intensity of the magnetic field radiated in all directions on the horizontal plane (that is, the plane parallel to the antenna bearing plate) is relatively uniform.

Moreover, comparing Figures 19a to 19c with Figures 9a to 9c in the embodiment of the present application, it is not difficult to see that compared with the antenna structure in Figure 1, the coupled ring mode excited by the antenna structure in Figure 15 (that is, in The antenna in state 1) is more pure, its electromagnetic field and current distribution are more uniform, and the radiation pattern of the antenna in state 1 is more complementary to the radiation pattern in state 2.

Please refer to Figures 20a to 20c. Figures 20a, 20b, and 20c are the antenna local current distribution diagram, antenna local electric field distribution diagram, and antenna local magnetic field obtained when the antenna of the embodiment of the application is tested for simulation effects in state 2, respectively. Distribution. It is similar to the antenna local current distribution diagram, the antenna local electric field distribution diagram, and the antenna local magnetic field distribution diagram of the antenna structure in FIG. 1 , and will not be repeated here.

Please refer to Figures 21a to 21b. Figures 21a and 21b are the three-dimensional diagrams of the radiation direction of the antenna obtained when the antenna of the embodiment of the present application is tested for the simulation effect in state 1 and state 2 respectively, which is the same as the radiation direction of the antenna structure in Figure 1 The three-dimensional diagram is similar, and will not be repeated here.

Please refer to Figure 22a-Figure 22c, Figure 22a-Figure 22c is a two-dimensional comparison diagram of the antenna radiation direction obtained when the antenna of the embodiment of the application is tested in state 1 and state 2 respectively; it is different from the structure of the antenna in Figure 1 The two-dimensional comparison diagram of the radiation direction is similar and will not be repeated here.

Please refer to Figures 23a to 24c, Figures 23a to 23c are the antenna polarization direction vector diagrams obtained when the antenna of the embodiment of the present application is tested for the simulation effect in state 1, and Figures 24a to 24c are the antennas of the embodiment of the present application The antenna polarization direction vector diagram obtained during the simulation effect test in state 2, where the spherical coordinate system is used for the simulation effect test. It is similar to the antenna polarization direction vector diagram of the antenna structure in FIG. 1 , and will not be repeated here.

Please refer to FIG. 25a, which is a schematic structural diagram of an antenna according to an embodiment of the present application, wherein the number of radiation elements is four. The structure of the antenna 100B in the embodiment of the present application is basically the same as that of the antenna 100 provided in the embodiment. The difference is that the number of radiation elements is four, correspondingly, the number of switches is four, and the number of inductors for 4.

Specifically, the four switches include switches S1 _B , S2 _B , S3 _B and S4 _B distributed clockwise along the circumference of the annular radiator, and inductors L1 _B , L2 _B , L3 _B and L4 _B .

Among them, the switch S1 _B is set in the gap 141B between the main radiation unit 110B and the radiation unit 120B, the switch S2 _B is set in the gap 142B between the main radiation unit 110B and the radiation unit 130B, and the switch S3 _B is set in the radiation unit 130B In the gap 143B between the radiation unit 140B, the switch _S4B is disposed in the gap 144B between the radiation unit 140B and the radiation unit 120B. The inductance L1 _B and the switch S1 _B connected in series, one end is connected to the end of the first main radiating unit 111B close to the gap 141B, the other end is connected to the end of the radiating unit 120B close to the gap 141B, the inductance L2 _B and the switch S2 _B connected in series, one end Connected to one end of the second main radiation unit 112B close to the gap 142B, the other end is connected to one end of the radiation unit 130B close to the gap 142B, the inductance L3 _B and the switch S3 _B connected in series, one end connected to the end of the radiation unit 130B close to the gap 143B, and the other One end is connected to the end of the radiating unit 140B close to the gap 143B, the inductance L4 _B and the switch S4 _B connected in series, one end is connected to the end of the radiating unit 140B close to the gap 144B, and the other end is connected to the end of the radiating unit 120B close to the gap 144B. Of course, those skilled in the art can understand that the positions of the inductor and the switch can be exchanged, which does not limit the protection scope of the present application.

Please refer to Figures 25b to 25e, Figure 25b is a schematic diagram of the current flow in the antenna state 1 of the embodiment of the present application, Figure 25c is a schematic diagram of the current flow in the antenna state 2 of the embodiment of the present application, and Figure 25d is a schematic diagram of the current flow in the embodiment of the application A schematic diagram of the current flow in the antenna state 3, and FIG. 25e is a schematic diagram of the current flow in the antenna state 4 of the embodiment of the present application.

State 1 is: the main radiation unit 110B is connected to the feed source 200B, and the switches S1 _B , S2 _B , S3 _B , and S4 _B are all in the off state. At this time, the annular radiator can generate uniform and The circular current in the same direction, in this embodiment, as shown in FIG. 25b, the circular current _I0 flows from a position close to the positive pole of the feed source 200 through the entire circular radiator and then flows into a position close to the negative pole of the feed source 200B.

State 2 is: the main radiation unit 110B is connected to the feed source 200B, and the switches S1 _B , S2 _B , S3 _B , and S4 _B are all connected, as shown in Figure 25c, the first current I ₁ flows counterclockwise through the loop In the upper half of the radiator, the second current I ₂ flows clockwise through the lower half of the annular radiator.

State 3 is: the main radiating unit 110B is connected to the feed source 200B, and the switch S1 _B and the switch S3 _B are in the connected state, and the switch S2 _B and the switch S4 _B are in the disconnected state. The first current I ₁ flowing counterclockwise from S4 _B to the switch S2 _B and the second current I ₂ flowing clockwise from the switch S4 _B to the switch S2 _B.

State 4 is: the main radiation unit 110B is connected to the feed source 200B, and the switch _S2B and switch _S4B are in the connected state, and the switch _S1B and switch _S3B are in the disconnected state, as shown in Figure 25e. At this time, the ring radiator generates The first current I ₁ flows counterclockwise from the switch S1 _B to the switch S3 _B , and the second current I ₂ flows clockwise from the switch S1 _B to the switch S3 _B.

The antenna provided in this embodiment can make the antenna in different antenna states by controlling the switching between the connected state and the disconnected state of each switch. For example, when all the switches are in the disconnected state (that is, state 1), the antenna can understand It is a coupled loop antenna. When the switches are all in the connected state (that is, state 2), the antenna can be understood as a double wavelength mode of the traditional loop antenna. When the switch S1 _B and the switch S3 _B are in the connected state and the switch S2 _B and the switch S4 _B In the off state (that is, state 3), the radiation pattern of the antenna rotates 45° counterclockwise along the horizontal plane, forming a boundary condition of one wavelength mode of 45° counterclockwise in the horizontal plane. When the switch S2 _B is connected to the switch S4 _B state and the switch S1 _B and switch S3 _B are in the off state (that is, state 4), the radiation pattern of the antenna rotates 45° clockwise along the horizontal plane, forming a boundary condition of one wavelength mode with a clockwise rotation of 45° in the horizontal plane, and the radiation For the rotation of the direction diagram, please refer to the description of the simulation analysis later.

Of course, those skilled in the art can understand that in the embodiment of 4 switches, up to 16 (2 ⁴ ) states can be combined to generate current directions different from the above, which is not the scope of protection of the present application. have a limiting effect.

Please refer to FIG. 25 a to FIG. 26 , this embodiment also provides an electronic device 300B, which includes an antenna carrying board 310B and the antenna 100B involved in any one of the foregoing implementation manners. The antenna 100B is disposed on the antenna supporting board 310B.

Further, in order to better adjust the impedance of the antenna under different state lines, the electronic device provided in this embodiment also includes an anti-symmetrical feeding network, which is used to realize anti-symmetrical feeding, including: a first micro The strip line 321B and the second microstrip line 322B, the first main radiation unit 111B is connected to the negative pole of the feed source 200B through the first microstrip line 321B, and the second main radiation unit 112B is connected to the feed source 200B through the second microstrip line 322B Of course, those skilled in the art can understand that the positions of the first microstrip line 321B and the second microstrip line 322B can be exchanged, which does not limit the protection scope of the present application.

Further, the electronic device provided in this embodiment further includes an adjustable capacitor C, which is connected between the feed source 200B and the main radiation unit 110B, and can adjust the input impedance of the antenna in different states by adjusting the parameters of the capacitor. Specifically, the adjustable capacitor C is disposed on the microstrip line 322B. The specific parameter selection of the capacitor can be selected according to the actual use requirements of the antenna. This embodiment provides a reference parameter selection, as follows:

When the antenna is in state 1, the parameter selection of the capacitor can be 0.75pF, and when the antenna is in state 2, state 3, and state 4, the parameter selection of the capacitor can be 2.7pF. Please refer to the previous section for details about the state 1, state 2, state 3, and state 4 of the antenna.

Specifically, as shown in Figures 27a to 27c, the antenna carrying plate 310B has a first surface 311B, and a second surface 312B opposite to the first surface 311B (see Figure 27c), and the loop radiator is arranged on the antenna carrying plate The first surface 311B of 310B. In this embodiment, as shown in FIG. 27 c , the coupling stub is disposed on the second surface 312B of the antenna supporting board 310B.

Specifically, in this embodiment, an example of the size design and selection of the coupling branch is provided, as follows:

The coupling branch 171B, the coupling branch 172B, the coupling branch 173B, and the coupling branch 174B form an angle of 30° along the circumferential extension direction of the annular radiator.

The antenna provided in this embodiment can be switched between the connected state and the disconnected state through a plurality of switches, so that the antenna can switch between at least four antenna states and generate at least four different radiation patterns, and the four The radiation pattern has good complementarity, which greatly improves the radiation space coverage capability of the antenna.

The electronic equipment provided in this embodiment is simulated and analyzed by using the full-wave electromagnetic simulation software CST, and the effect curves shown in FIGS. 28 to 29 are obtained.

The simulation results obtained from the graphs shown in Figures 28 to 29 are shown in Table 3 below (please understand in conjunction with Figure 25a and Figure 26):

table 3

Please refer to FIGS. 28 to 29. FIG. 28 is an effect curve diagram of the comparison of the S parameters of the antenna obtained when the antenna of the embodiment of the present application is tested in state 1, state 2, state 3, and state 4 respectively. For the antenna of the embodiment of the present application, the radiation efficiency of the antenna obtained when the simulation effect test is performed under state 1, state 2, state 3, and state 4, and the effect curve of the system efficiency (ie efficiency) contrast; wherein, state 1 is All the sub-switch units are in the off state, that is, the switches S1 _B , S2 _B , switch S3 _B and switch S4 _B in the antenna are all in the off state, and the state 2 is that all the sub-switch units are connected The state of the state, that is: the switch S1 _B , the switch S2 _B , the switch S3 _B and the switch S4 _B in the antenna are all in the connection state, and the antenna excites the double wavelength mode of the loop antenna, and the state 3 is the antenna switch S1 _B and the switch S3 _B is in the connected state and switch S2 _B and switch S4 _B are in the disconnected state, and state 4 is the state in which switch S2 _B and switch S4 _B are in the connected state and switch S1 _B and switch S3 _B are in the disconnected state.

It can be seen from Figure 28 that in the 2.4GHz to 2.5GHz frequency band, the S11 value of the antenna in state 1 is about -12dB to --5dB, and the S11 value of the antenna in state 2 is about -18dB to -12.8dB , the S11 value of the antenna in state 3 is about -9dB~--6.5dB, and the S11 value of the antenna in state 4 is about --9dB~--6.5dB. Moreover, it can also be seen that within the working frequency band of 2.4GHz to 2.5GHz, the S11 parameters of the antenna in state 2 are better than those of the antenna in state 1, and the S11 parameters of the antenna in state 1 are better than those in state 3 The S11 parameters of the antenna in state 3 are the same as the S11 parameters of the antenna in state 4.

It can be seen from Figure 29 that when the working frequency range is 2.4GHz to 2.5GHz, the radiation efficiency of the antenna in state 1 is about -0.1dB to -0dB, the system efficiency is about -2.4dB to -0.2dB, and the antenna in state 2 The radiation efficiency of the antenna tends to 0, the system efficiency is about -0.5dB ~ -0dB, the radiation efficiency of the antenna in state 3 tends to 0, the system efficiency is about -1.5dB ~ -0.4dB, the antenna in state 1 The radiation efficiency tends to 0, and the system efficiency is -1.5dB～-0.4dB.

It can be seen that when the working frequency range is 2.4GHz to 2.5GHz, the radiation efficiencies of the antennas in state 1, state 2, state 3, and state 4 are basically the same, and the system efficiency of the antenna in state 2 is the best. The system efficiency of the antenna in state 1 is increased by 1.9 dB, and the system efficiency of the antenna in state 1 is better than that of the antennas in state 3 and state 4.

Please refer to Fig. 30a to Fig. 30c. Fig. 30a, Fig. 30b and Fig. 30c are respectively the antenna local current distribution diagram, the antenna local electric field distribution diagram and the antenna local magnetic field obtained when the antenna of the embodiment of the present application performs the simulation effect test in state 1 Distribution.

It can be seen from Fig. 30a that the antenna in state 1 can generate a uniform and same-direction circular current flowing from a position close to the positive pole of the feed source to a position close to the negative pole of the feed source. It can be seen from Fig. 30b that the electric field intensity radiated by the radiating elements close to the feeding position is greater than the electric field intensity radiated by the radiating elements far away from the feeding position. It can be seen from Fig. 30c that, for the antenna in state 1, the intensity of the magnetic field radiated in all directions on the horizontal plane (that is, the plane parallel to the antenna bearing plate) is relatively uniform.

Please refer to Figures 31a to 31c. Figures 31a, 31b, and 31c are the antenna local current distribution diagram, antenna local electric field distribution diagram, and antenna local magnetic field obtained when the antenna of the embodiment of the present application is tested for simulation effects in state 2, respectively. Distribution.

It can be seen from Figure 31a that the antenna in state 2 can generate the first current and the second current, wherein, along the direction perpendicular to the radiator, the first current flows counterclockwise through the upper half of the annular radiator, and the second The second current flows clockwise through the lower half of the annular radiator. In this embodiment, the main radiation unit is on the upper part of the annular radiator. It can be seen from Fig. 31b that the electric field intensity of the left and right parts that are symmetrical about the centerline of the annular radiator (as shown by the dotted line in the figure) and far away from the centerline is relatively strong. , along the circumferential direction of the annular radiator, the electric field intensity is weaker near the centerline of the annular radiator. Wherein, the centerline of the above-mentioned annular radiator is the centerline passing through the midpoint of the slot 113 . It can be seen from Fig. 31c that, for the antenna in state 2, the intensity of the magnetic field radiated in all directions on the horizontal plane (ie, on the plane parallel to the antenna bearing plate) is uneven.

Please refer to Fig. 32a to Fig. 32c. Fig. 32a, Fig. 32b, and Fig. 32c are the antenna local current distribution diagram, antenna local electric field distribution diagram, and antenna local magnetic field obtained when the antenna of the embodiment of the present application performs the simulation effect test in state 3 respectively. Distribution.

It can be seen from FIG. 32 a that the antenna in state 3 can generate a first current flowing counterclockwise from switch S2 _B to switch S4 _B and a second current flowing clockwise from switch S2 _B to switch S4 _B. It can be seen from Fig. 32b that the electric field intensity radiated by the radiating element far away from the feeding position is smaller than that radiated by the radiating element close to the feeding position, and the area with the strongest electric field intensity is concentrated near the switch S2 _B . It can be seen from Fig. 32c that, for the antenna in state 3, the magnetic field intensity radiated in all directions on the horizontal plane (that is, the plane parallel to the antenna carrier plate) is uneven, and the area with the strongest magnetic field intensity is concentrated near the switch _S4B .

In Fig. 33a, it can be seen from Fig. 33a that the antenna in state 4 can generate a first current I 1B flowing counterclockwise from switch S1 _B to switch S3 _B and a second current I _1B flowing clockwise from switch S1 _B to switch S3 _B. current I _2B . It can be seen from Figure 33b that the electric field intensity radiated by the radiating element far away from the feeding position is smaller than that radiated by the radiating element close to the feeding position, and the area with the strongest electric field intensity is concentrated near the switch S1 _B , it can be seen from Fig. 33c that the antenna in state 4 has uneven magnetic field intensity radiated in all directions on the horizontal plane (that is, the plane parallel to the antenna bearing plate), and the area with the strongest magnetic field intensity is concentrated near the switch S4 _B .

Please refer to Figure 34a to Figure 34d, Figure 34a, Figure 34b, Figure 34c, and Figure 34d are the antenna radiation directions obtained when the antenna of the embodiment of the present application is tested for the simulation effect in State 1, State 2, State 3, and State 4 respectively From the three-dimensional diagram, it can be seen from Figure 34a that the antenna in state 1 produces stronger and more uniform radiation intensity on the horizontal plane (that is, the XOY plane, the plane parallel to the antenna bearing plate), and in the Z-axis direction (that is, the There are concave points (that is, points with very low radiation intensity) on the vertical direction of the antenna supporting board). It can be seen from FIG. 34b that the antenna in state 2 produces stronger radiation intensity in the direction of the Z axis, and weaker radiation intensity in the direction of the X axis.

It can be seen from Figure 34c that the antenna in state 3 produces stronger radiation intensity in the direction that rotates the Y axis by 45° counterclockwise, and weaker radiation intensity in the direction perpendicular to this direction.

It can be seen from Figure 34d that the antenna in state 4 produces stronger radiation intensity in the direction that rotates the Y axis by 45° clockwise, and weaker radiation intensity in the direction perpendicular to this direction.

It can be seen that the antenna provided by this embodiment can make the antenna be in different antenna states by controlling the switching between the connected state and the disconnected state of each switch. For example, when all the switches are in the disconnected state (that is, state 1), the antenna It can be understood as a coupled loop antenna. When all the switches are in the connected state (that is, state 2), the antenna can be understood as a double wavelength mode of the traditional loop antenna. When the switch S1 _B and the switch S3 _B are in the connected state and the switch S2 _B and the switch When S4 _B is in the off state (that is, state 3), the radiation pattern of the antenna rotates 45° counterclockwise along the horizontal plane, forming a boundary condition of a double wavelength mode that rotates 45° counterclockwise in the horizontal plane. When the switch S2 _B and the switch S4 _B In the connected state and the switch S1 _B and the switch S3 _B are in the disconnected state (that is, state 4), the radiation pattern of the antenna rotates 45° clockwise along the horizontal plane, forming the boundary condition of the double-wavelength mode that the horizontal plane rotates 45° clockwise .

Please refer to Fig. 35a-Fig. 35c. Fig. 35a-Fig. 35c are the two-dimensional comparison diagrams of antenna radiation directions obtained when the antenna of the embodiment of the present application is tested in state 1 and state 2 respectively; among them, Fig. 35a is the XOZ plane Figure 35b is a two-dimensional comparison diagram of the radiation direction on the YOZ plane, and Figure 35c is a two-dimensional comparison diagram of the radiation direction on the XOY plane.

Please refer to Figure 35a, combined with Figure 34a and Figure 34b, the radiation intensity of the antenna in state 1 is stronger in the X-axis direction, and the radiation intensity in the Z-axis direction is weaker, and the radiation intensity of the antenna in state 2 is in the X-axis direction The intensity of the radiation is weaker, and the radiation intensity in the Z-axis direction is stronger.

Please refer to FIG. 35b , combined with FIG. 34a and FIG. 34b , the radiation intensity of the antenna in state 1 is stronger in the direction of the Y axis, and the radiation intensity in the direction of the Z axis is weaker and less uniform. The radiation intensity of the antenna in state 2 is stronger and more uniform on the YOZ plane.

Please refer to FIG. 35c, and combine FIG. 34a and FIG. 34b, the radiation intensity of the antenna in state 1 on the XOY plane is relatively strong and uniform. The radiation intensity of the antenna in state 2 is weaker and less uniform on the X axis, and the radiation intensity on the Y axis is stronger but less uniform.

From the above comparative analysis, it can be seen that in this embodiment, the antenna in state 1 can generate a horizontal omnidirectional radiation pattern, and the radiation intensity is relatively uniform. The antenna of 2 can produce Broadside radiation pattern, and the radiation intensity on the Z axis is strong. The antenna in state 3 can generate a Broadside radiation pattern, and the radiation intensity generated in the direction of 45° counterclockwise on the Y axis is the strongest, and the antenna in state 4 can generate a Broadside radiation pattern, and rotate clockwise on the Y axis The radiation intensity generated in the direction of 45° is the strongest. It can be seen that the present application can make the antenna generate different and complementary radiation patterns in state 1, state 2, state 3, and state 4 through the switch circuit, thereby improving the spatial coverage of the radiation direction of the antenna, in order to realize the radiation direction of the antenna Omni-directional coverage lays the groundwork.

Please refer to Figs. 36a to 36c. Figs. 36a to 36c are antenna polarization direction vector diagrams obtained when the antenna of the embodiment of the present application is tested for simulation effects in state 1, where a spherical coordinate system is used for the simulation effect test.

Figure 36a is the omnidirectional vector diagram of the antenna polarization direction in state 1. It can be seen from Figure 36a that the pole is located in the Z-axis direction, and Figure 36b is the angle Theta(θ) direction of the antenna in state 1 (the angle θ is located in the The polarization component on the XOZ plane of the Karl coordinate system), Fig. 36c shows the antenna in state 1 at angle Phi

Direction (angle

The polarization component on the XOY plane of the Cartesian coordinate system). It can be seen from Figure 36a and Figure 36c that the antenna in state 1 is at an angle

The polarization components of the antenna are

(linear polarization). Since the direction of the magnetic field is perpendicular to the direction of the electric field, it can be concluded that the main component of the far field of the magnetic field is H _θ . Among them, about angle θ, angle

It can be understood with reference to the angle description in State 1 of the previous embodiment.

Please refer to Figures 37a to 37c. Figures 37a to 37c are the antenna polarization direction vector diagrams obtained when the antenna of the embodiment of the present application is tested for simulation effects in state 2, wherein the spherical coordinate system is used for the simulation effect test;

Fig. 37a is the omnidirectional vector diagram of the antenna polarization direction in state 2. It can be seen from Fig. 37a that the pole is located in the direction of the X axis. Figure 37b is the polarization component of the antenna in state 2 at the angle Theta (θ) direction (the angle θ is located on the XOZ plane of the Cartesian coordinate system), and Figure 37c is the polarization component of the antenna in state 2 at the angle Phi

Direction (angle

It can be seen from Fig. 37a and Fig. 37c that the polarization component of the antenna in state 2 in the direction of angle Theta (θ) is basically consistent with the omnidirectional vector diagram of the antenna polarization direction. Therefore, the electric field far field of the antenna in state 2 is mainly The component is E _θ , and the polarization component of the antenna is E _θ (linear polarization). Since the direction of the magnetic field is perpendicular to the direction of the electric field, it can be concluded that the main component of the far field of the magnetic field is

Since the Theta (θ) direction is consistent with the X axis, the polarization direction of the antenna is the Ex line polarization.

Among them, about angle θ, angle

It can be understood with reference to the angle description in State 2 of the previous embodiment.

Please refer to Figures 38a to 38c. Figures 38a to 38c are the antenna polarization direction vector diagrams obtained when the antenna of the embodiment of the present application is tested for the simulation effect in state 3, wherein the spherical coordinate system is used for the simulation effect test;

Fig. 38a is the omnidirectional vector diagram of the antenna polarization direction in state 3. It can be seen from Fig. 38a that the pole is located in the direction of 45° clockwise rotation of the X axis. Figure 38b is the polarization component of the antenna in state 3 in the direction of angle Theta (θ) (the angle θ is located on the plane that rotates the XOZ plane of the Cartesian coordinate system 45° clockwise around the Z axis), and Figure 38c is in state 3 Antenna at angle Phi

Direction (angle

From Figure 38a and Figure 38c, it can be seen that the polarization component of the antenna in state 3 in the direction of angle Theta (θ) is basically consistent with the omnidirectional vector diagram of the antenna polarization direction, therefore, the electric field of the antenna in state 3 is dominated by the far field The component is E _θ , and the polarization component of the antenna is E _θ (linear polarization). Since the direction of the magnetic field is perpendicular to the direction of the electric field, it can be concluded that the main component of the far field of the magnetic field is

Since the direction of Theta (θ) is consistent with the direction in which the X axis rotates 45° clockwise, the main polarization direction of the antenna is +45° linear polarization.

Among them, about angle θ, angle

Fig. 39a is the omnidirectional vector diagram of the antenna polarization direction in state 4. It can be seen from Fig. 39a that the pole is located in the direction where the X axis rotates 45° counterclockwise. Figure 39b is the polarization component of the antenna in state 4 at the angle Theta(θ) (the angle Theta(θ) is located on the plane that rotates the XOZ plane of the Cartesian coordinate system by 45° counterclockwise around the Z axis), and Figure 39c is the polarization component in the Antenna in state 3 at angle Phi

Direction (angle

It can be seen from Fig. 39a and Fig. 39c that the polarization component of the antenna in state 4 in the direction of angle Theta (θ) is basically consistent with the omnidirectional vector diagram of the antenna polarization direction. Therefore, the electric field far field of the antenna in state 4 is mainly The component is E _θ , and the polarization component of the antenna is E _θ (linear polarization). Since the direction of the magnetic field is perpendicular to the direction of the electric field, it can be concluded that the main component of the far field of the magnetic field is

Since the direction of Theta (θ) is consistent with the direction in which the X axis rotates 45° counterclockwise, the main polarization direction of the antenna is -45° linear polarization.

Among them, about angle θ, angle

Obviously, those skilled in the art can make various changes and modifications to the application without departing from the spirit and scope of the application. In this way, if these modifications and variations of the present application fall within the scope of the claims of the present application and their equivalent technologies, the present application is also intended to include these modifications and variations.

Claims

An antenna, characterized in that the antenna comprises:

The annular radiator, the annular radiator includes a plurality of radiation units, and there is a gap between the opposite ends of any two adjacent radiation units, wherein:

The plurality of radiating units includes a main radiating unit;

The main radiating unit is provided with a gap at the middle position, and the slit divides the main radiating unit into a first main radiating unit and a second main radiating unit arranged end-to-end at intervals; the first main radiating unit The end opposite to the second main radiating unit is fed in an anti-symmetrical feeding manner; and

a switch circuit, the switch circuit is used to control the electrical connection state of a first radiating unit pair among the plurality of radiating units, the first radiating unit pair includes adjacent first radiating units and second radiating units, the The gap between the first radiation unit and the second radiation unit is a first gap.
The antenna according to claim 1, characterized in that,

The switch circuit includes a first sub-switch unit connected between the first radiating unit and the second radiating unit of the first radiating unit pair, and the first sub-switching unit has a connection state and a disconnection state. status, where

When the first sub-switch unit is in the connected state, the first radiating unit and the second radiating unit of the first radiating unit pair are electrically connected through the first sub-switching unit;

When the first sub-switch unit is in the off state, the first radiating unit and the second radiating unit of the first radiating unit pair are coupled through the first gap.
The antenna according to claim 2, characterized in that, the operating frequency band of the antenna when the first sub-switch unit is in the off state, and the antenna is in the operating frequency band when the first sub-switch unit is in the The working frequency band in the connected state, including the same frequency band.
The antenna according to claim 3, wherein the antenna further comprises a first matching device, the first matching device is connected in series with the first sub-switch unit, and the first sub-switch unit is connected to the The first matching device is connected between opposite ends of the first radiating element and the second radiating element of the first radiating element pair.
The antenna according to any one of claims 1-4, wherein the antenna further comprises a first coupling stub arranged corresponding to the first gap;

Opposite ends of the first radiating element and the second radiating element of the first radiating element pair are coupled through the first coupling stub.
The antenna according to claim 5, wherein the first coupling stub is spaced apart from the annular radiator, and the length of the first coupling stub extending in the circumferential direction of the annular radiator exceeds the The length of the first gap extending in the circumferential direction of the annular radiator.
The antenna according to claim 5 or 6, characterized in that, the first coupling branch is spaced apart from the annular radiator in the axial direction of the annular radiator, or the first coupling branch is located at The inner peripheral side or the outer peripheral side of the annular radiator is arranged at a distance from the annular radiator.
The antenna according to any one of claims 1-7, wherein the switching circuit comprises a plurality of sub-switching units, the plurality of radiating units comprises a plurality of radiating unit pairs, and the plurality of radiating unit pairs Each radiation unit pair includes two adjacent radiation units, the plurality of sub-switch units correspond to the plurality of radiation unit pairs, and each sub-switch unit in the plurality of sub-switch units is used to control the corresponding The electrical connection status of two adjacent radiating elements in a radiating element pair.
The antenna according to claim 8, wherein the antenna comprises a plurality of coupling stubs; the plurality of coupling stubs are in one-to-one correspondence with the plurality of radiating element pairs, and the adjacent two of each radiating element pair The opposite ends of the radiation units are coupled through the corresponding one of the coupling stubs when the corresponding sub-switch unit is in the off state.
The antenna according to claim 8 or 9, wherein the antenna includes a plurality of matching devices; the plurality of matching devices correspond to the plurality of sub-switch units one by one, and each of the plurality of matching devices Each matching device is connected in series with a corresponding sub-switch unit, and each matching device and its sub-switch unit connected in series are connected between two adjacent radiating units in the corresponding radiating unit pair.
The antenna according to any one of claims 8-10, characterized in that,

When the plurality of sub-switch units are all in an off state, the annular radiator generates an annular current flowing through each radiation unit of the plurality of radiation units;

When the plurality of sub-switch units are all in a connected state, the annular radiator generates a first current and a second current, and the first current and the second current flow in opposite directions.
The antenna according to any one of claims 1-11, wherein the first main radiation unit and the second main radiation unit are symmetrical about the slot.
The antenna according to any one of claims 1-12, characterized in that, the ring radiator adopts a centrosymmetric structure.
The antenna according to any one of claims 1-13, wherein the number of the plurality of radiation elements is 3 or 4.
An electronic device, characterized by comprising the antenna according to any one of claims 1-14.
The electronic device according to claim 15, wherein the electronic device further comprises an antisymmetric feed network, the antisymmetric feed network includes a first radio frequency microstrip line and a second radio frequency microstrip line, the Among the opposite ends of the first main radiating unit and the second main radiating unit, one end is connected to the anode of the feed source through the first radio frequency microstrip line, and the other end is connected to the feeder through the second radio frequency microstrip line. source negative.
The electronic device according to claim 16, wherein the anti-symmetric feeding network further comprises an adjustable capacitor, and the adjustable capacitor is connected between the feeding source and the main radiating unit.
The electronic device according to any one of claims 15-17, wherein the electronic device further comprises an antenna carrying plate, the antenna carrying plate has a first surface, and a a second surface, the annular radiator is disposed on the first surface of the antenna bearing plate;

When the antenna further includes a first coupling stub, the first coupling stub is disposed on the first surface or the second surface of the antenna supporting board.
The electronic device according to claim 18, wherein the antenna carrying board is a PCB board or a dielectric board, and the electronic device is a router.