WO2022227009A1 - Dispositif de charge sans fil d'automobile compatible emc - Google Patents

Dispositif de charge sans fil d'automobile compatible emc Download PDF

Info

Publication number
WO2022227009A1
WO2022227009A1 PCT/CN2021/091511 CN2021091511W WO2022227009A1 WO 2022227009 A1 WO2022227009 A1 WO 2022227009A1 CN 2021091511 W CN2021091511 W CN 2021091511W WO 2022227009 A1 WO2022227009 A1 WO 2022227009A1
Authority
WO
WIPO (PCT)
Prior art keywords
voltage inverter
signal
frequency
toggling
charging controller
Prior art date
Application number
PCT/CN2021/091511
Other languages
English (en)
Inventor
Stephane SCHULER
Original Assignee
Shanghai Square Plus Information Technology Consulting Ltd.
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Shanghai Square Plus Information Technology Consulting Ltd. filed Critical Shanghai Square Plus Information Technology Consulting Ltd.
Priority to PCT/CN2021/091511 priority Critical patent/WO2022227009A1/fr
Publication of WO2022227009A1 publication Critical patent/WO2022227009A1/fr

Links

Images

Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/44—Circuits or arrangements for compensating for electromagnetic interference in converters or inverters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J50/00—Circuit arrangements or systems for wireless supply or distribution of electric power
    • H02J50/10—Circuit arrangements or systems for wireless supply or distribution of electric power using inductive coupling
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J50/00—Circuit arrangements or systems for wireless supply or distribution of electric power
    • H02J50/70—Circuit arrangements or systems for wireless supply or distribution of electric power involving the reduction of electric, magnetic or electromagnetic leakage fields
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J7/00—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries
    • H02J7/00032—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries characterised by data exchange
    • H02J7/00034—Charger exchanging data with an electronic device, i.e. telephone, whose internal battery is under charge
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J7/00—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries
    • H02J7/007—Regulation of charging or discharging current or voltage
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/4815—Resonant converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H02M7/539—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters with automatic control of output wave form or frequency
    • H02M7/5395—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters with automatic control of output wave form or frequency by pulse-width modulation
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J2207/00—Indexing scheme relating to details of circuit arrangements for charging or depolarising batteries or for supplying loads from batteries
    • H02J2207/20—Charging or discharging characterised by the power electronics converter
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/01—Resonant DC/DC converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H02M3/33573—Full-bridge at primary side of an isolation transformer
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H02M7/5387—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
    • H02M7/53871—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration with automatic control of output voltage or current

Definitions

  • the field of the invention is wireless charging devices.
  • Wireless charging applications for smartphones are increasingly popular, mostly for the convenience they offer.
  • wireless charging transmitters enhance safety by providing a repository for the driver’s phone, reducing driver distraction (most countries around the world are prohibiting smartphone usage while driving) and avoiding the need for charger cords that may present a danger of becoming entangled with the vehicle controls.
  • NFC Near Field Communication
  • LTE Long Term Evolution
  • a MP-A13 antenna transmitter has been certified by the WPC within its Qi standard.
  • This construction implements a high order low-pass filter that drags with it a number of caveats: besides costs for the filter itself, the filter introduces an efficiency loss causing heat generation that in turn causes the smartphone repository to significantly heat up, undermining the charging operation.
  • the heating up is usually mitigated by embedding an active cooling system in the wireless charging transmitter that is aimed at cooling the wireless charging transmitter and the in-charge device, which temperature has to be kept below 40degC to protect its battery.
  • a charging controller for a wireless charging transmitter.
  • the charging controller comprises a voltage inverter with output terminals electrically connectable to an inductive wireless charging antenna and configurable to operate the voltage inverter at a nominal switching frequency, f op , the nominal switching frequency having an associated period, T op , wherein the period, T op , comprises a first half period, T pos , and a second half period, T neg .
  • the charging controller is configured to supply to the output terminals in the first half period, T pos , an output signal comprising a sequence, S pos , of pulses at a toggling frequency, f sw , the pulses alternating between a positive amplitude, V pos , and an off-state, and in the second half period, T neg : an output signal comprising a sequence, S neg , of pulses at a toggling frequency, f sw , the pulses alternating between an off-state and a negative amplitude, V neg .
  • the toggling frequency, f sw is a, N, multiple of the voltage inverter nominal switching frequency, f op , and, N, is a positive number greater than 1, and wherein the voltage levels, V pos , and V neg , are of opposite polarity.
  • the charging controller is configured to provide a voltage inverter output signal alternating the sequences, S pos , and, S neq , characterized by a spectral signature equivalent to a square wave spectral signature of a same fundamental frequency, f op , and a same power with harmonics attenuated in the AM-band.
  • the charging controller is configured to provide a voltage inverter output signal alternating the sequences, S pos , and, S neq , characterized by a spectral signature which at least one harmonic amplitude in the AM radio band is of lower amplitude than a same harmonic of the voltage inverter output signal spectral signature of a frequency, f op , and a same power.
  • the same harmonic is harmonic 5 for operation frequencies, f op , higher than 112kHz and harmonic 7 for operation frequencies, f op , lower than 112kHz.
  • the charging controller is configured to set, N, to be greater than or equal to 92.
  • the charging controller is configured to set, N, to be greater than or equal to 160.
  • the charging controller is configured to provide the toggling sequences such that, S pos , and, S neq , are identical or reversed.
  • the voltage inverter is an H-bridge topology voltage inverter.
  • the charging controller further comprises a DC-DC converter with a configurable output voltage to supply power to the voltage inverter at, V pos , and, V neg , amplitudes.
  • the charging controller further comprises an amplitude modulation (AM) demodulator circuit configured to demodulate a load modulated signal sent by an in-charge device and to extract data from the modulated signal.
  • AM amplitude modulation
  • the charging controller further comprises a voltage inverter driver to control the voltage inverter output signal and generate the, S pos , and, S neq , alternating toggling sequences at the toggling frequency, f sw , and the voltage inverter output amplitudes, V pos , and, V neg .
  • the voltage inverter driver further comprises a clocking system configurable to programmably frequency modulate the toggling frequency, f sw , in polarity and depth.
  • the voltage inverter driver further comprises a microcontroller to control a wireless charging operation by controlling the DC-DC converter output voltage level and the voltage inverter based on the received data from the in-charge device through the demodulator circuit.
  • a charging controller for a wireless charging transmitter.
  • the wireless charging transmitter comprising a voltage inverter, wherein the voltage inverter comprises: a first low side switch controllable by a first signal and a first high side switch controllable by a second signal, a second low side switch controllable by a third signal, a second high side switch controllable by a fourth signal and output terminals electrically connectable to an inductive wireless charging antenna.
  • the charging controller is configurable to operate at a nominal frequency, f op , the nominal frequency having an associated period, comprising a first half period and a second half period.
  • the charging controller comprises a voltage inverter driver, wherein the voltage inverter driver is configured to provide, in the first half period, the second signal and the third signal at a level associated with an off-state of the respective switches, and the first signal comprising a first toggling sequence, S 1 , and the fourth signal comprising a fourth toggling sequence, S 4 , and in the second half period the first signal and the fourth signal at a level associated with an off-state of the respective switches, and the second signal comprising a second toggling sequence, S 2 , and the third signal comprising a third toggling sequence, S 3 .
  • the voltage inverter driver is configured to provide, in the first half period, the second signal and the third signal at a level associated with an off-state of the respective switches, and the first signal comprising a first toggling sequence, S 1 , and the fourth signal comprising a fourth toggling sequence, S 4 , and in the second half period the first signal and the fourth signal at a level associated with an off-state of the respective switches, and the
  • the voltage inverter driver is configured to provide each toggling sequence as toggled on-states and off-states at levels associated respectively with an on-state and an off-state of the respective switches, the first toggling sequence having a first toggling frequency, f sw1 , wherein the first toggling frequency is a multiple by a first multiple, N 1 , of the wireless charger nominal frequency, f op , the second toggling sequence having a second toggling frequency, f sw2 , wherein the second toggling frequency is a multiple by a second multiple, N 2 , of the wireless charger nominal frequency, f op , the third toggling sequence having a third toggling frequency, f sw3 , wherein the third toggling frequency is a multiple by a third multiple, N 3 , of the wireless charger nominal frequency, f op , the fourth toggling sequence having a fourth toggling frequency, f sw4 , wherein the fourth toggling frequency is a multiple by a fourth multiple.
  • N 4 , of the wireless charger nominal frequency, f op , and N 1 , and, N 4 , are positive numbers, and at least, N 1 , or, N 4 , is greater than 1 and N 1 , and, N 4 , are positive numbers, and at least, N 1 , or, N 4 , is greater than 1.
  • the voltage inverter driver further comprises a clocking system configurable to programmably frequency modulate the toggling frequency, f sw1 , f sw2 , f sw3 , and, f sw4 , of the switch control signals S 1 , S 2 , S 3 , and, S 4 , in polarity and depth.
  • the voltage inverter driver is configured to provide toggling sequences S 1 , S 2 , S 3 , and, S 4 , such that the voltage inverter output signal generated by the toggling sequences, S 1 , S 2 , S 3 , and, S 4 , is characterized by a spectral signature which is equivalent to a square wave spectral signature of a same fundamental frequency, f op , and a same power with harmonics attenuated in the AM-band.
  • the voltage inverter driver is configured to provide toggling sequences, S 1 , S 2 , S 3 , and, S 4 , such that the voltage inverter output signal generated by the toggling sequences, S 1 , S 2 , S 3 , and, S 4 , is characterized by a spectral signature which at least one harmonic amplitude in the AM radio band is of lower amplitude than a same harmonic of the voltage inverter output signal spectral signature of a frequency, f op , and a same power.
  • the same harmonic is harmonic 5 for operation frequencies, f op , higher than 112kHz and harmonic 7 for operation frequencies, f op , lower than 112kHz.
  • the voltage inverter driver is configured to set, N 2 , and, N 4 , to be equal to 1 and, N 1 , is equal to, N 3 , or, N 1 , and, N 3 , to be equal to 1 and, N 2 , is equal to, N 4 .
  • the voltage inverter driver is configured to set, N, to be greater than or equal to 92.
  • the voltage inverter driver is configured to set, N, to be greater than or equal to 160.
  • the voltage inverter driver is configured to provide the toggling sequences such that, S 1 , and, S 3 , are identical or reversed, and such that, S 2 , and, S 4 , are identical or reversed.
  • the voltage inverter driver further comprises a microcontroller for controlling a wireless charging operation by controlling a DC-DC converter and the voltage inverter based on the received data from a target device through an amplitude demodulator circuit.
  • the charging controller further comprises a DC-DC converter with a configurable output voltage, configured to receive power from a DC power supply and to supply power to the voltage inverter, and an amplitude modulation (AM) demodulator circuit configured to demodulate a load modulated signal sent by an in charge target device and to extract data from the modulated signal.
  • a DC-DC converter with a configurable output voltage, configured to receive power from a DC power supply and to supply power to the voltage inverter
  • AM amplitude modulation
  • a wireless charging transmitter comprising a charging system according to the first aspect or the second aspect, wherein the wireless charging device further comprises an inductive wireless charging antenna electrically connected to the output terminals of the voltage inverter and a DC power source to supply the voltage inverter Driver.
  • the wireless charging transmitter further comprises a low-pass or band-rejection filter installed between the voltage inverter and the inductive wireless charging antenna and a power line filter installed downstream the DC power source.
  • a method of operating a charging controller comprises providing in the first half period, T pos , an output signal comprising a sequence, S pos , of pulses at a toggling frequency, f sw , the pulses alternating between a positive amplitude, V pos , and an off-state, and providing in the second half period, T neg , an output signal comprising a sequence, S neg , of pulses at a toggling frequency, f sw , the pulses alternating between an off-state and a negative amplitude, V neg .
  • the toggling frequency, f sw is a multiple, N, of the voltage inverter nominal switching frequency, f op , and, N, is a positive number greater than 1, and wherein the voltage levels, V pos , and V neg , are of opposite polarity.
  • a method of operating a charging controller comprises providing in the first half period the second signal and the third signal at a level associated with an off-state of the respective switches, and the first signal comprising a first toggling sequence, S 1 , and the fourth signal comprising a fourth toggling sequence, S 4 ; and providing in the second half period the first signal and the fourth signal at a level associated with an off-state of the respective switches, and the second signal comprising a second toggling sequence, S 2 , and the third signal comprising a third toggling sequence, S 3 .
  • Fig. 1A and 1B are functional diagrams of current state of the art solutions that have been certified by the Wireless Power Consortium.
  • Fig 1B has the features of Fig. 1a and, in addition, shows the implementation of an additional high order low-pass filter aimed at preventing the AM-Band jamming caused by the charging antenna power feed signal and a power line filter to prevent interferences through line conduction.
  • Fig. 2A and 2B are time and frequency signal analysis of the antenna power feed signal as used in the current state of the art solutions.
  • Fig. 2C and 2D are time and frequency signal analysis assuming a trapezoid antenna power feed signal.
  • Fig. 3A, 3B and 3C are time signal analysis of a square, a trapezoid and a PWM signal power feed signals for energy comparison purposes.
  • Fig. 4A, 4B and 4C are time and frequency signal analysis of the antenna power feed signal as proposed by this disclosure.
  • Fig. 5A and 5B are graphs illustrating examples of sequential signal organizations according to embodiments.
  • Fig. 5C is the comparative electromagnetic signature of the signal of Fig. 5A and 5B.
  • Fig. 6A and 6B are schematic diagrams illustrating electronic circuits that generate the signal of Fig. 5C embedded in the circuits of Fig. 3A and 3B respectively.
  • Fig. 6C and 6D are part schematic and part graphical diagrams illustrating two configuration options to control the H-bridge switches according to embodiments.
  • motor vehicle hereafter may be understood to be a truck, a car, a sport utility vehicle or a suburban utility vehicle (SUV) , or any known automobile in the art.
  • the term “coupled” or “coupled to, “openable to” or “operatively connected to, “ or “connected” or “connected to” may indicate establishing either a direct or indirect connection and is not limited to either unless expressly referenced as such.
  • like or identical reference numerals are used in the figures to identify common or the same elements. The figures are not necessarily to scale und certain features and certain views of the figures may be shown exaggerated in scale for purposes of clarification.
  • the invention relates to a wireless charging transmitter working according to the Qi standard released by the Wireless Power Consortium and installed in a vehicle.
  • the wireless charging transmitter is usually installed between the two front seats of a vehicle, a location where it can interfere electromagnetically with other applications and functions of the vehicle embedded in its vicinity.
  • the person skilled in the art would appreciate the invention may be adapted to other systems not compliant with the standard.
  • a well-documented interference is the jamming of the AM-Band radio by the harmonics of the wireless charging signal. This problem is acute for the high power chargers (>5W) that are needed to satisfy an end user demand for short charging durations.
  • the MP-A13 solution proposes a ⁇ -shaped filter using inductances and high temperature stability ceramic capacitances. It is to note here that selecting the inductance is a challenge in itself with no power inductors having been designed for the particular purpose of a power filter.
  • the filter dissipates a significant portion of the signal power. Most of this energy is converted into heat, raising the filter inductors temperature significantly. Instead of being broadcasted, the feed signal harmonics are now converted into heat, negatively affecting the charging efficiency at the same time.
  • this invention proposes a solution which uses a feed signal, the harmonics of which do not need extensive filtering. This can provide higher efficiency and consequently a lower temperature elevation of the wireless charging transmitter unit. Depending on the application and level of EMC emissions required, filters may no longer be needed at all, or, if they are, they can be significantly reduced in size. This provides for a significant cost reduction. Furthermore, the lower temperature elevation enables simpler active cooling systems, further reducing costs.
  • Embodiments of the invention are directed to the definition and generation of a power feed signal for a wireless charging antenna with the purposes of:
  • the invention provides an electromagnetically quieter, smaller sized and cheaper wireless charging transmitter unit which is easier to embed in strictly constrained environments such as in motor vehicles.
  • construction is segmented in two parts:
  • the first part consists in selecting a voltage inverter output power feed signal that is more convenient for the purpose of limiting electromagnetic emissions other than the one used to carry the energy to the charging device which may be also referred to as an in-charge target device.
  • the second part consists of electronic circuitry configured to generate the power feed signal defined in the first part. Since many alternatives and variants would be apparent to the skilled person, both in terms of circuitry and/or integration, embodiments are described which focus on a single versatile solution allowing all possible configurations of the newly defined voltage inverter output power feed signal.
  • Fig. 1A and 1B are functional diagrams which describe current state of the art solutions that are certified by the Wireless Power Consortium within its Qi standard.
  • Fig. 1A and 1B only show a single charging antenna for simplification purposes. However, many systems use three or more charging antennas that are selected through a multiplexer. The multiplexer has been omitted for simplicity.
  • the DC power source 190 is not considered part of the wireless charging system since it is dependent on the environment (for example 12V for most automotive applications) .
  • Fig. 1A is a functional diagram illustrating the basic components needed to build a wireless charging function. From a high level perspective, a wireless charger transmitter can comprise two main functional blocks, namely:
  • a charging controller 100 which manages all aspects of the wireless power transfer, implementing the Wireless Consortium Qi standard.
  • a wireless charging antenna 150 which comprises at least one radiating coil 151 coupled serially to a capacitance (not represented) .
  • the serial inductance 151 and coupled capacitance implement a low-pass filter, for which the cut-off frequency f c is typically set just below 100kHz.
  • the charging controller 100 block is further broken down into four sub-blocks:
  • a voltage inverter driver 110 itself embedding a microcontroller 115 which executes a firmware code implementing the Wireless Consortium Qi standard and interfaces to and from the other sub-blocks of the controller 100 and the wireless charging antenna 150.
  • a voltage inverter 130 which converts the power supply DC output voltage 125 into an AC square signal 135 which is used to feed the wireless charging antenna 150.
  • the voltage inverter 130 is an H-bridge topology inverter made of four switches, typically power MOSFETs that are controlled by the voltage inverter driver 110.
  • a nominal operating frequency f op is defined in accordance with the Qi standard. This operating frequency f op is typically in the range of 100 to 140kHz.
  • the voltage inverter 130 is further controlled to superimpose a Frequency Shift Keying (FSK) modulation used for digital communication towards the in-charge device 180.
  • FSK Frequency Shift Keying
  • a DC-DC converter 120 which converts a DC input voltage 195 from the DC power source 190 into the DC output voltage 125 needed to provide the requested power by the in-charge device (a smartphone for example) .
  • the DC output voltage 125 is controlled by the voltage inverter driver 110.
  • the control method of the DC output voltage 125 can be either directly through a Pulse width modulation signal (PWM) or any digital communication 105 between the voltage inverter driver and the DC-DC converter 120.
  • PWM Pulse width modulation signal
  • the DC-DC converter 120 can be a Buck or Buck-Boost topology, depending on requirements.
  • An Amplitude Modulation (AM) demodulator 160 which demodulates the signal received from the in-charge device 180 through load modulation according to the Qi standard and feeds it back to the microcontroller 115 of the voltage inverter driver 110, thus closing the charging regulation loop.
  • This demodulation is typically implemented by a simple low-pass envelope detector that is read by the microcontroller 115 through an input capture port 165.
  • Fig. 1B is a functional diagram illustrating a variation of the functional diagram which does not jam the AM-Band radio. All of the blocks and sub-blocks of Fig. 1A are included, each operating in the same manner as described above. The following additional blocks are provided:
  • a high order low-pass filter 140 is inserted between the voltage inverter 130 and the wireless charging antenna 150. Its primary purpose is to attenuate the interference potential of the voltage inverter 130 output AC signal 135 harmonics above the operating frequency f op .
  • a power line filter 145 is provided upstream of the DC-DC converter 120. Its purpose is to reduce transmission of interference from the voltage inverter 130 along the wireless charger transmitter power supply lines.
  • This filter usually comprises a power choke combined with one or more inductors to create a low-pass filter.
  • the power line filter 145 may not be needed for consumer market wireless charger transmitters. In automotive applications, however, it is mandatory to prevent interference from radiating through the vehicle wire harness.
  • Fig. 2A is a graph illustrating the temporal response of the voltage inverter AC signal output 135 as used by the state of the art solutions illustrated in Fig. 1A and 1B, and described above.
  • the voltage inverter 130 is controlled so as to generate a square signal 230.
  • a pure sinusoidal signal 220 with the same amplitude has been illustrated as well.
  • the x-axis in the time domain 200 has been set to an angle in degree and in the frequency domain by an harmonic count 210. Obtaining the actual frequency can be done by multiplying the operation frequency f op by the harmonic count.
  • the MW radio band 250 and SW radio band 251 representations use the operation frequency f op to place the signals in their actual context.
  • the amplitude of the signals has been normalized to 1 in the y-axis and both time and frequency representations 201 and 211. In reality, this amplitude depends on the DC converter 120 output voltage 125. Note that all frequency domain representations of this disclosure have been computed with the same Fast Fourier Transform tool (Cooley Tukey algorithm) in the same context for accurate comparison purposes.
  • interference from the square signal spectral signature 231 with the MW radio band is to be expected at harmonics 5, 7, 9, 11 and 13 and interference with the SW radio band at harmonic 47 for an operation frequency f op of 127.7kHz. Should the operation frequency f op be below 112kHz, the interfering harmonics would be 7, 9, 11, 13 and 15.
  • Measurements taken at 15W charging power confirm a level of radiation in excess of 12 to 18dB ⁇ V/m over the class 5 limits that are defined by the CISPR25 standard used for automotive applications.
  • Fig. 1B a low-pass filter 140.
  • an operation frequency f op very close to the MW radio band 250 starting frequency of 560kHz
  • designing an analogue filter with sufficient attenuation is very challenging.
  • Its cut-off frequency f c is to be chosen close to the operating frequency f op and with an attenuation factor high enough to sufficiently dampen the harmonic 5. Practically this can be achieved using a so-called ⁇ -shaped LC filter.
  • experience teaches that a low-pass filter 140 insertion may attenuate harmonic 5 just enough for 15W charging power, practically limiting the power of wireless charging transmitters in the automotive environment. This causes a problem as the market, particularly in Asia, is pushing towards higher charging powers.
  • the low-pass filter 140 brings further problems:
  • the present invention proposes to abandon the AC square voltage inverter output signal 230 and use a signal which has a more convenient spectral signature for wireless charging applications, so as to minimize interferences with the AM-Band. This provides a particular advantage for automotive embedded wireless chargers.
  • a candidate of choice would obviously be an AC sine signal 220 with its pure spectral signature 221.
  • Another type of signal with a favorable spectral signature would be the trapezoid signal 240 of Fig. 2C.
  • the signature depends highly on the rising and falling time, since a trapezoid signal with short rising and falling times is close to a square signal.
  • An example of trapezoid signal with an angle ⁇ (245) of 56.25deg is illustrated in Fig. 2C.
  • the corresponding spectral signature is illustrated in Fig. 2D.
  • the angle ⁇ (245) is chosen such that it can fully encompass the corresponding sine signal 220 to ensure the trapezoid signal total energy is higher than that of the sine signal 220. This condition is satisfied for all angles ⁇ (245) between 0 and 57.29 degrees.
  • Both the sine signal 220 and the trapezoid signal 240 with an angle ⁇ (245) of 56.25deg would pass the CISPR25 class 5 limits requirement without the need for a low-pass filter 140. This would make them ideal candidates of choice for the voltage inverter AC output signal 135 but for the difficulty of generating them from a DC signal without significant power losses.
  • Fig. 3A and 3B are graphs which compare the sine, square and trapezoid signals in terms of energy.
  • the x-axis 300 represents the voltage inverter AC output signal 135 angle.
  • the y-axis 301 represents the amplitude of the signal. All signal amplitudes have been normalized to 1.
  • the energy amount of the signal can be normalized with the following formula:
  • the percentage of the energy carried by the fundamental frequency f op (harmonic 1 in the spectral signature) is as follows:
  • sine and trapezoid signals are better suited than the square signal in wireless charging applications.
  • the temperature elevation of the wireless charger transmitter has to be dissipated to minimize thermal conduction by contact to the in-charge device 180.
  • Lithium-ion batteries must not be charged at temperatures over 40degC.
  • most wireless charging receivers are programmed to lower the energy transfer to regulate the battery temperature, resulting in extended charging times.
  • embodiments of the present invention provide a voltage inverter AC output signal 135 that mimics a sine or a trapezoid signal by using a Pulse Width Modulation signal 350 as shown in Fig. 3C.
  • the definition of the Pulse Width Modulation signal 350 is given as an example among many others: the spectral signature of the signal can be adjusted by altering the pulse durations and phases. The person skilled in the art would appreciate that these durations and phases may be changed, and still be within the scope of the invention. The invention is not limited to specific values for the phases and durations.
  • the Pulse Width Modulation signal 350 has a normalized energy of 4.24 which places it between the sine 320 and trapezoid signal 340. With 97%of the energy carried by the fundamental frequency f op , the losses are slightly higher than the trapezoid signal but still ten times lower as with the square signal.
  • Fig. 4A and 4B are graphs which illustrate, respectively, the Pulse Width Modulation signal 450 compared with the sine signal 420 and the corresponding frequency spectral signature of that signal compared to the current solution square signal 230.
  • the frequency spectral signature 451 of the Pulse Width Modulation signal 450 is significantly less radiating in the AM radio bands 461. This is achieved by mimicking the trapezoid signal 330 signature for the harmonics up to 9. It Introduces, as expected, new high frequency harmonics above 17 that do not disturb the wireless charging transmitter, since they are outside the frequency range defined by the Qi standard for all communications and energy transfer.
  • Pulse Width Modulation signal 450 of Fig. 4A involves switching the voltage inverter 130 at a higher frequency f sw than the frequency f op .
  • the Pulse Width Modulation signal 450 of Fig. 4A is implemented with a frequency f sw that is a N times multiple of the frequency f op .
  • N has been chosen equal to 160: it provides a discrete voltage inverter AC output signal 135 in 160 shorter signals of 160 times the frequency f op .
  • the invention is not limited to any specific value of N.
  • N factor the higher the N factor the better the approximation of the targeted signal of frequency f op . It is considered that a sine signal approximation which is almost perfect for N is equal or greater than 420. Practically, however, the factor N becomes relatively quickly limited by the high power switches and pre-driver technology maximum frequency combined with the inherent losses resulting from switching a signal at such a high frequency f sw .
  • N greater or equal to 92 the spectral signature of the signal satisfies the CISPR25 class 4 limits at 15W. With N greater or equal to 160, the CISPR25 class 5 limits can be achieved in the same 15W conditions.
  • N is equal to 160 for an operation frequency f op at 127.772kHz
  • the maximum H-bridge inverter switching frequency f sw is equal to 20.44352MHz. Switching a power signal at such a high frequency f sw presents challenges that will be addressed below.
  • the Pulse Width Modulation output signal 450 of Fig. 4A with frequency f sw has a lower energy than that of the square output signal 230 of Fig. 2A at frequency f op .
  • the amplitude of the signal of the Pulse Width Modulation output signal 450 has to be increased to carry the same energy as its fundamental frequency. Practically, this may be achieved by increasing the power supply voltage 125. This adjustment may be executed automatically by the regulation loop as defined by the Qi standard. Fig.
  • FIG. 4C is a graph illustrating the spectral signature of the Pulse Width Modulation output signal 450 with an amplitude of 1.234 (instead of 1) which allows the fundamental frequency of the Pulse Width Modulation output signal to have the same energy as the square output signal 230. From Fig. 4C, it can be seen that all harmonics interfering with the MW radio band 461, namely 5 to 13, have significantly lower amplitude than the corresponding square signal. For harmonics 5 to 9, the lower amplitude is sufficient to achieve CISPR25 class 5 targets without even the need for the low-pass filter 140 to be implemented. In some designs, harmonics 11 and 13 may still be above the CISPR25 class 5 limits. If it is considered necessary to remove harmonics 11 and 13, then a low-pass filter 140 implementation may be used. The characteristics can be lessened with a higher cut-off frequency f c . A higher cut-off frequency f c will lower thermal losses.
  • the organization of the Pulse Width modulation can be implemented in several ways. Many of these ways result in creating a DC component in the frequency signature of the signal, thus making them unsuitable.
  • the DC component may be fully filtered by either the wireless charging antenna 150 or the low-pass filter 140 when the latter is present. This leaves two sequence organizations suitable. These are represented in Fig. 5A and 5B. In Fig. 5A and 5B, the sequences have been simplified for visual description clarity. The simplified solutions would be unsuitable to solutions involving electromagnetic interference mitigation.
  • the toggling sequences S pos , and, S neq are identical.
  • Fig. 5A is a graph representing a signal that is positive /negative symmetrical and that generates only the odd frequency harmonics. This signal is generated by driving the voltage inverter 130 with the same signal definition during the positive half period [0, ⁇ ] and the negative half period [ ⁇ , 2 ⁇ ] .
  • the toggling sequences S pos , and, S neq are reversed, i.e. they are the reverse of each other.
  • Fig. 5B is a graph representing a signal that is ⁇ symmetrical. This signal frequency signature will display both even and odd harmonics.
  • Fig. 5B type of signal can be generated by reverse sequencing the signal definition driving the voltage inverter 130 in the [0, ⁇ ] timeframe to drive the voltage inverter during the second half period [ ⁇ , 2 ⁇ ] .
  • the signal of Fig. 5B can be of interest since it allows further spreading of the energy along the even harmonics.
  • Embodiments of the present invention provides a method of controlling the voltage inverter 130 of a wireless charging transmitter in such a way that generates a voltage inverter AC output signal 135 Pulse Width Modulation (PWM) at N times the operation frequency f op .
  • PWM Pulse Width Modulation
  • This is implemented in a manner that provides a convenient frequency spectral signature for the system.
  • the invention seeks to effectively decrease the thermal losses associated with the filtering of high energy square signal harmonics.
  • the primary target for automotive applications is to achieve a CISPR25 class 5 level that prevents AM radio bands interference.
  • the secondary target would be to reduce constraints mostly in size and audible noise limits on the active cooling system that is needed to maintain the in-charge device 180 battery temperature below 40degC for continuous maximum power charging. Both size and audible noise are sensitive issues for the automotive industry, the latter being even more critical for silent electrical vehicles.
  • the electronic circuit to be embedded, according to embodiments, in the voltage inverter driver 110 for generating the Pulse Width Modulation signal 450 is now described.
  • the wireless charging antenna 150 has a low-pass characteristic inherited from its serial inductance 151 and capacitance assembly.
  • Inexpensive microcontrollers are clocked at a frequency only a couple of times higher than the frequency f sw preventing direct control of the Pulse Width Modulation.
  • the voltage inverter 130 control signals need to be perfectly synchronized to ensure that no short is created between the DC power source 195 and the ground GND.
  • a Frequency Shift Keying FSK modulation is to be used to communicate with the in-charge device 180. This modulation can only be implemented by modulating the frequency f sw , making it even harder to do with a microcontroller directly controlled Pulse Width Modulation signal.
  • MOSFET technology can be used only with great difficulty above 5MHz due to the switching losses involved. In most cases, the use of Gallium Nitride technology is recommended.
  • a charging controller 100 which comprises a voltage inverter driver 110 and a voltage inverter 130.
  • the voltage inverter 130 has output terminals electrically connectable to an inductive wireless charging antenna 150.
  • the charging controller 100 comprises the voltage inverter driver 110 and the voltage inverter 130.
  • the charging controller is configurable to operate the voltage inverter at a nominal switching frequency f op .
  • the nominal switching frequency has an associated period T op , wherein the period T op , comprises a first half period T pos , and a second half period T neg .
  • the charging controller is configured to supply to the output terminals, in the first half period T pos : an output signal comprising a sequence S pos , of pulses at a toggling frequency, f sw , the pulses alternating between a positive amplitude, V pos , and an off-state, and in the second half period T neg an output signal comprising a sequence S neg , of pulses at a toggling frequency f sw , the pulses alternating between an off-state (i.e.
  • the toggling frequency f sw is a N multiple of the voltage inverter nominal switching frequency f op , and N is a positive number greater than 1, and wherein the voltage levels V pos , and V neg , are of opposite polarity.
  • a voltage inverter driver 110 is configured to be connectable to a voltage inverter 130 and configured to provide a control signal to that voltage inverter in the form of toggling sequences.
  • the H-bridge type voltage inverter 130 would typically comprise a first low side switch controllable by a first signal and a first high side switch controllable by a second signal, a second low side switch controllable by a third signal, a second high side switch controllable by a fourth signal.
  • the voltage inverter output terminals are electrically connectable to an inductive wireless charging antenna.
  • the voltage inverter 130 is configurable to operate at an operation frequency f op .
  • the operation frequency has an associated period T op , comprising a first half period T pos and a second half period T neg .
  • the voltage inverter driver 110 is configured to provide the first to fourth signals to such an H-bridge voltage inverter. In half periods in which a switch is to be switched on, when connected to a voltage inverter driver 110 according to an embodiment, the voltage inverter 130 switch receives a toggling sequence.
  • the voltage inverter driver 110 is configured to provide the second signal and the third signal at a level associated with an off-state of the respective switches, the first signal comprising a first toggling sequence S 1 , and the fourth signal comprising a fourth toggling sequence S 4 .
  • the voltage inverter driver 110 is configured to provide the first signal and the fourth signal at a level associated with an off-state of the respective switches, a second signal comprising a second toggling sequence S 2 , and the third signal comprising a third toggling sequence S 3 .
  • the toggling sequences S 1 , S 2 , S 3 and S 4 generated by the voltage inverter driver 110 result in a voltage inverter 130 signal that is characterized by a spectral signature which is equivalent to a square wave spectral signature of a same fundamental frequency f op and a same power with harmonics attenuated in the AM-band.
  • voltage inverter output signal generated by the toggling sequences S 1 , S 2 , S 3 and S 4 is characterized by a spectral signature which at least one harmonic amplitude in the AM radio band is of lower amplitude than a same harmonic of the voltage inverter output signal spectral signature of a frequency f op and a same power.
  • the voltage inverter output signal 230 spectral signature first MW band interfering harmonic is of lower amplitude than the same harmonic of the square wave signal so as to allow shifting the low-pass filter 140 cut frequency towards higher frequencies and reduce that way the losses in the filter 140.
  • this harmonic is the number 5 harmonic and for embodiments using an operation frequency f op lower than 112kHz, this harmonic is harmonic number 7.
  • this harmonic 5 is the first harmonic to interfere with the MW radio band.
  • Fig. 6A and 6B are schematic diagrams showing a possible voltage inverter driver 110 implementation to generate the sequences S1, S2, S3 and S4 needed to control the voltage inverter 130 as to create the desired voltage inverter output signal 135.
  • the toggling sequences toggle a voltage level between a level associated with an off state of the respective switch, and a level which is at or greater than a level that turns on the switch.
  • a voltage inverter driver 110 according to an embodiment is described below:
  • the serial output of the n bits shift register 610 is connected in daisy chain to the serial input of the n bits shift register 612 to build a N bits shift register where N is equal to 2 times n corresponding to the resolution of the desired Pulse Width Modulation signal.
  • the output of the n bits shift register 612 is connected to the input of the n bits shift register 610 to form a N bits rotary shift register.
  • the serial output of the n bits register bank 610 is used to control the high side switch driver 620 and the serial output of the n bits register bank 612 is used to control the high side switch driver 622.
  • the serial output of the n bits shift register 611 is connected in daisy chain to the serial input of the n bits shift register 613 to build a N bits shift register where N is equal to 2 times n corresponding to the resolution of the desired Pulse Width Modulation signal.
  • the output of the n bits shift register 613 is connected to the input of the n bits shift register 611 to form a N bits rotary shift register.
  • the serial output of the n bits register bank 611 is used to control the low side switch driver 621 and the serial output of the n bits register bank 613 is used to control the low side switch driver 623.
  • the microcontroller 115 initializes the n bits shift registers 610 to 613 with sequences of bits S 2 , S 1 , S 4 and S 3 respectively, prior to any charging activity.
  • parallel programming was chosen as the simplest possible way using commercially available logic gates. This programming step, to be done at initialisation, will store the desired Pulse Width Modulation signal definition in the N bits register banks.
  • the microcontroller 115 also controls the shifting frequency of N bits registers through a clocking system 640 which baseline frequency is the switch frequency f sw . It is necessary to implement the frequency shift key modulation needed for communication towards the in charge target device 180.
  • Each switch driver 620 to 623 is in turn controlling the switch state of the voltage inverter switches 131 to 134.
  • a voltage inverter driver 110 that is suited to any definition of the voltage inverter output signal 135 using a single frequency f sw .
  • the sequences S 1 , S 2 , S 3 and S 4 allow full control of the wireless charger power signal over the period of f op using the same resolution N.
  • many topologies of circuits may be suitable to achieve the desired voltage inverter output signal 135. This includes topologies using independent register banks of different sizes N 1 , N 2 , N 3 and N 4 operating at different frequencies f sw1 , f sw2 , f sw3 and f sw4 .
  • Fig. 6C and 6D are part schematic and part graphical diagrams illustrating possible N bits shift register bank configurations for generating the expected voltage inverter Pulse Width Modulation (PWM) output signal 135 using the positive /negative symmetry organization described in Fig. 5A.
  • PWM Pulse Width Modulation
  • a bit set to 1 turns on the switch and a bit set to 0 turns the switch off.
  • the n bits shift register pair 611 and 613 control the low side switches of the voltage inverter 130.
  • the n bits shift register 611 is initialised by the microcontroller 115 with the hexadecimal 4639EFBFFFFFFBF38C20h and the n bits shift register 613 with the hexadecimal value 0000000000000000h.
  • the n bits shift register pair 610 and 612 control the high side switches of the voltage inverter 130.
  • the n bits shift register 610 is initialised by the microcontroller 115 with the hexadecimal value 0000000000000000h and the n bits shift register 612 with the hexadecimal value FFFFFFFFFFFFFFh.
  • the voltage inverter switches 131 to 134 are driven by the signals as shown in Fig. 6C and generate the voltage inverter output signal 135 (V 135 ) according to the signal definition 450.
  • the high side switches 132 and 134 operate the same way as in the state of the art solution. They can consequently use the same switches (MOSFETs) and the same high side MOSFETs drivers.
  • the low side switches are switched at much higher frequencies to generate the requested Pulse Width Modulation signal. These high frequencies are likely, depending on the discretisation factor N to force the use of switches that can operate at higher frequencies with lower losses and less distorted signal outputs such as Gallium Nitride FET (GaNFETs) .
  • GaNFETs Gallium Nitride FET
  • Fig. 6D is a diagram of a more complex implementation, which however provides a n improved performance due to its T ability to split the switching losses between the high side and low side switches, reducing the thermal losses caused by switching. It may, for lower values of N, allow the use of MOSFETs for both high side and low side switches:
  • the state of the voltage inverter 130 halves is defined by both switch states: should any of the high side or low side switch be off-state, the bridge will be turned off. To be on state, both switches have to be turned on.
  • the n bits shift register pair 611 and 613 controls the low side switches of the voltage inverter 130.
  • the n bits shift register 611 is initialised by the microcontroller 115 with the hexadecimal value 7E3FEFFFFFFFFBFF8FE0h and the n bits shift register 613 with the hexadecimal value 0000000000000000h.
  • the n bits shift register pair 610 and 612 controls the high side switches of the voltage inverter 130.
  • the n bits shift register 610 is initialised by the microcontroller 115 with the hexadecimal value 0000000000000000h and the n bits shift register 612 with the hexadecimal value C7F9FFBFFFFFFFF3FC3Ch.
  • the voltage inverter switches 131 to 134 are driven as shown in Fig. 6D and generate the voltage inverter output signal 135 (V 135 ) according to the signal definition 450.
  • the above hexadecimal value of 4639EFBFFFFFFBF38C20h is given as a static example of signal reconstruction to illustrate the operation of the configurations illustrated in Fig. 6A and 6B using the voltage inverter 130 control method of Fig. 6C and 6D. While the hexadecimal value 4639EFBFFFFFFBF38C20h is outputting a signal that prevents AM band radio jamming, other hexadecimal values are producing signals with frequency signatures that would be equally acceptable.

Abstract

Dispositif de commande de charge pour un émetteur de charge sans fil, le dispositif de commande de charge comprenant un onduleur de tension doté de bornes de sortie pouvant être électriquement connectées à une antenne de charge sans fil inductive et pouvant être configurées pour actionner l'onduleur de tension à une fréquence de commutation nominale, f op, la fréquence de commutation nominale comprenant une période associée, T op, la période T op comprenant une première demi-période, T pos, et une seconde demi-période, T neg. Le dispositif de commande de charge est configuré pour alimenter les bornes de sortie dans la première demi-période Tpos, un signal de sortie comprenant une séquence, S pos, d'impulsions à une fréquence de basculement, f sw, les impulsions alternant entre une amplitude positive, V pos, et un état d'arrêt, et dans la seconde demi-période T neg, un signal de sortie comprenant une séquence, S neg, d'impulsions à une fréquence de basculement, f sw, les impulsions alternant entre un état d'arrêt et une amplitude négative, V neg. La fréquence de basculement f sw est un multiple N de la fréquence de commutation nominale f op de l'onduleur de tension, et N est un nombre positif supérieur à 1, les niveaux de tension V pos et V neg présentant une polarité opposée. Les séquences de basculement sont définies de manière à obtenir une signature spectrale qui donne lieu à une interférence plus faible dans la bande AM que les approches classiques.
PCT/CN2021/091511 2021-04-30 2021-04-30 Dispositif de charge sans fil d'automobile compatible emc WO2022227009A1 (fr)

Priority Applications (1)

Application Number Priority Date Filing Date Title
PCT/CN2021/091511 WO2022227009A1 (fr) 2021-04-30 2021-04-30 Dispositif de charge sans fil d'automobile compatible emc

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
PCT/CN2021/091511 WO2022227009A1 (fr) 2021-04-30 2021-04-30 Dispositif de charge sans fil d'automobile compatible emc

Publications (1)

Publication Number Publication Date
WO2022227009A1 true WO2022227009A1 (fr) 2022-11-03

Family

ID=83847504

Family Applications (1)

Application Number Title Priority Date Filing Date
PCT/CN2021/091511 WO2022227009A1 (fr) 2021-04-30 2021-04-30 Dispositif de charge sans fil d'automobile compatible emc

Country Status (1)

Country Link
WO (1) WO2022227009A1 (fr)

Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
GB2623136A (en) * 2022-11-14 2024-04-10 Mclaren Applied Ltd Variable switching frequency

Citations (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPH05130792A (ja) * 1991-10-25 1993-05-25 Hitachi Ltd パルス幅変調インバータによる誘導電動機の制御装置
CN101496277A (zh) * 2007-07-26 2009-07-29 三菱电机株式会社 功率变换装置
TW201141031A (en) * 2010-05-04 2011-11-16 Univ Nat Formosa Method of suppressing noise of inverter
CN110336385A (zh) * 2018-03-28 2019-10-15 苹果公司 具有正弦脉冲宽度调制的无线充电装置
CN110768560A (zh) * 2019-10-30 2020-02-07 渤海大学 半周期三脉冲波低品质因数串联谐振型中频感应加热逆变控制方法
CN111901052A (zh) * 2020-07-28 2020-11-06 中国矿业大学 多调制波复合spwm控制的电能与信号并行无线传输系统

Patent Citations (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPH05130792A (ja) * 1991-10-25 1993-05-25 Hitachi Ltd パルス幅変調インバータによる誘導電動機の制御装置
CN101496277A (zh) * 2007-07-26 2009-07-29 三菱电机株式会社 功率变换装置
TW201141031A (en) * 2010-05-04 2011-11-16 Univ Nat Formosa Method of suppressing noise of inverter
CN110336385A (zh) * 2018-03-28 2019-10-15 苹果公司 具有正弦脉冲宽度调制的无线充电装置
CN110768560A (zh) * 2019-10-30 2020-02-07 渤海大学 半周期三脉冲波低品质因数串联谐振型中频感应加热逆变控制方法
CN111901052A (zh) * 2020-07-28 2020-11-06 中国矿业大学 多调制波复合spwm控制的电能与信号并行无线传输系统

Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
GB2623136A (en) * 2022-11-14 2024-04-10 Mclaren Applied Ltd Variable switching frequency

Similar Documents

Publication Publication Date Title
EP3022823B1 (fr) Système et procédé pour une coexistence efficace de communication de données et de transfert de puissance sans fil
EP3058661B1 (fr) Réglage d'un transmetteur de puissance sans fil
ES2590467T3 (es) Sistemas, procedimientos y aparatos para un rectificador monofásico de alto factor de potencia
JP6199408B2 (ja) Ｄｃバイアスを使用した高電力のｒｆ電界効果トランジスタスイッチング
WO2022227009A1 (fr) Dispositif de charge sans fil d'automobile compatible emc
US10958154B2 (en) Wireless receiver rectifier low side current limited operation
US9866126B2 (en) Galvanic isolator and circuit using galvanic isolation
US9601999B2 (en) Dynamic switch scaling for switched-mode power converters
WO2013025720A1 (fr) Systèmes, procédés et dispositifs pour signalisation à plusieurs niveaux par champ de transfert de puissance sans fil
US9871413B2 (en) Wireless power receiving apparatus
JP2022534880A (ja) 複数のディザリングプロファイル信号生成
JP2011114885A (ja) 非接触電力伝送装置
WO2012164844A1 (fr) Dispositif et système d'alimentation électrique sans fil
EP3243255A1 (fr) Procédés, circuits et articles de fabrication pour commander un transfert d'énergie sans fil en réponse à des états de circuit d'unité de commande
WO2022266914A1 (fr) Commande d'émetteurs de chargeur sans fil sans cc/cc dans un environnement sensible à l'emc
Sarin et al. Comparison of switched receivers for direct-sequence spread-spectrum wireless power transfer
WO2022227008A1 (fr) Dispositif de charge sans fil sans convertisseur cc-cc
Zhu et al. A modified QPSK modulation technique for direct antenna modulation (DAM) systems
KR101052905B1 (ko) 전원 공급 장치
WO2015034684A1 (fr) Système, appareil et procédés pour un circuit de filtre d'émissions intégré dans un câble électrique
KR20150104382A (ko) 차량용 무선 충전 장치
JP5706538B2 (ja) 低損失低雑音電動機制御システム
CN114374256A (zh) 用于对电能存储单元充电的方法和电压转换器
US20140213208A1 (en) Noise shaping for switching circuitry
JP4170310B2 (ja) 送信器およびトランシーバ

Legal Events

Date Code Title Description
121 Ep: the epo has been informed by wipo that ep was designated in this application

Ref document number: 21938483

Country of ref document: EP

Kind code of ref document: A1

NENP Non-entry into the national phase

Ref country code: DE

122 Ep: pct application non-entry in european phase

Ref document number: 21938483

Country of ref document: EP

Kind code of ref document: A1