WO2022028168A1 - 过零检测电路、pfc电路及两路交错并联pfc电路 - Google Patents

过零检测电路、pfc电路及两路交错并联pfc电路 Download PDF

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Publication number
WO2022028168A1
WO2022028168A1 PCT/CN2021/104092 CN2021104092W WO2022028168A1 WO 2022028168 A1 WO2022028168 A1 WO 2022028168A1 CN 2021104092 W CN2021104092 W CN 2021104092W WO 2022028168 A1 WO2022028168 A1 WO 2022028168A1
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Prior art keywords
zero
detection circuit
crossing detection
resistor
switch tube
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PCT/CN2021/104092
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English (en)
French (fr)
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韦康
朱益波
刘宏森
郑煦
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杭州中恒电气股份有限公司
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Publication of WO2022028168A1 publication Critical patent/WO2022028168A1/zh

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
    • H02M1/083—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the ignition at the zero crossing of the voltage or the current
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01R—MEASURING ELECTRIC VARIABLES; MEASURING MAGNETIC VARIABLES
    • G01R19/00—Arrangements for measuring currents or voltages or for indicating presence or sign thereof
    • G01R19/175—Indicating the instants of passage of current or voltage through a given value, e.g. passage through zero
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
    • H02M1/088—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the simultaneous control of series or parallel connected semiconductor devices
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/12—Arrangements for reducing harmonics from ac input or output
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
    • H02M1/4208—Arrangements for improving power factor of AC input
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H02M3/1584—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load with a plurality of power processing stages connected in parallel
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0003—Details of control, feedback or regulation circuits
    • H02M1/0009—Devices or circuits for detecting current in a converter
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0048—Circuits or arrangements for reducing losses
    • H02M1/0054—Transistor switching losses
    • H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H02M3/1584—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load with a plurality of power processing stages connected in parallel
    • H02M3/1586—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load with a plurality of power processing stages connected in parallel switched with a phase shift, i.e. interleaved
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Definitions

  • the invention relates to the technical field of zero-crossing detection, in particular to a zero-crossing detection circuit, a PFC circuit and a two-way staggered parallel PFC circuit.
  • Zero-crossing detection refers to: in the power supply system, the waveform is converted from the positive half cycle to the negative half cycle or the negative half cycle to the positive half cycle.
  • the system When passing near the zero position, the system outputs a zero-crossing signal, and the switch circuit responds to the zero-crossing signal. switch.
  • Existing zero-crossing detection usually adopts optocoupler isolation or Hall sensor.
  • the above methods usually have problems such as low bandwidth, which causes the detected zero-crossing to deviate from the real zero-crossing, so that there is a large negative current in the switched circuit, thereby reducing the reliability of the corresponding system.
  • one of the objectives of the present invention is to provide a zero-crossing detection circuit, which can accurately output a zero-crossing signal during zero-crossing to turn off the corresponding main switch tube and reduce the number of switched circuits negative current in the circuit, thereby improving the reliability and system efficiency of the circuit.
  • a zero-crossing detection circuit comprising a current transformer, a main switch tube and a negative current regulating circuit; wherein:
  • the current transformer includes a primary winding and a secondary winding, the primary winding and the main switch tube are connected in series to form a first converter, and the first converter is connected to an AC source in cooperation;
  • the negative current regulating circuit includes a first resistor, a third resistor, a comparison unit, a trigger unit and a DC source; the comparison unit is connected to the trigger unit; the DC source is connected to the comparison unit and the trigger unit connection; the first resistor and the third resistor are connected in series and connected to the comparison unit, and the first end and the second end of the secondary winding are respectively connected to both ends of the first resistor;
  • the induced current generated by the secondary winding flows into the comparison unit through the second terminal, the first resistor and the third resistor , so that the comparison unit outputs a switching signal, the trigger unit switches from an off state to an operating state in response to the switching signal and outputs a zero-crossing signal, and the main switch tube is turned off in response to the zero-crossing signal.
  • the comparison unit includes a comparison switch tube and a second resistor, the first end is connected to the DC source, the third resistor is connected in series between the second end and the forward end of the comparison switch tube, so The second resistor is connected in series between the ground and the negative terminal of the comparison switch, the base of the comparison switch is connected to the negative terminal or is grounded through the fifth resistor, and the base of the comparison switch is connected to the the trigger unit.
  • the comparison unit includes a comparison switch tube and a second resistor, the second resistor is connected in series between the DC source and the forward end of the comparison switch tube, and the third resistor is connected in series with the first end and the comparison switch tube Between the negative terminals of , the second terminal is grounded, the base of the comparison switch is connected to the positive terminal or is connected to a DC source via a fifth resistor, and the base of the comparison switch is connected to the trigger unit.
  • the trigger unit includes a trigger switch tube and a fourth resistor, the positive end of the trigger switch tube is connected to the DC source, the fourth resistor is connected in series between the ground and the negative end of the trigger switch tube, and the trigger switch tube is connected in series with the DC source.
  • the base of the switch tube is connected to the base of the comparison switch tube; when the trigger unit switches from the off state to the running state, the negative end of the trigger switch tube outputs a zero-crossing signal.
  • the trigger unit includes a trigger switch tube and a fourth resistor, the fourth resistor is connected in series between the DC source and the positive terminal of the trigger switch tube, the negative terminal of the trigger switch tube is grounded, and the trigger switch tube is connected to the ground.
  • the base of the switch tube is connected to the base of the comparison switch tube; when the trigger unit switches from the off state to the running state, the positive terminal of the trigger switch tube outputs a zero-crossing signal.
  • the negative current regulating circuit further includes a controller, the input end of the controller is connected to the trigger unit and receives the zero-crossing signal, and the output end of the controller is connected to the main switch; When the trigger signal outputs a zero-crossing signal, the controller controls the main control tube to turn off.
  • Another object of the present invention is to provide a PFC circuit for zero-crossing detection, which can reduce the negative direction flowing through the switched zero-crossing detection circuit when the first zero-crossing detection circuit and the second zero-crossing detection circuit are switched. current, thereby improving the reliability and system efficiency of the circuit.
  • the second objective of the present invention is achieved by adopting the following technical solution: applying the above zero-crossing detection circuit to a PFC circuit, which includes an AC source, a first diode, a second diode, a first inductor, a capacitor, a load and Two sets of zero-crossing detection circuits; of which:
  • One end of the first inductor is connected to the positive pole of the AC source, and the other end is marked as the connection terminal f.
  • the anode of the first diode and the cathode of the second diode are both connected to the negative pole of the AC source.
  • a zero-crossing detection circuit is matched and connected between the connection terminal f and the cathode of the first diode, and the second zero-crossing detection circuit is matched and connected between the connection terminal f and the anode of the second diode.
  • the loads are connected in parallel between the cathode of the first diode and the anode of the second diode.
  • the controller also includes a controller, and the main switch tubes and trigger units of the first zero-crossing detection circuit and the second zero-crossing detection circuit are all connected to the controller;
  • the controller controls the main switch of the first zero-crossing detection circuit to be turned off and the main switch of the second zero-crossing detection circuit to be turned on; when When the trigger unit of the second zero-crossing detection circuit outputs a zero-crossing signal, the controller controls the main switch tube of the second zero-crossing detection circuit to be turned off and the main switch tube of the first zero-crossing detection circuit to be turned on.
  • the main switch tube, the comparison switch tube and the trigger switch tube of the first zero-crossing detection circuit and the second zero-crossing detection circuit are all SI MOSFET tubes, IGBT tubes, GaN MOSFET tubes, SIC MOSFETs, triodes, Either a thyristor and a relay, or a bidirectional switch formed by their combination.
  • the third object of the present invention is to provide a two-way staggered parallel PFC circuit with zero-crossing detection, in which the first zero-crossing detection circuit and the second zero-crossing detection circuit are switched, the third zero-crossing detection circuit and the fourth zero-crossing detection circuit are switched.
  • the detection circuit is switched, the negative current flowing through the zero-crossing detection circuit after the switching can be reduced, thereby improving the reliability of the circuit.
  • the above-mentioned zero-crossing detection circuit is applied to a two-way interleaved parallel PFC circuit, which includes an AC source, a first diode, a second diode, a first inductor, The second inductor, capacitor, load and four sets of zero-crossing detection circuits; wherein:
  • the anode of the first diode and the cathode of the second diode are both connected to the cathode of the AC source, and the capacitor and the load are connected in parallel between the cathode of the first diode and the anode of the second diode ;
  • the first inductor is connected to the positive pole of the AC source, and the other end is marked as the connection terminal f1.
  • the first zero-crossing detection circuit is matched and connected between the connection terminal f1 and the cathode of the first diode.
  • the second zero-crossing detection circuit The circuit is matched and connected between the connection end f1 and the anode of the second diode;
  • connection terminal f2 One end of the second inductor is connected to the positive pole of the AC source, the other end is marked as the connection terminal f2, the third zero-cross detection circuit is connected between the connection terminal f2 and the cathode of the first diode, and the fourth zero-cross detection circuit is connected.
  • a circuit fitting is connected between the connection terminal f2 and the anode of the second diode.
  • the trigger unit when the negative current flows through the first converter and the value of the negative current is equal to the preset threshold, the trigger unit outputs a zero-crossing signal correspondingly, that is, there is no zero-crossing signal in the first converter at this time. Freewheeling, thereby reducing the negative current flowing through the switched circuit and providing a reliable basis for subsequent software development; by replacing the third resistor, the preset threshold value of the comparison unit can be adjusted so as to be more consistent with the actual situation. In order to fit, and then improve the flexibility of the zero-crossing detection circuit;
  • the first zero-crossing detection circuit when the actual waveform of the inductor current changes from the positive half cycle to the negative half cycle, the first zero-crossing detection circuit is turned off, and the second zero-crossing detection circuit operates to reduce the negative current in the second zero-crossing detection circuit. ;
  • the first zero-crossing detection circuit when the actual waveform of the current is converted from the negative half cycle to the positive half cycle, the first zero-crossing detection circuit is turned off, and the second zero-crossing detection circuit is operated to reduce the negative current in the second zero-crossing detection circuit. Therefore, it can reduce the negative current in the zero-crossing detection circuit after switching, and facilitate compensation of the input current distortion caused by the negative current, so as to reduce the harmonics of the input current.
  • Embodiment 1 is a circuit diagram of a zero-crossing detection circuit shown in Embodiment 1;
  • Embodiment 2 is a circuit diagram of an implementation manner of the comparison unit shown in Embodiment 2;
  • Embodiment 3 is a circuit diagram of another implementation manner of the comparison unit shown in Embodiment 2;
  • FIG. 4 is a circuit diagram of an implementation of the trigger unit shown in Embodiment 2;
  • FIG. 5 is a circuit diagram of another implementation manner of the trigger unit shown in Embodiment 2;
  • FIG. 6 is a circuit diagram of the negative current regulating circuit shown in Embodiment 2.
  • FIG. 7 is a circuit diagram of a PFC circuit with zero-crossing detection shown in Embodiment 3.
  • FIG. 8 is a circuit diagram of the two-way interleaved parallel PFC circuit with zero-crossing detection shown in the fourth embodiment.
  • the zero-crossing detection circuit 10 includes a current transformer CT, a main switch tube Q1 and a negative current regulating circuit 101 .
  • the current transformer CT includes a primary winding and a secondary winding.
  • the primary winding and the main switch tube Q1 are connected in series to form a first converter, and the first converter is connected to the AC source.
  • the primary winding has the same name terminal and the same name terminal.
  • the current flowing from the same name terminal of the primary winding to the same name terminal is recorded as the forward current of the zero-crossing detection circuit, and vice versa.
  • the current of the different name terminal is recorded as the negative current of the zero-crossing detection circuit.
  • the secondary winding also has the same name terminal and the different name terminal, wherein the first terminal A1 can be the same name terminal of the secondary winding, and the second terminal A2 can be the same name terminal of the secondary winding, and the first converter flows through the positive terminal.
  • the induced current generated by the secondary winding flows out from the first terminal A1, and flows in from the second terminal A2 after passing through the negative regulating circuit 101; on the contrary, when the second converter flows through the negative current, the secondary side The induced current generated by the winding flows out from the second terminal A2 and flows in from the first terminal A1 after passing through the negative regulating circuit 101 .
  • the negative current regulating circuit 101 includes a first resistor R1, a third resistor R3, a comparison unit 1011, a trigger unit 1012 and a DC source.
  • the first resistor R1 is connected in series between the first terminal A1 and the second terminal A2.
  • the first resistor R1 can be regarded as a pull-down resistor, so that the voltage of the second terminal A2 is low
  • the voltage of the first terminal A1; when the second converter flows through a negative current, the first resistor R1 can be regarded as a pull-up resistor, so that the voltage of the second terminal A2 is higher than the voltage of the first terminal A1.
  • One end of the third resistor R3 can be connected to any end of the first resistor R1, and both the first resistor R1 and the second resistor R3 are connected to the comparison unit 1011, and the comparison unit 1011 is provided with a predetermined value according to the resistance value of the third resistor R3.
  • the threshold value is set, so the third resistor R3 can be selected as a resistance device with adjustable resistance value such as a sliding varistor.
  • the comparison unit 1011 does not output switching signal, the trigger unit 1012 is in the off state;
  • the triggering unit 1012 is still in the off state.
  • the induced current generated by the secondary winding flows out from the second terminal A2, and is input from the first terminal A1 after passing through the negative current regulating circuit.
  • the unit 1011 also outputs a switching signal, and the triggering unit 1012 responds to the switching signal and switches from the off state to the running state, and outputs a zero-crossing signal at the same time.
  • the main switch tube Q1 is turned off in response to the zero-crossing signal, so that the first converter is turned off. It is explained here that the main switch Q1 can be any one of SI MOSFET, IGBT, GaN MOSFET, SIC MOSFET, triode, thyristor and relay, or a bidirectional switch formed by their combination.
  • the trigger unit 1012 when the negative current flows through the first converter and the value of the negative current is equal to the preset threshold, the trigger unit 1012 outputs a zero-crossing signal correspondingly, that is, the first inverter at this time. There is no freewheeling current in the converter, thereby reducing the negative current flowing through the switched circuit and providing a reliable basis for subsequent software development; by replacing the third resistor R3, the preset threshold value of the comparison unit 1011 can be adjusted , so as to better fit the actual situation, thereby improving the flexibility of the zero-crossing detection circuit 10 .
  • the secondary winding is not limited to one, but can also be multiple and extend out of the first end A1 and the second end A2 after being connected in series in the same direction, so that the connection between the first end A1 and the second end A2
  • the current has the effect of multiplying, so as to improve the reliability of the detection results of the parts.
  • the zero-crossing detection circuit further includes a controller 1013.
  • the input end of the controller 1013 is connected to the trigger unit 1012 and receives the zero-crossing signal, and the output end of the controller 1013 is connected to the main Switch tube Q1; when the trigger signal outputs a zero-crossing signal, the controller 1013 controls the main switch tube Q1 to turn off.
  • the controller 1013 may use a DSP processor or a microcontroller or the like.
  • This embodiment provides a zero-crossing detection circuit, which is performed on the basis of the first embodiment.
  • the comparison unit 1011 may include a comparison switch transistor Q2 and a second resistor R2.
  • the first terminal A1 is connected to the DC source
  • the third resistor R3 is connected in series between the second terminal A2 and the positive terminal of the comparison switch Q2
  • the second resistor R2 is connected in series between the ground and the negative terminal of the comparison switch Q2.
  • the base of the comparison switch Q2 is connected to the negative terminal or grounded through the fifth resistor, and the base of the comparison switch Q2 is connected to the trigger unit 1012 .
  • the comparison switch Q2 can be any one of SI MOSFET, IGBT, GaN MOSFET, SIC MOSFET, triode, thyristor and relay, or a bidirectional switch formed by their combination. It is explained here that in the comparison unit 1011, the current flows from the positive end of the comparison switch transistor Q2 to the negative end. For example, when the comparison switch Q2 selects a PNP transistor, the positive end is the emitter, and the negative end is the collector.
  • the comparison unit 1011 includes a comparison switch tube Q2 and a second resistor R2, and the second resistor R2 is connected in series between the DC source and the forward end of the comparison switch tube Q2,
  • the third resistor R3 is connected in series between the first terminal A1 and the negative terminal of the comparison switch Q2, the second terminal A2 is grounded, and the base and the positive terminal of the comparison switch Q2 are connected or connected to the DC source through the fifth resistor, And the base of the comparison switch transistor Q2 is connected to the trigger unit 1012 .
  • the comparison switch Q2 can be any one of SI MOSFET, IGBT, GaN MOSFET, SIC MOSFET, triode, thyristor and relay, or a bidirectional switch formed by their combination, or a bidirectional switch formed by their combination. It is explained here that in the comparison unit 1011, the current flows from the positive end of the comparison switch transistor Q2 to the negative end. For example, when the comparison switch Q2 selects an NPN transistor, the positive end is the collector, and the negative end is the emitter.
  • the trigger unit 1012 includes a trigger switch tube Q3 and a fourth resistor R4, the forward end of the trigger switch tube Q3 is connected to the DC source, and the fourth resistor R4 is connected in series to the ground and the negative end of the trigger switch Q3, the base of the trigger switch Q3 can be connected to the base of the comparison switch Q2 to receive the switching signal; when the trigger unit 1012 receives the switching signal, the trigger unit 1012 is in the off state When switching to the running state, the negative terminal of the self-trigger switch tube Q3 outputs a zero-crossing signal.
  • the trigger switch Q3 can be any one of SI MOSFET, IGBT, GaN MOSFET, SIC MOSFET, triode, thyristor and relay, or a bidirectional switch formed by a combination thereof. It is explained here that in the comparison unit 1011, the current flows from the positive end of the trigger switch Q3 to the negative end. For example, when the comparison switch Q2 selects a PNP transistor, the positive end is the emitter, and the negative end is the collector.
  • the trigger unit 1012 can cooperate to output a zero-crossing signal.
  • the trigger unit 1012 includes a trigger switch tube Q3 and a fourth resistor R4, and the fourth resistor R4 is connected in series between the DC source and the forward end of the trigger switch tube Q3, The negative terminal of the trigger switch Q3 is grounded, and the base of the trigger switch Q3 is connected to the base of the comparison switch Q2 to receive the switching signal; when the trigger unit 1012 receives the switching signal, the trigger unit 1012 switches from the off state to the running state In the state and the negative terminal of the self-trigger switch tube Q3 outputs a zero-crossing signal.
  • the trigger switch tube Q3 can be any one of SI MOSFET tube, IGBT tube, GaN MOSFET tube, SIC MOSFET, triode, thyristor and relay, or a bidirectional switch formed by their combination, or a bidirectional switch formed by their combination. It is explained here that in the comparison unit 1011, the current flows from the positive end of the trigger switch Q3 to the negative end. For example, when the trigger switch Q3 selects an NPN transistor, the positive end is the collector, and the negative end is the emitter.
  • the trigger unit 1012 can cooperate to output a zero-crossing signal.
  • the comparison unit 1011 and the trigger unit 1012 have various implementation manners, and a combination of the trigger unit 1012 shown in FIG. 2 and the trigger unit 1012 shown in FIG. 4 is preferably used.
  • the circuit diagram is shown in FIG. 6 , the comparison switch Q2 and the trigger switch Q3 are both PNP triodes, and the negative current regulating circuit 101 also includes a third diode D3, the anode of which is connected to the third diode D3.
  • the collector of the trigger switch Q3 is connected, and the cathode is connected to the base of the comparison switch Q2, so as to play a protective role.
  • This embodiment provides a PFC circuit with zero-crossing detection, as shown in FIG. 7 , which includes the zero-crossing detection circuit 10 in the first embodiment and/or the second embodiment.
  • the PFC circuit with zero-crossing detection includes an AC source, a first diode D1 , a second diode D2 , a first inductor L1 , a capacitor C, a load Rx and two sets of zero-crossing detection circuits 10 .
  • the two sets of zero-crossing detection circuits 10 are respectively denoted as a first zero-crossing detection circuit and a second zero-crossing detection circuit.
  • first inductor L1 One end of the first inductor L1 is connected to the positive pole of the AC source, and the other end is marked as the connection terminal f.
  • the anode of the first diode D1 and the cathode of the second diode D2 are connected to the negative pole of the AC source.
  • the first zero-crossing The detection circuit is matched and connected between the connection terminal f and the cathode of the first diode D1
  • the second zero-crossing detection circuit is matched and connected between the connection terminal f and the anode of the second diode D2, and the capacitor C and the load Rx are both connected. It is connected in parallel between the cathode of the first diode D1 and the anode of the second diode D2.
  • the AC power supply outputs positive current or negative current in one cycle, and the positive current and negative current are not the positive current and negative current flowing through the first converter.
  • the second diode D2 When the AC source is in the positive half cycle, the second diode D2 is turned on, the main switch Q1 of the first zero-crossing detection circuit is turned off, and the main switch Q1 of the second zero-crossing detection circuit is turned on, and the current passes through the AC in turn.
  • Source-first inductor L1-second zero-crossing detection circuit-second diode D2-AC source while the first inductor L1 stores energy; when the main switch Q1 of the second zero-crossing detection circuit is turned off, the first The main switch tube Q1 of the zero-crossing detection circuit is turned on.
  • the current is the forward current of the first converter, and the current flows through the AC source - the first inductor L1 - the first zero-crossing in sequence.
  • the current is For the forward current of the first converter, please refer to the circuit diagrams shown in FIG. 6 and FIG. 7 .
  • the induced current of the current transformer CT flows out from the first terminal A1 and flows through the first resistor R1 And generate a negative voltage between the second terminal A2 and the first terminal A1, and the current flows from the second terminal A2 back to the first current transformer CT.
  • the voltage of the first terminal A1 is equal to the output voltage VCC of the DC source
  • the second terminal The voltage of A2 is equal to the voltage generated by VCC plus R1, that is, the second terminal A2 is a negative voltage relative to the first terminal A1
  • the base of the trigger switch tube Q3 outputs a high-level switching signal.
  • the main switch Q1 of the second zero-cross detection circuit When the AC source is in the negative half cycle, the main switch Q1 of the second zero-cross detection circuit is turned off, and the main switch Q1 of the first zero-cross detection circuit is turned on, in the first zero-cross detection circuit, the current is
  • the negative current of the first converter can refer to the circuit diagrams shown in FIG. 6 and FIG. 7.
  • the first zero-crossing detection circuit when the current flowing through the second diode D2 drops to zero, the second diode D2 continues to be turned on. The diode D2 makes the current of the second diode D2 increase in the negative direction.
  • the CT current induced by the current transformer flows out from the second end A2 and flows through the first resistor R1 to generate a gap between the second end A2 and the first end A1.
  • the current flows from the first terminal A1 back to the current transformer CT, the voltage of the second terminal A2 is equal to the voltage generated by VCC plus the first resistor R1, then the second terminal A2 is a positive voltage relative to the first terminal A1, when the negative voltage
  • the forward current increases to the preset value set by the first resistor R1
  • the conduction of the switch tube Q3 is triggered, and the collector of the trigger switch tube Q3 is flipped from high level to low level, thereby generating an edge signal, the edge signal That is, the zero-crossing signal, which can be captured by the controller.
  • the current is the forward current of the first converter, and the current passes through the AC source - the first diode D1 - the first zero-crossing detection circuit - the first inductor L1 - the AC source in sequence, and the first An inductor L1 stores energy; when the main switch Q1 of the first zero-crossing detection circuit is turned off, the main switch Q1 of the second zero-crossing detection circuit is turned on, and the current flows through the AC source-first diode D1- Load Rx-second zero-crossing detection circuit-first inductance L1-AC source, and the above description can be referred to for the description related to the zero-crossing detection, which will not be repeated here.
  • the first zero-crossing detection circuit when the actual waveform of the current is converted from the positive half cycle to the negative half cycle, the first zero-crossing detection circuit is turned off, and the second zero-crossing detection circuit is operated, so as to reduce the negative current in the second zero-crossing detection circuit;
  • the first zero-crossing detection circuit when the actual waveform of the current changes from the negative half cycle to the positive half cycle, the first zero-crossing detection circuit is turned off, and the second zero-crossing detection circuit is operated to reduce the negative current in the second zero-crossing detection circuit. Therefore, it can reduce the negative current in the zero-crossing detection circuit 10 after switching, and facilitate compensation of the input current distortion caused by the negative current to reduce the harmonics of the input current.
  • the PFC circuit with zero-crossing detection may further include a controller 1013 , and the main switch Q1 and trigger unit 1012 of the first zero-crossing detection circuit and the second zero-crossing detection circuit are all connected to the controller 1013 .
  • the processor is not limited to using a DSP processor or a microcontroller.
  • the processor controls the main switch Q1 of the first zero-crossing detection circuit to be turned off and the main switch Q1 of the second zero-crossing detection circuit to be turned on;
  • the processor controls the main switch Q1 of the second zero-crossing detection circuit to be turned off and the main switch Q1 of the first zero-crossing detection circuit to be turned on.
  • the technical solution facilitates the overall coordination of the first zero-crossing detection circuit and the second zero-crossing detection circuit, and the first zero-crossing detection circuit and the second zero-crossing detection circuit use the same processor, thereby reducing the frequency
  • the complexity of the PFC circuit with zero detection has the advantages of saving resources and simplifying the circuit.
  • This embodiment provides a two-way interleaved parallel PFC circuit with zero-crossing detection, as shown in FIG. 8 , which includes the zero-crossing detection circuit 10 in the first embodiment and/or the second embodiment. Specifically, it includes an AC source, a first diode D1 , a second diode D2 , a first inductor L1 , a second inductor L2 , a capacitor C, a load Rx and four sets of zero-crossing detection circuits 10 .
  • the four groups of zero-crossing detection circuits 10 are respectively denoted as a first zero-crossing detection circuit, a second zero-crossing detection circuit and a fourth zero-crossing detection circuit.
  • the anode of the first diode D1 and the cathode of the second diode D2 are both connected to the negative electrode of the AC source, and the capacitor C and the load Rx are both connected in parallel to the cathode of the first diode D1 and the anode of the second diode D2 between;
  • the first inductor L1 is connected to the positive pole of the AC source, and the other end is marked as the connection terminal f1.
  • the first zero-crossing detection circuit is matched and connected between the connection terminal f1 and the cathode of the first diode D1.
  • the second zero-crossing detection circuit The circuit is connected between the connection end f1 and the anode of the second diode D2; one end of the second inductor L2 is connected to the positive electrode of the AC source, the other end is marked as the connection end f2, and the third zero-crossing detection circuit is connected to the connection.
  • a fourth zero-crossing detection circuit is matched and connected between the connection terminal f2 and the anode of the second diode D2.
  • the two-way staggered parallel PFC circuit with zero-crossing detection may further include a controller 1013 , and the main switch Q1 and trigger unit 1012 of each zero-crossing detection circuit 10 are connected to the controller 1013 .
  • the processor is not limited to adopting a DSP processor or a microcontroller, and the specific operation of the controller 1013 can also refer to the relevant description of the PFC circuit with zero-crossing detection in the third embodiment, which will not be repeated here.

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Abstract

本发明公开一种过零检测电路，涉及过零检测技术领域，包括电流互感器、主开关管以及负向电流调节电路；电流互感器包括原边绕组和副边绕组，原边绕组和主开关管串联后构成第一变换器，第一变换器配合连接至交流源；负向电流调节电路包括第一电阻、第三电阻、比较单元、触发单元以及直流源；当第一变换器流经负向电流且负向电流的数值等于预设阈值时，副边绕组生成的感应电流经由第二端、第一电阻以及第三电阻流入比较单元，使得触发单元并输出过零信号，主开关管响应过零信号并关断。本发明还公开一种带过零检测的PFC电路和两路交错并联PFC电路。本发明在过零时输出过零信号以关断对应的主开关管，以提高结果的可靠性和系统效率。

Description

过零检测电路、PFC电路及两路交错并联PFC电路 技术领域
本发明涉及过零检测技术领域，尤其涉及一种过零检测电路、PFC电路及两路交错并联PFC电路。
背景技术
过零检测指的是：在电源系统中，波形从正半周向负半周或负半周向正半周转换，在经过零位附近时，系统输出过零信号，开关电路响应该过零信号进行相应的切换。
现有的过零检测通常采用光耦隔离或霍尔传感器等方式。但是，上述方式通常存在带宽低等问题，导致检测的过零偏离于真实的过零，使得切换后的电路中存在较大的负向电流，从而降低对应系统的可靠性。
发明内容
为了克服现有技术的不足，本发明的目的之一在于提供一种过零检测电路，其在过零时可以准确输出过零信号以关断对应的主开关管，并减小切换后的电路中的负向电流，从而提高该电路的可靠性和系统效率。
本发明的目的之一采用如下技术方案实现：一种过零检测电路，包括电流互感器、主开关管以及负向电流调节电路；其中：
所述电流互感器包括原边绕组和副边绕组，所述原边绕组和所述主开关管串联后构成第一变换器，所述第一变换器配合连接至交流源；
所述负向电流调节电路包括第一电阻、第三电阻、比较单元、触发单元以及直流源；所述比较单元和所述触发单元连接；所述直流源与所述比较单 元和所述触发单元连接；所述第一电阻和所述第三电阻串联后并连接至所述比较单元，所述副边绕组的第一端和第二端分别连接至所述第一电阻的两端；
当所述第一变换器流经负向电流且所述负向电流的数值等于预设阈值时，所述副边绕组生成的感应电流经由第二端、第一电阻以及第三电阻流入比较单元，使得所述比较单元输出切换信号，所述触发单元响应所述切换信号自截止状态切换至运行状态并输出过零信号，所述主开关管响应所述过零信号并关断。
进一步地，所述比较单元包括比较开关管和第二电阻，所述第一端与所述直流源连接，所述第三电阻串联于第二端和比较开关管的正向端之间，所述第二电阻串联于地和比较开关管的负向端之间，所述比较开关管的基极和负向端连接或经由第五电阻接地，且所述比较开关管的基极连接至所述触发单元。
进一步地，所述比较单元包括比较开关管和第二电阻，所述第二电阻串联于直流源和比较开关管的正向端之间，所述第三电阻串联于第一端和比较开关管的负向端之间，所述第二端接地，所述比较开关管的基极和正向端连接或经由第五电阻与直流源连接，且所述比较开关管的基极连接至所述触发单元。
进一步地，所述触发单元包括触发开关管和第四电阻，触发开关管的正向端与直流源连接，所述第四电阻串联于地和触发开关管的负向端之间，所述触发开关管的基极与比较开关管的基极连接；所述触发单元自截止状态切换至运行状态时，所述触发开关管的负向端输出过零信号。
进一步地，所述触发单元包括触发开关管和第四电阻，所述第四电阻串联于直流源和触发开关管的正向端之间，所述触发开关管的负向端接地，所 述触发开关管的基极与比较开关管的基极连接；所述触发单元自截止状态切换至运行状态时，所述触发开关管的正向端输出过零信号。
进一步地，负向电流调节电路还包括控制器，所述控制器的输入端连接至所述触发单元并接收所述过零信号，所述控制器的输出端连接至主开关管；当所述触发信号输出过零信号时，所述控制器控制所述主控制管关断。
本发明的目的之二在于提供一种过零检测的PFC电路，在第一过零检测电路和第二过零检测电路进行切换时，可以减小切换后的过零检测电路流经的负向电流，从而提高该电路的可靠性和系统效率。
本发明的目的之二采用如下技术方案实现：将上述的过零检测电路应用于PFC电路中，其包括交流源、第一二极管、第二二极管、第一电感、电容、负载以及两组过零检测电路；其中：
第一电感的一端连接于交流源的正极，另一端记为连接端f，所述第一二极管的阳极、所述第二二极管的阴极均与所述交流源的负极连接，第一过零检测电路配合连接于连接端f和第一二极管的阴极之间，第二过零检测电路配合连接于连接端f和第二二极管的阳极之间，所述电容和所述负载均并联于第一二极管的阴极和第二二极管的阳极之间。
进一步地，还包括控制器，所述第一过零检测电路和所述第二过零检测电路的主开关管、触发单元均与所述控制器连接；
当所述第一过零检测电路的触发单元输出过零信号时，所述控制器控制第一过零检测电路的主开关管关断、第二过零检测电路的主开关管导通；当所述第二过零检测电路的触发单元输出过零信号时，所述控制器控制第二过零检测电路的主开关管关断、第一过零检测电路的主开关管导通。
进一步地，所述第一过零检测电路和所述第二过零检测电路的主开关管、 比较开关管以及触发开关管均为SI MOSFET管、IGBT管、GaN MOSFET管、SIC MOSFET、三极管、晶闸管和继电器中的任一种，或者它们的组合构成的双向开关。
本发明的目的之三在于提供一种带过零检测的两路交错并联PFC电路，在第一过零检测电路和第二过零检测电路进行切换、第三过零检测电路和第四过零检测电路进行切换时，可以减小切换后的过零检测电路流经的负向电流，从而提高该电路的可靠性。
本发明的目的之三采用如下技术方案实现：将上述的过零检测电路应用于两路交错并联PFC电路中，其包括交流源、第一二极管、第二二极管、第一电感、第二电感、电容、负载以及四组过零检测电路；其中：
第一二极管的阳极、第二二极管的阴极均与所述交流源的负极连接，所述电容和负载均并联于第一二极管的阴极和第二二极管的阳极之间；
第一电感的一端连接于交流源的正极，另一端记为连接端f1，第一过零检测电路配合连接于所述连接端f1和第一二极管的阴极之间，第二过零检测电路配合连接于所述连接端f1和第二二极管的阳极之间；
第二电感的一端连接于交流源的正极，另一端记为连接端f2，第三过零检测电路配合连接于所述连接端f2和第一二极管的阴极之间，第四过零检测电路配合连接于所述连接端f2和第二二极管的阳极之间。
相比现有技术，本发明的有益效果在于：
在该过零检测电路中，当第一变换器流经负向电流且负向电流的数值等于预设阈值时，该触发单元对应输出过零信号，即此时的第一变换器中不存在续流，从而减小切换后的电路流经的负向电流，并为后续的软件开发提供可靠的基础；通过第三电阻的更换，以调节比较单元的预设阈值，以便于与 实际情况更为贴合，进而提高该过零检测电路的灵活性；
在PFC电路中，当电感电流的实际波形从正半周向负半周转换时，第一过零检测电路截止，第二过零检测电路运行，以减小第二过零检测电路中的负向电流；对应的，当电流的实际波形从负半周向正半周转换时，第一过零检测电路截止，第二过零检测电路运行，以减小第二过零检测电路中的负向电流。因此，其可以减小切换后的过零检测电路中的负向电流，并便于补偿由于负向电流引起的输入电流畸变、以减小输入电流谐波。
附图说明
图1为实施例一所示过零检测电路的电路图；
图2为实施例二所示比较单元的一种实现方式的电路图；
图3为实施例二所示比较单元的另一种实现方式的电路图；
图4为实施例二所示触发单元的一种实现方式的电路图；
图5为实施例二所示触发单元的另一种实现方式的电路图；
图6为实施例二所示负向电流调节电路的电路图；
图7为实施例三所示带过零检测的PFC电路的电路图；
图8为实施例四所示带过零检测的两路交错并联PFC电路的电路图。
图中：10、过零检测电路；101、负向电流调节电路；1011、比较单元；1012、触发单元；1013、控制器。
具体实施方式
以下将结合附图，对本发明进行更为详细的描述，需要说明的是，以下参照附图对本发明进行的描述仅是示意性的，而非限制性的。各个不同实施例之间可以进行相互组合，以构成未在以下描述中示出的其他实施例。
实施例一
本实施例提供了一种过零检测电路，旨在解决“对于存在续流的元器件的电路而言，难以准确地确定过零”的问题。具体地，参照图1所示，该过零检测电路10包括电流互感器CT、主开关管Q1以及负向电流调节电路101。
电流互感器CT包括原边绕组和副边绕组，原边绕组和主开关管Q1串联后构成第一变换器，第一变换器配合连接至交流源。原边绕组具有同名端和异名端，在此将电流自原边绕组的异名端流向同名端的电流记为该过零检测电路的正向电流，反之将电流自原边绕组的同名端流向异名端的电流记为该过零检测电路的负向电流。副边绕组也具有同名端和异名端，其中第一端A1可以为该副边绕组的同名端，第二端A2为可以副边绕组的异名端，且在第一变换器流经正向电流时，副边绕组生成的的感应电流自第一端A1流出，并经由负向调节电路101后自第二端A2流入；反之，在第二变换器流经负向电流时，副边绕组生成的感应电流自第二端A2流出，并经由负向调节电路101后自第一端A1流入。
负向电流调节电路101包括第一电阻R1、第三电阻R3、比较单元1011、触发单元1012以及直流源。其中第一电阻R1串联于第一端A1和第二端A2之间，当第一变换器流经正向电流时，该第一电阻R1可以视为下拉电阻，使得第二端A2的电压低于第一端A1的电压；当第二变换器流经负向电流时，该第一电阻R1可以视为上拉电阻，使得第二端A2的电压高于第一端A1的电压。
第三电阻R3的一端可以与第一电阻R1的任意一端连接，且第一电阻R1和第二电阻R3均连接于比较单元1011中，该比较单元1011根据第三电阻R3的阻值设置有预设阈值，因此该第三电阻R3可以选用滑动变阻器等电 阻值可调的电阻器件。
当第一变换器流经正向电流时，副边绕组产生的感应电流自第一端A1流出，并经过负向电流调节电路101后自第二端A2输入，此时比较单元1011未输出切换信号，则触发单元1012处于截止状态；
当第一变换器流经负向电流且数值小于预设阈值时，副边绕组产生的感应电流自第二端A2流出，并经过负向电流调节电路后自第一端A1输入，此时比较单元1011仍未输出切换信号，则触发单元1012仍处于截止状态。
当第一变换器流经负向电流且数值等于预设阈值时，副边绕组产生的感应电流自第二端A2流出，并经过负向电流调节电路后自第一端A1输入，此时比较单元1011还输出切换信号，则触发单元1012响应该切换信号并自截止状态切换至运行状态，同时输出过零信号。
该主开关管Q1响应过零信号并关断，以使得第一变换器截止。在此说明的是，该主开关管Q1可以为SI MOSFET管、IGBT管、GaN MOSFET管、SIC MOSFET、三极管、晶闸管和继电器中的任一种，或者它们的组合构成的双向开关。
综上，在该过零检测电路10中，当第一变换器流经负向电流且负向电流的数值等于预设阈值时，该触发单元1012对应输出过零信号，即此时的第一变换器中不存在续流，从而减小切换后的电路流经的负向电流，并为后续的软件开发提供可靠的基础；通过第三电阻R3的更换，以调节比较单元1011的预设阈值，以便于与实际情况更为贴合，进而提高该过零检测电路10的灵活性。
在此值得说明的是，该副边绕组不限于一个，也可以是多个并在同向串联后延伸出第一端A1和第二端A2，从而对第一端A1和第二端A2的电流 起到成倍放大的效果，以便于提高零件检测结果的可靠度。
作为可选的技术方案，参照图1所示，该过零检测电路还包括控制器1013，控制器1013的输入端连接至触发单元1012并接收过零信号，控制器1013的输出端连接至主开关管Q1；当触发信号输出过零信号时，控制器1013控制主开关管Q1关断。该控制器1013可以采用DSP处理器或微控制器等。
实施例二
本实施例提供一种过零检测电路，本实施例在实施例一的基础上进行的。
参照图1和图2所示，比较单元1011可以包括比较开关管Q2和第二电阻R2。其中，第一端A1与直流源连接，第三电阻R3串联于第二端A2和比较开关管Q2的正向端之间，第二电阻R2串联于地和比较开关管Q2的负向端之间，比较开关管Q2的基极和负向端连接或经由第五电阻后接地，且比较开关管Q2的基极连接至触发单元1012。
该比较开关管Q2可以为SI MOSFET管、IGBT管、GaN MOSFET管、SIC MOSFET、三极管、晶闸管和继电器中的任一种，或者它们的组合构成的双向开关。在此说明的是，在该比较单元1011中，电流自比较开关管Q2的正向端流向负向端。例如当比较开关管Q2选用PNP三极管时，则正向端为发射极，负向端为集电极。
通过该技术方案，当第一变换器的负向电流增大至预设阈值时，则第二端A2的电压也配合增大至符合比较开关管Q2的导通范围，从而该比较开关管Q2输出高电平至触发单元1012，其即为切换信号。
作为可选的技术方案，参照图1和图3所示，比较单元1011包括比较开关管Q2和第二电阻R2，第二电阻R2串联于直流源和比较开关管Q2的正向端之间，第三电阻R3串联于第一端A1和比较开关管Q2的负向端之间，第 二端A2接地，述比较开关管Q2的基极和正向端连接或经由第五电阻与直流源连接，且比较开关管Q2的基极连接至触发单元1012。
该比较开关管Q2可以为SI MOSFET管、IGBT管、GaN MOSFET管、SIC MOSFET、三极管、晶闸管和继电器中的任一种，或者它们的组合构成的双向开关，或者它们的组合构成的双向开关。在此说明的是，在该比较单元1011中，电流自比较开关管Q2的正向端流向负向端。例如当比较开关管Q2选用NPN三极管时，则正向端为集电极，负向端为发射极。
通过该技术方案，当第一变换器的负向电流增大至预设阈值时，则第一端A1的电压也配合减小至符合比较开关管Q2的导通范围，从而该比较开关管Q2输出高电平至触发单元1012，其即为切换信号。
作为可选的技术方案，参照图1和图4所示，触发单元1012包括触发开关管Q3和第四电阻R4，触发开关管Q3的正向端与直流源连接，第四电阻R4串联于地和触发开关管Q3的负向端之间，触发开关管Q3的基极可以与比较开关管Q2的基极连接，以接收切换信号；当触发单元1012接收切换信号时，触发单元1012自截止状态切换至运行状态时且自触发开关管Q3的负向端输出过零信号。
该触发开关管Q3可以为SI MOSFET管、IGBT管、GaN MOSFET管、SIC MOSFET、三极管、晶闸管和继电器中的任一种，或者它们的组合构成的双向开关。在此说明的是，在该比较单元1011中，电流自触发开关管Q3的正向端流向负向端。例如当比较开关管Q2选用PNP三极管时，则正向端为发射极，负向端为集电极。
通过该技术方案，当第一变换器的负向电流增大至预设阈值时，该触发单元1012可以配合输出过零信号。
作为可选的技术方案，参照图1和图5所示，触发单元1012包括触发开关管Q3和第四电阻R4，第四电阻R4串联于直流源和触发开关管Q3的正向端之间，触发开关管Q3的负向端接地，触发开关管Q3的基极与比较开关管Q2的基极连接，以接收切换信号；当触发单元1012接收切换信号时，触发单元1012自截止状态切换至运行状态时且自触发开关管Q3的负向端输出过零信号。
该触发开关管Q3可以为SI MOSFET管、IGBT管、GaN MOSFET管、SIC MOSFET、三极管、晶闸管和继电器中的任一种，或者它们的组合构成的双向开关，或者它们的组合构成的双向开关。在此说明的是，在该比较单元1011中，电流自触发开关管Q3的正向端流向负向端。例如当触发开关管Q3选用NPN三极管时，则正向端为集电极，负向端为发射极。
通过该技术方案，当第一变换器的负向电流增大至预设阈值时，该触发单元1012可以配合输出过零信号。
作为可选的技术方案，该实施例中比较单元1011和触发单元1012具有多种实现方式，其中优选采用图2所示的触发单元1012和图4所示的触发单元1012的组合，组合后的电路图如图6所示，该比较开关管Q2和触发开关管Q3均采用PNP三级管，该负向电流调节电路101还包括第三二极管D3，该第三二极管D3的阳极与触发开关管Q3的集电极连接，阴极与比较开关管Q2的基极连接，从而起到保护作用。
实施例三
本实施例提供一种带过零检测的PFC电路，参照图7所示，其包括上述实施例一和/或实施例二中的过零检测电路10。具体地，该带过零检测的PFC电路包括交流源、第一二极管D1、第二二极管D2、第一电感L1、电容C、 负载Rx以及两组过零检测电路10。将两组过零检测电路10分别记为第一过零检测电路和第二过零检测电路。
第一电感L1的一端连接于交流源的正极，另一端记为连接端f，第一二极管D1的阳极、第二二极管D2的阴极均与交流源的负极连接，第一过零检测电路配合连接于连接端f和第一二极管D1的阴极之间，第二过零检测电路配合连接于连接端f和第二二极管D2的阳极之间，电容C和负载Rx均并联于第一二极管D1的阴极和第二二极管D2的阳极之间。
在此值得说明的是，交流电源的一个周期内输出正电流或负电流，该正电流和负电流并不是第一变换器流经的正向电流和负向电流。
当交流源处于正半周时，第二二极管D2导通，第一过零检测电路的主开关管Q1关断、第二过零检测电路的主开关管Q1导通，该电流依次经过交流源-第一电感L1-第二过零检测电路-第二二极管D2-交流源，同时第一电感L1储能；当第二过零检测电路的主开关管Q1关断时、第一过零检测电路的主开关管Q1导通，在第一过零检测电路中，该电流即为第一变换器的正向电流，电流依次流经交流源-第一电感L1-第一过零检测电路-负载Rx-第二二极管D2-交流源。
当交流源处于正半周、第二过零检测电路的主开关管Q1关断时、第一过零检测电路的主开关管Q1导通时，在第一过零检测电路中，该电流即为第一变换器的正向电流，可以参照图6和图7所示的电路图，在第一过零检测电路中，电流互感器CT的感应电流从第一端A1流出，流经第一电阻R1并产生第二端A2与第一端A1之间负电压，电流从第二端A2流回第一电流互感器CT，此时第一端A1的电压等于直流源的输出电压VCC，第二端A2的电压等于VCC加上R1上产生的电压，既第二端A2相对第一端A1为负 电压，触发开关管Q3基极输出为高电平的切换信号。
当交流源处于负半周、第二过零检测电路的主开关管Q1关断时、第一过零检测电路的主开关管Q1导通时，在第一过零检测电路中，该电流即为第一变换器的负向电流，该可以参照图6和图7所示的电路图，在第一过零检测电路中，当流经第二二极管D2电流下降至零时继续导通第二二极管D2，使第二二极管D2电流负向增加，此时电流互感器感应CT电流从第二端A2流出，流经第一电阻R1产生第二端A2与第一端A1之间正电压，电流从第一端A1流回电流互感器CT，第二端A2电压等于VCC加上第一电阻R1上产生的电压，则第二端A2相对第一端A1为正电压，当负向电流增加到通过第一电阻R1设置的预设值时，触发开关管Q3的导通，且触发开关管Q3的集电极自高电平翻转为低电平，从而产生边沿信号，该边沿信号即为过零信号，该过零信号可以经由控制器捕捉。
反之，当交流源处于负半周时，第一二极管D1导通，第二过零检测电路的主开关管Q1关断、第一过零检测电路的主开关管Q1导通，在第二过零检测电路中，该电流即为第一变换器的正向电流，该电流依次经过交流源-第一二极管D1-第一过零检测电路-第一电感L1-交流源，同时第一电感L1储能；当第一过零检测电路的主开关管Q1关断时、第二过零检测电路的主开关管Q1导通，电流依次流经交流源-第一二极管D1-负载Rx-第二过零检测电路-第一电感L1-交流源，其中与过零检测相关说明的可以参照上述说明，在此不做赘述。
通过该技术方案，当电流的实际波形从正半周向负半周转换时，第一过零检测电路截止，第二过零检测电路运行，以减小第二过零检测电路中的负向电流；对应的，当电流的实际波形从负半周向正半周转换时，第一过零检 测电路截止，第二过零检测电路运行，以减小第二过零检测电路中的负向电流。因此，其可以减小切换后的过零检测电路10中的负向电流，并便于补偿由于负向电流引起的输入电流畸变、以减小输入电流谐波。
作为可选的技术方案，该带过零检测的PFC电路还可以包括控制器1013，第一过零检测电路和第二过零检测电路的主开关管Q1、触发单元1012均与控制器1013连接。该处理器不限于采用DSP处理器或微控制器。
当第一过零检测电路的触发单元1012输出过零信号时，处理器控制第一过零检测电路的主开关管Q1关断、第二过零检测电路的主开关管Q1导通；当第二过零检测电路的触发单元1012输出过零信号时，处理器控制第二过零检测电路的主开关管Q1关断、第一过零检测电路的主开关管Q1导通。
通过该技术方案，便于对第一过零检测电路和第二过零检测电路进行统筹协调，且第一过零检测电路和第二过零检测电路对用同一处理器，从而降低了该带过零检测的PFC电路的复杂度，起到了节约资源、简化线路的优点。
实施例四
本实施例提供一种带过零检测的两路交错并联PFC电路，参照图8所示，其包括上述实施例一和/或实施例二中的过零检测电路10。具体地，其包括交流源、第一二极管D1、第二二极管D2、第一电感L1、第二电感L2、电容C、负载Rx以及四组过零检测电路10。将四组过零检测电路10分别记为第一过零检测电路、第二过零检测电路以及第四过零检测电路。
第一二极管D1的阳极、第二二极管D2的阴极均与交流源的负极连接，电容C和负载Rx均并联于第一二极管D1的阴极和第二二极管D2的阳极之间；
第一电感L1的一端连接于交流源的正极，另一端记为连接端f1，第一 过零检测电路配合连接于连接端f1和第一二极管D1的阴极之间，第二过零检测电路配合连接于连接端f1和第二二极管D2的阳极之间；第二电感L2的一端连接于交流源的正极，另一端记为连接端f2，第三过零检测电路配合连接于连接端f2和第一二极管D1的阴极之间，第四过零检测电路配合连接于连接端f2和第二二极管D2的阳极之间。
本实施例的带过零检测的两路交错并联PFC电路的具体运行可以参照实施例三中的带过零检测的PFC电路的说明，在此不再赘述。
作为可选的技术方案，该带过零检测的两路交错并联PFC电路还可以包括控制器1013，各个过零检测电路10主开关管Q1、触发单元1012均与控制器1013连接。该处理器不限于采用DSP处理器或微控制器，该控制器1013的具体运行也具体运行也可以参照实施例三中的带过零检测的PFC电路的相关说明，在此不再赘述。
上述实施方式仅为本发明的优选实施方式，不能以此来限定本发明保护的范围，本领域的技术人员在本发明的基础上所做的任何非实质性的变化及替换均属于本发明所要求保护的范围。

Claims (10)

  1. 一种过零检测电路，其特征在于，包括电流互感器、主开关管以及负向电流调节电路；其中：
    所述电流互感器包括原边绕组和副边绕组，所述原边绕组和所述主开关管串联后构成第一变换器，所述第一变换器配合连接至交流源；
    所述负向电流调节电路包括第一电阻、第三电阻、比较单元、触发单元以及直流源；所述比较单元和所述触发单元连接；所述直流源与所述比较单元和所述触发单元连接；所述第一电阻和所述第三电阻串联后并连接至所述比较单元，所述副边绕组的第一端和第二端分别连接至所述第一电阻的两端；
    当所述第一变换器流经负向电流且所述负向电流的数值等于预设阈值时，所述副边绕组生成的感应电流经由第二端、第一电阻以及第三电阻流入比较单元，使得所述比较单元输出切换信号，所述触发单元响应所述切换信号自截止状态切换至运行状态并输出过零信号，所述主开关管响应所述过零信号并关断。
  2. 根据权利要求1所述的过零检测电路，其特征在于，所述比较单元包括比较开关管和第二电阻，所述第一端与所述直流源连接，所述第三电阻串联于第二端和比较开关管的正向端之间，所述第二电阻串联于地和比较开关管的负向端之间，所述比较开关管的基极和负向端连接或经由第五电阻接地，且所述比较开关管的基极连接至所述触发单元。
  3. 根据权利要求1所述的过零检测电路，其特征在于，所述比较单元包括比较开关管和第二电阻，所述第二电阻串联于直流源和比较开关管的正向端之间，所述第三电阻串联于第一端和比较开关管的负向端之间，所述第二端接地，所述比较开关管的基极和正向端连接或经由第五电阻与直流源连接， 且所述比较开关管的基极连接至所述触发单元。
  4. 根据权利要求2或3所述的过零检测电路，其特征在于，所述触发单元包括触发开关管和第四电阻，触发开关管的正向端与直流源连接，所述第四电阻串联于地和触发开关管的负向端之间，所述触发开关管的基极与比较开关管的基极连接；所述触发单元自截止状态切换至运行状态时，所述触发开关管的负向端输出过零信号。
  5. 根据权利要求2或3所述的过零检测电路，其特征在于，所述触发单元包括触发开关管和第四电阻，所述第四电阻串联于直流源和触发开关管的正向端之间，所述触发开关管的负向端接地，所述触发开关管的基极与比较开关管的基极连接；所述触发单元自截止状态切换至运行状态时，所述触发开关管的正向端输出过零信号。
  6. 根据权利要求1所述的过零检测电路，其特征在于，负向电流调节电路还包括控制器，所述控制器的输入端连接至所述触发单元并接收所述过零信号，所述控制器的输出端连接至主开关管；当所述触发信号输出过零信号时，所述控制器控制所述主控制管关断。
  7. 一种带过零检测的PFC电路，其特征在于，将权利要求1-5任一项所述的过零检测电路应用于PFC电路中，其包括交流源、第一二极管、第二二极管、第一电感、电容、负载以及两组过零检测电路；其中：
    第一电感的一端连接于交流源的正极，另一端记为连接端f，所述第一二极管的阳极、所述第二二极管的阴极均与所述交流源的负极连接，第一过零检测电路配合连接于连接端f和第一二极管的阴极之间，第二过零检测电 路配合连接于连接端f和第二二极管的阳极之间，所述电容和所述负载均并联于第一二极管的阴极和第二二极管的阳极之间。
  8. 根据权利要求7所述的带过零检测的PFC电路，其特征在于，还包括控制器，所述第一过零检测电路和所述第二过零检测电路的主开关管、触发单元均与所述控制器连接；
    当所述第一过零检测电路的触发单元输出过零信号时，所述控制器控制第一过零检测电路的主开关管关断、第二过零检测电路的主开关管导通；当所述第二过零检测电路的触发单元输出过零信号时，所述控制器控制第二过零检测电路的主开关管关断、第一过零检测电路的主开关管导通。
  9. 根据权利要求8所述的带过零检测的PFC电路，其特征在于，所述第一过零检测电路和所述第二过零检测电路的主开关管、比较开关管以及触发开关管均为SI MOSFET管、IGBT管、GaN MOSFET管、SIC MOSFET、三极管、晶闸管和继电器中的任一种，或者它们的组合构成的双向开关。
  10. 一种带过零检测的两路交错并联PFC电路，其特征在于，将权利要求1-6任一项所述的过零检测电路应用于两路交错并联PFC电路中，其包括交流源、第一二极管、第二二极管、第一电感、第二电感、电容、负载以及四组过零检测电路；其中：
    第一二极管的阳极、第二二极管的阴极均与所述交流源的负极连接，所述电容和负载均并联于第一二极管的阴极和第二二极管的阳极之间；
    第一电感的一端连接于交流源的正极，另一端记为连接端f1，第一过零检测电路配合连接于所述连接端f1和第一二极管的阴极之间，第二过零检测电路配合连接于所述连接端f1和第二二极管的阳极之间；
    第二电感的一端连接于交流源的正极，另一端记为连接端f2，第三过零检测电路配合连接于所述连接端f2和第一二极管的阴极之间，第四过零检测电路配合连接于所述连接端f2和第二二极管的阳极之间。
PCT/CN2021/104092 2020-08-03 2021-07-01 过零检测电路、pfc电路及两路交错并联pfc电路 WO2022028168A1 (zh)

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Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN115453187A (zh) * 2022-09-14 2022-12-09 联桥科技有限公司 一种非隔离的交流电压过零检测电路

Families Citing this family (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN112039315B (zh) * 2020-08-03 2021-11-05 杭州中恒电气股份有限公司 过零检测电路、pfc电路及两路交错并联pfc电路
CN115588988A (zh) * 2022-11-08 2023-01-10 阳光电源股份有限公司 一种变换器及其过零点控制方法

Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN102545582A (zh) * 2012-02-09 2012-07-04 华为技术有限公司 无桥功率因数校正电路及其控制方法
US20130249504A1 (en) * 2012-03-25 2013-09-26 Niko Semiconductor Co., Ltd. Power factor correction (pfc) controller and bridgeless pfc circuit with the same
CN103475195A (zh) * 2013-08-29 2013-12-25 华为技术有限公司 一种同步整流控制电路及同步整流控制方法
CN104237615A (zh) * 2013-06-09 2014-12-24 中兴通讯股份有限公司 电流过零检测装置、信号获取电路及电路系统
CN112039315A (zh) * 2020-08-03 2020-12-04 杭州中恒电气股份有限公司 过零检测电路、pfc电路及两路交错并联pfc电路

Family Cites Families (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN108448913B (zh) * 2018-03-07 2020-01-07 浙江大学 一种单级式基于交错并联无桥pfc电路和llc谐振的隔离型ac-dc变换器
CN110365203B (zh) * 2019-06-19 2021-07-09 广州金升阳科技有限公司 电流采样电路、电流过零检测电路、图腾柱无桥pfc电路及其控制方法

Patent Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN102545582A (zh) * 2012-02-09 2012-07-04 华为技术有限公司 无桥功率因数校正电路及其控制方法
US20130249504A1 (en) * 2012-03-25 2013-09-26 Niko Semiconductor Co., Ltd. Power factor correction (pfc) controller and bridgeless pfc circuit with the same
CN104237615A (zh) * 2013-06-09 2014-12-24 中兴通讯股份有限公司 电流过零检测装置、信号获取电路及电路系统
CN103475195A (zh) * 2013-08-29 2013-12-25 华为技术有限公司 一种同步整流控制电路及同步整流控制方法
CN112039315A (zh) * 2020-08-03 2020-12-04 杭州中恒电气股份有限公司 过零检测电路、pfc电路及两路交错并联pfc电路

Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN115453187A (zh) * 2022-09-14 2022-12-09 联桥科技有限公司 一种非隔离的交流电压过零检测电路

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