WO2021092816A1 - 互调干扰信号的重构方法和装置 - Google Patents

互调干扰信号的重构方法和装置 Download PDF

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Publication number
WO2021092816A1
WO2021092816A1 PCT/CN2019/118230 CN2019118230W WO2021092816A1 WO 2021092816 A1 WO2021092816 A1 WO 2021092816A1 CN 2019118230 W CN2019118230 W CN 2019118230W WO 2021092816 A1 WO2021092816 A1 WO 2021092816A1
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sequence
frequency point
interference
frequency
intermodulation interference
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PCT/CN2019/118230
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English (en)
French (fr)
Inventor
张治�
胡荣贻
邢金强
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Oppo广东移动通信有限公司
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Priority to PCT/CN2019/118230 priority Critical patent/WO2021092816A1/zh
Priority to CN201980098178.5A priority patent/CN114073012B/zh
Publication of WO2021092816A1 publication Critical patent/WO2021092816A1/zh

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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/06—Receivers
    • H04B1/10—Means associated with receiver for limiting or suppressing noise or interference
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/06—Receivers
    • H04B1/10—Means associated with receiver for limiting or suppressing noise or interference
    • H04B1/12—Neutralising, balancing, or compensation arrangements

Definitions

  • This application relates to the field of communication technology, and in particular to a method and device for reconstructing intermodulation interference signals, electronic equipment, chips, and non-volatile computer storage media.
  • OFDM Orthogonal Frequency Division Multiplexing
  • a technical problem to be solved by some embodiments of the present invention is that the intermodulation interference signal can be reconstructed, which can then be used to eliminate intermodulation interference in a multi-carrier system.
  • An embodiment of the present application provides a method for reconstructing an intermodulation interference signal.
  • the method includes: obtaining a digital downlink signal containing useful signals and intermodulation interference signals; selecting an amplitude calculation model corresponding to each frequency point in the frequency band where the useful signal is located from a model library, and based on the local uplink signal and the baseband The selected amplitude calculation model determines the amplitude of each frequency point in the intermodulation interference sequence; based on the gain of the intermodulation interference channel at each frequency point and the amplitude of each frequency point in the intermodulation interference sequence, the intermodulation interference signal is reconstructed .
  • the model library includes the amplitude calculation model corresponding to each frequency point that produces intermodulation interference.
  • An embodiment of the present application also provides a device for reconstructing intermodulation interference signals.
  • the device includes: an acquisition module, a selection module, an amplitude calculation module and a reconstruction module.
  • the acquisition module is used to acquire the digital downlink signal containing useful signals and intermodulation interference signals;
  • the selection module is used to select the amplitude calculation model corresponding to each frequency point in the frequency band where the useful signal is located from the model library;
  • the amplitude calculation The module is used to determine the amplitude of each frequency point in the intermodulation interference sequence based on the local uplink signal in the form of baseband and the selected amplitude calculation model;
  • the reconstruction module is used to determine the gain and intermodulation of each frequency point based on the intermodulation interference channel
  • the amplitude of each frequency point in the interference sequence is used to reconstruct the intermodulation interference signal.
  • the model library includes the amplitude calculation model corresponding to each frequency point that produces intermodulation interference.
  • An embodiment of the present application also provides a non-volatile computer storage medium that stores a program executable by a processor. When the program is executed by the processor, the aforementioned method for reconstructing intermodulation interference signals is implemented.
  • An embodiment of the present application also provides an electronic device, including: at least one processor; and a memory communicatively connected with the at least one processor; wherein the memory stores one or more programs that can be executed by the at least one processor.
  • One or more programs contain instructions, which when executed by at least one processor, cause at least one processor to perform the aforementioned method for reconstructing intermodulation interference signals.
  • An embodiment of the present application also provides a chip, including: at least one processor; and a memory communicatively connected with the at least one processor.
  • the memory stores one or more programs that can be executed by at least one processor; the one or more programs contain instructions that, when executed by at least one processor, cause at least one processor to execute the aforementioned intermodulation interference signal The reconstruction method.
  • the intermodulation interference sequence is obtained according to the pre-established amplitude calculation model and the local uplink signal in the form of baseband, and combined with the estimation of the intermodulation interference channel, Reconstructing the intermodulation interference signal can more accurately reconstruct the intermodulation interference signal, and then can eliminate the intermodulation interference in the multi-carrier system.
  • Fig. 1 is a scenario where intermodulation interference is generated according to an embodiment.
  • Fig. 2 is a flowchart of a method for reconstructing an intermodulation interference signal according to an embodiment.
  • Fig. 3 is a diagram of functional modules involved in a method for reconstructing an intermodulation interference signal according to an embodiment.
  • Fig. 4 is a flowchart of a model establishment process in a method for reconstructing an intermodulation interference signal according to an embodiment.
  • Fig. 5 is a schematic diagram of a convolution operation process in a method for reconstructing an intermodulation interference signal according to an embodiment.
  • Fig. 6 is a block diagram of an intermodulation interference signal reconstruction device according to an embodiment.
  • Fig. 7 is a cascaded schematic diagram of the analog domain and digital domain intermodulation interference cancellation in an electronic device according to an embodiment.
  • Fig. 8 is a schematic structural diagram of an electronic device according to an embodiment.
  • This application mainly solves the problem of potential intermodulation interference caused by uplink transmission to downlink reception in a multi-carrier system.
  • Figure 1 a typical scenario where intermodulation interference is generated with obvious power is shown.
  • the electronic device shown in the figure has a transmitting antenna TA and a receiving antenna RA, which can transmit signals on the frequency band Band1 and Band2, and receive signals on the frequency band Band.
  • the generation mechanism and propagation link of intermodulation interference are very complicated.
  • Intermodulation interference is mainly caused by non-linear devices in the link, such as power amplifiers PA1 and PA2.
  • the possible propagation link is: the local uplink signal sent by the baseband chip (Baseband IC) enters the radio frequency chip for modulation and other processing, after passing through the power amplifier PA1, the high-power signal in it passes through the printed circuit board (Printed circuit board, referred to as "PCB") leaks to the input port of the power amplifier PA2, passes through the amplifier together with the input signal to produce multi-tone mixing, and then passes through the signal transmission link and is transmitted by the transmitting antenna and received by the receiving antenna. On the other hand, it radiates to the receiving end through the link.
  • PCB printed circuit board
  • the received signal entering the radio frequency chip may not only include the useful signal from the base station, but also may include the local uplink signal generated through the propagation link.
  • the intermodulation interference signal may not only include the useful signal from the base station, but also may include the local uplink signal generated through the propagation link.
  • Time-frequency scheduling and other technologies have been used to solve the problem of intermodulation self-interference.
  • Time-frequency scheduling needs to suspend the transmission or reception of one end according to the interference intensity, time slot ratio, etc., and even involve more complicated network transformations. The problem will reduce the throughput of the system and affect the peak network speed.
  • the research direction is to add an interference cancellation module in the transceiver to eliminate (or suppress) intermodulation from the received signal.
  • Self-interference and the specific explanation is as follows.
  • the received signal entering the baseband processor includes the demodulated received signal and the intermodulation interference signal, and the local uplink signal (transmission signal) corresponding to the intermodulation interference signal is the signal that the electronic device is sending. And its baseband form is known to this electronic device. If the intermodulation interference signal can be estimated according to the baseband form of the local uplink signal of the electronic device, and this estimated intermodulation interference signal can be subtracted from the received signal, the useful signal can be easily obtained.
  • intermodulation interference channel
  • the intermodulation interference channel should also include all the devices involved in the processing of the baseband signal inside the radio frequency chip, as well as the radio frequency. All devices involved in the demodulation of the received signal within the chip. For example, the nonlinear characteristics of radio frequency devices are a factor that causes intermodulation interference.
  • the estimated intermodulation interference signal can be obtained based on the local uplink signal in the form of baseband and the estimated intermodulation interference channel. Based on this, this application provides a method for reconstructing intermodulation interference signals. By estimating the intermodulation interference channel and combining the local uplink signal in the form of baseband to reconstruct the intermodulation interference signal, the reconstructed intermodulation interference signal can be used. Eliminate intermodulation interference signals from the received signal.
  • a method for reconstructing intermodulation interference signals is provided, as shown in FIG. 2.
  • This method can be used in multi-carrier systems that use specific frequency bands, such as long-term evolution (Long Term Evolution, "LTE") systems that use carrier aggregation (Carrier Aggregation, "CA”), or LTE and New Radio (New Radio) systems. , Referred to as "NR") concurrent system.
  • LTE Long-term Evolution
  • CA Carrier Aggregation
  • NR New Radio
  • this application is not limited to the examples here, and any system involving at least two carrier frequency bands should fall within the protection scope of this application. Take a system involving two carrier frequency bands as an example.
  • one of the two carrier frequency bands is called the first frequency band or high frequency band, and the other frequency band is called the second frequency band or low frequency band.
  • the carrier frequency of is higher than the carrier frequency in the second frequency band.
  • step 201 a digital downlink signal is acquired.
  • the digital downstream signal can be obtained by directly sampling the output signal of the radio frequency IC, for example, by using an analog-to-digital converter (ADC) to sample.
  • ADC analog-to-digital converter
  • step 202 an amplitude calculation model corresponding to each frequency point in the frequency band where the useful signal is located is selected from the model library.
  • the model library includes an amplitude calculation model corresponding to each frequency point that generates intermodulation interference.
  • a variety of models can be used, such as polynomial models, Hammerstein models, and so on. However, this application should not be limited to the two models listed here, and I will not list them one by one here.
  • Each frequency point in the model library can be obtained through analysis or actual measurement in advance, and the amplitude calculation model corresponding to each frequency point is derived through modeling.
  • the amplitude calculation model corresponding to each frequency point involves the superposition of each amplitude in the baseband sequence corresponding to at least two carrier frequency bands involved in the multi-carrier system.
  • the inventor also discovered in the research process that only the frequency or frequency band of the intermodulation product of the local uplink signal falls on the frequency point of the useful signal or falls within the frequency band of the useful signal, will the received signal be affected. Make an impact. For example, if the intermodulation interference signal generated is in the frequency band [1-5] and the receiving frequency band is in the frequency band [8-12], there will be no substantial interference. On the one hand, after passing through the intermodulation interference channel, the frequency band of the local uplink signal will be widened. The expanded frequency band may only partially overlap with the receiving frequency band. The intermodulation interference signal falling into this overlapped part actually causes the received signal. interference.
  • the intermodulation interference is relatively weak, and the interference signal at some frequency points is very weak, which may not cause actual interference to the received signal. Therefore, the amplitude calculation model can be selected according to the frequency point or frequency band of the useful signal, so as to more accurately reconstruct the intermodulation interference signal.
  • step 203 the amplitude of each frequency point in the intermodulation interference sequence is determined based on the local uplink signal in the form of baseband and the selected amplitude calculation model.
  • the local uplink signal in the form of baseband can be obtained from the transmitting end.
  • the local uplink signal in the form of baseband can be directly divided into two channels, one is sent to the radio frequency chip, and the other is led to the receiving end.
  • the time delay between signal transmission and reconstruction intermodulation interference is measured.
  • the delay adjustment is performed on the link leading to the receiving end.
  • the local uplink signal in the form of baseband is used as data
  • the form of flow leads to the receiving end.
  • the local uplink signal in the form of baseband can be stored in a memory when the baseband processor sends the local uplink signal to the radio frequency chip.
  • the local uplink signal in the baseband form can be directly read from the memory.
  • the read local uplink signal in the form of baseband and the digital downlink signal are synchronously measured, and the correlation between the signals at both ends is measured. Synchronize adjustments based on relevance. All the synchronization adjustment methods in the prior art are applicable to this application, and will not be repeated here.
  • step 204 the intermodulation interference signal is reconstructed based on the gain of the intermodulation interference channel at each frequency point and the amplitude of each frequency point in the intermodulation interference sequence.
  • the intermodulation interference channel Due to the complexity of the intermodulation interference channel, it is greatly affected by the environment in which the electronic device is located. In practical applications, the intermodulation interference channel can be estimated in advance, or the intermodulation interference channel can be estimated regularly or irregularly for subsequent use. For example, when the user's environment changes greatly, when the temperature changes significantly, the working status of the radio frequency device changes, and when the previous channel information is used for communication and the quality is found to be poor, the intermodulation interference channel can be re-estimated .
  • the electronic device when performing intermodulation interference channel estimation, can be placed in an environment where no other transmitters send signals, but only the electronic device transmits radio frequency signals. For example, when the electronic device is turned on, or when the electronic device is idle (that is, the user has no communication requirements, and there is no useful signal from the base station). In this case, the signal received by the receiving end is an intermodulation interference signal.
  • the signal received by an electronic device when performing intermodulation interference channel estimation, if the signal received by an electronic device contains both useful signals from other transmitters and intermodulation interference signals, at this time, frequency multiplexing or time In the above, the useful signal and the intermodulation interference signal are separated in the channel estimation data frame, that is, the intermodulation interference signal in the received signal is separated. In this case, time resources can be reserved for intermodulation interference channel estimation.
  • a dedicated reference signal (or reference sequence) can be designed for intermodulation interference channel estimation.
  • an existing data frame in the existing communication protocol for example, a pilot signal, that is, a training sequence
  • an idle frame to insert data into the idle frame as a reference sequence. Intermodulation interference channel estimation.
  • the OFDM symbol uses a comb-shaped pilot reference sequence.
  • the transmitting end sends this pilot reference sequence, and the receiving end can receive a complete OFDM symbol as a reference signal, denoted as X r (k); then obtain the local uplink signal in the form of baseband, Denoted as X b (k); using channel estimation algorithm to estimate the channel state information of intermodulation interference, denoted as Save the channel state information of the intermodulation interference for use in interference cancellation.
  • the existing channel estimation algorithm (marked as the "first channel estimation algorithm") can be used to obtain Intermodulation interference channel information. That is, the gain of the intermodulation interference channel to the transmitted signal at different frequency points or frequency bands.
  • the reference sequence is also transmitted after carrier modulation, after obtaining the actual sequence corresponding to the intermodulation interference signal in the received signal, you can first determine the actual sequence from the model library.
  • the amplitude calculation model corresponding to each frequency point in the frequency band, and the reference sequence in the form of baseband is input into the determined amplitude calculation model to obtain the amplitude corresponding to each frequency point in the intermodulation interference sequence; then the second channel estimation algorithm is used to combine The amplitude corresponding to each frequency point in the actual sequence and the intermodulation interference sequence is estimated to obtain the gain of the intermodulation interference channel at each frequency point.
  • the intermodulation interference signal When reconstructing the intermodulation interference signal, first analyze the local uplink signal in the form of baseband to obtain the intermodulation interference sequence, including the frequency point and the amplitude corresponding to the frequency point; then obtain the gain of the intermodulation interference channel at each frequency point, press The frequency point multiplies the amplitude and the gain to determine the reconstructed intermodulation interference signal, that is, the amplitude of the intermodulation interference signal at each frequency point.
  • calculations can be performed on frequency points one by one; the amplitude and gain corresponding to all frequency points can also be formed into vectors for vector operations.
  • the method for reconstructing intermodulation interference signals provided in this embodiment can be executed in a baseband processor without adding additional hardware circuit burden.
  • the method for reconstructing intermodulation interference signals provided in this embodiment can be executed by a processor other than the baseband processor.
  • the baseband processor can obtain the local uplink signal in the form of baseband and the digital Downlink signal.
  • part of the steps in the method for reconstructing intermodulation interference signals provided in this embodiment are executed by a baseband processor, and other steps are executed by other processors, such as the estimation of the intermodulation interference channel or the establishment of a model library. Can be done by other processors.
  • this application should not be limited to the examples here, and the technicians can flexibly merge or split the steps according to actual needs.
  • the method for reconstructing intermodulation interference signals realizes the accurate reconstruction of intermodulation interference signals in the digital domain, and provides a possibility for eliminating the intermodulation interference between uplink transmission signals and downlink reception signals in a multi-carrier system. s solution.
  • the functional modules involved in the method for reconstructing intermodulation interference signals are as shown in FIG. 3.
  • the useful signal can be obtained based on the reconstructed intermodulation interference signal and the digital downlink signal.
  • the local downlink signal in the form of baseband is output to the radio frequency chip through a digital-to-analog converter (DAC) on the one hand, and input to the amplitude corresponding to each frequency point in the frequency band where the useful signal is selected from the model library on the other hand.
  • DAC digital-to-analog converter
  • a method for reconstructing intermodulation interference signals is provided.
  • the model library is established by the following method: firstly determine the first type of interference frequency point and the second type of interference frequency point respectively; then, based on the convolution operation, obtain the amplitude of each frequency point in the first type of interference frequency point The formula for calculating the value and the formula for calculating the amplitude of each frequency point in the second type of interference frequency point; then, based on the amplitude calculation formula corresponding to the same frequency point in the first type of interference frequency point and the second type of interference frequency point, the same frequency is determined The amplitude calculation model corresponding to the point.
  • the high-frequency and low-frequency frequencies in a specific frequency band may produce up intermodulation, which is expressed as the a-th harmonic frequency of the high-frequency frequency and the Ma-order of the low-frequency frequency.
  • the interference frequency point generated by the upper intermodulation is recorded as the first type of interference frequency point.
  • the high-band frequency and the low-band frequency in a specific frequency band may produce lower intermodulation, which is expressed as the difference between the frequency of the a-th harmonic of the high-band frequency and the M-a-harmonic of the low-band frequency.
  • the interference frequency point generated by the lower intermodulation is recorded as the second type of interference frequency point.
  • intermodulation interference is very complicated, and the frequency components it generates are very large.
  • analysis using a polynomial model found that the higher the order, the weaker the power of its components, and the more complex the frequency components. When the order is too high, the interference generated can even be ignored. Therefore, in practical applications, you can consider those orders that may have interference effects on the received useful signal, such as second-order, third-order, etc., and it is not necessary to determine all orders as target orders.
  • the first type of interference frequency points include at least the sum of the high-band frequency points and the low-band frequency points in the specific frequency band.
  • the second type of interference frequency points include at least the difference between the high-band frequency points and the low-band frequency points in a specific frequency band.
  • At least one convolution operation is performed on the baseband sequence of the high frequency band and the baseband sequence of the low frequency band to obtain the amplitude calculation formula of each frequency point in the first type of interference frequency point.
  • Step 401 Determine the bandpass signal of the target order of the local uplink signal.
  • the bandpass form of the modeled output signal can be denoted as (A+B)+(A+B) 2 +...+(A +B) N.
  • N is the number of carriers.
  • the "high” and “low” in the A component of the high frequency band and the B component of the low frequency band are not absolute values, but actually refer to A The frequency band where the component is located is higher than the frequency band where the B component is located, and it is introduced to distinguish the two frequency components involved in intermodulation interference.
  • Step 402 Analyze interference items.
  • the term that will cause interference is the cross term, which can be simplified as mA a B Na according to the binomial theorem. For example, if the power of the second-order component is relatively strong, the second-order component can be considered first. At this time, only the 2AB term has frequency band crossover, which will produce upper intermodulation and lower intermodulation.
  • the 3A 2 B and 3AB 2 items in the third-order components have frequency band crossover, which will produce harmonics, upper intermodulation and lower intermodulation.
  • step 403 the upper intermodulation model and the lower intermodulation model are analyzed and obtained according to the interference items obtained by the analysis.
  • the bandpass expression form is X(t)+X 2 (t)+...X N (t), where w 0n , w 1n are carrier frequencies, a 0n , a 1n , b 0n , b 1n are modulation amplitudes.
  • w 0 is used to represent a frequency band, and this frequency band has multiple carrier frequencies, so each carrier frequency is recorded as w 0n , and the upper limit of n is the aforementioned N; a 0 , b 0 is used to express the two modulation signals of the frequency band, that is, the baseband signal.
  • each carrier corresponds to a modulation amplitude, so it is also recorded as a 0n and b 0n accordingly .
  • the other group of w 1n , b 0n , and b 1n has the same meaning and is used to represent the frequency and corresponding modulation amplitude of each carrier in another frequency band.
  • the baseband expression form of the second-order lower intermodulation product of the N carrier is actually the convolution result of the baseband signals of the two frequency bands.
  • a sequence corresponds to the baseband signal of the high frequency band, which can be expressed as [a 00 +jb 00 a 01 +jb 01 ...a 0N-1 +jb 0N-1 ]
  • the other sequence corresponds to the conjugate inverted form of the low-frequency baseband signal, which can be expressed as [a 1N-1 -jb 1N-1 a 1N-2 -jb 1N-2 ...a 10 -jb 10 ].
  • the baseband expression form of the second-order upper intermodulation product of the N carrier also corresponds to the convolution result of the baseband signals of the two frequency bands.
  • a sequence corresponds to the baseband signal of the high frequency band, which can be expressed as [a 00 + jb 00 a 01 +jb 01 ...a 0N-1 +jb 0N-1 ]
  • the other sequence corresponds to the low-frequency baseband signal, which can be expressed as [a 10 +jb 10 a 11 +jb 11 ...a 1N-1 +jb 1N-1 ].
  • the short-form expression of the intermodulation product band-pass form of the target order will involve the discrimination and calculation of low-order upper intermodulation and lower intermodulation many times.
  • the intermodulation produced by the cross term involves three more complicated discriminations: the combination of several convolutions, upper intermodulation and lower intermodulation, and frequency band distribution.
  • a 2 B A ⁇ A ⁇ B.
  • the calculation of upper and lower intermodulation involves two convolution operations. One is the harmonic term generated by A ⁇ A, which can actually be regarded as intermodulation A special form, the second is the up-intermodulation and down-intermodulation interference signals generated by the harmonic term and B.
  • the construction process is still based on the above-mentioned convolutional modeling model, and for higher-order components, the conclusion is derived based on the above-mentioned model. The same modeling calculation method is available. Of course, the calculation process will be more cumbersome and the amount of calculation will be larger.
  • Interference modeling for the target band-limited frequency band involves multiple orders of harmonics, intermodulation, and the mixing of the two.
  • the binomial theorem is supplemented to determine the frequency band distribution of different orders of interference and harmonics
  • the interference frequency corresponding to the order of the actual interference is determined according to the band-limited frequency range, and the modeling result is intercepted. That is, if a band-limited interference frequency band is to be eliminated, it will involve convolution modeling operations of different orders and some baseband signals.
  • the receiving frequency band is located in [2-8]
  • the second-order intermodulation component frequency band is located in [5-15]
  • the third-order intermodulation component frequency band is located in [7-20]. Part of the modeling is sufficient, and it is not necessary to perform convolution calculations on the entire baseband signal to save calculations.
  • step 404 for each cross term, convolution modeling is performed in combination with the intermodulation model.
  • this application proposes a fast convolution algorithm as shown in FIG. Efficient modeling operations to save time and computing resources, and can easily use computing chips for processing.
  • the baseband sequence of the high frequency band is [a 00 +jb 00 a 01 +jb 01 ...a 0N-1 +jb 0N- 1 ]
  • the conjugate reverse order of the low-frequency baseband sequence is [a 1N-1 -jb 1N-1 a 1N-2 -jb 1N-2 ...a 10 -jb 10 ].
  • one sequence can be determined as the first sequence, denoted as h(n), and the other sequence is the second sequence, denoted as x(n).
  • the baseband sequence of the high frequency band is [a 00 +jb 00 a 01 +jb 01 ...a 0N-1 +jb 0N-1 ]
  • the baseband sequence of the low frequency band is [a 10 +jb 10 a 11 +jb 11 ...a 1N-1 +jb 1N-1 ]. Then, it can be determined from the two that one sequence is the third sequence, denoted as h(n), and the other sequence is the fourth sequence, denoted as x(n).
  • the harmonic term involved in step 403 can be regarded as a convolution of the same sequence as x(n) and h(n).
  • the length of the last segment may be less than M bits, and each segment is recorded as h i (n);
  • step (a) that is, step (1) in Figure 5
  • step (a) involves zero padding at the end of x(n)
  • step (1) again Abandon the fragments with the same number of bits at the end of the superimposed result, and obtain the final result of the target convolution x(n)*h(n)
  • the intermodulation interference modeling of the band-limited frequency band involves high-order, it can be combined with the ( 3) and (4), it is enough to perform convolution calculations on the segments that actually cause interference, thereby avoiding unnecessary calculations.
  • Step 405 superimpose the convolution result.
  • Each item in the sequence obtained by convolution is an amplitude calculation formula.
  • the convolution result of each cross term is superimposed according to the frequency point.
  • the model coefficients are the same and can be added directly.
  • the amplitude calculation formula of each frequency point in the first type of interference frequency point is obtained by accumulating the corresponding amplitude calculation formulas of the same frequency point generated in different orders.
  • the amplitude calculation formulas for each frequency point in the second type of interference frequency points are obtained by accumulating the corresponding amplitude calculation formulas of the same frequency points generated in different orders.
  • the method for establishing the model of this application is suitable for systems with or without memory, and can be generalized To any order and frequency band, interference reconstruction can be carried out according to the target order or the band-limited interference part of the receiving frequency band.
  • the method for reconstructing intermodulation interference signals provided in the present application can make subsequent intermodulation interference cancellation in the digital domain without additional hardware overhead.
  • the designed fast convolution algorithm reduces the time and computing resource requirements for interference reconstruction.
  • a device for reconstructing an intermodulation interference signal including an acquisition module 601, a selection module 602, an amplitude calculation module 603, and a reconstruction module 604.
  • the acquisition module 601 is used to acquire a digital downlink signal containing a useful signal and an intermodulation interference signal.
  • the selection module 602 is used to select the amplitude calculation model corresponding to each frequency point in the frequency band where the useful signal is located from the model library.
  • the model library here includes the amplitude calculation model corresponding to each frequency point that produces intermodulation interference.
  • the amplitude calculation module 603 is used for determining the amplitude of each frequency point in the intermodulation interference sequence based on the local uplink signal in the form of baseband and the selected amplitude calculation model.
  • the reconstruction module 604 is configured to reconstruct the intermodulation interference signal based on the gain of the intermodulation interference channel at each frequency point and the amplitude of each frequency point in the intermodulation interference sequence.
  • the intermodulation interference signal reconstruction device may further include a model building module for establishing a model library by the following method: determining the first type of interference frequency point, the first type of interference frequency point at least includes the first type of interference frequency point in the specific frequency band The sum of the frequency of the first frequency band and the frequency of the second frequency band; determine the second type of interference frequency point, the second type of interference frequency point contains at least the difference between the frequency point of the first frequency band and the frequency point of the second frequency band in the specific frequency band; based on convolution operation , Get the amplitude calculation formula of each frequency point in the first type of interference frequency point and the amplitude calculation formula of each frequency point in the second type of interference frequency point; based on the same in the first type of interference frequency point and the second type of interference frequency point The amplitude calculation formula corresponding to the frequency point determines the amplitude calculation model corresponding to the same frequency point.
  • a model building module for establishing a model library by the following method: determining the first type of interference frequency point, the first type of interference
  • the model building module obtains the amplitude calculation formula of each frequency point in the first type of interference frequency point and the amplitude calculation formula of each frequency point in the second type of interference frequency point based on the convolution operation
  • the value of the first frequency band The baseband sequence and the baseband sequence of the second frequency band are subjected to at least one convolution operation to obtain the amplitude calculation formula of each frequency point in the first type of interference frequency point; the conjugate of the baseband sequence of the first frequency band and the baseband sequence of the second frequency band Perform at least one convolution operation in reverse order to obtain the amplitude calculation formula of each frequency point in the second type of interference frequency point.
  • the model building module determines the first sequence and the second sequence of the baseband sequence of the high frequency band and the baseband sequence of the low frequency band when performing at least one convolution operation on the baseband sequence of the high frequency band and the baseband sequence of the low frequency band; A segment length, the first sequence is segmented; the second sequence is zero-filled; the number of zero-filling bits is determined according to the length of the first segment; the zero-filled second sequence is overlapped based on the first overlap length Segmentation, where the first overlap length is the same as the number of zero padding bits; calculate the convolution of each segment of the first sequence with each segment of the second sequence through fast Fourier transform and inverse fast Fourier transform; superimpose all volumes The product results, the amplitude calculation formula of each frequency point in the first type of interference frequency point is obtained.
  • model building module when the model building module performs at least one convolution operation on the conjugate reverse order of the baseband sequence of the high frequency band and the baseband sequence of the low frequency band, it determines the third of the conjugate reverse order of the baseband sequence of the high frequency band and the baseband sequence of the low frequency band.
  • Sequence and the fourth sequence segment the third sequence based on the length of the second segment; add zeros to the fourth sequence; wherein the number of zero-fills is determined according to the length of the second segment; based on the second overlap length,
  • the fourth sequence after zero padding is overlapped and segmented, where the second overlap length is the same as the number of zero padding bits; the fast Fourier transform and the inverse fast Fourier transform are used to calculate the difference between each segment of the third sequence and the fourth sequence.
  • Convolution of each segment superimpose all convolution results to obtain the amplitude calculation formula of each frequency point in the second type of interference frequency point.
  • the intermodulation interference signal reconstruction device may further include a first channel estimation module for estimating the gain of the intermodulation interference channel at each frequency point, including: obtaining the intermodulation interference signal in the received signal Corresponding actual sequence; Obtain a reference sequence in the form of baseband; Among them, the reference sequence is used for intermodulation interference channel estimation; According to the actual sequence, reference sequence and the first channel estimation algorithm, the gain of the intermodulation interference channel at each frequency point is obtained.
  • a first channel estimation module for estimating the gain of the intermodulation interference channel at each frequency point, including: obtaining the intermodulation interference signal in the received signal Corresponding actual sequence; Obtain a reference sequence in the form of baseband; Among them, the reference sequence is used for intermodulation interference channel estimation; According to the actual sequence, reference sequence and the first channel estimation algorithm, the gain of the intermodulation interference channel at each frequency point is obtained.
  • the intermodulation interference signal reconstruction device may further include a second channel estimation module for estimating the gain of the intermodulation interference channel at each frequency point, including: obtaining the intermodulation interference signal in the received signal Corresponding actual sequence; determine the amplitude calculation model corresponding to each frequency point in the frequency band where the actual sequence is located from the model library; determine each frequency in the intermodulation interference sequence based on the reference sequence in the baseband form and the determined amplitude calculation model The amplitude corresponding to each point; according to the actual sequence, the amplitude corresponding to each frequency point in the intermodulation interference sequence, and the second channel estimation algorithm, the gain of the intermodulation interference channel at each frequency point is obtained.
  • a second channel estimation module for estimating the gain of the intermodulation interference channel at each frequency point, including: obtaining the intermodulation interference signal in the received signal Corresponding actual sequence; determine the amplitude calculation model corresponding to each frequency point in the frequency band where the actual sequence is located from the model library; determine each frequency in the intermodulation interference sequence based on
  • the reconstruction module is also used to multiply the amplitude of each frequency point in the intermodulation interference sequence by the gain of the corresponding frequency point in the intermodulation interference channel, as the reconstructed intermodulation interference signal at each frequency point The amplitude.
  • the reconstructed intermodulation interference signal is used to obtain the useful signal from the digital downlink signal.
  • the foregoing device embodiment corresponds to the foregoing embodiment of the intermodulation interference signal reconstruction method, and this embodiment can be implemented in cooperation with the foregoing embodiment of the intermodulation interference signal reconstruction method.
  • the relevant technical details mentioned in the foregoing embodiment of the method for reconstructing intermodulation interference signals are still valid in this embodiment, and in order to reduce repetition, details are not repeated here.
  • the related technical details mentioned in this embodiment can also be applied to the foregoing embodiment of the method for reconstructing intermodulation interference signals.
  • a functional module may be software modules or hardware modules.
  • a functional module can be a physical unit, can also be a part of a physical unit, and can also be implemented as a combination of multiple physical units.
  • this embodiment does not introduce units that are not closely related to solving the technical problems proposed by this application, but this does not mean that there are no other units in this embodiment.
  • an electronic device including a digital domain intermodulation cancellation module, which includes an intermodulation interference signal reconstruction device such as that shown in FIG. 6.
  • the electronic device may also include an analog domain intermodulation cancellation module, such as some existing devices that implement intermodulation interference cancellation in the analog domain.
  • the digital domain intermodulation cancellation module and the analog domain intermodulation cancellation module are cascaded, which enriches the application scenarios of the intermodulation interference signal reconstruction method or device provided in this application.
  • analog domain intermodulation cancellation module is generally located in front of the radio frequency chip to eliminate intermodulation interference from the received signal.
  • the digital domain intermodulation cancellation module is generally located between the radio frequency chip and the baseband chip, and further eliminates the intermodulation interference from the received signal, which is beneficial to better eliminate the intermodulation interference.
  • an electronic device including: at least one processor 801; and a memory 802; wherein the memory stores one or more programs that can be executed by at least one processor,
  • the program contains instructions, which are executed by at least one processor, so that the at least one processor can execute the method for reconstructing an intermodulation interference signal in any one of the foregoing embodiments of the present application.
  • the memory 802 and the processor 801 are connected in a bus manner, and the bus may include any number of interconnected buses and bridges, and the bus connects one or more various circuits of the processor 801 and the memory 802 together.
  • the bus can also connect various other circuits such as peripheral devices, voltage regulators, power management circuits, etc., which are all known in the art, and therefore, no further descriptions are provided herein.
  • the bus interface provides an interface between the bus and the transceiver.
  • the transceiver may be one element or multiple elements, such as multiple receivers and transmitters, providing a unit for communicating with various other devices on the transmission medium.
  • the data processed by the processor is transmitted on the wireless medium through the antenna, and further, the antenna also receives the data and transmits the data to the processor 801.
  • the processor 801 is responsible for managing the bus and general processing, and can also provide various functions, including timing, peripheral interfaces, voltage regulation, power management, and other control functions.
  • the memory 802 may be used to store data used by the processor 801 when performing operations.
  • the electronic device in this embodiment may be, but is not limited to, a terminal device or a network device.
  • the "terminal equipment” used here includes, but is not limited to, via wireless interfaces, such as cellular networks, wireless local area networks (WLAN), digital TV networks such as DVB-H networks, satellite networks, AM-FM Broadcast transmitter; and/or another terminal device that is set to receive/send communication signals; and/or Internet of Things (IoT) equipment.
  • a terminal device set to communicate through a wireless interface may be referred to as a "wireless communication terminal", a “wireless terminal” or a "mobile terminal".
  • Examples of mobile terminals include, but are not limited to, satellite or cellular phones; Personal Communications System (PCS) terminals that can combine cellular radio phones with data processing, fax, and data communication capabilities; can include radio phones, pagers, Internet/intranet PDA with internet access, web browser, memo pad, calendar, and/or Global Positioning System (GPS) receiver; and conventional laptop and/or palmtop receivers or others including radio telephone transceivers Electronic device.
  • Terminal equipment can refer to access terminals, user equipment (UE), user units, user stations, mobile stations, mobile stations, remote stations, remote terminals, mobile equipment, user terminals, terminals, wireless communication equipment, user agents, or User device.
  • the access terminal can be a cellular phone, a cordless phone, a Session Initiation Protocol (SIP) phone, a wireless local loop (Wireless Local Loop, WLL) station, a personal digital processing (Personal Digital Assistant, PDA), with wireless communication Functional handheld devices, computing devices or other processing devices connected to wireless modems, in-vehicle devices, wearable devices, terminal devices in 5G networks, or terminal devices in the future evolution of PLMN, etc.
  • the network device can provide communication coverage for a specific geographic area, and can communicate with terminal devices located in the coverage area.
  • the network equipment may be a base station (Base Transceiver Station, BTS) in a GSM system or a CDMA system, a base station (NodeB, NB) in a WCDMA system, or an evolved base station (Evolutional Base Station) in an LTE system.
  • BTS Base Transceiver Station
  • Node B, eNB or eNodeB or a wireless controller in Cloud Radio Access Network (CRAN)
  • the network equipment can be a mobile switching center, a relay station, an access point, a vehicle-mounted device, or a wearable Devices, hubs, switches, bridges, routers, network-side devices in 5G networks, or network devices in the future evolution of the Public Land Mobile Network (PLMN), etc.
  • PLMN Public Land Mobile Network
  • a non-volatile computer storage medium that stores a program that can be executed by a processor.
  • the program is executed by the processor, the intermodulation interference signal in any of the above-mentioned embodiments of the present application is realized.
  • the reconstruction method is provided that stores a program that can be executed by a processor.
  • a chip including: at least one processor; and a memory communicatively connected with the at least one processor.
  • the memory stores one or more programs that can be executed by at least one processor; the one or more programs contain instructions that, when executed by at least one processor, cause at least one processor to execute the aforementioned intermodulation interference signal The reconstruction method.
  • the program is stored in a storage medium and includes several instructions to enable a device (which can be A single-chip microcomputer, a chip, etc.) or a processor (processor) execute all or part of the steps of the methods described in the embodiments of the present application.
  • the aforementioned storage media include: U disk, mobile hard disk, read-only memory (ROM, Read-Only Memory), random access memory (RAM, Random Access Memory), magnetic disks or optical disks and other media that can store program codes. .

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Abstract

本申请部分实施例提供了一种互调干扰信号的重构方法，用于使用特定频段的多载波系统。该方法包括：获取(201)包含有用信号和互调干扰信号的数字下行信号；从包括产生互调干扰的各频点对应的幅值计算模型的模型库中选取(202)与有用信号所处的频段中各频点对应的幅值计算模型；基于基带形式的本地上行信号和选取的幅值计算模型，确定(203)互调干扰序列中各频点的幅值；基于互调干扰信道在各频点的增益和互调干扰序列中各频点的幅值，重构(204)互调干扰信号。

Description

互调干扰信号的重构方法和装置 技术领域
本申请涉及通信技术领域，特别涉及一种互调干扰信号的重构方法和装置，电子设备，芯片以及非易失性计算机存储介质。
背景技术
随着通信技术的发展，日益增长的数据需求与高效可靠的频谱资源日益枯竭之间的矛盾也愈发尖锐。为了充分利用频谱资源，正交频分复用(Orthogonal Frequency Division Multiplexing，简称“OFDM”)调制技术通过频分复用实现了高速串行数据的并行传输。发展到5G商用时代，OFDM调制技术仍然是5G移动通信系统的关键技术之一，也是航空通信、卫星通信甚至是6G等系统的备选方案之一。
为了能够在有限的频谱资源上传输更多的数据，研究人员开发了一种全双工技术，能够实现无线通信设备在同一时间或单一频带上进行发射和接收信号，理论上可以提高频谱效率。然而，由于现有的射频器件的非线性特性等因素，OFDM等多载波系统中存在潜在的互调自干扰问题，严重时甚至淹没接收信号，将直接影响收发机正常工作。为了保证OFDM等多载波系统正常通信，需要有效地抑制自干扰信号。此外，不同场景中网络制式尤其是多种网络制式并存时，互调自干扰问题会更加突出。
发明内容
本发明部分实施例所要解决的一个技术问题在于可以重构互调干扰信号，进而可用于消除多载波系统中的互调干扰。
本申请的一个实施例提供了一种互调干扰信号的重构方法。该方法包括：获取包含有用信号和互调干扰信号的数字下行信号；从模型库中选取与有用信号所处的频段中各频点对应的幅值计算模型，并基于基带形式的本地上行信号和选取的幅值计算模型，确定互调干扰序列中各频点的幅值；基于互调干扰信道在各频点的增益和互调干扰序列中各频点的幅值，重构互调干扰信号。其中，模型库包括产生互调干扰的各频点对应的幅值计算模型。
本申请的一个实施例还提供了一种互调干扰信号的重构装置。该装置包括：获取模块、选取模块、幅值计算模块和重构模块。其中，获取模块用于获取包含有用信号和互调干扰信 号的数字下行信号；选取模块用于从模型库中选取与有用信号所处的频段中各频点对应的幅值计算模型；幅值计算模块用于基于基带形式的本地上行信号和选取的幅值计算模型，确定互调干扰序列中各频点的幅值；重构模块用于基于互调干扰信道在各频点的增益和互调干扰序列中各频点的幅值，重构互调干扰信号。其中的模型库包括产生互调干扰的各频点分别对应的幅值计算模型。
本申请的一个实施例还提供了一种非易失性计算机存储介质，存储有可被处理器执行的程序，该程序在被处理器执行时，实现前述的互调干扰信号的重构方法。
本申请的一个实施例还提供了一种电子设备，包括：至少一个处理器；以及与至少一个处理器通信连接的存储器；其中，存储器存储有可被至少一个处理器执行的一个或多个程序；一个或多个程序包含指令，该指令在被至少一个处理器执行时，使得至少一个处理器执行前述的互调干扰信号的重构方法。
本申请的一个实施例还提供了一种芯片，包括：至少一个处理器；与所述至少一个处理器通信连接的存储器。其中，存储器存储有可被至少一个处理器执行的一个或多个程序；一个或多个程序包含指令，该指令在被至少一个处理器执行时，使得至少一个处理器执行前述的互调干扰信号的重构方法。
在本申请的实施例提供的互调干扰信号的重构方法中，通过根据预先建立的幅值计算模型和基带形式的本地上行信号得到互调干扰序列，并结合对互调干扰信道的估计，重构互调干扰信号，可以较为准确地重构互调干扰信号，进而可以消除多载波系统中的互调干扰。
附图说明
一个或多个实施例通过与之对应的附图中的图片进行示例性说明，这些示例性说明并不构成对实施例的限定，附图中具有相同参考数字标号的元件表示为类似的元件，除非有特别申明，附图中的图不构成比例限制。
图1为根据一个实施例的一种产生互调干扰的场景。
图2为根据一个实施例的互调干扰信号的重构方法的流程图。
图3为根据一个实施例的互调干扰信号的重构方法涉及的功能模块图。
图4为根据一个实施例的互调干扰信号的重构方法中模型建立过程的流程图。
图5为根据一个实施例的互调干扰信号的重构方法中卷积运算过程示意图。
图6为根据一个实施例的互调干扰信号的重构装置的框图。
图7为根据一个实施例的电子设备中模拟域和数字域互调干扰消除的级联示意图。
图8为根据一个实施例的电子设备的结构示意图。
具体实施方式
为了使本发明的目的、技术方案及优点更加清楚明白，以下结合附图及实施例，对本发明部分实施例进行进一步详细说明。应当理解，此处所描述的具体实施例仅仅用以解释本发明，并不用于限定本发明。
本申请主要解决多载波系统中，上行发送对下行接收造成的潜在互调干扰问题。如图1所示，展示了一种较为典型的、功率明显的产生互调干扰的场景。图中所示电子设备具有发射天线TA和接收天线RA，可以在频段Band1和Band2上发射信号，在频段Band上接收信号。互调干扰的产生机理和传播链路十分复杂，互调干扰主要产生于链路中的非线性器件，如功率放大器PA1，PA2等。如图中虚线所示，可能的传播链路为：由基带芯片(Baseband IC)发送的本地上行信号进入射频芯片进行调制等处理，经过功率放大器PA1后，其中的高功率信号经印制电路板(Printed circuit board，简称“PCB”)泄露至功率放大器PA2的输入端口，与输入信号一同经过放大器，产生多音混频，然后一方面经过信号传输链路之后由发射天线发射被接收天线接收，另一方面通过链路辐射至接收端。由此可见，在电子设备接收信号时，如果也同时发射信号，进入射频芯片(RFIC)的接收信号除了包含来自基站的有用信号之外，还可能包含有本地上行信号经过该传播链路而产生的互调干扰信号。
为了解决互调自干扰问题，目前研究方向主要聚焦在两个方面：(1)已经对于射频器件的线性性能进行了一些研究。但是，器件性能的优化是一个长期的研究开发工作，技术难度较高，且需要针对不同的器件专门研究，成本较高。(2)时频调度等技术已被用于解决互调自干扰问题，时频调度需要根据干扰强度、时隙配比等情况暂停某一端的发射或接收工作，甚至会涉及较为复杂的网络改造问题，会降低系统的吞吐量，影响网络峰值速率。看到上述两个研究方向存在的问题，发明人尝试了另外的研究方向来解决互调自干扰问题，该研究方向为在收发机中增设干扰消除模块从接收信号中消除(或抑制)互调自干扰，并且具体解释如下。对于电子设备而言，进入基带处理器的接收信号包含解调后的接收信号和互调干扰信号，而与互调干扰信号对应的本地上行信号(发射信号)是本电子设备正在发送的信号，并且其基带形式是为本电子设备所知的。如果可以根据电子设备的本地上行信号的基带形式估计出互调干扰信号，从接收信号中减去这个估计的互调干扰信号，就可以很方便地得到有用信号。
假设将本地上行信号从发射端基带发送(即离开基带芯片，或离开基带处理器)到接收端基带解调(即进入基带芯片)所经过传播链路看作一信道(以下称为互调干扰信道)。实际上，由于互调的传播路径十分复杂，除了图1中示出的可能的传播链路之外，互调干扰 信道还应包含射频芯片内部对基带信号进行处理所涉及的所有器件，以及射频芯片内部对接收信号进行解调等处理所涉及的所有器件。比如，射频器件的非线性特性是引起互调干扰的一个因素。如果能采用某种方法对互调干扰信道进行估计，那么就可以根据基带形式的本地上行信号和估计的互调干扰信道得到估计的互调干扰信号。基于此，本申请提供了一种互调干扰信号的重构方法，通过对互调干扰信道进行估计，结合基带形式的本地上行信号重构互调干扰信号，可以采用重构的互调干扰信号从接收信号中消除互调干扰信号。
在一个实施例中，提供了一种互调干扰信号的重构方法，如图2所示。该方法可用于使用特定频段的多载波系统中，比如，采用载波聚合(Carrier Aggregation，简称“CA”)的长期演进(Long Term Evolution，简称“LTE”)系统，或者LTE和新空口(New Radio，简称“NR”)并发的系统。但本申请并不限于此处的举例，任何涉及至少两个载波频段的系统均应落入本申请的保护范围之内。以涉及两个载波频段的系统为例进行说明，为方便描述，两个载波频段中的一个频段称为第一频段或高频段，另一个频段称为第二频段或低频段，第一频段内的载波频率高于第二频段内的载波频率。
在步骤201中，获取数字下行信号。
数字下行信号可以对射频IC的输出信号直接进行采样得到，比如采用模数转换器(ADC)采样。这一技术在现有的移动终端收发机中非常常见，在此不进行详细说明。
在步骤202中，从模型库中选取与有用信号所处的频段中各频点对应的幅值计算模型。
在本实施例中，模型库包括产生互调干扰的各频点对应的幅值计算模型。进行建立模型库时，可以采用多种模型，比如多项式模型，Hammerstein模型等。但本申请不应局限于此处列举的两种模型，在此不一一例举。模型库中的每一个频点可以预先通过分析或者实测得到，每一个频点对应的幅值计算模型则通过建模推导得到。每一个频点对应的幅值计算模型涉及多载波系统中涉及的至少两个载波频段对应的基带序列中各幅值的叠加。
值得一提的是，发明人在研究过程中还发现，只有本地上行信号的互调产物的频点或频段落在有用信号的频点上或落入有用信号的频段内，才会对接收信号产生影响。举例来说，如果产生的互调干扰信号位于[1-5]频段，而接收频段是在[8-12]，这样不会有实质干扰。一方面，在经过互调干扰信道之后，本地上行信号的频段会被展宽，展宽后的频段可能只与接收频段存在一部分的重叠，落入重叠的这一部分的互调干扰信号对接收信号实际造成干扰。另一方面，实际上，互调干扰相对较弱，某些频点的干扰信号本身就很弱，未必会对接收信号造成实际干扰。因此，可以根据有用信号所在的频点或频段来选取幅值计算模型，从而较为准确地重构互调干扰信号。
在选取幅值计算模型之后，在步骤203中，基于基带形式的本地上行信号和选取的幅 值计算模型，确定互调干扰序列中各频点的幅值。
在本实施例中，基带形式的本地上行信号可以从发射端获得。
在一种示例中，可以直接将基带形式的本地上行信号分成两路，一路发送给射频芯片，另一路引向接收端。对信号的发送到重构互调干扰之间的时延进行测量，在进行互调干扰信号的重构时，在引至接收端的链路中进行时延调整，基带形式的本地上行信号以数据流的形式引向接收端。
在另一种示例中，比如，实际测得的时延过大时，基带形式的本地上行信号可以在基带处理器发送本地上行信号给射频芯片时存储在一存储器中。在进行互调干扰信号重构时，可直接从存储器中读取该基带形式的本地上行信号。读取的基带形式的本地上行信号与数字下行信号做同步测量，测得两端信号的相关性。根据相关性进行同步调整。现有技术中的同步调整方法均可适用于本申请，在此不一一赘述。
在步骤204中，基于互调干扰信道在各频点的增益，和互调干扰序列中各频点的幅值，重构互调干扰信号。
由以上分析可知，互调干扰信号的估计越准确，重构得到的互调干扰信号也就越准确。由于互调干扰信道的复杂性，其受电子设备所处的环境的影响较大。在实际应用中，可以预先对互调干扰信道进行估计，或者定期或不定期对互调干扰信道进行估计，以供后续使用。比如，当用户所处环境产生较大变化，当温度发生明显变化导致射频器件工作状态发生变化，当采用之前的信道信息进行通信而发现质量不佳时，都可以对互调干扰信道重新进行估计。
在一个示例中，在进行互调干扰信道估计时，可以使电子设备处于无其他发射机发送信号，仅本电子设备发射射频信号的环境中。比如，电子设备开机的时候，或者电子设备空闲的时候(即用户没有通信需求，也不会有基站传来有用信号)。在这种情况下，接收端接收到的信号为互调干扰信号。在另一个示例中，在进行互调干扰信道估计时，如果电子设备接收的信号既包含来自其他发射机的有用信号，又包含了互调干扰信号，此时，可以通过频率复用或在时间上将有用信号和互调干扰信号在信道估计数据帧中分开，即分离得到接收信号中的互调干扰信号。在这种情况下，可以预留时间资源进行互调干扰信道估计。
在一个示例中，可以为进行互调干扰信道估计而设计专门的参考信号(或参考序列)。在另一个示例中，也可以采用现有通信协议中已经有的数据帧(比如，导频信号即训练序列)作为参考序列，或者利用空闲帧，在空闲帧中插入数据作为参考序列，来进行互调干扰信道估计。
在一个示例中，OFDM符号采用梳状导频参考序列。在对互调干扰信道进行估计时，发送端发送此导频参考序列，同时接收端可以接收一个完整的OFDM符号作为参考信号，记 为X r(k)；然后获取基带形式的本地上行信号，记为X b(k)；采用信道估计算法，估计互调干扰的信道状态信息，记为
Figure PCTCN2019118230-appb-000001
保存该互调干扰的信道状态信息以便进行干扰消除时使用。
在一个示例中，在获取接收信号中的互调干扰信号对应的实际序列之后，结合基带形式的本地上行信号，采用现有的信道估计算法(标记为“第一信道估计算法”)即可获得互调干扰信道的信息。即互调干扰信道对于发射信号在不同频点或频段的增益。在另一个示例中，由于参考序列也是经过载波调制之后再发射出去的，因此，在获取接收信号中的互调干扰信号对应的实际序列之后，可以先从模型库中确定与实际序列所处的频段中各频点对应的幅值计算模型，并将基带形式的参考序列输入确定的幅值计算模型，得到互调干扰序列中各频点对应的幅值；再采用第二信道估计算法，结合实际序列和互调干扰序列中各频点对应的幅值，估计得到互调干扰信道在各频点的增益。
在重构互调干扰信号时，首先分析基带形式的本地上行信号，得到互调干扰序列，包括频点及对应于频点的幅值；然后获取互调干扰信道在各频点的增益，按频点将幅值与增益相乘，确定重构的互调干扰信号，即互调干扰信号在各频点的幅值。在实际应用中，可以逐个频点进行计算；也可以将所有频点对应的幅值和增益分别组成向量，进行向量运算。
在一个示例中，本实施例提供的互调干扰信号的重构方法可以在基带处理器内执行，无需增加额外的硬件电路负担。在另一个示例中，本实施例提供的互调干扰信号的重构方法可以由不同于基带处理器的其他处理器执行，此时，可以从基带处理器获取基带形式的本地上行信号，以及数字下行信号。在又一个示例中，本实施例提供的互调干扰信号的重构方法中的部分步骤由基带处理器执行，而其他步骤由其他处理器执行，比如，互调干扰信道的估计或者建立模型库可以由其他处理器完成。但是，本申请不应限定于此处的举例，技术人员可以根据实际需要，灵活进行步骤的合并或拆分。
本实施例提供的互调干扰信号的重构方法在数字域实现了对互调干扰信号的准确重构，为消除多载波系统中上行发送信号对下行接收信号的互调干扰提供了一种可行的解决方案。
在一个实施例中，互调干扰信号的重构方法涉及的功能模块，如图3所示。在本实施例中，有用信号可以基于重构的互调干扰信号和数字下行信号得到。具体地，基带形式的本地下行信号一方面通过数模转换器(DAC)输出至射频芯片，另一方面输入至从模型库中选取的与有用信号所处的频段中各频点对应的幅值计算模型，计算得到互调干扰序列中各频点 的幅值；接着基于互调干扰信道在各频点的增益和互调干扰序列中各频点的幅值，重构互调干扰信号；最后，从数字下行信号中减去重构的互调干扰信号，得到有用信号。
在一个实施例中，提供了一种互调干扰信号的重构方法。在本实施例中，模型库通过以下方法建立：先分别确定第一类干扰频点和第二类干扰频点；接着，基于卷积运算，得到第一类干扰频点中各频点的幅值计算式和第二类干扰频点中各频点的幅值计算式；然后，基于第一类干扰频点和第二类干扰频点中相同频点对应的幅值计算式，确定相同频点对应的幅值计算模型。
采用多项式模型分析射频形式的本地上行信号发现，特定频段内高频段频点和低频段频点可能产生上互调，表现为高频段频点的a次谐波频率与低频段频点的M-a次谐波的频率之和。其中，M为多项式模型中分量的阶次，比如M＝2时，对应二阶分量，M＝3时，对应三阶分量。a可在1至M-之间取值，a＝1表示频点本身，a＝2表示二次谐波。为方便说明，将上互调产生的干扰频点记为第一类干扰频点。
类似地，特定频段内高频段频点和低频段频点可能产生下互调，表现为高频段频点的a次谐波频率与低频段频点的M-a次谐波的频率之差。为方便说明，将下互调产生的干扰频点记为第二类干扰频点。
实际中，互调干扰非常复杂，其产生的频率成分十分多。但是，在采用多项式模型分析发现，阶次越高，其分量的功率越弱，而频率成分越复杂，在阶次过高时，其产生的干扰甚至可以忽略。因此，在实际应用时，可以考虑那些可能对接收的有用信号产生干扰影响的阶次，比如，二阶，三阶等分量，不必将所有阶次确定为目标阶次。
在一个示例中，第一类干扰频点至少包含特定频段内高频段频点和低频段频点的和。第二类干扰频点至少包含特定频段内高频段频点和低频段频点的差。在确定第一类干扰频点和第二类干扰频点之后，可以基于卷积运算，分别得到第一类干扰频点中各频点的幅值计算式和第二类干扰频点中各频点的幅值计算式。具体地，对高频段的基带序列与低频段的基带序列进行至少一次卷积运算，得到第一类干扰频点中各频点的幅值计算式。对高频段的基带序列与低频段的基带序列的共轭倒序进行至少一次卷积运算，得到第二类干扰频点中各频点的幅值计算式。
以下说明本实施例的幅值计算模型的推导过程，如图4所示。
步骤401，确定本地上行信号目标阶次的带通信号。
假设本地上行信号的射频形式包含高频段的A分量和低频段的B分量，则可将建模输出信号的带通形式记为(A+B)+(A+B) 2+…+(A+B) N。其中，N为载波数。n阶带通信号可记为 X n(t)＝(A+B) n,n的取值可为2，3，…，N。值得说明的是，多载波系统中涉及的两个频段中，高频段的A分量和低频段的B分量中的“高”和“低”并不是针对绝对值而言的，实际指的是A分量所处的频段高于B分量所处的频段，为区分在产生互调干扰涉及的两个频率分量而引入。
如前所述，由于多形式模型中阶次越高，其分量的功率越弱，而频率成分越复杂，在阶次过高时，其产生的干扰甚至可以忽略。因此，在实际确定目标阶次时，可以考虑那些可能对接收的有用信号产生干扰影响的阶次，比如，二阶，三阶等分量，不必将所有阶次确定为目标阶次。
步骤402，分析干扰项。
一般地，会产生干扰的项为交叉项，根据二项式定理，可简为mA aB N-a。比如，二阶分量的功率较强，可以先考虑二阶分量，此时，只有其中的2AB项存在频段交叉，会产上互调和下互调。三阶分量中的3A 2B，3AB 2项存在频段交叉，会产生谐波，上互调和下互调。
步骤403，根据分析得到的干扰项，分析得到上互调模型和下互调模型。
以N载波二阶下互调模型建模为例，其带通表达形式为X(t)+X 2(t)+…X N(t)，其中
Figure PCTCN2019118230-appb-000002
w 0n，w 1n为载波频率，a 0n，a 1n，b 0n，b 1n为调制幅值。由于互调干扰涉及两个频段的信号，这里用w 0表示一个频段，且该频段有多个载波频率，所以每一个载波频率记作w 0n，这个n上限就是前述的N；a 0、b 0来表述该频段的两路调制信号，也就是基带信号，同样每个载波都对应一个调制幅值，所以也相应地几记为a 0n、b 0n。另一组w 1n、b 0n、b 1n具有相同的含义，用来表示另一个频段的每个载波的频率及对应的调制幅度。
分析带通表达形式中涉及频段交叉的项，N载波的二阶下互调产物相应的频点表达式为
Figure PCTCN2019118230-appb-000003
相应互调分量的基带表达形式为
Figure PCTCN2019118230-appb-000004
考虑到OFDM调制中的子载波间隔，表达式(1)所示的这些频点中，有些是相等的， 实际就是一个频点，其干扰需要累加，因此，可对这些频点进行整合。整合后，可得到2N-1个不同的数，对应2N-1个不同的频点，整合后的表达式为
Figure PCTCN2019118230-appb-000005
相应的互调产物表达式对应为
Figure PCTCN2019118230-appb-000006
上述表达式(3)中由低到高列出了第二类干扰频点，表达式(4)则列出了各频点对应的幅值计算式。
进一步分析可发现，N载波的二阶下互调产物基带表达形式实际上为两个频段基带信号的卷积结果，其中，一个序列对应高频段的基带信号，可表示为[a 00+jb 00a 01+jb 01…a 0N-1+jb 0N-1]，另一个序列对应低频段基带信号的共轭倒序形式，可表示为[a 1N-1-jb 1N-1a 1N-2-jb 1N-2…a 10-jb 10]。
采用类似的分析可发现，N载波的二阶上互调产物基带表达形式同样对应为两个频段基带信号的卷积结果，其中，一个序列对应高频段的基带信号，可表示为[a 00+jb 00a 01+jb 01…a 0N-1+jb 0N-1]，另一个序列对应低频段的基带信号，可表示为[a 10+jb 10a 11+jb 11…a 1N-1+jb 1N-1]。
当考虑三阶或者更高阶次的互调产物时，可以根据二项式定理分析目标阶次的互调产物带通形式表达简式，判断上互调形式与下互调形式的组合，此时目标项会多次涉及低阶次的上互调、下互调的判别与计算。以三阶分量的互调产物为例，记其带通信号简式为(A+B) 3＝A 3+B 3+3A 2B+3B 2A，相比之下，交叉项产生的互调信号涉及数次卷积、上互调和下互调的组合形式和频段分布这三个较为复杂的判别。分析其中的A 2B＝A·A·B项，上、下互调的计算会涉及两次卷积运算，一是A·A产生的谐波项，实际可将其看作是互调的一种特殊形式，二是谐波项与B产生的上互调与下互调干扰信号。其构建过程仍是以上述卷积建模模型为基础，对于更高阶次分量也是基于上述模型推导结论，有同样的建模计算方法，当然计算 过程会更为繁琐，计算量也更大。
针对目标带限频段进行干扰建模，会涉及多个阶次的谐波、互调以及二者的混频，此时辅以二项式定理来判断不同阶次干扰的频段分布以及谐波、互调的组合情况，再根据带限频段范围确定实际造成干扰的阶次对应的干扰频点，截取建模结果。也就是或，如果要针对某个带限干扰频段进行消除，则会涉及不同阶次以及部分基带信号的卷积建模运算。举例来说，接收频段位于[2-8]，二阶的互调分量频段位于[5-15],三阶的互调分量频段位于[7-20]，只需要对存在交叉(干扰)的部分进行建模即可，没必要对整个基带信号进行卷积计算，以节省运算量。
步骤404，对每个交叉项，结合互调模型进行卷积建模。
考虑到卷积运算涉及额外的时间和计算资源，且针对带限频段的直接干扰建模会涉及大量不必要的运算结果，为此本申请提出一种如图5所示的快速卷积算法进行高效建模运算，以节省时间和计算资源，并且能够方便地采用计算芯片进行处理。
记两段卷积的序列为x(n)和h(n)。
比如，对高频段的基带序列与低频段的基带序列的共轭倒序进行卷积运算时，高频段的基带序列为[a 00+jb 00a 01+jb 01…a 0N-1+jb 0N-1]，低频段基带序列的共轭倒序为[a 1N-1-jb 1N-1a 1N-2-jb 1N-2…a 10-jb 10]。那么，可从两者中确定一个序列为第一序列，记为h(n)，另一个序列为第二序列，记为x(n)。
又比如，对高频段的基带序列与低频段的基带序列进行卷积运算时，高频段的基带序列为[a 00+jb 00a 01+jb 01…a 0N-1+jb 0N-1]，低频段的基带序列为[a 10+jb 10a 11+jb 11…a 1N-1+jb 1N-1]。那么，可从两者中确定一个序列为第三序列，记为h(n)，另一个序列为第四序列，记为x(n)。
又比如，步骤403中涉及的谐波项，可看作x(n)和h(n)为相同的序列的卷积。
选定h(n)的分段长度，记作M，最后一个分段的长度可能不足M位，每段记作h i(n)；
计算x(n)*h i(n)，具体地：
(a)对x(n)进行重叠分段操作，记作
Figure PCTCN2019118230-appb-000007
首先对x(n)前部补零，当补零个数为M-1位时，最为节省运算量，重叠的长度也为M-1；为了整数分段，末尾可能需要进行补零，所产生的多余结果也要在最终图5(4)的结果中删去；
(b)选定变换长度L，通过快速傅里叶变换FFT和快速傅里叶逆变换IFFT快速计算每个
Figure PCTCN2019118230-appb-000008
结果记作
Figure PCTCN2019118230-appb-000009
按图5中(3)的方法叠加步骤(b)中每个
Figure PCTCN2019118230-appb-000010
最终结果，记作
Figure PCTCN2019118230-appb-000011
即为对应h i(n)段卷积x(n)*h i(n)的最终结果；
重复上述步骤计算每段x(n)*h i(n)的结果，然后叠加计算；由于步骤(a)也即图5中(1)步骤涉及到x(n)末尾的补零，这里再舍弃叠加结果末尾相同位数的片段，求得目标卷积x(n)*h(n)的最终结果；当带限频段的互调干扰建模涉及高阶次时，可结合图5中(3)和(4)，只对实际造成干扰的分段进行卷积计算即可，进而避免不必要的运算。
步骤405，叠加卷积结果。卷积得到的序列中每一项就是一个幅值计算式。
针对干扰阶次，按频点叠加每个交叉项的卷积结果。对于某一干扰阶次，模型系数是同一个，可直接相加。
针对带限干扰频段，叠加不同阶次干扰项在目标频点的建模结果。如果要计算不同阶次的某一频段的干扰，涉及多个阶次，其模型系数不同，可以按比例值相加。这些模型系数可以提前测得。
对于第一类干扰频点，将在不同阶次中产生的相同频点对应幅值计算式累加就得到了第一类干扰频点中各频点的幅值计算式。对于第二类干扰频点，将在不同阶次中产生的相同频点对应幅值计算式累加也就得到了第二类干扰频点中各频点的幅值计算式。
值得说明的是，由于采用本申请对互调干扰信道进行估计可以估计出系统记忆效应对频域信号不同点的增益，因此，本申请模型的建立方法适用于有记忆或无记忆系统，可以推广到任意阶次和频段，可根据目标阶次或者接收频段的带限干扰部分进行干扰重构。此外，本申请提供的互调干扰信号的重构方法可以使得后续在数字域进行互调干扰消除，无需额外的硬件开销。所设计的快速卷积算法降低了干扰重构对时间和计算资源的需求。
在一个实施例中，提供了一种互调干扰信号的重构装置，如图6所示，包括获取模块601、选取模块602、幅值计算模块603和重构模块604。
其中，获取模块601用于获取包含有用信号和互调干扰信号的数字下行信号。选取模块602用于从模型库中选取与有用信号所处的频段中各频点对应的幅值计算模型。这里的模型库包括产生互调干扰的各频点分别对应的幅值计算模型。幅值计算模块603用于基于基带形式的本地上行信号和选取的幅值计算模型，确定互调干扰序列中各频点的幅值。重构模块604用于基于互调干扰信道在各频点的增益和互调干扰序列中各频点的幅值，重构互调干扰信号。
在本实施例中，通过对互调干扰信号进行重构，为消除电子设备中上行发送信号对下 行接收信号的互调干扰提供了一种可行的解决方案。
在一个实施例中，互调干扰信号的重构装置还可以包含模型建立模块，用于通过以下方法建立模型库：确定第一类干扰频点，第一类干扰频点至少包含特定频段内第一频段频点和第二频段频点的和；确定第二类干扰频点，第二类干扰频点至少包含特定频段内第一频段频点和第二频段频点的差；基于卷积运算，得到第一类干扰频点中各频点的幅值计算式和第二类干扰频点中各频点的幅值计算式；基于第一类干扰频点和第二类干扰频点中相同频点对应的幅值计算式，确定相同频点对应的幅值计算模型。
另外，模型建立模块在基于卷积运算，得到第一类干扰频点中各频点的幅值计算式和第二类干扰频点中各频点的幅值计算式时，对第一频段的基带序列与第二频段的基带序列进行至少一次卷积运算，得到第一类干扰频点中各频点的幅值计算式；对第一频段的基带序列与第二频段的基带序列的共轭倒序进行至少一次卷积运算，得到第二类干扰频点中各频点的幅值计算式。
另外，模型建立模块在对高频段的基带序列与低频段的基带序列进行至少一次卷积运算时，确定高频段的基带序列与低频段的基带序列中的第一序列和第二序列；基于第一分段长度，对第一序列进行分段；对第二序列进行补零；其中，补零位数根据第一分段长度确定；基于第一重叠长度对补零后的第二序列进行重叠分段，其中，第一重叠长度与补零位数相同；通过快速傅里叶变换和快速傅里叶逆变换计算第一序列的每一段与第二序列的每一段的卷积；叠加所有卷积结果，得到第一类干扰频点中各频点的幅值计算式。
另外，模型建立模块在对高频段的基带序列与低频段的基带序列的共轭倒序进行至少一次卷积运算时，确定高频段的基带序列与低频段的基带序列的共轭倒序中的第三序列和第四序列；基于第二分段长度，对第三序列进行分段；对第四序列进行补零；其中，补零位数根据第二分段长度确定；基于第二重叠长度，对补零后的第四序列进行重叠分段，其中，第二重叠长度与补零位数相同；通过快速傅里叶变换和快速傅里叶逆变换计算第三序列的每一段与第四序列的每一段的卷积；叠加所有卷积结果，得到第二类干扰频点中各频点的幅值计算式。
在一个实施例中，互调干扰信号的重构装置还可以包含第一信道估计模块，用于对互调干扰信道在各频点的增益进行估计，包括：获取接收信号中的互调干扰信号对应的实际序列；获取基带形式的参考序列；其中，参考序列用于进行互调干扰信道估计；根据实际序列、参考序列和第一信道估计算法，得到互调干扰信道在各频点的增益。
在一个实施例中，互调干扰信号的重构装置还可以包含第二信道估计模块，用于对互调干扰信道在各频点的增益进行估计，包括：获取接收信号中的互调干扰信号对应的实际序列；从模型库中确定与实际序列所处的频段中各频点对应的幅值计算模型；基于基带形式的参考序列和确定的幅值计算模型，确定互调干扰序列中各频点对应的幅值；根据实际序列、互调干扰序列中各频点对应的幅值和第二信道估计算法，得到互调干扰信道在各频点的增益。
在一个实施例中，重构模块还用于将互调干扰序列中各频点的幅值与互调干扰信道中对应频点的增益相乘，作为重构的互调干扰信号在各频点的幅值。
在一个实施例中，重构的互调干扰信号用于从数字下行信号中得到有用信号。
不难发现，上述装置实施例为与前述互调干扰信号的重构方法实施例相对应，本实施例可与前述互调干扰信号的重构方法实施例互相配合实施。前述互调干扰信号的重构方法实施例中提到的相关技术细节在本实施例中依然有效，为了减少重复，这里不再赘述。相应地，本实施例中提到的相关技术细节也可应用在前述互调干扰信号的重构方法实施例中。
值得说明的是，上述功能模块可以是软件模块，也可以是硬件模块。在实际应用中，一个功能模块可以是一个物理单元，也可以是一个物理单元的一部分，还可以以多个物理单元的组合实现。此外，为了突出本申请的创新部分，本实施方式中并没有将与解决本申请所提出的技术问题关系不太密切的单元引入，但这并不表明本实施方式中不存在其它的单元。
在一个实施例中，提供了一种电子设备，如图7所示，包括数字域互调消除模块，其包含比如图6中互调干扰信号的重构装置。该电子装置还可以包含模拟域互调消除模块，比如现有的一些在模拟域实现互调干扰消除的装置。数字域互调消除模块与模拟域互调消除模块级联，丰富了本申请提供的互调干扰信号的重构方法或装置的应用场景。
值得说明的是，模拟域互调消除模块一般位于射频芯片之前，从接收信号中消除互调干扰。而数字域互调消除模块一般位于射频芯片和基带芯片之间，进一步从接收信号中消除互调干扰，有利于更好地消除互调干扰。
在一个实施例中，提供了一种电子设备，如图8所示，包括：至少一个处理器801；以及存储器802；其中，存储器存储有可被至少一个处理器执行的一个或多个程序，程序包含指令，该指令被至少一个处理器执行，以使至少一个处理器能够执行本申请上述任一实施例的互调干扰信号的重构方法。
其中，存储器802和处理器801采用总线方式连接，总线可以包括任意数量的互联的总线和桥，总线将一个或多个处理器801和存储器802的各种电路连接在一起。总线还可以 将诸如外围设备、稳压器和功率管理电路等之类的各种其他电路连接在一起，这些都是本领域所公知的，因此，本文不再对其进行进一步描述。总线接口在总线和收发机之间提供接口。收发机可以是一个元件，也可以是多个元件，比如多个接收器和发送器，提供用于在传输介质上与各种其他装置通信的单元。经处理器处理的数据通过天线在无线介质上进行传输，进一步，天线还接收数据并将数据传送给处理器801。
处理器801负责管理总线和通常的处理，还可以提供各种功能，包括定时，外围接口，电压调节、电源管理以及其他控制功能。而存储器802可以被用于存储处理器801在执行操作时所使用的数据。
本实施例的电子设备可以为，但不限于，终端设备或者网络设备。作为在此使用的“终端设备”包括但不限于经由无线接口，如，针对蜂窝网络、无线局域网(Wireless Local Area Network，WLAN)、诸如DVB-H网络的数字电视网络、卫星网络、AM-FM广播发送器；和/或另一终端设备的被设置成接收/发送通信信号的装置；和/或物联网(Internet of Things，IoT)设备。被设置成通过无线接口通信的终端设备可以被称为“无线通信终端”、“无线终端”或“移动终端”。移动终端的示例包括但不限于卫星或蜂窝电话；可以组合蜂窝无线电电话与数据处理、传真以及数据通信能力的个人通信系统(Personal Communications System，PCS)终端；可以包括无线电电话、寻呼机、因特网/内联网接入、Web浏览器、记事簿、日历以及/或全球定位系统(Global Positioning System，GPS)接收器的PDA；以及常规膝上型和/或掌上型接收器或包括无线电电话收发器的其它电子装置。终端设备可以指接入终端、用户设备(User Equipment，UE)、用户单元、用户站、移动站、移动台、远方站、远程终端、移动设备、用户终端、终端、无线通信设备、用户代理或用户装置。接入终端可以是蜂窝电话、无绳电话、会话启动协议(Session Initiation Protocol，SIP)电话、无线本地环路(Wireless Local Loop，WLL)站、个人数字处理(Personal Digital Assistant，PDA)、具有无线通信功能的手持设备、计算设备或连接到无线调制解调器的其它处理设备、车载设备、可穿戴设备、5G网络中的终端设备或者未来演进的PLMN中的终端设备等。网络设备可以为特定的地理区域提供通信覆盖，并且可以与位于该覆盖区域内的终端设备进行通信。可选地，网络设备可以是GSM系统或CDMA系统中的基站(Base Transceiver Station，BTS)，也可以是WCDMA系统中的基站(NodeB，NB)，还可以是LTE系统中的演进型基站(Evolutional Node B，eNB或eNodeB)，或者是云无线接入网络(Cloud Radio Access Network，CRAN)中的无线控制器，或者该网络设备可以为移动交换中心、中继站、接入点、车载设备、可穿戴设备、集线器、交换机、网桥、路由器、5G网络中的网络侧设备或者未来演进的公共陆地移动网络(Public Land Mobile Network，PLMN)中的网络设备等。
在一个实施例中，提供了一种非易失性计算机存储介质，存储有可被处理器执行的程序，该程序在被处理器执行时，实现本申请上述任一实施例的互调干扰信号的重构方法。
在一个实施例中，提供了一种芯片，包括：至少一个处理器；与所述至少一个处理器通信连接的存储器。其中，存储器存储有可被至少一个处理器执行的一个或多个程序；一个或多个程序包含指令，该指令在被至少一个处理器执行时，使得至少一个处理器执行前述的互调干扰信号的重构方法。
本领域技术人员可以理解，实现上述实施例方法中的全部或部分步骤是可以通过程序来指令相关的硬件来完成，该程序存储在一个存储介质中，包括若干指令用以使得一个设备(可以是单片机，芯片等)或处理器(processor)执行本申请各个实施例所述方法的全部或部分步骤。而前述的存储介质包括：U盘、移动硬盘、只读存储器(ROM，Read-Only Memory)、随机存取存储器(RAM，Random Access Memory)、磁碟或者光盘等各种可以存储程序代码的介质。
本领域的普通技术人员可以理解，上述各实施方式是实现本申请的具体实施例，而在实际应用中，可以在形式上和细节上对其作各种改变，而不偏离本申请的精神和范围。

Claims (21)

  1. 一种互调干扰信号的重构方法，包括：
    获取数字下行信号；其中，所述数字下行信号包括有用信号和互调干扰信号；
    从模型库中选取与所述有用信号所处的频段中各频点对应的幅值计算模型；其中，所述模型库包括产生互调干扰的各频点对应的幅值计算模型；
    基于基带形式的本地上行信号和所述选取的幅值计算模型，确定互调干扰序列中各频点的幅值；
    基于互调干扰信道在所述各频点的增益和所述互调干扰序列中各频点的幅值，重构所述互调干扰信号。
  2. 如权利要求1所述的方法，其中，所述模型库通过以下方法建立：
    确定第一类干扰频点；其中，所述第一类干扰频点至少包括特定频段内第一频段频点和第二频段频点的和，所述第一频段内的载波频率高于所述第二频段内的载波频率；
    确定第二类干扰频点；其中，所述第二类干扰频点至少包括所述特定频段内所述第一频段频点和所述第二频段频点的差；
    基于卷积运算，得到所述第一类干扰频点中各频点的幅值计算式和所述第二类干扰频点中各频点的幅值计算式；
    基于所述第一类干扰频点和所述第二类干扰频点中相同频点对应的幅值计算式，确定所述相同频点对应的幅值计算模型。
  3. 如权利要求2所述的方法，其中，所述基于卷积运算，得到所述第一类干扰频点中各频点的幅值计算式和所述第二类干扰频点中各频点的幅值计算式，包含：
    对所述第一频段的基带序列与所述第二频段的基带序列进行至少一次卷积运算，得到所述第一类干扰频点中各频点的幅值计算式；
    对所述第一频段的基带序列与所述第二频段的基带序列的共轭倒序进行至少一次卷积运算，得到所述第二类干扰频点中各频点的幅值计算式。
  4. 如权利要求3所述的方法，其中，所述对所述第一频段的基带序列与所述第二频段的基带序列进行至少一次卷积运算，包括：
    确定所述第一频段的基带序列与所述第二频段的基带序列中的第一序列和第二序列；
    基于第一分段长度，对所述第一序列进行分段；
    对所述第二序列进行补零；其中，补零位数根据所述第一分段长度确定；
    基于第一重叠长度，对补零后的所述第二序列进行重叠分段，其中，所述第一重叠长度与所述补零位数相同；
    通过快速傅里叶变换和快速傅里叶逆变换计算所述第一序列的每一段与所述第二序列的每一段的卷积；
    叠加所有卷积结果，得到所述第一类干扰频点中各频点的幅值计算式。
  5. 如权利要求3所述的方法，其中，所述对所述第一频段的基带序列与所述第二频段的基带序列的共轭倒序进行至少一次卷积运算，包括：
    确定所述第一频段的基带序列与所述第二频段的基带序列的共轭倒序中的第三序列和第四序列；
    基于第二分段长度，对所述第三序列进行分段；
    对所述第四序列进行补零；其中，补零位数根据所述第二分段长度确定；
    基于第二重叠长度，对补零后的所述第四序列进行重叠分段，其中，所述第二重叠长度与所述补零位数相同；
    通过快速傅里叶变换和快速傅里叶逆变换计算所述第三序列的每一段与所述第四序列的每一段的卷积；
    叠加所有卷积结果，得到所述第二类干扰频点中各频点的幅值计算式。
  6. 如权利要求1至5中任意一项所述的方法，其中，所述互调干扰信道在各频点的增益通过以下方法估计得到：
    获取接收信号中的互调干扰信号对应的实际序列；
    获取基带形式的参考序列；其中，所述参考序列用于进行互调干扰信道估计；
    根据所述实际序列、所述参考序列和第一信道估计算法，得到所述互调干扰信道在所述各频点的增益。
  7. 如权利要求1至5中任意一项所述的方法，其中，所述互调干扰信道在各频点的增益通过以下方法估计得到：
    获取接收信号中的互调干扰信号对应的实际序列；
    从所述模型库中确定与所述实际序列所处的频段中各频点对应的幅值计算模型；
    基于基带形式的参考序列和所述确定的幅值计算模型，确定互调干扰序列中各频点对应的幅值；
    根据所述实际序列、所述互调干扰序列中各频点对应的幅值和第二信道估计算法，得到所述互调干扰信道在各频点的增益。
  8. 如权利要求1至7任意一项所述的方法，其中，重构所述互调干扰信号，包括：
    基于互调干扰序列中各频点的幅值与互调干扰信道中对应频点的增益的乘积，确定所述重构的互调干扰信号。
  9. 如权利要求1至8任意一项所述的方法，其中，所述有用信号基于所述重构的互调干扰信号和所述数字下行信号得到。
  10. 一种互调干扰信号的重构装置，包括：
    获取模块，用于获取数字下行信号；其中，所述数字下行信号包含有用信号和互调干扰信号；
    选取模块，用于从模型库中选取与所述有用信号所处的频段中各频点对应的幅值计算模型；其中，所述模型库包括产生互调干扰的各频点对应的幅值计算模型；
    幅值计算模块，用于基于基带形式的本地上行信号和所述选取的幅值计算模型，确定互调干扰序列中各频点的幅值；
    重构模块，用于基于互调干扰信道在各频点的增益，和所述互调干扰序列中各频点的幅值，重构所述互调干扰信号。
  11. 如权利要求10所述的装置，其中，所述装置还包括模型建立模块；所述模型建立模块用于通过以下方法建立模型库：
    确定第一类干扰频点；其中，所述第一类干扰频点是少包括特定频段内第一频段频点和第二频段频点的和；所述第一频段内的载波频率高于所述第二频段内的载波频率；
    确定第二类干扰频点；其中，所述第二类干扰频点至少包括所述特定频段内所述第一频段频点和所述第二频段频点的差；
    基于卷积运算，得到所述第一类干扰频点中各频点的幅值计算式和所述第二类干扰频点中各频点的幅值计算式；
    基于所述第一类干扰频点和所述第二类干扰频点中相同频点对应的幅值计算式，确定所述相同频点对应的幅值计算模型。
  12. 如权利要求11所述的装置，其中，所述模型建立模块还用于：
    在基于卷积运算，得到所述第一类干扰频点中各频点的幅值计算式和所述第二类干扰频 点中各频点的幅值计算式时，对所述第一频段的基带序列与所述第二频段的基带序列进行至少一次卷积运算，得到所述第一类干扰频点中各频点的幅值计算式，对所述第一频段的基带序列与所述第二频段的基带序列的共轭倒序进行至少一次卷积运算，得到所述第二类干扰频点中各频点的幅值计算式。
  13. 如权利要求12所述的装置，其中，所述模型建立模块还用于：
    在对所述第一频段的基带序列与所述第二频段的基带序列进行至少一次卷积运算时，确定所述第一频段的基带序列与所述第二频段的基带序列中的第一序列和第二序列；
    基于第一分段长度，对所述第一序列进行分段；
    对所述第二序列进行补零；其中，补零位数根据所述第一分段长度确定；
    基于第一重叠长度，对补零后的所述第二序列进行重叠分段，其中，所述第一重叠长度与所述补零位数相同；
    通过快速傅里叶变换和快速傅里叶逆变换计算所述第一序列的每一段与所述第二序列的每一段的卷积；
    叠加所有卷积结果，得到所述第一类干扰频点中各频点的幅值计算式。
  14. 如权利要求12所述的装置，其中，所述模型建立模块还用于：
    在对所述第一频段的基带序列与所述第二频段的基带序列的共轭倒序进行至少一次卷积运算，确定所述第一频段的基带序列与所述第二频段的基带序列的共轭倒序中的第三序列和第四序列；
    基于第二分段长度，对所述第三序列进行分段；
    对所述第四序列进行补零；其中，补零位数根据所述第二分段长度确定；
    基于第二重叠长度，对补零后的所述第四序列进行重叠分段，其中，所述第二重叠长度与所述补零位数相同；
    通过快速傅里叶变换和快速傅里叶逆变换计算所述第三序列的每一段与所述第四序列的每一段的卷积；
    叠加所有卷积结果，得到所述第二类干扰频点中各频点的幅值计算式。
  15. 如权利要求10至14中任意一项所述的装置，其中，所述装置包括第一信道估计模块；第一信道估计模块用于通过以下方法估计得到所述互调干扰信道在各频点的增益：
    获取接收信号中的互调干扰信号对应的实际序列；
    获取基带形式的参考序列；其中，所述参考序列用于进行互调干扰信道估计；
    根据所述实际序列、所述参考序列和第一信道估计算法，得到所述互调干扰信道在所述各频点的增益。
  16. 如权利要求10至14中任意一项所述的装置，其中，所述装置包括第二信道估计模块；第二信道估计模块用于通过以下方法估计得到所述互调干扰信道在各频点的增益：
    获取接收信号中的互调干扰信号对应的实际序列；
    从所述模型库中确定与所述实际序列所处的频段中各频点对应的幅值计算模型；
    基于基带形式的参考序列和所述确定的幅值计算模型，确定互调干扰序列中各频点对应的幅值；
    根据所述实际序列、所述互调干扰序列中各频点对应的幅值和第二信道估计算法，得到所述互调干扰信道在各频点的增益。
  17. [根据细则91更正 11.12.2019]　
    如权利要求10至16中任意一项所述的装置，其中，所述重构模块还用于基于互调干扰序列中各频点的幅值与互调干扰信道中对应频点的增益的乘积，确定所述重构的互调干扰信号。
  18. [根据细则91更正 11.12.2019]　
    如权利要求10至17中任意一项所述的装置，其中，所述有用信号基于所述重构的互调干扰信号和所述数字下行信号得到。
  19. 一种电子设备，包括：
    至少一个处理器；
    存储器，与所述至少一个处理器通信连接；其中，
    所述存储器存储有可被所述至少一个处理器执行的一个或多个程序；
    所述一个或多个程序包含指令，所述指令在被至少一个处理器执行时，使得所述至少一个处理器执行权利要求1至9中任意一项所述的互调干扰信号的重构方法。
  20. 一种计算机可读存储介质，存储有可被处理器执行的程序，所述程序在被处理器执行时，实现权利要求1至9中任意一项所述的互调干扰信号的重构方法。
  21. 一种芯片，包括：
    至少一个处理器；
    存储器，与所述至少一个处理器通信连接；其中，
    所述存储器存储有可被所述至少一个处理器执行的一个或多个程序；
    所述一个或多个程序包含指令，所述指令在被至少一个处理器执行时，使得所述至少一个处理器执行权利要求1至9中任意一项所述的互调干扰信号的重构方法。
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