WO2020103434A1 - 自适应抵消无源互调信号的装置、方法及应用设备 - Google Patents

自适应抵消无源互调信号的装置、方法及应用设备

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Publication number
WO2020103434A1
WO2020103434A1 PCT/CN2019/090975 CN2019090975W WO2020103434A1 WO 2020103434 A1 WO2020103434 A1 WO 2020103434A1 CN 2019090975 W CN2019090975 W CN 2019090975W WO 2020103434 A1 WO2020103434 A1 WO 2020103434A1
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WIPO (PCT)
Prior art keywords
signal
passive intermodulation
intermodulation
frequency
amplitude
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Application number
PCT/CN2019/090975
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English (en)
French (fr)
Inventor
孟庆南
Original Assignee
香港梵行科技有限公司
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Publication date
Priority claimed from CN201821919998.5U external-priority patent/CN209088944U/zh
Application filed by 香港梵行科技有限公司 filed Critical 香港梵行科技有限公司
Publication of WO2020103434A1 publication Critical patent/WO2020103434A1/zh

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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/38—Transceivers, i.e. devices in which transmitter and receiver form a structural unit and in which at least one part is used for functions of transmitting and receiving
    • H04B1/40—Circuits
    • H04B1/50—Circuits using different frequencies for the two directions of communication
    • H04B1/52—Hybrid arrangements, i.e. arrangements for transition from single-path two-direction transmission to single-direction transmission on each of two paths or vice versa
    • H04B1/525—Hybrid arrangements, i.e. arrangements for transition from single-path two-direction transmission to single-direction transmission on each of two paths or vice versa with means for reducing leakage of transmitter signal into the receiver

Definitions

  • the invention relates to the field of communication technology, and in particular to an apparatus, method and application equipment for adaptively canceling passive intermodulation signals.
  • wireless transceiver devices In communication systems, a large number of wireless transceiver devices are used.
  • the wireless transceiver equipment itself contains devices that generate passive intermodulation signals, such as RF duplexers, filters, combiners, etc .; the link from the antenna port of the wireless transceiver equipment to the antenna also contains many passive intermodulation signals.
  • Devices such as couplers, RF cables, tower-mounted amplifiers, etc.
  • the passive intermodulation signal level generated by the transmitting channel is as low as possible when the wireless transceiver equipment is working, so as to prevent the passive intermodulation signal from falling into the receiving channel and causing intermodulation interference to the receiving channel.
  • the current passive intermodulation cancellation technology generally has two ways:
  • Comparative document CN100490307C discloses an invention patent titled: "Signal Processing Circuit, Base Station and Method for Eliminating Intermodulation Products".
  • This patent divides the original carrier of the input non-linear unit into two channels, and inputs two branches respectively.
  • One original carrier passes through the non-linear unit to generate a processing signal containing the first set of intermodulation products
  • the second original carrier passes through the splitter, frequency multiplier, mixer and adjustment circuit.
  • Generate a control signal containing the second set of higher-order intermodulation products and finally superimpose the two signals. It uses the second set of high-order intermodulation and the first set of intermodulation products to have the same frequency, close to the same amplitude, and opposite phase to cancel the intermodulation signal.
  • the technical solution has the following shortcomings: 1.
  • the technical solution is not applicable to passive devices, it does not consider the difference of intermodulation values at different positions inside the nonlinear unit, this difference is very obvious for passive devices, in passive circuits
  • the amplitude attenuation and phase change of the transmitted signal are very large.
  • the intermodulation signal generated at the front end of the circuit will be greatly attenuated during signal transmission.
  • the intermodulation signal output by the circuit only contains the intermodulation signal generated at the end of the circuit. Therefore, for the duplexer In other words, if the signal is taken from the front end of the non-linear unit, the generated intermodulation cancellation signal cannot be canceled with the antenna port intermodulation signal; 2.
  • the intermodulation cancellation signal generated by this technical solution is the second group of high-order intermodulation
  • the product is limited to a fixed-order intermodulation product, which can only eliminate the intermodulation signal of the nonlinear unit in the corresponding frequency band, which has limitations.
  • Comparative document 201310048951.1 discloses an invention patent entitled "An Intermodulation Cancellation Device for Passive Devices". This patent directly couples the emission signal containing high-order intermodulation products from the output of the passive device. After the adjustment of the source regulator is transmitted to the end of the RF link with the intermodulation signal generator, it is adjusted again by the passive regulator to obtain the same frequency, level and opposite phase as the intermodulation signal transmitted by the passive device. The cancellation signal of the signal is superimposed on the output signal of the passive nonlinear unit through the coupler to achieve intermodulation cancellation.
  • the technical solution has the following disadvantages: 1.
  • the technical solution uses a passive regulator, amplitude adjustment and phase adjustment are passive devices, if you want to achieve amplitude adjustment and phase adjustment, you need to drive the passive regulator with the help of external force, such as using a motor drive , Or directly driven by manual, these methods will make the actual application cost high, and it is not easy to commercialize; 2. Because there is no feedback detection circuit for passive intermodulation cancellation results, the cancellation results cannot be monitored and adjusted in real time.
  • the purpose of the present invention is to provide a digitally adaptive device for canceling the passive intermodulation signal in the wireless transceiver system in response to the defects of the prior art, so that it can connect the wireless transceiver device and the antenna port of the device to the antenna
  • the invention provides a device for adaptively canceling passive intermodulation signals. Its technical solution is as follows: it includes a coupler, duplexer, antenna, antenna feed component, canceler circuit, receiving unit, and passive intermodulation detection circuit. Digital processing unit, transmitting circuit unit and transceiver module;
  • the transmission signal of the transceiver module is linearly amplified by the transmission circuit unit, so that the duplexer and its antenna link generate a passive intermodulation signal, and some of the passive intermodulation signal falls into the receiving frequency band of the duplexer And the components with a certain frequency interval from the received signal;
  • the coupler couples the radio frequency signal from the link of the antenna port of the duplexer to the canceller circuit;
  • the radio frequency signal includes a transmission signal, a passive intermodulation signal, and a reception signal;
  • a main path of the coupler The port is connected to the antenna port of the duplexer, another main channel port is connected to the antenna feed component on the antenna link, the coupling port of the coupler and the RF port of the canceller circuit are connected;
  • the canceller circuit uses the transmitted signal from the radio frequency signal from the coupler to generate an intermodulation signal in the canceller circuit. After the intermodulation signal is reflected, the amplitude adjustment and phase adjustment of the canceller circuit are performed, and the output is coupled to The main path of the coupler forms an intermodulation cancellation signal having the same frequency, the same amplitude and the opposite phase as the component frequency falling within the receiving frequency band and having a certain frequency interval from the receiving signal in the passive intermodulation signal;
  • the passive intermodulation detection circuit is used to obtain the radio frequency signal after the receiving port of the duplexer through the receiving unit, and after gain-adjustable amplification, down conversion, and finally converted into a digital signal and input to the digital processing unit,
  • the radio frequency signal includes components of the received signal and the passive intermodulation signal that fall into the receiving frequency band;
  • the digital processing unit is used to detect the amplitude of the passive intermodulation signal according to the frequency information of the transmitted signal, and when the detected amplitude is greater than the preset value, control the canceller circuit to generate an intermodulation cancellation signal Cancel with the passive intermodulation signal in the radio frequency signal.
  • the canceller circuit uses the transmit signal from the radio frequency signal from the coupler to generate a mutual frequency with the same frequency, different amplitude and different phase in the canceller circuit as the passive intermodulation signal in the radio frequency signal Modulation signal, and the amplitude relationship and phase relationship between the components of the intermodulation signal falling into the receiving frequency band and the components of the passive intermodulation signal generated by the duplexer and its antenna link falling into the receiving frequency band
  • the amplitude relationship and phase relationship between them are consistent;
  • the amplitude of the intermodulation signal generated by the power of the received signal and the passive intermodulation signal in the radio frequency signal coupled to the canceller circuit on the intermodulation signal generator in the canceller circuit is much smaller than the passive intermodulation
  • the amplitude of the signal does not affect the passive intermodulation cancellation results
  • the intermodulation signal After being reflected, the intermodulation signal passes through the amplitude adjustment and phase adjustment of the canceller circuit, and is coupled to the main path of the coupler to form a certain frequency interval with the passive intermodulation signal that falls into the receiving frequency band and is received from the receiving signal
  • the intermodulation cancellation signal of the same frequency, the same amplitude and the opposite phase of the component, the intermodulation cancellation signal cancels the component in the passive intermodulation signal, the passive intermodulation signal after cancellation is less than or equal to the passive intermodulation pre Set value;
  • the transmitted and received signals in the duplexer and its antenna link operate normally in the duplexer and its antenna link;
  • the respective components include a single third-order component, or a single fifth-order component, or even a single higher-order component, or multiple different-frequency third-order components, or multiple different-frequency fifth-order components, or even multiple multiple-frequency components Higher order components, or both 3rd and 5th order components and even higher order components.
  • the digital processing unit is used to detect the amplitude of the passive intermodulation signal according to the frequency information of the transmitted signal, and when the detected amplitude is greater than the preset value, control the canceller circuit to generate
  • the method for canceling the intermodulation cancellation signal and the passive intermodulation signal in the radio frequency signal is as follows:
  • the digital processing unit first calculates the frequency information of the passive intermodulation signal related to it based on the frequency information of the transmitted signal, and converts it into the filtering parameter of the passive intermodulation signal;
  • bandwidth information and passive intermodulation signal frequency bandwidth information to obtain the frequency interval between them, and then select the corresponding digital filtering method and integration method, and finally realize the amplitude detection of passive intermodulation signal ;
  • the canceller circuit When the detection amplitude is less than or equal to the preset value, the canceller circuit does not generate an intermodulation cancellation signal, and does not affect the passive intermodulation index of the duplexer and its antenna link;
  • the adjustment of the amplitude and phase of the canceller circuit is controlled to produce the same frequency and amplitude as the passive intermodulation signal of the duplexer and its antenna link
  • the same and opposite phase intermodulation cancellation signal cancels with the passive intermodulation signal in the radio frequency signal, and maintains the real-time adjustment of the amplitude and phase of the canceller circuit based on the detection result of the amplitude of the passive intermodulation signal
  • the working state in which the passive intermodulation signal cancellation result is less than or equal to the preset value.
  • the method for the digital processing unit to calculate the amplitude of the passive intermodulation signal is:
  • the digital processing unit first calculates the frequency information of the passive intermodulation signal related to the transmitted signal frequency information
  • bandwidth information and passive intermodulation signal frequency bandwidth information to find the frequency interval between them, and calculate the passive intermodulation signal amplitude according to the frequency interval;
  • the method for calculating the amplitude of the passive intermodulation signal is a direct filter integration method or a segmented filter integration method
  • the direct filtering integration method refers to directly digitally filtering and integrating the amplitude based on the bandwidth of the passive intermodulation signal, at which time the frequency interval between each order component of the passive intermodulation signal falling into the receiving frequency band and the receiving signal To be greater than or equal to the passive intermodulation signal in the digital filtering algorithm of the digital filter passband to stopband transition band bandwidth, this frequency interval is the basis of the direct filter integration method;
  • the segmented filtering integration method refers to dividing the bandwidth of the passive intermodulation signal into several sub-bandwidths, performing digital filtering and integrating to obtain the amplitude according to each sub-bandwidth, and then accumulating the amplitudes corresponding to all the sub-bandwidths to obtain the entire signal amplitude.
  • this frequency interval is the use of segmented filter integration The basis of law.
  • it also includes a frequency discrimination circuit for the transmitted signal
  • the digital processing unit acquiring the transmitted signal frequency information and the received signal frequency information includes:
  • the transmission signal frequency discrimination circuit uses the transmission signal frequency discrimination circuit to obtain the transmission signal from the transmission circuit unit, convert it into a digital signal, enter the digital processing unit for frequency discrimination processing, obtain the relevant transmission signal frequency information, and the duplex frequency interval between the transmission signal and the received signal Calculate the frequency information of the corresponding received signal; or
  • the canceler circuit includes an amplitude modulation phase modulator and an intermodulation signal generator.
  • the amplitude modulation phase modulator includes an amplitude modulation circuit and a phase modulation circuit.
  • One end of the amplitude modulation phase modulator and the coupling port of the coupler directly or Connected by a radio frequency switch, the other end is connected to the intermodulation signal generator.
  • the amplitude modulation circuit is composed of an adjustable attenuator and a fixed attenuator; the phase modulation circuit includes at least two adjustable phase shifters; the amplitude adjustment range of the amplitude modulation phase modulator is greater than 30dB, and the phase adjustment range is greater than 180 Degree; the load-bearing power of the amplitude-modulation phase modulator in the canceller circuit is greater than or equal to the load-bearing power threshold of the canceller circuit, and the operating frequency band of the amplitude-modulation phase modulator includes the transmitting frequency band and the receiving frequency band of the duplexer
  • the gain fluctuation in the frequency band of the AM phase modulator is related to the transmitting frequency band and the receiving frequency band and needs to be within a certain threshold range.
  • the canceller circuit includes an amplitude modulation phase modulator, an intermodulation signal generator, a second amplitude modulation circuit, a first circulator, and a second circulator.
  • the amplitude modulation phase modulator includes a first amplitude modulation circuit and a phase modulation Circuit, one end of the AM phase modulator and the second AM circuit are connected to the first circulator, the other end of the AM phase modulator and the second AM circuit are connected to the intermodulation signal generator through the second circulator,
  • the coupling port between the first circulator and the coupler is directly or through a radio frequency switch.
  • the second amplitude modulation circuit is used to make the intermodulation signal generator withstand a suitable power radio frequency signal; the amplitude modulation phase modulator is used for amplitude modulation and phase modulation processing of the intermodulation signal generated by the intermodulation signal generator
  • the first amplitude modulation circuit includes at least one adjustable attenuator; the phase modulation circuit includes at least two adjustable phase shifters; the second amplitude modulation circuit is composed of a fixed attenuator or an adjustable attenuator;
  • the frequency bandwidth of the first circulator and the second circulator includes the transmission frequency band and the reception frequency band of the duplexer; the amplitude adjustment range of the amplitude modulation phase modulator is greater than 30dB, the phase adjustment range is greater than 180 degrees, and the amplitude modulation phase modulation
  • the working frequency band of the amplifier includes the receiving frequency band of the duplexer.
  • the gain fluctuation in the frequency band of the AM phase modulator is related to the receiving frequency band and needs to be within a certain threshold range; the load
  • the intermodulation signal generator includes a single diode, a single transistor or multiple diodes connected in parallel; the specific model of the diode or the specific model of the transistor and the amplitude characteristic and phase of the intermodulation signal of the third, fifth or higher order of the intermodulation signal The characteristics are related; the carrying power of the intermodulation signal generator is greater than or equal to the difference between the carrying power threshold of the canceller circuit and the link loss from the radio frequency input port of the canceller circuit to the intermodulation signal generator.
  • the passive intermodulation detection circuit includes a local oscillator and a low-noise amplifier connected in sequence between its RF input port and digital sampling signal output port, RF filter and small signal amplification unit, mixer, and IF filter The output terminal of the local oscillator is connected to a mixer.
  • the passive intermodulation detection circuit includes a low-noise amplifier, a radio frequency filtering and small signal amplifying unit and a down-conversion and analog-to-digital conversion unit connected between the radio frequency input port and the digital sampling signal output port in sequence.
  • the passive intermodulation detection circuit includes at least a down-conversion module and a high-speed analog-to-digital converter, and the passive intermodulation detection circuit is connected to the digital processing unit through a high-speed analog-to-digital converter;
  • the down conversion module may convert the received radio frequency signal into an intermediate frequency signal, or convert the received radio frequency signal into a zero intermediate frequency signal;
  • the sampling dynamic range of the high-speed analog-to-digital converter needs to be greater than the difference between the maximum power value of the received signal and the power value corresponding to the preset value of the passive intermodulation, and the sampling rate is greater than or equal to 2 times the bandwidth of the duplexer receiving band ;
  • the minimum power that the passive intermodulation detection circuit can sample is less than or equal to the passive intermodulation power value corresponding to the preset value, and at the same time, the circuit can adjust the link gain according to the amplitude of the total power of the received RF signal.
  • the radio frequency signal obtained by the source intermodulation detection circuit contains components of the received signal and the passive intermodulation signal falling into the receiving frequency band.
  • the passive intermodulation detection circuit couples the RF signal from the link in front of the RF input port of the receiving unit through a coupler, and the RF input port of the receiving unit passes through the main path of the coupler and the duplexer receiving port connection;
  • the gain of the passive intermodulation detection circuit is determined by the required passive intermodulation preset value, the minimum sampling power of the high-speed analog-to-digital converter in the passive intermodulation detection circuit, the link noise figure, and the coupling degree of the receiving component;
  • the maximum value of the received signal power of the passive intermodulation detection circuit is greater than m, where m is the difference between the maximum received signal power specified by the communication standard corresponding to the device and the coupling degree of the receiving component.
  • the passive intermodulation detection circuit obtains a radio frequency signal from a radio frequency amplifier in the receiving unit through a power splitter or coupler, and the radio frequency input port of the receiving unit is connected to the receiving port of the duplexer;
  • the duplexer represents a passive device in a wireless transceiver device; the antenna feed component and antenna represent a passive device in an antenna link of a wireless transceiver system, and the antenna feed component represents an antenna link A combination of single or multiple passive devices.
  • passive devices include cables, connectors, couplers, and combiners.
  • the signal that excites the duplexer and its antenna link to generate a passive intermodulation signal is the same as the signal that excites the intermodulation signal generator to generate an intermodulation signal, both of which originate from the transmitting circuit unit.
  • the signal is transmitted, so the passive intermodulation signal generated by the passive device and the intermodulation signal generated by the intermodulation signal generator have the same frequency and the same bandwidth;
  • the antenna link is the link from the antenna port of the duplexer to the antenna
  • the transmission signal is composed of a multi-tone signal or a multi-carrier modulation signal.
  • the passive intermodulation signals with a certain frequency interval from the received signal when the duplexer or the antenna feeder component or the antenna generates a single or multiple passive devices simultaneously and superimposes them only When a single 3rd order, or a single 5th order or a single higher order component falls into the receiving band of the duplexer, and the passive intermodulation index tested from the receiving port of the duplexer fails to meet the preset value requirements,
  • the maximum amplitude of the intermodulation cancellation signal that the intermodulation signal generator can generate is greater than the amplitude of a single component of the passive intermodulation signal of the duplexer and its antenna link that falls into the corresponding frequency of the receiving frequency band;
  • the maximum amplitude of the intermodulation cancellation signal corresponding to the frequency of the passive intermodulation component that the intermodulation signal generator can generate is greater than the passive intermodulation of the duplexer and its antenna link.
  • the intermodulation signal generator can The maximum amplitude of the generated intermodulation cancellation signal corresponding to the frequency of the passive intermodulation component is greater than the multiple corresponding frequency components that fall into the receiving frequency band in the passive intermodulation signal of the duplexer and its antenna link Amplitude; the amplitude relationship and phase relationship between multiple specific order components in the intermodulation signal generated on the intermodulation signal generator and the passive intermodulation signal generated by the duplexer and its antenna link The amplitude relationship and the phase relationship between multiple specific order components in.
  • the canceller circuit is connected to the antenna link behind the duplexer antenna port through a coupler; a main access port of the coupler is connected to the duplexer antenna port and the distance needs to be controlled from 0 to 1 meter Within the range, the other main channel port of the coupler is connected to the antenna feeder component, and the coupling port of the coupler is connected to the canceler circuit; the insertion loss of the coupler is less than 0.2dB, the coupling degree of the coupler ranges from 25dB to 45dB, coupling The coupling port of the coupler is a forward coupling port relative to the transmitted signal.
  • the carrying power of the coupler must be greater than the maximum transmit power peak of the device that adaptively cancels the passive intermodulation signal.
  • the bandwidth of the coupler includes the transmit frequency band, the receive frequency band, and both Duplex interval between, the frequency fluctuation of the coupler's frequency band is related to the transmission frequency band and the reception frequency band and needs to be within a certain threshold range; the load-carrying power threshold of the canceller circuit must be greater than or equal to the power gate of the coupler The difference between the limit value and the coupling degree of the coupler; in order for the intermodulation signal generator in the canceller circuit to generate a passive intermodulation cancellation signal, the minimum value of the power of the transmitted signal loaded on the canceller circuit must be greater than a certain Power threshold.
  • the digital processing unit is connected to the canceller circuit through a multi-channel digital-to-analog converter, and transfers the controlled amounts of amplitude and phase to the canceller circuit.
  • the amplitude adjustment accuracy and phase adjustment accuracy requirements of the canceller circuit Mainly derived from the need for passive intermodulation signal cancellation capabilities;
  • one interface is used to obtain the sampling signal of the high-speed analog-to-digital converter in the passive intermodulation detection circuit, so as to carry out the digitalization of the passive intermodulation signal Filtering and amplitude calculation;
  • another interface is used to configure the parameters of the passive intermodulation detection circuit through a bus, which includes an I2C bus and an SPI bus;
  • the transmission signal frequency discrimination circuit is connected to the digital processing unit through a high-speed analog-to-digital converter; at the same time, there is also an interface between the digital processing unit and the transmission signal frequency discrimination circuit for configuring the transmission signal frequency discrimination circuit through the bus Parameters of
  • the digital processing unit is provided with at least one information interaction interface, whose functions include program download, configuration information input, remote alarm and maintenance;
  • the configuration information that needs to be input includes the transmission signal bandwidth and frequency band of the device, the reception signal bandwidth and frequency band, and passive The order and frequency band information of the main interference components in the intermodulation signal, the preset value of the passive intermodulation signal and the time-varying curve, the maximum number of cancellations;
  • the digital processing unit can obtain the transmitted signal frequency information and the information exchange interface Receive signal frequency information;
  • the information interaction interface can also interact with Internet background resources: upload passive intermodulation values during the operation of the device, experience curves of passive intermodulation values changing with time, and passive The status information of each module circuit in the intermodulation signal adaptive cancellation device; or download the integrated optimized passive intermodulation signal preset value and time-varying curve;
  • the digital processing unit includes at least a logic processing and arithmetic processing device with digital signal processing functions for receiving digital signals, arithmetic processing, digital signal output, control and configuration signal output, etc.
  • the logic processing and arithmetic processing includes but is not limited to field programmable gate array device, central processor, digital signal processor; the hardware composition of the information interaction interface of the digital processing unit includes but not limited to Ethernet interface, optical fiber interface, RS-485 bus interface;
  • the number of digits of the digital-to-analog converter in the digital processing unit ranges from 10 to 18 bits, and there are at least three digital-to-analog converters.
  • One main channel port of the coupler is connected to the antenna port of the duplexer, another main channel port is connected to the antenna feed component on the antenna link, and the coupling port of the coupler and the RF port of the canceller circuit are connected;
  • the signal sending end of the transceiving module is connected to the transmitting signal input port of the duplexer via the transmitting circuit unit, and the signal receiving end of the transceiving module is connected to the transmitting port of the duplexer via the receiving unit;
  • the passive intermodulation detection circuit is connected to the receiving signal output port of the duplexer through the receiving unit, and the digital sampling signal output terminal of the passive intermodulation detection circuit is connected to the digital sampling signal receiving terminal of the digital processing unit.
  • the control quantity signal output terminal of the digital processing unit is connected to the control quantity signal input terminal of the canceller circuit.
  • the digital processing unit includes a transmission signal receiving port, a first data transmission port, a second data transmission port, and an information interaction interface.
  • the radio frequency port of the transmission signal frequency discrimination circuit is The transmission circuit unit is connected, the transmission signal output end of the transmission signal frequency discrimination circuit is connected to the transmission signal receiving port of the digital processing unit, and the configuration of the first data transmission port of the digital processing unit and the passive intermodulation detection circuit.
  • the information receiving port is connected, and the second data transmission port of the digital processing unit is connected to the configuration information receiving port of the transmission signal frequency discrimination circuit.
  • the digital processing unit when the radio frequency signal in the passive intermodulation detection circuit is too large and the link is blocked, the digital processing unit will reduce the link gain of the passive intermodulation detection circuit to normally process the received signal and stop detecting passive intermodulation Signal amplitude; when the passive intermodulation detection circuit is not blocked, the digital processing unit in the process of calculating the passive intermodulation amplitude needs to process the signal from the passive intermodulation detection circuit that contains passive There is a certain frequency interval between the intermodulation signal and the received signal and the passive intermodulation signal and the received signal.
  • the present invention provides an analog wireless transceiver device using an apparatus for adaptively canceling passive intermodulation signals.
  • the technical solution includes: an apparatus for adaptively canceling passive intermodulation signals, and the apparatus for adaptively canceling passive intermodulation signals
  • the duplexer is the duplexer of the wireless transceiver equipment; the receiving unit of the apparatus for adaptively canceling passive intermodulation signals multiplexes the components or units of the receiving link of the analog wireless transceiver equipment;
  • the passive intermodulation detection circuit of the source intermodulation signal device is newly added in the analog wireless transceiver device; the transmission circuit unit of the device for adaptively canceling the passive intermodulation signal multiplexes the transmission link of the analog wireless transceiver device Components or units of the device; the digital processing unit of the device for adaptively canceling passive intermodulation signals multiplexes the components or units of the digital processing unit of the analog wireless transceiver equipment, or adds a digital processing unit to the analog wireless transceiver equipment
  • the coupling port of the coupler transmits signals relative to the analog wireless transceiver device as Forward coupling port;
  • the canceler circuit of the device for adaptively canceling passive intermodulation signals is newly added in the analog wireless transceiver device, and its radio frequency port is directly connected to the coupling port of the coupler;
  • the antenna feed component and antenna of the passive intermodulation signal device are the corresponding components and antennas on the antenna link of the analog wireless transceiver device;
  • each antenna port of the duplexer in each transceiver link is immediately adjacent to a coupler and a canceller circuit.
  • the invention provides a tower-top amplifying device using a device for adaptively canceling passive intermodulation signals.
  • the technical solution is as follows: it includes a device for adaptively canceling passive intermodulation signals and a double device for adaptively canceling passive intermodulation signals.
  • the working device is the duplexer of the tower top amplifying device; the receiving unit of the device that adaptively cancels the passive intermodulation signal multiplexes the receiving unit of the tower top amplifying device, and the passive intermodulation of the device that adaptively cancels the passive intermodulation signal
  • the modulation detection circuit needs to be newly added in the tower top amplification device, and the transmission circuit unit of the device for adaptively canceling the passive intermodulation signal multiplexes the transmission circuit unit of the tower top amplification device.
  • the transmission circuit unit is composed of a frequency discriminating coupler And the cable between the transmitting port of the duplexer and the transceiver module, wherein the coupling port of the frequency discriminating coupler is connected to the RF input port of the transmitting signal discriminating circuit, and the frequency discriminating coupler is a forward coupling port relative to the transmitting signal.
  • One main channel port of the frequency coupler is connected to the transmitting port of the duplexer, and the other main channel port is connected to the transmitting port of the transceiver module; the digital processing unit of the device that adaptively cancels the passive intermodulation signal multiplexes the digital processing of the tower top amplification device Unit, the coupler of the device that adaptively cancels the passive intermodulation signal needs to be added to the tower-top amplifying device, a main channel port of the coupler is directly connected to the antenna port of the duplexer of the wireless transceiver device, The coupling port of the coupler is a positive coupling port with respect to the transmitted signal of the tower top amplifying device; the canceler circuit of the device for adaptively canceling the passive intermodulation signal needs to be newly added in the tower top amplifying device.
  • the radio frequency port of the canceller circuit and the coupling port of the coupler are directly connected, and the antenna feed component and antenna of the device for adaptively canceling the passive intermodulation signal are the corresponding components and antennas on the antenna link of the tower top amplifying device.
  • the present invention provides a method for adaptively canceling passive intermodulation signals.
  • the technical solution includes the following steps:
  • S1 Obtain the transmitted signal bandwidth and frequency band, the received signal bandwidth and frequency band, the order and frequency band information of the main interference components in the passive intermodulation signal, the desired passive intermodulation preset value, and the time-varying curve, amplitude and The initial empirical data of the phase and the information of the maximum number of cancellations are converted into corresponding configuration parameters;
  • step S3 According to the configuration parameters of the received signal and the passive intermodulation signal in step S1 and the digital filtering parameters of the passive intermodulation signal obtained in step S2, digitally filter the sampled signal to filter out the passive intermodulation signal For other signal components other than those, obtain the amplitude value of the passive intermodulation signal that falls into the receiving frequency band;
  • step S4 determine the current working state; the default value of the state identification of the working state is: "initial working mode”; if the state identification value of the working state is "initial working mode", continue to step S5-1, otherwise continue to step S5-2 ;
  • step S5-1 Compare the passive intermodulation signal amplitude value obtained in step S3 with the passive intermodulation preset value in step S1 to determine whether the passive intermodulation signal amplitude is less than or equal to the passive intermodulation preset value ;
  • step S6 If the judgment result in step S5-1 is "Yes", then maintain the high isolation state of the link between the intermodulation signal generator and the coupler; and return to step S2;
  • step S7 If the judgment result of step S5-1 is "No", then) switch to the low isolation state of the link between the intermodulation signal generator and the coupler; and set the state identification value of the working state to "offset operation" Status "; proceed to step S8;
  • step S5-2 Compare the passive intermodulation signal amplitude value obtained in step S3 with the passive intermodulation preset value in step S1 to determine whether the passive intermodulation signal amplitude is less than or equal to the passive intermodulation preset value ; If the judgment result of step S5-2 is "Yes”, then maintain the state and return to step S2; if the judgment result of step S5-2 is "No", then execute step S8;
  • step S8 Calculate the amplitude and phase adjustment values of the canceller circuit according to the amplitude value of the passive intermodulation signal in step S3; and distribute to the amplitude modulator and phase modulator in the canceller circuit to implement cancellation; after completing the current round of cancellation processing After that, it will continue to return to step S2 to continue the next round of cancellation processing.
  • the beneficial effects of the present invention are as follows: 1.
  • the passive intermodulation signal generated by the wireless transceiver device and the passive intermodulation signal generated by any device or component in the link behind the antenna port of the wireless transceiver device fall into the component of the receiving frequency band It is cancelled on the radio frequency link in the wireless transceiver device, and a result that is better than a predetermined passive intermodulation requirement index is obtained at the receiving port of the passive device.
  • the above effect 1 makes it possible to reduce the passive intermodulation index requirements for each device in the wireless transceiver system while keeping the system passive intermodulation index unchanged, thereby reducing the manufacturing cost of each passive device;
  • the above effect 1 can also be used to eliminate the effect of deterioration of passive intermodulation indicators due to the increase in working time of the components or antennas on the duplexer or its antenna link, thereby extending the life cycle of the wireless transceiver system ;
  • the above effect 1 can also increase the index above the preset value when the system needs a better passive intermodulation index.
  • the passive intermodulation signal cancellation effect can be monitored in real time and adaptively adjusted dynamically, so that when it passes the passive device or the subsequent link When the power level, operating frequency of the signal changes, and the ambient temperature changes, it can respond dynamically and in real time to make the passive intermodulation signal cancellation result meet the expected target value. This has important practical significance.
  • FIG. 1 is a schematic structural diagram of an apparatus for adaptively canceling passive intermodulation signals according to an embodiment of the present invention.
  • FIG. 2 is a schematic diagram of the first structure of the canceller circuit B in the embodiment of the present invention.
  • FIG 3 is a schematic diagram of a second structure of the canceller circuit B in the embodiment of the present invention.
  • FIG. 4 is a schematic diagram of the superheterodyne structure of the passive intermodulation detection circuit D in the embodiment of the present invention.
  • FIG. 5 is a schematic diagram of the structure of the receiving zero intermediate frequency of the passive intermodulation detection circuit D in the embodiment of the present invention.
  • FIG. 6 is a flowchart of a method for adaptively canceling passive intermodulation signals in an embodiment of the present invention.
  • FIG. 8 is a diagram of the cancellation effect of the fifth-order component after the cancellation of the third-order component of the device of the embodiment of the present invention.
  • FIG. 9 is a schematic structural diagram of an analog wireless transceiver device of an apparatus for adaptively canceling passive intermodulation signals according to an embodiment of the present invention.
  • FIG. 10 is a schematic structural diagram of a tower-top amplifying device of an apparatus for adaptively canceling passive intermodulation signals according to an embodiment of the present invention.
  • 11 is a schematic diagram of one example of use of the wireless transceiver device and multiple transceiver links of the present invention.
  • FIG. 12 is a schematic diagram of one example of use of a wireless transceiver device of the present invention having multiple transceiver links.
  • this embodiment relates to an apparatus for adaptively canceling passive intermodulation signals, which includes a coupler A, a canceler circuit B, a passive intermodulation detection circuit D, and a digital processing unit E , Duplexer A0, transmitting circuit unit F, antenna feeder A2, antenna A1, transceiver module G, receiving unit C; the signal of the transceiver module G is linearly amplified by the transmitting circuit unit F, generating a signal greater than 40dBm
  • the duplexer A0 and the antenna feed component A2 and antenna A1 on the antenna link generate a passive intermodulation signal, and some of the passive intermodulation signals fall into the receiving frequency band of the duplexer A0 and have a certain degree with the received signal
  • the components of the frequency interval can make the passive intermodulation signal fall into the receiving frequency band of the duplexer A0 according to different configurations of the transmitted signal.
  • the transmitted signal is composed of a multi-tone signal or a multi-carrier modulation signal.
  • the transmission frequency band is 925MHz to 960MHz
  • the reception frequency band is 880MHz to 915MHz;
  • the coupler A couples the radio frequency signal from the link of the antenna port of the duplexer A0 to the canceler circuit B;
  • the radio frequency signal includes a transmission signal, a passive intermodulation signal, and a reception signal;
  • the coupler A One main path port is connected to the antenna port of the duplexer A0, the other main path port is connected to the antenna feed component A2 on the antenna link, the coupling port of the coupler A and the radio frequency port of the canceller circuit B;
  • the coupler A is close to the antenna port of the duplexer A0, that is, the distance is 0 meters;
  • one of the functions of the passive intermodulation cancellation function is to reduce the passive intermodulation index requirements for the passive device
  • the second role is to eliminate the deterioration of the passive intermodulation index of the passive device with the increase of working time
  • the third role is to improve the passive intermodulation index of the passive device.
  • the canceller circuit B will use the transmission signal from the radio frequency signal from the coupler A to generate on the intermodulation signal generator B2 the same frequency, different amplitude and amplitude as the passive intermodulation signal in the radio frequency signal Intermodulation signals with different phases, and the intermodulation signal in the intermodulation signal falls into a single third-order component, or a single fifth-order component, or a single higher-order component, or multiple third-order components at different frequencies, or more 5th-order components at different frequency points, or higher-order components of multiple different frequency points, or there are simultaneous 3rd-order components, 5th-order components and even higher-order components.
  • the intermodulation cancellation signal and the passive intermodulation signal The components are cancelled, and the passive intermodulation signal after cancellation is less than or equal to the preset value of passive intermodulation; at the same time, the transmitted and received signals in the duplexer A0 and its antenna link are in the duplexer A0 and its antenna link working normally.
  • the intermodulation signal generator B2 When actually selecting the specific devices that constitute the intermodulation signal generator B2, the intermodulation signal generator B2 should produce an intermodulation with the same frequency, different amplitude and different phase as the passive intermodulation signal in the radio frequency signal Signal, and the intermodulation signal falls into a single third-order component, or a single fifth-order component, or a single higher-order component of the receiving frequency band, or a third-order component of multiple different frequency points, or a plurality of different frequency points 5th order components, or higher order components of multiple different frequency points, or there are amplitude relationship and phase relationship between 3rd order component, 5th order component and even higher order components at the same time as the duplexer A0 and its A single 3rd order component, or a single 5th order component, or a single higher order component in the passive intermodulation signal generated by the antenna link that falls into the receiving frequency band, or a 3rd order component at multiple different frequency points, or multiple different The amplitude relationship and phase relationship between the 5th-order
  • the amplitude adjustment and phase adjustment of the AM phase modulator B1 are realized by the amplitude and phase control parameters calculated by the digital processing unit E; and the calculation of the amplitude and phase control parameters of the digital processing unit E requires sampling by the passive intermodulation detection circuit D signal.
  • the signal that excites the duplexer A0 and its antenna link to generate a passive intermodulation signal is the same as the signal that excites the intermodulation signal generator B2 to generate an intermodulation signal, both from the transmission of the transmission circuit unit F Signal, so the passive intermodulation signal generated by the passive device and the intermodulation signal generated by the intermodulation signal generator B2 have the same frequency and the same bandwidth;
  • the antenna link is from the antenna port of the duplexer A0 to the antenna A1 Link, the antenna feed component A2 represents a combination of single or multiple passive devices in the antenna link, these passive devices include cables, connectors, couplers, and combiners;
  • the transmitted signal is composed of multi-tone signals Or consist of multi-carrier modulated signals;
  • the duplexer A0 or the antenna feeder A2 or the antenna A1 When the duplexer A0 or the antenna feeder A2 or the antenna A1 generates a single or multiple passive devices simultaneously and superimposes the passive intermodulation signal with a certain frequency interval from the received signal, there will be only a single 3 Order, or a single 5th order or a higher order component falls into the receiving band of the duplexer A0 and causes the passive intermodulation index tested from the receiving port of the duplexer A0 to fail to meet the preset value requirements, so that all The passive intermodulation value of the receiving port of the duplexer A0 meets the preset value requirement and makes the cancellation capability of the device greater than 20dB: the maximum amplitude of the intermodulation cancellation signal that can be generated by the intermodulation signal generator B2 Greater than the amplitude of a single component of the passive intermodulation signal of the duplexer A0 and its antenna link that falls into the corresponding frequency of the receiving frequency band;
  • the intermodulation signal generator B2 can generate The maximum amplitude of the intermodulation cancellation signal corresponding to the frequency of the passive intermodulation component is greater than the amplitude of multiple corresponding frequency components that fall into the receiving frequency band in the passive intermodulation signal of the duplexer A0 and its antenna link Value; the phase relationship between the multiple specific order components in the intermodulation signal generated on
  • the duplexer A0 or the antenna feeder A2 or the antenna A1 When the duplexer A0 or the antenna feeder A2 or the antenna A1 generates a single or multiple passive devices simultaneously and superimposes the passive intermodulation signal with a certain frequency interval from the received signal, there are 3rd order, When the 5th order or higher order component falls into the receiving frequency band of the duplexer A0 and all causes the passive intermodulation index tested from the receiving port of the duplexer A0 to fail to meet the preset value requirements, the duplexer The passive intermodulation value of the A0 receiving port meets the requirements of the preset value and makes the cancellation capability of the device greater than 20dB: the intermodulation cancellation signal corresponding to the frequency of the passive intermodulation component that can be generated by the intermodulation signal generator B2 The maximum amplitude of is greater than the amplitude of multiple corresponding frequency components that fall into the receiving frequency band in the passive intermodulation signal of the duplexer A0 and its antenna link; generated on the intermodulation signal generator B2 The amplitude
  • the passive intermodulation detection circuit D is used to obtain the radio frequency signal after the receiving port of the duplexer A0, after gain-adjustable amplification, down conversion, and finally converted into a digital signal and input to the digital processing unit E,
  • the radio frequency signal behind the receiving port of the duplexer A0 includes components of the received signal and the passive intermodulation signal that fall into the receiving frequency band.
  • the radio frequency port of the passive intermodulation detection circuit D or a coupler directly couples the radio frequency signal from the link in front of the radio frequency input port of the receiving unit C, and at this time the radio frequency input port of the receiving unit C passes through the main unit of the coupler
  • the channel is connected to the receiving port of the duplexer A0; the passive intermodulation detection circuit D obtains a radio frequency signal from a radio frequency amplifier in the receiving unit C through a power splitter or a coupler.
  • the radio frequency input port and the receiving port of the duplexer A0 are directly connected; the passive intermodulation detection circuit D is connected to the digital processing unit E through a high-speed analog-to-digital converter.
  • the radio frequency signal acquired by the passive intermodulation detection circuit D contains components of the received signal and the passive intermodulation signal falling into the receiving frequency band; the passive dynamic intermodulation detection circuit D has a receiving dynamic range greater than the input passive intermodulation The difference between the maximum power value of the received signal of the detection circuit D and the power value corresponding to the preset value of passive intermodulation.
  • the passive intermodulation detection circuit D obtains a signal from a link in front of the RF input port of the receiving unit C through a coupler, this coupler is called a receiving component, and the gain of the passive intermodulation detection circuit D is determined by the demand.
  • Passive intermodulation preset value, minimum sampling power of high-speed analog-to-digital converter in passive intermodulation detection circuit D, link noise figure, coupling degree of receiving components and other parameters are determined; the passive intermodulation detection circuit D
  • the maximum value of the received signal power is greater than: the difference between the maximum received signal power specified by the communication standard actually corresponding to the device and the coupling degree of the receiving component;
  • the passive intermodulation detection circuit D obtains a signal from the output terminal of a radio frequency amplifier in the receiving unit C through a power splitter or coupler, the power splitter or coupler is called a receiving component, and the passive mutual modulation
  • the gain of the modulation detection circuit D is determined by the required passive intermodulation preset value, the minimum sampling power of the high-speed analog-to-digital converter in the passive intermodulation detection circuit D, the link noise figure, the signal attenuation of the receiving component, the receiving unit C
  • the gain and other parameters of the link from the radio frequency input port of the receiver to the receiving component are determined; the maximum value of the received signal power of the passive intermodulation detection circuit D is greater than: the maximum received signal power specified in the communication standard corresponding to the device plus The gain of the link from the RF input port of the upper receiving unit C to the receiving component, and then the signal attenuation of the receiving component is subtracted.
  • the reception dynamic range of the passive intermodulation detection circuit D is greater than 70dB; the passive intermodulation detection circuit D is connected to the digital processing unit E through a high-speed analog-to-digital converter, and the sampling rate of the high-speed analog-to-digital converter is greater than or equal to 2 times
  • the duplexer A0 receives the band bandwidth.
  • the digital processing unit E first calculates the frequency information of the passive intermodulation signal related to it based on the frequency information of the transmitted signal, and converts it into the filtering parameter of the passive intermodulation signal, and then based on the received signal frequency and bandwidth information Obtain the frequency interval between them with the frequency and bandwidth information of the passive intermodulation signal, and then select the corresponding digital filtering method and integration method to finally realize the amplitude detection of the passive intermodulation signal; and then the passive intermodulation signal
  • the detected amplitude of the modulated signal is compared with the preset value of passive intermodulation: when the detected amplitude is less than or equal to the preset value, the canceller circuit B does not generate an intermodulation cancellation signal, and the duplex A0 and the passive intermodulation index of its antenna link have an impact; when the detected amplitude is greater than the preset value, the cancellation circuit B is controlled to adjust its amplitude and phase
  • the passive intermodulation signals with the same frequency, the same amplitude and the opposite phase of the passive intermodulation
  • One method for the digital processing unit E to obtain the transmitted signal frequency information and the received signal frequency information is to use the transmitted signal discriminator circuit E1 to obtain the transmitted signal from the transmitting circuit unit F of the device, convert it into a digital signal, and input
  • the digital processing unit E performs frequency discrimination processing to obtain relevant transmission signal frequency information, and estimates the corresponding reception signal frequency information from the duplex frequency interval between the transmission signal and the reception signal; acquiring the transmission signal frequency information and the reception signal frequency information
  • Another method is to obtain directly from the input information of the device through the information interaction interface in the digital processing unit E.
  • the digital processing unit E When the radio frequency signal in the passive intermodulation detection circuit D is too large and the link is blocked, the digital processing unit E will reduce the link gain of the passive intermodulation detection circuit D to process the received signal normally and stop detecting the passive intermodulation signal Amplitude; when the passive intermodulation detection circuit D is not blocked, the digital processing unit E needs to process the signal from the passive intermodulation detection circuit D in the process of calculating the passive intermodulation amplitude There is a certain frequency interval between the passive intermodulation signal and the received signal and the passive intermodulation signal and the received signal.
  • the method for calculating the amplitude of the passive intermodulation signal is: the digital processing unit E first calculates the frequency information of the passive intermodulation signal related to it based on the frequency information of the transmitted signal, and then the passive intermodulation according to the frequency and bandwidth information of the received signal The signal frequency and bandwidth information are used to obtain the frequency interval between them, and an appropriate algorithm is used to calculate the amplitude of the passive intermodulation signal according to the frequency interval; the algorithm for calculating the amplitude of the passive intermodulation signal includes but is not limited to direct filtering Integration method and segmented filtering integration method:
  • the direct filtering integration method refers to direct digital filtering and integration for the amplitude based on the bandwidth of the passive intermodulation signal, at which time the passive intermodulation signal falls into each order of the receiving frequency band
  • the frequency interval between the component and the received signal should be greater than or equal to the bandwidth of the transition band from the pass band to the stop band of the digital filter algorithm in the passive intermodulation signal.
  • This frequency interval is the basis for the direct filter integration method;
  • the segmented filtering and integration method refers to dividing the bandwidth of the passive intermodulation signal into several sub-bandwidths, performing digital filtering and integrating to obtain the amplitude according to each sub-bandwidth, and then accumulating the amplitudes corresponding to all the sub-bandwidths to obtain the entire signal amplitude.
  • the frequency interval between each order component and the received signal should be greater than or equal to the bandwidth of the transition band from the pass band to the stop band of the digital sub-band signal of each order component. This frequency interval is adopted by the segmented filter integration method in accordance with.
  • the canceler circuit B is connected to the antenna link behind the antenna port of the duplexer A0 through the coupler A; a main path port of the coupler A is connected to the antenna port of the duplexer A0, that is, the distance is 0 meters, the other main channel port of coupler A is connected to antenna feed component A2, the coupling port of coupler A is connected to canceler circuit B; the insertion loss of coupler A is less than 0.2dB, the coupling degree range of coupler A It is about 30dB.
  • the coupling port of coupler A is a forward coupling port relative to the transmitted signal.
  • the average power carried by coupler A is greater than 100 watts and the peak power carried by it is greater than 1000 watts.
  • the bandwidth of coupler A includes the transmit frequency band and the receive frequency band And the duplex interval between the two, the gain fluctuation in the frequency band of coupler A is related to the transmission frequency band and the reception frequency band and needs to be within a certain threshold range; the passive intermodulation index of coupler A is -117dBm / Hz;
  • the average power threshold carried by the canceler circuit B is greater than or equal to 20 dBm and the peak power threshold carried is greater than or equal to 30 dBm; to enable the intermodulation signal generator B2 in the canceler circuit B to generate a passive intermodulation cancellation signal,
  • the minimum value of the transmitted signal power loaded on the canceller circuit B must be greater than 10 watts;
  • the digital processing unit E is connected to the canceler circuit B through a multi-channel digital-to-analog converter, and transfers the control amounts of amplitude and phase to the canceler circuit B.
  • the amplitude adjustment accuracy of the canceler circuit B is less than 0.1 dB and the phase adjustment Accuracy is less than 1 degree;
  • the bus includes the I2C bus and the SPI bus;
  • the digital processing unit E obtains the transmitted signal frequency information and the received signal frequency information by using the transmitted signal frequency discriminating circuit E1
  • the radio frequency port of the transmitting signal frequency discriminating circuit E1 and the transmitting circuit unit F transmit Connected somewhere on the link
  • the transmission signal frequency discrimination circuit E1 is connected to the digital processing unit E through a high-speed analog-to-digital converter; at the same time, there is an interface between the digital processing unit E and the transmission signal frequency discrimination circuit E1.
  • Configure the parameters of the transmitted signal frequency discrimination circuit E1 through the bus such as local oscillator frequency, link gain, etc.
  • the bus includes an I2C bus and an SPI bus;
  • the digital processing unit E is equipped with at least one information interaction interface, and its functions include but are not limited to program download, configuration information input, remote alarm and maintenance;
  • the configuration information to be input includes the transmission signal bandwidth and frequency band of the device and the reception signal bandwidth and Frequency band, the order and frequency band information of the main interference components in the passive intermodulation signal, the preset value of the passive intermodulation signal and the time-varying curve, the maximum number of cancellations;
  • the digital processing unit E can be obtained through the information interaction interface Frequency information of the transmitted signal and frequency information of the received signal;
  • the information interaction interface can also perform data interaction with Internet background resources: upload the passive intermodulation value during the operation of the device, and the experience of the passive intermodulation value changing with time Curve, and the status information of each module circuit in the passive intermodulation signal adaptive cancellation device; or download the integrated optimized passive intermodulation signal preset value and the curve that changes with time.
  • the hardware configuration of the information interaction interface of the digital processing unit E includes an Ethernet interface, an optical fiber interface, and
  • the first solution of the canceler circuit B is shown in FIG. 2:
  • One end of the amplitude modulation phase modulator B1 in the canceler circuit B is directly connected to the coupling port of the coupler A, or through a radio frequency switch B3 is connected to the coupling port of coupler A, and the other end is connected to an intermodulation signal generator B2;
  • the amplitude modulation phase modulator B1 includes an amplitude modulation circuit and a phase modulation circuit; wherein the amplitude modulation circuit 1a is composed of a controllable attenuator and a fixed attenuator ;
  • the phase modulation circuit 2a includes at least two adjustable phase shifters; the amplitude adjustment range of the amplitude modulation phase modulator B1 is greater than 30dB, the phase adjustment range is greater than 180 degrees; the amplitude modulation phase modulator B1 carried in the canceller circuit B
  • the average power threshold value is greater than or equal to 20 dBm and the peak power threshold value is greater than or equal to 30
  • the transmission signal input to the RF signal of the canceller circuit B is directly input to the AM phase modulator B1 through the RF switch B3 or directly, and then input to the mutual exchange after being adjusted by the power of the AM circuit 1a in the AM phase modulator B1.
  • Modulation signal generator B2 so that the intermodulation signal generator B2 generates an intermodulation signal with the same frequency, different amplitude and different phase as the passive intermodulation signal in the radio frequency signal, and the intermodulation signal falls into the receiving frequency band
  • the intermodulation cancellation signal and the passive The components in the intermodulation signal are cancelled.
  • the canceled passive intermodulation signal is less than or equal to the preset value of passive intermodulation; at the same time, the transmitted and received signals in duplexer A0 and its antenna link are in duplexer A0 and Normal operation in its antenna link;
  • the second solution of the canceler circuit B is shown in FIG. 3: one end of the second amplitude modulation circuit 3 in the canceler circuit B is connected to the coupling port of the coupler A through the first circulator 4 Or, it can be connected to the coupling port of the coupler A through the first circulator 4 and the RF switch B3; the other end is connected to the intermodulation signal generator B2 through the second circulator 5; the amplitude and phase modulation of the canceler circuit B
  • One end of the circulator B1 is connected to the intermodulation signal generator B2 through the second circulator 5; the other end is connected to the coupling port of the coupler A through the first circulator 4 or may be connected to the coupler through the first circulator 4 and the RF switch B3
  • the coupling port of A is connected; the second amplitude modulation circuit 3 is used to make the intermodulation signal generator B2 withstand a suitable power RF signal; the amplitude modulation phase modulator B1 includes a first amplitude modulation circuit 1b and
  • the working frequency band of the phase modulator B1 includes the receiving frequency band of the duplexer A0.
  • the gain fluctuation in the frequency band of the amplitude modulator B1 is related to the receiving frequency band and needs to be within a certain threshold range; the canceler circuit B
  • the average power threshold carried by the second amplitude modulation circuit 3 is greater than or equal to 20 dBm and the peak power threshold carried is greater than or equal to 30 dBm;
  • the transmission signal input into the radio frequency signal of the canceller circuit B is input to the second amplitude modulation circuit 3 through the first circulator 4 or input to the second amplitude modulation circuit 3 through the radio frequency switch B3 and the first circulator 4, and then After adjusting the power of the second amplitude modulation circuit 3, it is input to the intermodulation signal generator B2 through the second circulator 5, so that the intermodulation signal generator B2 generates the same frequency and amplitude as the passive intermodulation signal in the radio frequency signal Intermodulation signals of different and different phases, and the intermodulation signal in the intermodulation signal falls into a single third-order component, or a single fifth-order component, or a single higher-order component, or multiple third-order components at different frequencies, Or 5th-order components of multiple different frequency points, or higher-order components of multiple different frequency points, or there are both 3rd-order components, 5th-order components and even higher-order components.
  • the passive intermodulation signal generated by the duplexer A0 and its antenna link falls into a single 3rd-order component, or a single 5th-order component, or a single higher-order component, or multiple 3 Order components, or 5th order components at multiple different frequency points, or higher order components at multiple different frequency points, or there are simultaneous amplitude relationships between 3rd order components, 5th order components, and even higher order components
  • the phase relationship is basically the same; and the amplitude of the intermodulation signal generated on the intermodulation signal generator B2 by the power of the received signal and the passive intermodulation signal in the radio frequency signal is much smaller than the amplitude of the passive intermodulation signal , Does not affect the passive intermodulation cancellation result; after being reflected, the intermodulation signal is input to the AM phase modulator B1 through the second circulator 5 and passes the first loop through the amplitude adjustment and phase adjustment of the AM phase modulator B1 4 or through the first circulator 4 and the RF switch B3 is finally coupled to the main path of the coupler A
  • the intermodulation signal generator B2 in the two solutions of the canceler circuit B includes but is not limited to a single diode, a single triode, or a parallel configuration of multiple diodes; the specific model of the diode or the specific model of the triode and the intermodulation are generated
  • the amplitude characteristic of the 3rd, 5th or higher order intermodulation signal of the signal is related to the phase characteristic; when multiple diodes of the same type are connected in parallel, the strength of the intermodulation signal will be enhanced; the power of the intermodulation signal generator B2 is greater than or equal to 20dBm.
  • the passive intermodulation detection circuit D includes at least a down-conversion module and a high-speed analog-to-digital converter; the down-conversion module can convert the received radio frequency signal into an intermediate frequency signal; the sampling dynamic range of the high-speed analog-to-digital converter requires Greater than 70dB, the number of digits of the analog-to-digital converter is 14 and the sampling rate is greater than or equal to 2 times the bandwidth of the duplexer A0 receiving band; the minimum power that the passive intermodulation detection circuit D can sample is less than or equal to -115dBm, and the The circuit can adjust the link gain according to the amplitude of the total power of the received radio frequency signal to avoid link blocking caused by the received signal or other signals; the gain of the passive intermodulation detection circuit D is preset by the required passive intermodulation The value, the minimum sampling power of the high-speed analog-to-digital converter in the passive intermodulation detection circuit D, the link noise figure, etc. are determined; the maximum value of the received signal power of the passive
  • the passive intermodulation detection circuit D may adopt a receiving superheterodyne structure as shown in FIG. 4 to convert the radio frequency signal into an intermediate frequency signal and then perform analog-to-digital conversion.
  • the passive intermodulation detection circuit D is composed of a low noise amplifier D1
  • the radio frequency filtering and small signal amplifying unit D2, the mixer D3, the local oscillator D4, the intermediate frequency filter D5, the intermediate frequency amplifier D6, and the analog-to-digital converter D7 wherein the pass band of the filtering components in the radio frequency filtering and small signal amplifying unit D2
  • the frequency band is the receiving frequency band of the duplexer A0.
  • the passive intermodulation detection circuit D may adopt a receiving zero-IF structure as shown in FIG. 5 to convert the radio frequency signal to a zero-IF signal and then perform analog-to-digital conversion.
  • the passive intermodulation detection circuit D is composed of a low noise amplifier D1 , RF filtering and small signal amplification unit D2, down conversion and analog-to-digital conversion unit D8, wherein the pass band frequency band of the filtering component in the RF filtering and small signal amplification unit D2 is the receiving frequency band of the duplexer A0, down conversion and analog
  • the function of the digital conversion unit D8 is to directly convert the radio frequency signal to a zero intermediate frequency signal and perform analog-to-digital conversion.
  • the digital processing unit E includes at least a logic processing and arithmetic processing device with digital signal processing function, which is used for digital signal reception, algorithm processing, digital signal output, control and configuration signal output, etc.
  • the logic processing and arithmetic processing devices include but are not limited to field programmable gate array devices, central processors, and digital signal processors;
  • the hardware configuration of the information interaction interface of the digital processing unit E includes an Ethernet interface and an RS-485 bus interface ;
  • the number of digital-to-analog converters in the digital processing unit E is between 12 bits, and there are at least 3 digital-to-analog converters;
  • the digital processing unit E runs corresponding to "an adaptive offset wireless transceiver system "Passive intermodulation signal method", the flow chart of this method is shown in Figure 6:
  • S1 Obtain the transmitted signal bandwidth and frequency band, the received signal bandwidth and frequency band, the order and frequency band information of the main interference components in the passive intermodulation signal through the digital processing unit E, the expected preset value of the passive intermodulation and the change with time The initial empirical data of the curve, amplitude and phase, the maximum number of cancellations and other information, and converted into the corresponding configuration parameters;
  • step S2 According to the configuration parameters of the transmitted signal in step S1, the digital processing unit E obtains the frequency point of the passive intermodulation signal and converts it into the corresponding digital filtering parameter and stores it in the parameter configuration table;
  • step S3 According to the configuration parameters related to the received signal in step S1, the configuration parameters of the passive intermodulation signal, and the digital filtering parameters of the passive intermodulation signal obtained in step S2, the digital processing unit E controls the passive intermodulation detection circuit D
  • the sampled signal is digitally filtered to filter out other signal components except the passive intermodulation signal, and the amplitude value of the passive intermodulation signal that falls into the receiving frequency band is obtained;
  • the algorithm for obtaining the amplitude value includes the segmented integration method 3. Direct integration method based on signal bandwidth;
  • step S4 determine the current working state; the default value of the state identification of the working state is: "initial working mode”; if the state identification value of the working state is "initial working mode", continue to step S5-1, otherwise continue to step S5-2 ;
  • step S5-1 Compare the passive intermodulation signal amplitude value obtained in step S3 with the passive intermodulation preset value in step S1 to determine whether the passive intermodulation signal amplitude is less than or equal to the passive intermodulation preset value;
  • step S6 If the judgment result in step S5-1 is "Yes", the canceller circuit B continues to maintain the high isolation state of the link between the intermodulation signal generator and the coupler A; and returns to step S2;
  • step S7 If the judgment result of step S5-1 is "No", the canceller circuit B switches to the low isolation state of the link between the intermodulation signal generator and the coupler A; and sets the state identification value of the working state and sets It is "offset working state”; proceed to step S8;
  • step S5-2 Compare the amplitude value of the passive intermodulation signal obtained in step S3 with the preset value of the passive intermodulation signal in step S1 to determine whether the amplitude of the passive intermodulation signal is less than or equal to the preset value of passive intermodulation; If the judgment result of step S5-2 is "Yes”, then maintain the state and return to step S2; if the judgment result of step S5-2 is "No", then execute step S8;
  • step S8 Calculate the amplitude and phase adjustment values of the canceller circuit according to the amplitude value of the passive intermodulation signal in step S3; and distribute to the amplitude modulator and phase modulator in the canceller circuit to implement cancellation; after completing the current round of cancellation processing After that, it will continue to return to step S2 to continue the next round of cancellation processing; the algorithm for determining the amplitude and phase adjustment values includes a two-dimensional minimum variance algorithm.
  • the double-tone signal causes the duplexer A0 and its antenna link to generate a passive intermodulation signal.
  • the amplitude of the third-order component in the passive intermodulation tested at the receiving port of the tool A0 is -94.7dBm, and the fifth-order component is -124.8dBm, and the seventh-order component is under the thermal noise of the spectrum analyzer; the duplexer A0 and
  • the passive intermodulation signal of the antenna link that falls into the receiving frequency band is less than or equal to the preset value of -112dBm, so it is mainly optimized for poor third-order passive intermodulation, and the amplitude difference between the third-order signal and the fifth-order signal is 30.1dB
  • the test value of the intermodulation signal generated by the specific diode selected at this time at the receiving port of the duplexer A0 is: the amplitude of the third-order component is -75.6dBm, and
  • the seventh-order component is under the thermal noise of the spectrum analyzer; it can be seen that the device causes poor passive intermodulation
  • the 3rd order component is optimized by 24.9dB, and the 5th order component is also optimized simultaneously. At this time, the frequency interval between each order component of the passive intermodulation signal falling into the receiving frequency band and the receiving signal is greater than or equal to 200 KHz.
  • the device can be applied to simulate wireless transceiver equipment and its antenna link in order to offset the unqualified passive intermodulation generated by passive devices, so that the passive intermodulation index of the wireless transceiver equipment and its antenna link meets the passive intermodulation preset Value; and when multiple wireless transceiver devices are used at the same time and the antenna link of each device is connected through the combiner to connect the antenna, the device corresponding to each antenna link can also cancel the
  • the unqualified passive intermodulation generated by the source device makes the passive intermodulation index of the wireless transceiver equipment and its antenna link meet the preset value of passive intermodulation;
  • the analog wireless transceiver equipment includes repeaters, radio stations, and towers
  • the antenna link includes but is not limited to cables, connectors, couplers, combiners, and antennas.
  • the duplexer A0 of the device is the duplexer A0 of the wireless transceiver device; the receiving unit C of the device multiplexes the wireless transceiver device
  • the receiving unit C is composed of a low noise amplifier C1, a power splitter C2, and a power amplifier C3, wherein a power splitting port of the power splitter C2 and the RF input of the passive intermodulation detection circuit D Port connection, the other power split port of power splitter C2 is connected to the RF input port of power amplifier C3, the power combining port of power splitter C2 is connected to the output port of low noise amplifier C1; the device is passive
  • the intermodulation detection circuit D needs to be newly added in the wireless transceiver device; the transmission circuit unit F of the device multiplexes the transmission circuit unit F of the wireless transceiver device, and the transmission circuit unit F is composed of a power amplifier F1, a coupler F2, and
  • Coupler A of this device needs to be newly added in the wireless transceiver device, a main access port of the coupler A is directly connected to the antenna port of the duplexer A0 of the wireless transceiver device;
  • the canceler circuit B needs to be newly added in the wireless transceiver device.
  • the radio frequency port of the canceler circuit B is directly connected to the coupling port of the coupler A.
  • the amplitude and phase of the canceler circuit B are adjusted by the digital processing unit E 3.
  • the transceiver module G in the device is the transceiver module G in the wireless transceiver device;
  • the antenna feed component A2 and the antenna A1 of the device are the correspondence on the external antenna link of the wireless transceiver device Components and antennas.
  • the duplexer A0 of the device is the duplexer A0 of the tower top amplifying device; the receiving unit C of the device
  • the receiving unit C of the multiplexing tower top amplifying device is composed of a low-noise amplifier C1, a power splitter C2, and a receiving passband filter C3, wherein a power splitting port of the power splitter C2 and no
  • the RF input port of the source intermodulation detection circuit D is connected, the other power split port of the power splitter C2 is connected to the RF input port of the receive passband filter C3, and the power combining port of the power splitter C2 and low noise
  • the output port of the amplifier C1 is connected; the passive intermodulation detection circuit D of this device needs to be newly added in the tower top amplifying device, and it obtains the radio frequency signal from the receiving link in the tower top amplifying device through the power splitter C2,
  • the radio frequency signal is
  • the transceiver module G and the digital processing unit E are provided with an interface to facilitate the tower top
  • the control information of the base station side transceiver equipment outside the amplification device is passed to the information interaction interface of the digital processing unit E; the antenna feed component A2 and the antenna A1 of the device are the corresponding components and antennas on the antenna link of the tower top amplification device .
  • each antenna port of the duplexer in each transceiver link is immediately adjacent to a coupler A, and Canceller circuit B;
  • the device described in this embodiment is applied to a wireless transceiver device.
  • a schematic diagram of one example of the use of multiple radio frequency links is shown in FIG. 11 of the specification: the entire link includes multiple wireless transceiver devices, and the multiple radio frequency system combiner H , Antenna A1 and antenna feed component A2, etc .; and each branch has a passive intermodulation cancellation device connected to a single transceiver link of the wireless transceiver equipment, and the duplexer A0, antenna A1, antenna feed on each branch link.
  • the passive intermodulation generated by component A2 and the like and the passive intermodulation generated by the combiner H of the multi-radio frequency system falling into the receiving frequency band can be cancelled within a certain range;
  • the entire link includes the wireless transceiver device , Multiple antennas A1-1, A1-2, ..., and multiple components A2-1, A2-2, ...; wireless transceiver equipment, each transceiver link has a passive intermodulation cancellation device connected, each The components of passive intermodulation caused by duplexers, components, antennas, etc. on the branch link falling into the receiving frequency band can be cancelled within a certain range;
  • the device designed by applying the invention when the component of the link passive intermodulation signal falling into the receiving frequency band is -90dBm / Hz to -95dBm / Hz, the device can make the passive intermodulation signal The cancellation result is greater than 20dB.
  • the component of the link passive intermodulation signal falling into the receiving frequency band is better than -95dBm / Hz, the device can make the passive intermodulation signal cancellation result better than -115dBm / Hz.

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Abstract

本发明涉及通信技术领域，具体涉及一种自适应抵消无源互调信号的装置、方法及应用设备。包括一个耦合器、双工器、天线、天馈组件、抵消器电路、接收单元、无源互调检测电路、数字处理单元、发射电路单元和收发模块；耦合器从双工器的天线口的链路上耦合射频信号输出给抵消器电路；所述射频信号中包含发射信号、无源互调信号和接收信号；所述耦合器的一个主通路端口与所述双工器的天线口连接、另一个主通路端口与天线链路上的天馈组件连接、耦合器的耦合端口和抵消器电路的射频端口连接。其能将无线收发设备以及该设备天线口至天线这一段链路上其他设备或组件产生的无源互调信号落入到接收频段的分量抵消。

Description

自适应抵消无源互调信号的装置、方法及应用设备 技术领域
本发明涉及通信技术领域，具体涉及一种自适应抵消无源互调信号的装置、方法及应用设备。
背景技术
在通信系统中，大量应用无线收发设备。无线收发设备本身包含有产生无源互调信号的器件，比如射频双工器、滤波器、合路器等；从无线收发设备天线口到天线的链路上也包含很多产生无源互调信号的器件，比如耦合器、射频电缆、塔顶放大器等。对于无线收发系统而言，如何抑制由无线收发系统中发射信号引起的对无线收发设备的接收机产生的互调干扰，一直是该类系统的关键问题。因此，要求无线收发设备在工作时，发射通道产生的无源互调信号电平尽可能低，以免无源互调信号落入接收通道，对接收通道造成互调干扰。当前无源互调抵消技术一般有两种方式：
对比文献CN100490307C公开了一种名称为：“信号处理电路、基站和消除互调产物的方法”发明专利，该专利将输入非线性单元的原载波分为两路，分别输入两只支路，第一路原载波经过非线性单元产生包含有第一组互调产物的处理信号，第二路原载波经过分路器、倍频器、混合器以及调节电路。产生含有第二组高次互调产物的控制信号，最后将两路信号叠加。它利用第二组高次互调与第一组互调产物的频率相同，幅度接近相同，相位相反，抵消互调信号。
该技术方案在以下不足：1、该技术方案不适用无源器件，它没有考虑非线性单元内部不同位置的互调值差异，对于无源器件这种差异是很明显的，在无源电路中，传输信号的幅度衰减和相位变化程度非常大。在多个位置产生互调的情况下，电路前端产生的互调信号会在信号传输过程中大幅度衰减，电路输出的互调信号只含有电路末端产生的互调信号，因此，对于双工器来说，若从非线性单元的前端取信号，所产生的互调抵消信号无法与天线端口的互调信号相抵消；2、该技术方案产生的互调抵消信号即第二组高次互调产物，被限定为固定阶次得互调产物，只能消除对应频段内的非线性单元的互调信号，存在局限性。
对比文献201310048951.1公开了一种名称为：“一种用于无源器件的互调抵消装置”发明专利，该专利从无源器件输出端直接耦合包含有高次互调产物的发射信号，通过无源调节器的调整传输至带有互调信号发生器的射频链路末端反射后，再次通过无源调节器的调整，获得与前述无源器件发射信号的互调信号相同频率、电平和相反相位的抵消信号，该信号通过耦合器与无源非线性单元输出端发射信号叠加，实现互调抵消。
该技术方案在以下不足：1、该技术方案采用无源调节器，幅度调节、相位调节均是无源器件，如果要实现幅度调节、相位调节需要借助外力驱动无源调节器，比如使用电机驱动，或者直接靠人工驱动，这些方式会使得实际应用成本高，且不便于产品化；2、由于没有无源互调抵消结果的反馈检测电路，抵消结果不能实时监控和调整。
除此之外，现有其它的降低无源互调信号电平的方法主要集中在无源器件的结构和生产工艺上，这些方法往往需要增加额外的成本，而且加厚金属镀层的电镀工艺往往会增加 污染。
发明内容
本发明的目的就是针对现有技术的缺陷，提供一种数字自适应的，用于抵消无线收发系统中的无源互调信号的装置，使其能将无线收发设备以及该设备天线口至天线这一段链路上其他设备或组件产生的无源互调信号落入到接收频段的分量抵消的自适应抵消无源互调信号的装置、方法及应用设备。
本发明一种自适应抵消无源互调信号的装置，其技术方案为：它包括一个耦合器、双工器、天线、天馈组件、抵消器电路、接收单元、无源互调检测电路、数字处理单元、发射电路单元和收发模块；
所述收发模块的发射信号经发射电路单元线性放大，使所述双工器及其天线链路产生无源互调信号，并且该无源互调信号中有落入到双工器接收频段的且与接收信号有一定频率间隔的分量；
所述耦合器从双工器的天线口的链路上耦合射频信号输出给抵消器电路；所述射频信号中包含发射信号、无源互调信号和接收信号；所述耦合器的一个主通路端口与所述双工器的天线口连接、另一个主通路端口与天线链路上的天馈组件连接、耦合器的耦合端口和抵消器电路的射频端口连接；
所述抵消器电路利用来自于耦合器的射频信号中的发射信号在抵消器电路中产生出互调信号，所述互调信号反射后通过抵消器电路的幅度调整和相位调整，并耦合输出至耦合器的主通路，形成与所述无源互调信号中落入接收频段的且与接收信号有一定频率间隔的分量频率相同、幅度相同和相位相反的互调抵消信号；
所述无源互调检测电路，作用是通过接收单元获取所述双工器接收端口后的射频信号，并经过增益可调控的放大，下变频，最终转换成数字信号并输入到数字处理单元，所述射频信号包含接收信号和无源互调信号中落入接收频段的分量；
所述数字处理单元用于依据发射信号频率信息，实现对无源互调信号的幅值检测，以及在检测幅值大于所述预设值时，控制所述抵消器电路产生出互调抵消信号与所述射频信号中的无源互调信号进行抵消。
较为优选的，所述抵消器电路利用来自于耦合器的射频信号中的发射信号在抵消器电路中产生出与所述射频信号中的无源互调信号频率相同、幅度不同和相位不同的互调信号，且该互调信号中落入接收频段的各个分量之间的幅度关系和相位关系与所述双工器及其天线链路产生的无源互调信号中落入接收频段的各个分量之间的幅值关系和相位关系一致；
而耦合到抵消器电路的射频信号中的接收信号和无源互调信号的功率在抵消器电路内的所述互调信号发生器上产生的互调信号的幅值远小于上述无源互调信号的幅值，不对无源互调抵消结果产生影响；
所述互调信号反射后通过抵消器电路幅度调整和相位调整，并耦合输出至耦合器的主通路，形成与所述无源互调信号中落入接收频段的且与接收信号有一定频率间隔的分量频率相同、幅度相同和相位相反的互调抵消信号，该互调抵消信号与所述无源互调信号中的分量进行抵消，抵消后的无源互调信号小于等于无源互调预设值；同时双工器及其天线链 路中的发射信号和接收信号在双工器及其天线链路中正常运作；
所述各个分量包含单个3阶分量、或单个5阶分量、甚至或单个更高阶次分量、或多个不同频率3阶分量、或多个不同频率5阶分量、甚至或多个不同频率的更高阶次分量、或同时有3阶分量和5阶分量甚至高阶次分量。
较为优选的，所述数字处理单元用于依据发射信号频率信息，实现对无源互调信号的幅值检测，以及在检测幅值大于所述预设值时，控制所述抵消器电路产生出互调抵消信号与所述射频信号中的无源互调信号进行抵消的方法如下：
所述数字处理单元首先依据发射信号频率信息，计算出与之相关的无源互调信号的频率信息，并将其转换为无源互调信号的滤波参数；
然后依据接收信号频率、带宽信息与无源互调信号频率、带宽信息求得它们之间的频率间隔，再选择相应的数字滤波方式和积分方式，最终实现对无源互调信号的幅值检测；
然后将所述无源互调信号的检测幅值与无源互调预设值进行对比：
当所述检测幅值小于等于所述预设值时，所述抵消器电路不产生互调抵消信号，不对所述双工器及其天线链路的无源互调指标产生影响；
当所述检测幅值大于所述预设值时，控制所述抵消器电路对其幅度和相位的调整产生出与所述双工器及其天线链路的无源互调信号频率相同、幅度相同和相位相反的互调抵消信号与所述射频信号中的无源互调信号进行抵消，并保持这种依据无源互调信号的幅值检测结果实时调控所述抵消器电路幅度和相位使无源互调信号抵消结果小于等于所述预设值的工作状态。
较为优选的，所述数字处理单元计算无源互调信号幅值的方法为：
所述数字处理单元首先依据发射信号频率信息计算出与之相关的无源互调信号的频率信息；
然后依据接收信号频率、带宽信息与无源互调信号频率、带宽信息求得它们之间的频率间隔，并依据该频率间隔计算无源互调信号幅值；
所述计算无源互调信号幅值的方法为直接滤波积分法或分段滤波积分法；
所述直接滤波积分法是指依据无源互调信号带宽直接数字滤波并积分求幅度，此时所述无源互调信号落入到接收频段的各阶次分量与接收信号之间的频率间隔要大于等于无源互调信号的数字滤波算法中数字滤波器通带到阻带的过渡带带宽，此频率间隔即是采用直接滤波积分法的依据；
所述分段滤波积分法是指将无源互调信号带宽分成数个子带宽，依据每个子带宽进行数字滤波并积分求幅度，再将所有子带宽对应的幅度进行累加获得整个信号幅值，此时所述各阶次分量与接收信号之间的频率间隔要大于等于各阶次分量边子带信号的数字滤波器通带到阻带的过渡带带宽，此频率间隔即是采用分段滤波积分法的依据。
较为优选的，还包括发射信号鉴频电路；
所述数字处理单元获取所述发射信号频率信息和接收信号频率信息包括：
利用发射信号鉴频电路从发射电路单元上获取发射信号，转换为数字信号，输入数字处理单元进行鉴频处理，获取相关发射信号频率信息，并由发射信号和接收信号之间的双工频率间隔推算相应接收信号频率信息；或
通过数字处理单元中的信息交互接口直接从该装置的输入信息中获取。
较为优选的，所述抵消器电路包括调幅调相器和互调信号发生器，所述调幅调相器包括调幅电路和调相电路，所述调幅调相器一端与耦合器的耦合端口直接或通过一个射频开关连接，另一端与互调信号发生器连接。
较为优选的，所述调幅电路由可调控衰减器和固定衰减器构成；调相电路至少包含2个可调控移相器；所述调幅调相器的幅度调整范围大于30dB，相位调整范围大于180度；所述抵消器电路中调幅调相器的承载功率大于等于所述抵消器电路的承载功率门限值，所述调幅调相器的工作频段包含所述双工器的发射频段和接收频段，调幅调相器的频带内增益波动与发射频段、接收频段相关且需在一定的门限值范围内。
较为优选的，所述抵消器电路包括调幅调相器、互调信号发生器、第二调幅电路、第一环行器和第二环行器，所述调幅调相器包括第一调幅电路和调相电路，所述调幅调相器和第二调幅电路的一端均连接第一环行器，所述调幅调相器和第二调幅电路的另一端均通过第二环行器与互调信号发生器连接，所述第一环行器与耦合器的耦合端口直接或通过一个射频开关连接。
较为优选的，所述第二调幅电路用于使互调信号发生器承受一个合适功率的射频信号；所述调幅调相器用于将互调信号发生器产生的互调信号进行调幅、调相处理；所述第一调幅电路至少包含1个可调控衰减器；所述调相电路至少包含2个可调控移相器；所述第二调幅电路由固定衰减器或可调控衰减器构成；所述第一环行器和第二环行器的频率带宽包括所述双工器的发射频段和接收频段；所述调幅调相器的幅度调整范围大于30dB，相位调整范围大于180度，所述调幅调相器的工作频段包含所述双工器的接收频段，调幅调相器的频带内增益波动与接收频段相关且需在一定的门限值范围内；所述抵消器电路中第二调幅电路的承载功率大于等于所述抵消器电路的承载功率门限值；
所述互调信号发生器包含并联的单个二极管、单个三极管或多个二极管；二极管具体型号或者三极管具体型号与产生互调信号3阶、5阶或更高阶互调信号的幅值特性和相位特性相关；所述互调信号发生器的承载功率大于等于所述抵消器电路承载功率门限值与从抵消器电路射频输入口到互调信号发生器的链路损耗的差值。
较为优选的，所述无源互调检测电路包括本振和依次连接在其射频输入端口和数字采样信号输出端口之间的低噪声放大器、射频滤波及小信号放大单元、混频器、中频滤波器、中频放大器和模数转换器，所述本振的输出端与混频器连接。
较为优选的，所述无源互调检测电路包括依次连接在其射频输入端口和数字采样信号输出端口之间的低噪声放大器、射频滤波及小信号放大单元和下变频及模数转换单元。
较为优选的，所述无源互调检测电路至少包括下变频模块和高速模数转换器，所述无源互调检测电路通过高速模数转换器与所述数字处理单元连接；
所述下变频模块可以将接收的射频信号转换成中频信号，或者将接收的射频信号转换成零中频信号；
所述高速模数转换器的采样动态范围需大于接收信号的最大功率值和无源互调预设值对应的功率值之间的差值，采样速率大于等于2倍的双工器接收频段带宽；
所述无源互调检测电路能够采样的最小功率小于等于预设值对应的无源互调功率值，同时该电路可以根据所接收的射频信号总功率的幅值调整链路增益，所述无源互调检测电路获取的射频信号中包含接收信号和无源互调信号落入接收频段的分量。
较为优选的，所述无源互调检测电路通过耦合器从接收单元射频输入口前的链路耦合射频信号，所述接收单元的射频输入端口通过该耦合器的主通路和双工器接收端口连接；
所述无源互调检测电路的增益由需求的无源互调预设值、无源互调检测电路中高速模数转换器的最小采样功率、链路噪声系数、接收组件的耦合度确定；所述无源互调检测电路的接收信号功率的最大值大于m，所述m为该装置实际对应的通信标准所规定的最大接收信号功率与接收组件耦合度之差。
较为优选的，所述无源互调检测电路通过功率分路器或者耦合器从接收单元中的一个射频放大器后获取射频信号，所述接收单元的射频输入端口和双工器接收端口连接；
所述无源互调检测电路的增益由需求的无源互调预设值、无源互调检测电路中高速模数转换器的最小采样功率、链路噪声系数、接收组件的信号衰减度、接收单元的射频输入口到接收组件这段链路的增益确定；所述无源互调检测电路的接收信号功率的最大值大于n，所述n＝该装置实际对应的通信标准所规定的最大接收信号功率+接收单元的射频输入口到接收组件这段链路的增益-接收组件的信号衰减度。
较为优选的，所述双工器代表无线收发设备中的无源器件；所述天馈组件和天线代表无线收发系统的天线链路中的无源器件，所述天馈组件代表天线链路中单个或多个无源器件的组合，这些无源器件包括电缆、连接器、耦合器、合路器。
较为优选的，激励所述双工器及其天线链路产生无源互调信号的信号和激励所述互调信号发生器产生互调信号的信号是同源的，均来源于发射电路单元的发射信号，所以无源器件产生的无源互调信号和互调信号发生器产生的互调信号的频率相同、带宽相同；
所述天线链路是从双工器天线口到天线这段链路；
所述发射信号由多音信号构成或者由多载波调制信号构成。
较为优选的，当所述双工器或天馈组件或天线单个产生的或多个无源器件同时产生并叠加而成的，与接收信号有一定频率间隔的无源互调信号中，仅有单个3阶、或单个5阶或单个更高阶次分量落入双工器的接收频带，且造成从双工器接收端口测试的无源互调指标达不到预设值要求时，所述互调信号发生器所能产生的互调抵消信号的最大幅值要大于所述双工器及其天线链路的无源互调信号中落入到接收频段对应频率的单个分量的幅值；
当所述双工器或天馈组件或天线单个产生的或多个无源器件同时产生并叠加而成的，与接收信号有一定频率间隔的无源互调信号中，仅有多个不同频率的3阶、或多个不同频率的5阶或多个不同频率的更高阶次分量落入双工器的接收频带，且造成从双工器接收端口测试的无源互调指标达不到预设值要求时，所述互调信号发生器所能产生的对应无源互调分量频率的互调抵消信号的最大幅值要大于所述双工器及其天线链路的无源互调信号中落入到接收频段的多个对应频率分量的幅值；所述互调信号发生器上产生的互调信号中多个特定阶次分量之间的相位关系与所述双工器及其天线链路产生的无源互调信号中多个特定阶次分量之间的相位关系一致；
当所述双工器或天馈组件或天线单个产生的或多个无源器件同时产生并叠加而成的，与接收信号有一定频率间隔的无源互调信号中，同时有3阶、5阶或更高阶次分量落入双工器的接收频带，且都造成从双工器接收端口测试的无源互调指标达不到预设值要求时，所述互调信号发生器所能产生的对应无源互调分量频率的所述互调抵消信号的最大幅值要大于所述双工器及其天线链路的无源互调信号中落入到接收频段的多个对应频率分量 的幅值；所述互调信号发生器上产生的互调信号中多个特定阶次分量之间的幅度关系和相位关系与所述双工器及其天线链路产生的无源互调信号中多个特定阶次分量之间的幅值关系和相位关系一致。
较为优选的，所述抵消器电路通过耦合器与双工器天线口后的天线链路连接；所述耦合器的一个主通路端口与双工器天线口连接且距离需控制在0到1米范围内，耦合器的另一个主通路端口与天馈组件连接，耦合器的耦合端口连接抵消器电路；所述耦合器的插入损耗小于0.2dB，耦合器的耦合度范围为25dB到45dB，耦合器的耦合端口相对于发射信号为正向耦合端口，耦合器的承载功率需大于自适应抵消无源互调信号的装置的最大发射功率峰值，耦合器的带宽包含发射频段，接收频段以及两者间的双工间隔，耦合器的频带内增益波动与发射频段、接收频段相关且需在一定的门限值范围内；所述抵消器电路的承载功率门限值需大于等于耦合器的功率门限值与耦合器的耦合度之差值；为使抵消器电路中互调信号发生器能产生无源互调抵消信号，加载在所述抵消器电路的发射信号功率的最小值需大于一定的功率门限值。
较为优选的，所述数字处理单元通过多路数模转换器与抵消器电路连接，将幅度、相位的控制量传递给抵消器电路，所述抵消器电路的幅度调整精度和相位调整精度的要求主要来源于无源互调信号抵消能力需求；
所述数字处理单元与无源互调检测电路之间至少存在两个接口：一个接口用于获取无源互调检测电路中高速模数转换器的采样信号，从而进行无源互调信号的数字滤波和幅度计算；另一个接口的用于通过总线配置无源互调检测电路的参数，所述总线包括I2C总线、SPI总线；
当所述数字处理单元获取所述发射信号频率信息和接收信号频率信息的方法是利用发射信号鉴频电路时，则发射信号鉴频电路的射频端口与所述发射电路单元中发射链路上的某处连接，发射信号鉴频电路通过高速模数转换器与所述数字处理单元连接；同时数字处理单元与发射信号鉴频电路之间还有一个接口，用于通过总线配置发射信号鉴频电路的参数；
所述数字处理单元具备至少一个信息交互接口，其作用包含程序下载，配置信息输入，远程告警和维护；其中需要输入的配置信息包括本装置发射信号带宽和频段、接收信号带宽和频段、无源互调信号中的主要干扰分量的阶次和频段信息、无源互调信号预设值以及随时间变化的曲线、最大抵消次数；所述数字处理单元可以通过信息交互接口获取发射信号频率信息和接收信号频率信息；所述的信息交互接口还可以与互联网后台资源进行数据交互：上传所述设备运行过程中的无源互调值，无源互调值随时间变化的经验曲线，以及无源互调信号自适应抵消装置中各模块电路的状态信息；或者下载综合优化后的无源互调信号预设值以及随时间变化的曲线；
所述数字处理单元至少包含具备数字信号处理功能的逻辑处理与运算处理器件，用于数字信号的接收、算法处理、数字信号的输出、控制和配置信号的输出等，所述逻辑处理与运算处理器件包含但不限于现场可编程门阵列器件，中央处理器，数字信号处理器；所述数字处理单元的信息交互接口的硬件构成包括但不限于以太网接口、光纤接口、RS-485总线接口；所述数字处理单元中的数模转换器的位数范围在10～18位之间，且至少有3个数模转换器。
所述耦合器的一个主通路端口与所述双工器的天线口连接、另一个主通路端口与天线链路上的天馈组件连接、耦合器的耦合端口和抵消器电路的射频端口连接；
所述收发模块的信号发送端经发射电路单元与双工器的发射信号输入端口连接，所述收发模块的信号接收端经接收单元与双工器发射端口连接；
所述无源互调检测电路通过接收单元与双工器的接收信号输出端口连接，所述无源互调检测电路的数字采样信号输出端与数字处理单元的数字采样信号接收端连接，所述数字处理单元的控制量信号输出端与抵消器电路的控制量信号输入端连接。
较为优选的，还包括发射信号鉴频电路，所述数字处理单元包括发射信号接收端口、第一数据传输端口、第二数据传输端口和信息交互接口，所述发射信号鉴频电路的射频端口与发射电路单元连接，所述发射信号鉴频电路的发射信号输出端与数字处理单元的发射信号接收端口连接，所述数字处理单元的第一数据传输端口与所述无源互调检测电路的配置信息接收端口连接，所述数字处理单元的第二数据传输端口与发射信号鉴频电路的配置信息接收端口连接。
较为优选的，当无源互调检测电路中的射频信号过大造成链路阻塞时，数字处理单元将缩小无源互调检测电路的链路增益以便正常处理接收信号并停止检测无源互调信号幅值；当无源互调检测电路没有阻塞时，所述数字处理单元在进行无源互调幅值计算过程中，需要处理的来源于无源互调检测电路的信号中包含有无源互调信号和接收信号且无源互调信号和接收信号之间有一定频率间隔。
本发明一种应用自适应抵消无源互调信号的装置的模拟无线收发设备，其技术方案为：包括自适应抵消无源互调信号的装置，所述自适应抵消无源互调信号的装置的双工器即是无线收发设备的双工器；所述自适应抵消无源互调信号的装置的接收单元复用模拟无线收发设备的接收链路的组件或单元；所述自适应抵消无源互调信号的装置的无源互调检测电路在所述模拟无线收发设备内新增；所述自适应抵消无源互调信号的装置的发射电路单元复用模拟无线收发设备的发射链路的组件或单元；所述自适应抵消无源互调信号的装置的数字处理单元复用模拟无线收发设备的数字处理单元的组件或单元，或者在所述模拟无线收发设备内新增数字处理单元，所述自适应抵消无源互调信号的装置数字处理单元集成于模拟无线收发设备的整机程序中；所述自适应抵消无源互调信号的装置的耦合器在所述模拟无线收发设备内新增，且其一个主通路端口和模拟无线收发设备的双工器天线口连接且距离需控制在0到1米范围内，耦合器的耦合端口相对于所述模拟无线收发设备发射信号为正向耦合端口；所述自适应抵消无源互调信号的装置的抵消器电路在所述模拟无线收发设备内新增，且其射频端口和耦合器的耦合端口直接连接；所述自适应抵消无源互调信号的装置的天馈组件和天线即为所述模拟无线收发设备的天线链路上的对应组件和天线；
当模拟无线收发设备有多个收发链路时，所述每一收发链路中双工器的每个天线口后均紧邻一个耦合器，以及抵消器电路。
本发明一种应用自适应抵消无源互调信号的装置的塔顶放大装置，其技术方案为：包括自适应抵消无源互调信号的装置，自适应抵消无源互调信号的装置的双工器即为塔顶放大装置的双工器；自适应抵消无源互调信号的装置的接收单元复用塔顶放大装置的接收单元，自适应抵消无源互调信号的装置的无源互调检测电路需在所述塔顶放大装置内新增，自适应抵消无源互调信号的装置的发射电路单元复用塔顶放大装置的发射电路单元，所述 发射电路单元由鉴频耦合器以及双工器发射端口和收发模块之间的电缆构成，其中鉴频耦合器的耦合端口和发射信号鉴频电路的射频输入端口连接，鉴频耦合器相对于发射信号为正向耦合端口，鉴频耦合器的一个主通路端口连接双工器发射端口，另一个主通路端口连接收发模块的发射端口；自适应抵消无源互调信号的装置的数字处理单元复用塔顶放大装置的数字处理单元，自适应抵消无源互调信号的装置的耦合器需在所述塔顶放大装置内新增，所述耦合器的一个主通路端口和无线收发设备的双工器的天线口直接连接，耦合器的耦合端口相对于所述塔顶放大装置的发射信号为正向耦合端口；自适应抵消无源互调信号的装置的抵消器电路需在所述塔顶放大装置内新增，所述抵消器电路的射频端口和耦合器的耦合端口直接连接，自适应抵消无源互调信号的装置的天馈组件和天线即为所述塔顶放大装置的天线链路上的对应组件和天线。
本发明一种自适应抵消无源互调信号的方法，其技术方案为：包括以下步骤：
S1：获取发射信号带宽和频段、接收信号带宽和频段、无源互调信号中的主要干扰分量的阶次和频段信息、期望的无源互调预设值以及随时间变化的曲线、幅度和相位的初始经验数据、最大抵消次数信息，并转换成相应的配置参数；
S2：依据步骤S1中有关发射信号的配置参数求得无源互调信号的频点，并转换成相应数字滤波参数存储入参量配置表中；
S3：依据步骤S1中有关接收信号、无源互调信号的配置参数以及由步骤S2中获取的无源互调信号的数字滤波参数，对采样信号进行数字滤波，滤除除无源互调信号以外的其他信号分量，求得落入到接收频段的无源互调信号的幅度值；
S4：判断当前工作状态；所述工作状态的状态标识默认值是：“初始工作模式”；如果工作状态的状态标识值是“初始工作模式”则继续步骤S5-1，否则继续步骤S5-2；
S5-1：将步骤S3获取的无源互调信号幅度值与步骤S1中的无源互调预设值进行对比，以判断无源互调信号幅度是否小于等于的无源互调预设值；
S6：如果步骤S5-1的判断结果为“是”，则保持互调信号发生器与耦合器间链路高隔离度状态；并返回步骤S2；
S7：如果步骤S5-1的判断结果为“否”，则)切换到互调信号发生器与耦合器之间链路低隔离度状态；且将工作状态的状态标识值并设置为“抵消工作状态”；继续执行步骤S8；
S5-2：将步骤S3获取的无源互调信号幅度值与步骤S1中的无源互调预设值进行对比，以判断无源互调信号幅度是否小于等于的无源互调预设值；如果步骤S5-2的判断结果为“是”，则保持状态，并返回步骤S2；如果步骤S5-2的判断结果为“否”，则执行步骤S8；
S8：依据步骤S3的无源互调信号的幅度值推算抵消器电路的幅度、相位调整值；并配送给抵消器电路中的调幅器、调相器，实施抵消；在完成当前一轮抵消处理后，将继续回到步骤S2继续下一轮的抵消处理。
本发明的有益效果为：1、能将无线收发设备产生的无源互调信号以及无线收发设备天线口之后链路中任何一个设备或组件产生的无源互调信号落入到接收频段的分量在无线收发设备中的射频链路上抵消，并且在所述无源器件的接收端口获得优于预定的无源互调要求指标的结果。
2、上述效果1使得在保持系统无源互调指标不变情况下，可以降低对无线收发系统 中各个器件的无源互调指标要求，从而降低各个无源器件的制造成本；
3、上述效果1也可以用来消除由于双工器或其天线链路上所述组件或天线随工作时间增长而出现的无源互调指标恶化的影响，从而延长该无线收发系统的生命周期；
4、上述效果1还可以在所述系统需要更好无源互调指标时，提升该指标到预设值以上。
5、当进行无线收发设备的双工器及其天线链路的无源互调抵消并在所述双工器接收端口获得优于预定的无源互调要求指标的结果时，不会对发射信号线性性能和接收信号线性性能产生不良影响；
6、由于采用了有源互调抵消电路，使得信号相位、幅度的调节可以量化，提高了调整精度和准度；
7、由于采用了无源互调信号抵消效果的反馈链路，使得无源互调信号抵消效果可以被实时监测并自适应的动态调整，以便当通过所述无源器件或后续链路上的信号的功率等级、工作频率发生变化时，以及环境温度等发生变化时，可以动态、实时响应，使无源互调信号抵消结果满足预期目标值。由此重要的实用意义。
附图说明
图1是本发明实施例一种自适应抵消无源互调信号的装置的结构示意图。
图2是本发明实施例中抵消器电路B的第一种结构示意图。
图3是本发明实施例中抵消器电路B的第二种结构示意图。
图4是本发明实施例中无源互调检测电路D的超外差结构示意图。
图5是本发明实施例中无源互调检测电路D的接收零中频结构示意图。
图6是本发明实施例中一种自适应抵消无源互调信号方法的流程图。
图7是本发明实施例装置3阶分量的抵消效果图。
图8是本发明实施例装置在3阶分量抵消后的5阶分量的抵消效果图。
图9是本发明实施例一种自适应抵消无源互调信号的装置的模拟无线收发设备的结构示意图。
图10是本发明实施例第一种自适应抵消无源互调信号的装置的塔顶放大装置的结构示意图。
图11是本发明无线收发设备与多个收发链路使用实例之一的示意图。
图12是本发明无线收发设备具有多个收发链路使用实例之一的示意图。
具体实施方式
下面结合附图和具体实施例对本发明作进一步的详细说明，便于清楚地了解本发明，但它们不对本发明构成限定。
实施例，如图1所示，本实施例涉及一种自适应抵消无源互调信号的装置，它包括一个耦合器A，抵消器电路B，无源互调检测电路D，数字处理单元E，双工器A0，发射电路单元F，天馈组件A2，天线A1，收发模块G，接收单元C；所述收发模块G的信号经发射电路单元F线性放大，产生大于40dBm的信号使所述双工器A0及其天线链路上的天馈组件A2和天线A1产生无源互调信号，并且该无源互调信号中有落入到双工器A0接收 频段的且与接收信号有一定频率间隔的分量，依据发射信号的不同配置可以使所述无源互调信号落入双工器A0接收频段的分量包含单个3阶分量、或单个5阶分量、甚至或单个更高阶次分量、或多个不同频率3阶分量、或多个不同频率5阶分量、甚至或多个不同频率的更高阶次分量、或同时有3阶分量和5阶分量甚至高阶次分量。发射信号由多音信号构成或者由多载波调制信号构成。本实施例中，发射频段为925MHz到960MHz，接收频段为880MHz到915MHz；
所述耦合器A从双工器A0的天线口的链路上耦合射频信号输出给抵消器电路B；所述射频信号中包含发射信号、无源互调信号和接收信号；所述耦合器A的一个主通路端口与所述双工器A0的天线口连接、另一个主通路端口与天线链路上的天馈组件A2连接、耦合器A的耦合端口和抵消器电路B的射频端口连接；所述耦合器A紧邻双工器A0天线口，也即距离为0米；
对于双工器A0及其天线链路上的天馈组件A2和天线A1等无源器件，所述无源互调抵消功能作用之一是降低对所述无源器件的无源互调指标要求，作用之二是消除所述无源器件随工作时间增长而出现的无源互调指标恶化的影响，作用之三是提升所述无源器件的无源互调指标。
所述抵消器电路B将利用来自于耦合器A的射频信号中的发射信号在所述互调信号发生器B2上产生出与所述射频信号中的无源互调信号频率相同、幅度不同和相位不同的互调信号，且该互调信号中落入接收频段的单个3阶分量、或单个5阶分量、或单个更高阶次分量，或者多个不同频点的3阶分量、或多个不同频点的5阶分量、或多个不同频点的更高阶次分量，或者同时有3阶分量、5阶分量甚至更高阶次分量之间的幅度关系和相位关系与所述双工器A0及其天线链路产生的无源互调信号中落入接收频段的单个3阶分量、或单个5阶分量、或单个更高阶次分量，或者多个不同频点的3阶分量、或多个不同频点的5阶分量、或多个不同频点的更高阶次分量，或者同时有3阶分量、5阶分量甚至更高阶次分量之间的幅值关系和相位关系基本一致；而耦合到抵消器电路B的射频信号中的接收信号和无源互调信号的功率在所述互调信号发生器B2上产生的互调信号的幅值远小于上述无源互调信号的幅值，不对无源互调抵消结果产生影响；所述互调信号反射后通过调幅调相器B1的幅度调整和相位调整，并耦合输出至耦合器A的主通路，形成与所述无源互调信号中落入接收频段的且与接收信号有一定频率间隔的分量频率相同、幅度相同和相位相反的互调抵消信号，该互调抵消信号与所述无源互调信号中的分量进行抵消，抵消后的无源互调信号小于等于无源互调预设值；同时双工器A0及其天线链路中的发射信号和接收信号在双工器A0及其天线链路中正常运作。
实际选择构成互调信号发生器B2的具体器件时，应使所述互调信号发生器B2上产生出与所述射频信号中的无源互调信号频率相同、幅度不同和相位不同的互调信号，且该互调信号中落入接收频段的单个3阶分量、或单个5阶分量、或单个更高阶次分量，或者多个不同频点的3阶分量、或多个不同频点的5阶分量、或多个不同频点的更高阶次分量，或者同时有3阶分量、5阶分量甚至更高阶次分量之间的幅度关系和相位关系与所述双工器A0及其天线链路产生的无源互调信号中落入接收频段的单个3阶分量、或单个5阶分量、或单个更高阶次分量，或者多个不同频点的3阶分量、或多个不同频点的5阶分量、或多个不同频点的更高阶次分量，或者同时有3阶分量、5阶分量甚至更高阶次分量之间 的幅值关系和相位关系基本一致；而且所述互调信号发生器B2所能产生的对应无源互调分量频率的所述互调抵消信号的最大幅值要大于所述双工器A0及其天线链路的无源互调信号中落入到接收频段的多个对应频率分量的幅值。
调幅调相器B1的幅度调整和相位调整通过数字处理单元E运算输出的幅度、相位控制参数实现；而数字处理单元E的幅度、相位控制参数的计算又需要无源互调检测电路D的采样信号。
激励所述双工器A0及其天线链路产生无源互调信号的信号和激励所述互调信号发生器B2产生互调信号的信号是同源的，均来源于发射电路单元F的发射信号，所以无源器件产生的无源互调信号和互调信号发生器B2产生的互调信号的频率相同、带宽相同；所述天线链路是从双工器A0天线口到天线A1这段链路，所述天馈组件A2代表天线链路中单个或多个无源器件的组合，这些无源器件包括电缆、连接器、耦合器、合路器；所述发射信号由多音信号构成或者由多载波调制信号构成；
当所述双工器A0或天馈组件A2或天线A1单个产生的或多个无源器件同时产生并叠加而成的与接收信号有一定频率间隔的无源互调信号中仅会有单个3阶、或单个5阶或单个更高阶次分量落入双工器A0的接收频带且造成从双工器A0接收端口测试的无源互调指标达不到预设值要求时，为使所述双工器A0接收端口的无源互调值满足预设值要求且使本装置的抵消能力大于20dB：所述互调信号发生器B2所能产生的所述互调抵消信号的最大幅值要大于所述双工器A0及其天线链路的无源互调信号中落入到接收频段对应频率的单个分量的幅值；
当所述双工器A0或天馈组件A2或天线A1单个产生的或多个无源器件同时产生并叠加而成的与接收信号有一定频率间隔的无源互调信号中仅有多个不同频率的3阶、或多个不同频率的5阶或多个不同频率的更高阶次分量落入双工器A0的接收频带且造成从双工器A0接收端口测试的无源互调指标达不到预设值要求时，为使所述双工器A0接收端口的无源互调值满足预设值要求且使本装置的抵消能力大于20dB：所述互调信号发生器B2所能产生的对应无源互调分量频率的互调抵消信号的最大幅值要大于所述双工器A0及其天线链路的无源互调信号中落入到接收频段的多个对应频率分量的幅值；所述互调信号发生器B2上产生的互调信号中多个特定阶次分量之间的相位关系与所述双工器A0及其天线链路产生的无源互调信号中多个特定阶次分量之间的相位关系基本一致；
当所述双工器A0或天馈组件A2或天线A1单个产生的或多个无源器件同时产生并叠加而成的与接收信号有一定频率间隔的无源互调信号中同时有3阶、5阶或更高阶次分量落入双工器A0的接收频带且都造成从双工器A0接收端口测试的无源互调指标达不到预设值要求时，为使所述双工器A0接收端口的无源互调值满足预设值要求且使本装置的抵消能力大于20dB：所述互调信号发生器B2所能产生的对应无源互调分量频率的所述互调抵消信号的最大幅值要大于所述双工器A0及其天线链路的无源互调信号中落入到接收频段的多个对应频率分量的幅值；所述互调信号发生器B2上产生的互调信号中多个特定阶次分量之间的幅度关系和相位关系与所述双工器A0及其天线链路产生的无源互调信号中多个特定阶次分量之间的幅值关系和相位关系基本一致。
所述无源互调检测电路D，作用是获取所述双工器A0接收端口后的射频信号，并经过增益可调控的放大，下变频，最终转换成数字信号并输入到数字处理单元E，所述双工 器A0接收端口后的射频信号包含接收信号和无源互调信号中落入接收频段的分量。
所述无源互调检测电路D的射频端口或者通过耦合器直接从接收单元C的射频输入口前的链路耦合射频信号，此时所述接收单元C的射频输入端口通过该耦合器的主通路和双工器A0接收端口连接；所述无源互调检测电路D或者通过功率分路器或者耦合器从接收单元C中某个射频放大器后获取射频信号，此时所述接收单元C的射频输入端口和双工器A0接收端口直接连接；无源互调检测电路D通过高速模数转换器与所述数字处理单元E连接。所述无源互调检测电路D获取的射频信号中包含接收信号和无源互调信号落入接收频段的分量；所述无源互调检测电路D的接收动态范围大于输入该无源互调检测电路D的接收信号的最大功率值和无源互调预设值对应的功率值之间的差值。
当所述无源互调检测电路D从接收单元C的射频输入端口前的链路通过耦合器获取信号时，此耦合器被称为接收组件，无源互调检测电路D的增益由需求的无源互调预设值、无源互调检测电路D中高速模数转换器的最小采样功率、链路噪声系数、接收组件的耦合度等参数确定；所述无源互调检测电路D的接收信号功率的最大值大于：该装置实际对应的通信标准所规定的最大接收信号功率与接收组件耦合度之差；
当所述无源互调检测电路D从接收单元C中某个射频放大器输出端通过功率分路器或者耦合器获取信号时，此功率分路器或者耦合器被称为接收组件，无源互调检测电路D的增益由需求的无源互调预设值、无源互调检测电路D中高速模数转换器的最小采样功率、链路噪声系数、接收组件的信号衰减度、接收单元C的射频输入口到接收组件这段链路的增益等参数确定；所述无源互调检测电路D的接收信号功率的最大值大于：该装置实际对应的通信标准所规定的最大接收信号功率加上接收单元C的射频输入口到接收组件这段链路的增益，再减去接收组件的信号衰减度。所述无源互调检测电路D的接收动态范围大于70dB；无源互调检测电路D通过高速模数转换器与所述数字处理单元E连接，高速模数转换器的采样速率大于等于2倍的双工器A0接收频段带宽。
所述数字处理单元E首先依据发射信号频率信息，计算出与之相关的无源互调信号的频率信息，并将其转换为无源互调信号的滤波参数，然后依据接收信号频率、带宽信息与无源互调信号频率、带宽信息求得它们之间的频率间隔，再选择相应的数字滤波方式和积分方式，最终实现对无源互调信号的幅值检测；然后将所述无源互调信号的检测幅值与无源互调预设值进行对比：当所述检测幅值小于等于所述预设值时，所述抵消器电路B不产生互调抵消信号，不对所述双工器A0及其天线链路的无源互调指标产生影响；当所述检测幅值大于所述预设值时，控制所述抵消器电路B对其幅度和相位的调整产生出与所述双工器A0及其天线链路的无源互调信号频率相同、幅度相同和相位相反的互调抵消信号与所述射频信号中的无源互调信号进行抵消，并保持这种依据无源互调信号的幅值检测结果实时调控所述抵消器电路B幅度和相位使无源互调信号抵消结果小于等于所述预设值的工作状态；
所述数字处理单元E获取所述发射信号频率信息和接收信号频率信息的一种方法是利用发射信号鉴频电路E1从所述装置的发射电路单元F上获取发射信号，转换为数字信号，输入数字处理单元E进行鉴频处理，获取相关发射信号频率信息，并由发射信号和接收信号之间的双工频率间隔推算相应接收信号频率信息；获取所述发射信号频率信息和接收信号频率信息的另一种方法是通过数字处理单元E中的信息交互接口直接从该装置的 输入信息中获取。
当无源互调检测电路D中的射频信号过大造成链路阻塞时，数字处理单元E将缩小无源互调检测电路D的链路增益以便正常处理接收信号并停止检测无源互调信号幅值；当无源互调检测电路D没有阻塞时，所述数字处理单元E在进行无源互调幅值计算过程中，需要处理的来源于无源互调检测电路D的信号中包含有无源互调信号和接收信号且无源互调信号和接收信号之间有一定频率间隔。
计算无源互调信号幅值的方法为：数字处理单元E首先依据发射信号频率信息计算出与之相关的无源互调信号的频率信息，然后依据接收信号频率、带宽信息与无源互调信号频率、带宽信息求得它们之间的频率间隔，并依据该频率间隔选择合适的算法计算无源互调信号幅值；所述计算无源互调信号幅值的算法包含但不限于直接滤波积分法和分段滤波积分法：所述直接滤波积分法是指依据无源互调信号带宽直接数字滤波并积分求幅度，此时所述无源互调信号落入到接收频段的各阶次分量与接收信号之间的频率间隔要大于等于无源互调信号的数字滤波算法中数字滤波器通带到阻带的过渡带带宽，此频率间隔即是采用直接滤波积分法的依据；所述分段滤波积分法是指将无源互调信号带宽分成数个子带宽，依据每个子带宽进行数字滤波并积分求幅度，再将所有子带宽对应的幅度进行累加获得整个信号幅值，此时所述各阶次分量与接收信号之间的频率间隔要大于等于各阶次分量边子带信号的数字滤波器通带到阻带的过渡带带宽，此频率间隔即是采用分段滤波积分法的依据。
本实施例中，所述抵消器电路B通过耦合器A与双工器A0天线口后的天线链路连接；所述耦合器A的一个主通路端口与双工器A0天线口连接即距离为0米，耦合器A的另一个主通路端口与天馈组件A2连接，耦合器A的耦合端口连接抵消器电路B；所述耦合器A的插入损耗小于0.2dB，耦合器A的耦合度范围为30dB左右，耦合器A的耦合端口相对于发射信号为正向耦合端口，耦合器A承载的平均功率大于100瓦特且承载的峰值功率大于1000瓦特，耦合器A的带宽包含发射频段，接收频段以及两者间的双工间隔，耦合器A的频带内增益波动与发射频段、接收频段相关且需在一定的门限值范围内；耦合器A的无源互调指标为-117dBm/Hz；所述抵消器电路B承载的平均功率门限值大于等于20dBm且承载的峰值功率门限值大于等于30dBm；为使抵消器电路B中互调信号发生器B2能产生无源互调抵消信号，加载在所述抵消器电路B的发射信号功率的最小值需大于10瓦特；
所述数字处理单元E通过多路数模转换器与抵消器电路B连接，将幅度、相位的控制量传递给抵消器电路B，所述抵消器电路B的幅度调整精度小于0.1dB和相位调整精度小于1度；
所述数字处理单元E与无源互调检测电路D之间至少存在两个接口：一个接口作用是获取无源互调检测电路D中高速模数转换器的采样信号，从而进行无源互调信号的数字滤波和幅度计算；另一个接口的作用是通过总线配置无源互调检测电路D的参数，例如本振频率，放大器增益等，所述总线包括I2C总线、SPI总线；
当所述数字处理单元E获取所述发射信号频率信息和接收信号频率信息的方法是利用发射信号鉴频电路E1时，则发射信号鉴频电路E1的射频端口与所述发射电路单元F中发射链路上的某处连接，发射信号鉴频电路E1通过高速模数转换器与所述数字处理单元E连接；同时数字处理单元E与发射信号鉴频电路E1之间还有一个接口，作用是通过 总线配置发射信号鉴频电路E1的参数，例如本振频率、链路增益等，所述总线包括I2C总线、SPI总线；
所述数字处理单元E具备至少一个信息交互接口，其作用包含但不限于程序下载，配置信息输入，远程告警和维护；其中需要输入的配置信息包括本装置发射信号带宽和频段、接收信号带宽和频段、无源互调信号中的主要干扰分量的阶次和频段信息、无源互调信号预设值以及随时间变化的曲线、最大抵消次数；所述数字处理单元E可以通过信息交互接口获取发射信号频率信息和接收信号频率信息；所述的信息交互接口还可以与互联网后台资源进行数据交互：上传所述设备运行过程中的无源互调值，无源互调值随时间变化的经验曲线，以及无源互调信号自适应抵消装置中各模块电路的状态信息；或者下载综合优化后的无源互调信号预设值以及随时间变化的曲线。数字处理单元E的信息交互接口的硬件构成包括以太网接口、光纤接口、RS-485总线接口。
本实施例中，所述抵消器电路B的第一种方案，如图2所示：所述抵消器电路B中的调幅调相器B1一端直接连接耦合器A的耦合端口，或者通过射频开关B3连接耦合器A的耦合端口，另一端连接互调信号发生器B2；所述调幅调相器B1包括调幅电路和调相电路；其中所述调幅电路1a由可调控衰减器和固定衰减器构成；调相电路2a至少包含2个可调控移相器；所述调幅调相器B1的幅度调整范围大于30dB，相位调整范围大于180度；所述抵消器电路B中调幅调相器B1承载的平均功率门限值大于等于20dBm且承载的峰值功率门限值大于等于30dBm，所述调幅调相器B1的工作频段包含所述双工器A0的发射频段和接收频段，调幅调相器B1的频带内增益波动与发射频段、接收频段相关且需在一定的门限值范围内；
进一步地，输入至所述抵消器电路B的射频信号中的发射信号经射频开关B3或直接输入到调幅调相器B1，再经调幅调相器B1中调幅电路1a的功率调整后输入到互调信号发生器B2，使互调信号发生器B2产生出与所述射频信号中的无源互调信号频率相同、幅度不同和相位不同的互调信号，且该互调信号中落入接收频段的单个3阶分量、或单个5阶分量、或单个更高阶次分量，或者多个不同频点的3阶分量、或多个不同频点的5阶分量、或多个不同频点的更高阶次分量，或者同时有3阶分量、5阶分量甚至更高阶次分量之间的幅度关系和相位关系与所述双工器A0及其天线链路产生的无源互调信号中落入接收频段的单个3阶分量、或单个5阶分量、或单个更高阶次分量，或者多个不同频点的3阶分量、或多个不同频点的5阶分量、或多个不同频点的更高阶次分量，或者同时有3阶分量、5阶分量甚至更高阶次分量之间的幅值关系和相位关系基本一致；而该射频信号中的接收信号和无源互调信号的功率在所述互调信号发生器B2上产生的互调信号的幅值远小于上述无源互调信号的幅值，不对无源互调抵消结果产生影响；所述互调信号反射后再次通过调幅调相器B1，并经调幅调相器B1的幅度调整和相位调整，并经射频开关B3或者直接输入到耦合器A，最后耦合输出至耦合器A的主通路，形成与所述耦合器A主通路的无源互调信号中落入接收频段的且与接收信号有一定频率间隔的分量频率相同、幅度相同和相位相反的互调抵消信号，该互调抵消信号与所述无源互调信号中的分量进行抵消，抵消后的无源互调信号小于等于无源互调预设值；同时双工器A0及其天线链路中的发射信号和接收信号在双工器A0及其天线链路中正常运作；
本实施例中，所述抵消器电路B第二种方案，如图3所示：所述抵消器电路B中的 第二调幅电路3一端通过第一环行器4与耦合器A的耦合端口连接，或者可以通过第一环行器4、射频开关B3与耦合器A的耦合端口连接；另一端通过第二环行器5与互调信号发生器B2连接；所述抵消器电路B中的调幅调相器B1一端通过第二环行器5与互调信号发生器B2连接；另一端通过第一环行器4与耦合器A的耦合端口连接，或者可以通过第一环行器4、射频开关B3与耦合器A的耦合端口连接；所述第二调幅电路3，作用是使互调信号发生器B2承受一个合适功率的射频信号；所述调幅调相器B1包含第一调幅电路1b和调相电路2b，作用是将互调信号发生器B2产生的互调信号，进行调幅、调相处理，以便与本装置中双工器A0及其天线链路产生的无源互调信号进行抵消；所述第一调幅电路1b至少包含1个可调控衰减器；所述调相电路2b至少包含2个可调控移相器；所述第二调幅电路3由固定衰减器或可调控衰减器构成；所述第一环行器4和第二环行器5的频率带宽包括所述双工器A0的发射频段和接收频段；所述调幅调相器B1的幅度调整范围大于30dB，相位调整范围大于180度，所述调幅调相器B1的工作频段包含所述双工器A0的接收频段，调幅调相器B1的频带内增益波动与接收频段相关且需在一定的门限值范围内；所述抵消器电路B中第二调幅电路3承载的平均功率门限值大于等于20dBm且承载的峰值功率门限值大于等于30dBm；
进一步地，输入至所述抵消器电路B射频信号中的发射信号经第一环行器4输入到第二调幅电路3或者经射频开关B3和第一环行器4输入到第二调幅电路3，再经第二调幅电路3的功率调整后通过第二环行器5输入到互调信号发生器B2，使互调信号发生器B2产生出与所述射频信号中的无源互调信号频率相同、幅度不同和相位不同的互调信号，且该互调信号中落入接收频段的单个3阶分量、或单个5阶分量、或单个更高阶次分量，或者多个不同频点的3阶分量、或多个不同频点的5阶分量、或多个不同频点的更高阶次分量，或者同时有3阶分量、5阶分量甚至更高阶次分量之间的幅度关系和相位关系与所述双工器A0及其天线链路产生的无源互调信号中落入接收频段的单个3阶分量、或单个5阶分量、或单个更高阶次分量，或者多个不同频点的3阶分量、或多个不同频点的5阶分量、或多个不同频点的更高阶次分量，或者同时有3阶分量、5阶分量甚至更高阶次分量之间的幅值关系和相位关系基本一致；而该射频信号中的接收信号和无源互调信号的功率在所述互调信号发生器B2上产生的互调信号的幅值远小于上述无源互调信号的幅值，不对无源互调抵消结果产生影响；所述互调信号反射后通过第二环行器5输入到调幅调相器B1，并经调幅调相器B1的幅度调整和相位调整，通过第一环行器4或通过第一环行器4和射频开关B3最后耦合输出至耦合器A的主通路，形成与所述耦合器A主通路的无源互调信号中落入接收频段的且与接收信号有一定频率间隔的分量频率相同、幅度相同和相位相反的互调抵消信号，该互调抵消信号与所述无源互调信号中的分量进行抵消，抵消后的无源互调信号小于等于无源互调预设值；同时双工器A0及其天线链路中的发射信号和接收信号在双工器A0及其天线链路中正常运作；
本实施例中，所述抵消器电路B两种方案中的互调信号发生器B2包含但不限于单个二极管、单个三极管或多个二极管的并联构成；二极管具体型号或者三极管具体型号与产生互调信号3阶、5阶或更高阶互调信号的幅值特性和相位特性相关；采用多个同型号二极管并联结构时，将增强互调信号强度；互调信号发生器B2的承载功率大于等于20dBm。
本实施例中，所述无源互调检测电路D至少包括下变频模块、高速模数转换器；下变 频模块可以将接收的射频信号转换成中频信号；高速模数转换器的采样动态范围需大于70dB，模数转换器的位数为14位，采样速率大于等于2倍的双工器A0接收频段带宽；所述无源互调检测电路D能够采样的最小功率小于等于-115dBm，同时该电路可以根据所接收的射频信号总功率的幅值调整链路增益从而避免接收信号或其他信号造成的链路阻塞；所述无源互调检测电路D的增益由需求的无源互调预设值、无源互调检测电路D中高速模数转换器的最小采样功率、链路噪声系数等确定；所述无源互调检测电路D的接收信号功率的最大值大于等于-50dBm。
所述无源互调检测电路D可以采用如图4所示的接收超外差结构将射频信号转换为中频信号再进行模数转换，此时无源互调检测电路D由低噪声放大器D1、射频滤波及小信号放大单元D2、混频器D3、本振D4、中频滤波器D5、中频放大器D6、模数转换器D7构成，其中射频滤波及小信号放大单元D2中的滤波组件的通带频段为双工器A0的接收频段。
所述无源互调检测电路D或者可以采用如图5所示的接收零中频结构将射频信号转换为零中频信号再进行模数转换，此时无源互调检测电路D由低噪声放大器D1、射频滤波及小信号放大单元D2、下变频及模数转换单元D8构成，其中射频滤波及小信号放大单元D2中的滤波组件的通带频段为双工器A0的接收频段，下变频及模数转换单元D8作用是将射频信号直接转换为零中频信号并进行模数转换。
本实施例中，所述数字处理单元E至少包含具备数字信号处理功能的逻辑处理与运算处理器件，用于数字信号的接收、算法处理、数字信号的输出、控制和配置信号的输出等，所述逻辑处理与运算处理器件包含但不限于现场可编程门阵列器件，中央处理器，数字信号处理器；所述数字处理单元E的信息交互接口的硬件构成包括以太网接口、RS-485总线接口；所述数字处理单元E中的数模转换器的位数为12位之间，且至少有3个数模转换器；所述数字处理单元E中运行对应“一种自适应抵消无线收发系统中无源互调信号的方法”的程序，该方法的流程图参见图6：
S1：通过数字处理单元E获取发射信号带宽和频段、接收信号带宽和频段、无源互调信号中的主要干扰分量的阶次和频段信息、期望的无源互调预设值以及随时间变化的曲线、幅度和相位的初始经验数据、最大抵消次数等信息，并转换成相应的配置参数；
S2：依据步骤S1中有关发射信号的配置参数，数字处理单元E求得无源互调信号的频点并转换成相应数字滤波参数存储入参量配置表中；
S3：依据步骤S1中有关接收信号的配置参数、无源互调信号的配置参数以及由步骤S2中获取的无源互调信号的数字滤波参数，数字处理单元E对无源互调检测电路D的采样信号进行数字滤波，滤除除无源互调信号以外的其他信号分量，求得落入到接收频段的无源互调信号的幅度值；所述求幅度值的算法包括分段积分法、依据信号带宽的直接积分法；
S4：判断当前工作状态；所述工作状态的状态标识默认值是：“初始工作模式”；如果工作状态的状态标识值是“初始工作模式”则继续步骤S5-1，否则继续步骤S5-2；
S5-1：将步骤S3获取的无源互调信号幅度值与步骤S1中的无源互调预设值进行对比以判断无源互调信号幅度是否小于等于的无源互调预设值；
S6：如果步骤S5-1的判断结果为“是”，则抵消器电路B继续保持互调信号发生器与 耦合器A之间链路高隔离度状态；并返回步骤S2；
S7：如果步骤S5-1的判断结果为“否”，则抵消器电路B切换到互调信号发生器与耦合器A之间链路低隔离度状态；且将工作状态的状态标识值并设置为“抵消工作状态”；继续执行步骤S8；
S5-2：将步骤S3获取的无源互调信号幅度值与步骤S1中的无源互调预设值进行对比以判断无源互调信号幅度是否小于等于的无源互调预设值；如果步骤S5-2的判断结果为“是”，则保持状态，并返回步骤S2；如果步骤S5-2的判断结果为“否”，则执行步骤S8；
S8：依据步骤S3的无源互调信号的幅度值推算抵消器电路的幅度、相位调整值；并配送给抵消器电路中的调幅器、调相器，实施抵消；在完成当前一轮抵消处理后，将继续回到步骤S2继续下一轮的抵消处理；所述求幅度、相位调整值的算法包括二维最小方差演算法。
本实施例中，如表1所示：
Figure PCTCN2019090975-appb-000001
所述发射电路单元F中有两个43dBm的单音信号构成了一个46dBm的双音信号，该双音信号使双工器A0及其天线链路产生了无源互调信号，并且实际在双工器A0接收端口测试到的无源互调中3阶分量幅值为-94.7dBm，且5阶分量为-124.8dBm，7阶分量在频谱仪热噪声之下；所述双工器A0及其天线链路的无源互调信号中落入接收频段的分量小于等于-112dBm的预设值，所以主要优化3阶无源互调不良，同时3阶信号和5阶信号幅值相差30.1dB；此时选用的特定二极管所产生的互调信号在双工器A0接收端口的测试值是：3阶分量幅值为-75.6dBm，且5阶分量为-106.3dBm，7阶分量在频谱仪热噪声之下，此时3阶信号和5阶信号幅值相差30.7dB；当无源互调抵消功能开启后，此时在双工器A0接收端口测试到的无源互调中3阶分量如图7所示，幅值为-119.6dBm，且5阶分量如图8所示，为-130.8dBm，7阶分量在频谱仪热噪声之下；可以看出造成装置无源互调不良的3阶分量优化了24.9dB，且5阶分量也同步被优化。此时，所述无源互调信号落入到接收频段的各阶次分量与接收信号之间的频率间隔大于等于200KHz。
本装置可以应用于模拟无线收发设备及其天线链路以便抵消无源器件产生的不合格 的无源互调使无线收发设备及其天线链路的无源互调指标满足无源互调预设值；并且当多个无线收发设备同时使用且每个设备的天线链路通过合路器合路后连接天线时，对应于每条天线链路的本装置也可以抵消该天线链路上的无源器件产生的不合格的无源互调使无线收发设备及其天线链路的无源互调指标满足无源互调预设值；所述模拟无线收发设备包括直放站、无线电台、塔顶放大器等设备，所述天线链路包含但不限于电缆、连接器、耦合器、合路器、天线。
本实施例装置应用于模拟无线收发设备的一个实例如图9所示：此时本装置的双工器A0即是无线收发设备的双工器A0；本装置的接收单元C复用无线收发设备的接收单元C，所述接收单元C由低噪声放大器C1、功率分路器C2、功率放大器C3构成，其中功率分路器C2的一个功率分路端口和无源互调检测电路D的射频输入口连接，功率分路器C2的另一个功率分路端口和功率放大器C3的射频输入端口连接，功率分路器C2的功率合路端口和低噪声放大器C1的输出口连接；本装置的无源互调检测电路D需在无线收发设备内新增；本装置的发射电路单元F复用无线收发设备的发射电路单元F，所述发射电路单元F由功率放大器F1、耦合器F2、功率推动放大器F3构成，其中耦合器F2的耦合端口和发射信号鉴频电路E1的射频输入端口连接，耦合器F2相对于发射信号为正向耦合端口，耦合器F2的一个主通路端口连接功率放大器F1，另一个主通路端口连接功率推动放大器F3；本装置的数字处理单元E需在无线收发设备内新增，所述数字处理单元E中将运行对应“一种自适应抵消无线收发系统中无源互调信号的方法”的程序；本装置的耦合器A需在无线收发设备内新增，所述耦合器A的一个主通路端口和无线收发设备的双工器A0的天线口直接连接；本装置的抵消器电路B需在无线收发设备内新增，所述抵消器电路B的射频端口和耦合器A的耦合端口直接连接，抵消器电路B的幅度、相位调整由数字处理单元E运算输出的幅度、相位控制参数实现；所述本装置中的收发模块G即是无线收发设备中的收发模块G；本装置的天馈组件A2和天线A1即为所述无线收发设备外天线链路上的对应组件和天线。
此外，本实施例所述装置应用在塔顶放大装置的一个实例如图10所示：此时本装置的双工器A0即为塔顶放大装置的双工器A0；本装置的接收单元C复用塔顶放大装置的接收单元C，所述接收单元C由低噪声放大器C1、功率分路器C2、接收通带滤波器C3构成，其中功率分路器C2的一个功率分路端口和无源互调检测电路D的射频输入口连接，功率分路器C2的另一个功率分路端口和接收通带滤波器C3的射频输入端口连接，功率分路器C2的功率合路端口和低噪声放大器C1的输出口连接；本装置的无源互调检测电路D需在所述塔顶放大装置内新增，它通过功率分路器C2从塔顶放大装置中的接收链路获取射频信号，该射频信号经过增益可调控的放大，下变频，最终转换成数字信号输入到数字处理单元E；本装置的发射电路单元F复用塔顶放大装置的发射电路单元F，所述发射电路单元F由鉴频耦合器F1以及双工器A0发射端口和收发模块G之间的电缆构成，其中鉴频耦合器F1的耦合端口和发射信号鉴频电路E1的射频输入端口连接，鉴频耦合器F1相对于发射信号为正向耦合端口，鉴频耦合器F1的一个主通路端口连接双工器A0发射端口，另一个主通路端口连接收发模块G的发射端口；本装置的数字处理单元E复用塔顶放大装置的数字处理单元E，所述数字处理单元E中对应“一种自适应抵消无线收发系统中无源互调信号的方法”的程序将集成于塔顶放大装置的整机程序中；本装置的耦合 器A需在所述塔顶放大装置内新增，所述耦合器A的一个主通路端口和无线收发设备的双工器A0的天线口直接连接，耦合器A的耦合端口相对于所述塔顶放大装置的发射信号为正向耦合端口；本装置的抵消器电路B需在所述塔顶放大装置内新增，所述抵消器电路B的射频端口和耦合器A的耦合端口直接连接，抵消器电路B的幅度调整和相位调整由数字处理单元E运算输出的幅度、相位控制参数实现；所述本装置中的收发模块G复用塔顶放大装置中的收发模块G，所述塔顶放大装置外部的基站侧收发设备的天线口与收发模块G连接进行射频发射信号和接收信号的交互，另外收发模块G与数字处理单元E之间具备一个接口，以便将塔顶放大装置外部的基站侧收发设备的控制信息传递给数字处理单元E的信息交互接口；本装置的天馈组件A2和天线A1即为所述塔顶放大装置的天线链路上的对应组件和天线。
此外，本实施例所述装置应用在无线收发设备且无线收发设备有多个收发链路时：所述每一收发链路中双工器的每个天线口后均紧邻一个耦合器A，以及抵消器电路B；
此外，本实施例所述装置应用在无线收发设备，在多射频链路使用实例之一的示意图如说明书附图11所示：整个链路包括多个无线收发设备，多射频系统合路器H，天线A1以及天馈组件A2等；且每个支路均有一个无源互调抵消装置与的无线收发设备单一收发链路连接，各个分支链路上双工器A0、天线A1、天馈组件A2等产生的无源互调以及多射频系统合路器H产生的无源互调落入到接收频段的分量均可在一定范围内被抵消；
此外，本实施例所述装置应用在无线收发设备，且所述的无线收发设备有多个收发链路时，使用实例之一的示意图如说明书附图12所示：整个链路包括无线收发设备，多根天线A1-1，A1-2，……，以及多个组件A2-1，A2-2，……；无线收发设备每个收发链路均有一个无源互调抵消装置连接，各个分支链路上双工器、组件、天线等产生的无源互调落入到接收频段的分量均可在一定范围内被抵消；
应用本发明设计完成的装置安装于无线收发系统后，在链路无源互调信号落入接收频段的分量为-90dBm/Hz到-95dBm/Hz时，所述装置可以使无源互调信号抵消结果大于20dB，在链路无源互调信号落入接收频段的分量优于-95dBm/Hz时，所述装置可以使无源互调信号抵消结果至少优于-115dBm/Hz。
应当理解的是，以上仅为本发明的具体实施方式，但本发明的保护范围并不局限于此，任何熟悉本领域的技术人员在本发明所揭露的技术范围内，可轻易想到的变化或替换，都应涵盖在本发明的保护范围之内。

Claims (23)

  1. 一种自适应抵消无源互调信号的装置，其特征在于：它包括一个耦合器(A)、双工器(A0)、天线(A1)、天馈组件(A2)、抵消器电路(B)、接收单元(C)、无源互调检测电路(D)、数字处理单元(E)、发射电路单元(F)和收发模块(G)；
    所述收发模块(G)的发射信号经发射电路单元(F)线性放大，使所述双工器(A0)及其天线链路产生无源互调信号，并且该无源互调信号中有落入到双工器(A0)接收频段的且与接收信号有一定频率间隔的分量；
    所述耦合器(A)从双工器(A0)的天线口的链路上耦合射频信号输出给抵消器电路(B)；所述射频信号中包含发射信号、无源互调信号和接收信号；所述耦合器(A)的一个主通路端口与所述双工器(A0)的天线口连接、另一个主通路端口与天线链路上的天馈组件(A2)连接、耦合器(A)的耦合端口和抵消器电路(B)的射频端口连接；
    所述抵消器电路(B)利用来自于耦合器(A)的射频信号中的发射信号在抵消器电路(B)中产生出互调信号，所述互调信号通过抵消器电路(B)的幅度调整和相位调整，并耦合输出至耦合器(A)的主通路，形成与所述无源互调信号中落入接收频段的且与接收信号有一定频率间隔的分量频率相同、幅度相同和相位相反的互调抵消信号；
    所述无源互调检测电路(D)，作用是通过接收单元(C)获取所述双工器(A0)接收端口后的射频信号，并经过增益可调控的放大，下变频，最终转换成数字信号并输入到数字处理单元(E)，所述射频信号包含接收信号和无源互调信号中落入接收频段的分量；
    所述数字处理单元(E)用于依据发射信号频率信息，实现对无源互调信号的幅值检测，以及在检测幅值大于所述预设值时，控制所述抵消器电路(B)产生出互调抵消信号与所述射频信号中的无源互调信号进行抵消。
  2. 根据权利要求1所述的自适应抵消无源互调信号的装置，其特征在于：所述双工器(A0)代表无线收发设备中的无源器件；所述天馈组件(A2)和天线(A1)代表无线收发系统的天线链路中的无源器件，所述天馈组件(A2)代表天线链路中单个或多个无源器件的组合，这些无源器件包括电缆、连接器、耦合器、合路器。
  3. 根据权利要求1所述的自适应抵消无源互调信号的装置，其特征在于：所述抵消器电路(B)利用来自于耦合器(A)的射频信号中的发射信号在抵消器电路(B)中产生出与所述射频信号中的无源互调信号频率相同、幅度不同和相位不同的互调信号，且该互调信号中落入接收频段的各个分量之间的幅度关系和相位关系与所述双工器(A0)及其天线链路产生的无源互调信号中落入接收频段的各个分量之间的幅值关系和相位关系一致；
    而耦合到抵消器电路(B)的射频信号中的接收信号和无源互调信号的功率在抵消器电路(B)内的所述互调信号发生器(B2)上产生的互调信号的幅值远小于上述无源互调信号的幅值，不对无源互调抵消结果产生影响；
    所述互调信号反射后通过抵消器电路(B)幅度调整和相位调整，并耦合输出至耦合器(A)的主通路，形成与所述无源互调信号中落入接收频段的且与接收信号有一定频率间隔的分量频率相同、幅度相同和相位相反的互调抵消信号，该互调抵消信号与所述无源互调信号中的分量进行抵消，抵消后的无源互调信号小于等于无源互调预设值；同时双工器(A0)及其天线链路中的发射信号和接收信号在双工器(A0)及其天线链路中正常运作；
    所述各个分量包含单个3阶分量、或单个5阶分量、甚至或单个更高阶次分量、或多个不同频率3阶分量、或多个不同频率5阶分量、甚至或多个不同频率的更高阶次分量、或同时有3阶分量和5阶分量甚至高阶次分量。
  4. 根据权利要求1所述的自适应抵消无源互调信号的装置，其特征在于，所述数字处理单元(E)用于依据发射信号频率信息，实现对无源互调信号的幅值检测，以及在检测幅值大于所述预设值时，控制所述抵消器电路(B)产生出互调抵消信号与所述射频信号中的无源互调信号进行抵消的方法如下：
    所述数字处理单元(E)首先依据发射信号频率信息，计算出与之相关的无源互调信号的频率信息，并将其转换为无源互调信号的滤波参数；
    然后依据接收信号频率、带宽信息与无源互调信号频率、带宽信息求得它们之间的频率间隔，再选择相应的数字滤波方式和积分方式，最终实现对无源互调信号的幅值检测；
    然后将所述无源互调信号的检测幅值与无源互调预设值进行对比：
    当所述检测幅值小于等于所述预设值时，所述抵消器电路(B)不产生互调抵消信号，不对所述双工器(A0)及其天线链路的无源互调指标产生影响；
    当所述检测幅值大于所述预设值时，控制所述抵消器电路(B)对其幅度和相位的调整产生出与所述双工器(A0)及其天线链路的无源互调信号频率相同、幅度相同和相位相反的互调抵消信号与所述射频信号中的无源互调信号进行抵消，并保持这种依据无源互调信号的幅值检测结果实时调控所述抵消器电路(B)幅度和相位使无源互调信号抵消结果小于等于所述预设值的工作状态。
  5. 根据权利要求1所述的自适应抵消无源互调信号的装置，其特征在于，还包括发射信号鉴频电路(E1)；
    所述数字处理单元(E)获取所述发射信号频率信息和接收信号频率信息包括：
    利用发射信号鉴频电路(E1)从发射电路单元(F)上获取发射信号，转换为数字信号，输入数字处理单元(E)进行鉴频处理，获取相关发射信号频率信息，并由发射信号和接收信号之间的双工频率间隔推算相应接收信号频率信息；或
    通过数字处理单元(E)中的信息交互接口直接从该装置的输入信息中获取。
  6. 根据权利要求3所述的自适应抵消无源互调信号的装置，其特征在于，激励所述双工器(A0)及其天线链路产生无源互调信号的信号和激励所述互调信号发生器(B2)产生互调信号的信号是同源的，均来源于发射电路单元(F)的发射信号，所以无源器件产生的无源互调信号和互调信号发生器(B2)产生的互调信号的频率相同、带宽相同；
    所述天线链路是从双工器(A0)天线口到天线(A1)这段链路；
    所述发射信号由多音信号构成或者由多载波调制信号构成。
  7. 根据权利要求1所述的自适应抵消无源互调信号的装置，其特征在于，当所述双工器(A0)或天馈组件(A2)或天线(A1)单个产生的或多个无源器件同时产生并叠加而成的，与接收信号有一定频率间隔的无源互调信号中，仅有单个3阶、或单个5阶或单个更高阶次分量落入双工器(A0)的接收频带，且造成从双工器(A0)接收端口测试的无源互调指标达不到预设值要求时，所述互调信号发生器(B2)所能产生的互调抵消信号的最大幅值要大于所述双工器(A0)及其天线链路的无源互调信号中落入到接收频段对应频率的单个分量的幅值；
    当所述双工器(A0)或天馈组件(A2)或天线(A1)单个产生的或多个无源器件同时产生并叠加而成的，与接收信号有一定频率间隔的无源互调信号中，仅有多个不同频率的3阶、或多个不同频率的5阶或多个不同频率的更高阶次分量落入双工器(A0)的接收频带，且造成从双工器(A0)接收端口测试的无源互调指标达不到预设值要求时，所述互调信号发生器(B2)所能产生的对应无源互调分量频率的互调抵消信号的最大幅值要大于所述双工器(A0)及其天线链路的无源互调信号中落入到接收频段的多个对应频率分量的幅值；所述互调信号发生器(B2)上产生的互调信号中多个特定阶次分量之间的相位关系与所述双工器(A0)及其天线链路产生的无源互调信号中多个特定阶次分量之间的相位关系一致；
    当所述双工器(A0)或天馈组件(A2)或天线(A1)单个产生的或多个无源器件同时产生并叠加而成的，与接收信号有一定频率间隔的无源互调信号中，同时有3阶、5阶或更高阶次分量落入双工器(A0)的接收频带，且都造成从双工器(A0)接收端口测试的无源互调指标达不到预设值要求时，所述互调信号发生器(B2)所能产生的对应无源互调分量频率的所述互调抵消信号的最大幅值要大于所述双工器(A0)及其天线链路的无源互调信号中落入到接收频段的多个对应频率分量的幅值；所述互调信号发生器(B2)上产生的互调信号中多个特定阶次分量之间的幅度关系和相位关系与所述双工器(A0)及其天线链路产生的无源互调信号中多个特定阶次分量之间的幅值关系和相位关系一致。
  8. 根据权利要求1所述的自适应抵消无源互调信号的装置，其特征在于：当无源互调检测电路(D)中的射频信号过大造成链路阻塞时，数字处理单元(E)将缩小无源互调检测电路(D)的链路增益以便正常处理接收信号并停止检测无源互调信号幅值；
    当无源互调检测电路(D)没有阻塞时，所述数字处理单元(E)在进行无源互调幅值计算过程中，需要处理的来源于无源互调检测电路(D)的信号中包含有无源互调信号和接收信号且无源互调信号和接收信号之间有一定频率间隔。
  9. 根据权利要求4所述的自适应抵消无源互调信号的装置，其特征在于，所述数字处理单元(E)计算无源互调信号幅值的方法为：
    所述数字处理单元(E)首先依据发射信号频率信息计算出与之相关的无源互调信号的频率信息；
    然后依据接收信号频率、带宽信息与无源互调信号频率、带宽信息求得它们之间的频率间隔，并依据该频率间隔计算无源互调信号幅值；
    所述计算无源互调信号幅值的方法为直接滤波积分法或分段滤波积分法；
    所述直接滤波积分法是指依据无源互调信号带宽直接数字滤波并积分求幅度，此时所述无源互调信号落入到接收频段的各阶次分量与接收信号之间的频率间隔要大于等于无源互调信号的数字滤波算法中数字滤波器通带到阻带的过渡带带宽，此频率间隔即是采用直接滤波积分法的依据；
    所述分段滤波积分法是指将无源互调信号带宽分成数个子带宽，依据每个子带宽进行数字滤波并积分求幅度，再将所有子带宽对应的幅度进行累加获得整个信号幅值，此时所述各阶次分量与接收信号之间的频率间隔要大于等于各阶次分量边子带信号的数字滤波器通带到阻带的过渡带带宽，此频率间隔即是采用分段滤波积分法的依据。
  10. 根据权利要求1所述的自适应抵消无源互调信号的装置，其特征在于：所述抵消 器电路(B)通过耦合器(A)与双工器(A0)天线口后的天线链路连接；所述耦合器(A)的一个主通路端口与双工器(A0)天线口连接且距离需控制在0到1米范围内，耦合器(A)的另一个主通路端口与天馈组件(A2)连接，耦合器(A)的耦合端口连接抵消器电路(B)；耦合器(A)的耦合端口相对于发射信号为正向耦合端口，耦合器(A)的承载功率需大于自适应抵消无源互调信号的装置的最大发射功率峰值，耦合器(A)的带宽包含发射频段，接收频段以及两者间的双工间隔，耦合器(A)的频带内增益波动与发射频段、接收频段相关且需在一定的门限值范围内；所述抵消器电路(B)的承载功率门限值需大于等于耦合器(A)的功率门限值与耦合器(A)的耦合度之差值；为使抵消器电路(B)中互调信号发生器(B2)能产生无源互调抵消信号，加载在所述抵消器电路(B)的发射信号功率的最小值需大于一定的功率门限值。
  11. 根据权利要求1所述的自适应抵消无源互调信号的装置，其特征在于：所述无源互调检测电路(D)通过耦合器从接收单元(C)射频输入口前的链路耦合射频信号，所述接收单元(C)的射频输入端口通过该耦合器的主通路和双工器(A0)接收端口连接；
    所述无源互调检测电路(D)的增益由需求的无源互调预设值、无源互调检测电路(D)中高速模数转换器的最小采样功率、链路噪声系数、接收组件的耦合度确定；所述无源互调检测电路(D)的接收信号功率的最大值大于m，所述m为该装置实际对应的通信标准所规定的最大接收信号功率与接收组件耦合度之差。
  12. 根据权利要求1所述的自适应抵消无源互调信号的装置，其特征在于：所述无源互调检测电路(D)通过功率分路器或者耦合器从接收单元(C)中的一个射频放大器后获取射频信号，所述接收单元(C)的射频输入端口和双工器(A0)接收端口连接；
    所述无源互调检测电路(D)的增益由需求的无源互调预设值、无源互调检测电路(D)中高速模数转换器的最小采样功率、链路噪声系数、接收组件的信号衰减度、接收单元(C)的射频输入口到接收组件这段链路的增益确定；所述无源互调检测电路(D)的接收信号功率的最大值大于n，所述n＝该装置实际对应的通信标准所规定的最大接收信号功率+接收单元(C)的射频输入口到接收组件这段链路的增益-接收组件的信号衰减度。
  13. 根据权利要求5所述的自适应抵消无源互调信号的装置，其特征在于：所述数字处理单元(E)通过多路数模转换器与抵消器电路(B)连接，将幅度、相位的控制量传递给抵消器电路(B)，所述抵消器电路(B)的幅度调整精度和相位调整精度的要求主要来源于无源互调信号抵消能力需求；
    所述数字处理单元(E)与无源互调检测电路(D)之间至少存在两个接口：一个接口用于获取无源互调检测电路(D)中高速模数转换器的采样信号，从而进行无源互调信号的数字滤波和幅度计算；另一个接口的用于通过总线配置无源互调检测电路(D)的参数，所述总线包括I2C总线、SPI总线；
    当所述数字处理单元(E)获取所述发射信号频率信息和接收信号频率信息的方法是利用发射信号鉴频电路(E1)时，则发射信号鉴频电路(E1)的射频端口与所述发射电路单元(F)中发射链路上的某处连接，发射信号鉴频电路(E1)通过高速模数转换器与所述数字处理单元(E)连接；同时数字处理单元(E)与发射信号鉴频电路(E1)之间还有一个接口，用于通过总线配置发射信号鉴频电路(E1)的参数；
    所述数字处理单元(E)具备至少一个信息交互接口，其作用包含程序下载，配置信 息输入，远程告警和维护；其中需要输入的配置信息包括本装置发射信号带宽和频段、接收信号带宽和频段、无源互调信号中的主要干扰分量的阶次和频段信息、无源互调信号预设值以及随时间变化的曲线、最大抵消次数；所述数字处理单元(E)可以通过信息交互接口获取发射信号频率信息和接收信号频率信息；所述的信息交互接口还可以与互联网后台资源进行数据交互：上传所述设备运行过程中的无源互调值，无源互调值随时间变化的经验曲线，以及无源互调信号自适应抵消装置中各模块电路的状态信息；或者下载综合优化后的无源互调信号预设值以及随时间变化的曲线；
    所述数字处理单元(E)至少包含具备数字信号处理功能的逻辑处理与运算处理器件，用于数字信号的接收、算法处理、数字信号的输出、控制和配置信号的输出等，所述逻辑处理与运算处理器件包含但不限于现场可编程门阵列器件，中央处理器，数字信号处理器；所述数字处理单元(E)的信息交互接口的硬件构成包括但不限于以太网接口、光纤接口、RS-485总线接口；所述数字处理单元(E)中的数模转换器的位数范围在10～18位之间，且至少有3个数模转换器。
  14. 根据权利要求1所述的自适应抵消无源互调信号的装置，其特征在于，所述抵消器电路(B)包括调幅调相器(B1)和互调信号发生器(B2)，所述调幅调相器(B1)包括调幅电路(1a)和调相电路(2a)，所述调幅调相器(B1)一端与耦合器(A)的耦合端口直接或通过一个射频开关(B3)连接，另一端与互调信号发生器(B2)连接。
  15. 根据权利要求14所述的自适应抵消无源互调信号的装置，其特征在于，所述调幅电路(1a)由可调控衰减器和固定衰减器构成；调相电路(2a)至少包含2个可调控移相器；所述抵消器电路(B)中调幅调相器(B1)的承载功率大于等于所述抵消器电路(B)的承载功率门限值，所述调幅调相器(B1)的工作频段包含所述双工器(A0)的发射频段和接收频段，调幅调相器(B1)的频带内增益波动与发射频段、接收频段相关且需在一定的门限值范围内。
  16. 根据权利要求1所述的自适应抵消无源互调信号的装置，其特征在于，所述抵消器电路(B)包括调幅调相器(B1)、互调信号发生器(B2)、第二调幅电路(3)、第一环行器(4)和第二环行器(5)，所述调幅调相器(B1)包括第一调幅电路(1b)和调相电路(2b)，所述调幅调相器(B1)和第二调幅电路(3)的一端均连接第一环行器(4)，所述调幅调相器(B1)和第二调幅电路(3)的另一端均通过第二环行器(5)与互调信号发生器(B2)连接，所述第一环行器(4)与耦合器(A)的耦合端口直接或通过一个射频开关(B3)连接。
  17. 根据权利要求16所述的自适应抵消无源互调信号的装置，其特征在于：所述第二调幅电路(3)用于使互调信号发生器(B2)承受一个合适功率的射频信号；所述调幅调相器(B1)用于将互调信号发生器(B2)产生的互调信号进行调幅、调相处理；所述第一调幅电路(1b)至少包含1个可调控衰减器；所述调相电路(2b)至少包含2个可调控移相器；所述第二调幅电路(3)由固定衰减器或可调控衰减器构成；所述第一环行器(4)和第二环行器(5)的频率带宽包括所述双工器(A0)的发射频段和接收频段；所述调幅调相器(B1)的工作频段包含所述双工器(A0)的接收频段，调幅调相器(B1)的频带内增益波动与接收频段相关且需在一定的门限值范围内；所述抵消器电路(B)中第二调幅电路(3)的承载功率大于等于所述抵消器电路(B)的承载功率门限值；
    所述互调信号发生器(B2)包含并联的单个二极管、单个三极管或多个二极管；二极管具体型号或者三极管具体型号与产生互调信号3阶、5阶或更高阶互调信号的幅值特性和相位特性相关；所述互调信号发生器(B2)的承载功率大于等于所述抵消器电路(B)承载功率门限值与从抵消器电路(B)射频输入口到互调信号发生器(B2)的链路损耗的差值。
  18. 根据权利要求1所述的自适应抵消无源互调信号的装置，其特征在于：所述无源互调检测电路(D)至少包括下变频模块和高速模数转换器，所述无源互调检测电路(D)通过高速模数转换器与所述数字处理单元(E)连接；
    所述下变频模块可以将接收的射频信号转换成中频信号，或者将接收的射频信号转换成零中频信号；
    所述高速模数转换器的采样动态范围需大于接收信号的最大功率值和无源互调预设值对应的功率值之间的差值；
    所述无源互调检测电路(D)能够采样的最小功率小于等于预设值对应的无源互调功率值，同时该电路可以根据所接收的射频信号总功率的幅值调整链路增益，所述无源互调检测电路(D)获取的射频信号中包含接收信号和无源互调信号落入接收频段的分量。
  19. 根据权利要求1所述的自适应抵消无源互调信号的装置，其特征在于：所述无源互调检测电路(D)包括本振(D4)和依次连接在其射频输入端口和数字采样信号输出端口之间的低噪声放大器(D1)、射频滤波及小信号放大单元(D2)、混频器(D3)、中频滤波器(D5)、中频放大器(D6)和模数转换器(D7)，所述本振(D4)的输出端与混频器(D3)连接。
  20. 根据权利要求1所述的自适应抵消无源互调信号的装置，其特征在于：所述无源互调检测电路(D)包括依次连接在其射频输入端口和数字采样信号输出端口之间的低噪声放大器(D1)、射频滤波及小信号放大单元(D2)和下变频及模数转换单元(D8)。
  21. 一种模拟无线收发设备，其特征在于：包括如上述权利要求1-20所述的自适应抵消无源互调信号的装置，所述自适应抵消无源互调信号的装置的双工器(A0)即是无线收发设备的双工器(A0)；所述自适应抵消无源互调信号的装置的接收单元(C)复用模拟无线收发设备的接收链路的组件或单元；所述自适应抵消无源互调信号的装置的无源互调检测电路(D)在所述模拟无线收发设备内新增；所述自适应抵消无源互调信号的装置的发射电路单元(F)复用模拟无线收发设备的发射链路的组件或单元；所述自适应抵消无源互调信号的装置的数字处理单元(E)复用模拟无线收发设备的数字处理单元的组件或单元，或者在所述模拟无线收发设备内新增数字处理单元(E)，所述自适应抵消无源互调信号的装置数字处理单元(E)集成于模拟无线收发设备的整机程序中；所述自适应抵消无源互调信号的装置的耦合器(A)在所述模拟无线收发设备内新增，且其一个主通路端口和模拟无线收发设备的双工器(A0)天线口连接且距离需控制在0到1米范围内，耦合器(A)的耦合端口相对于所述模拟无线收发设备发射信号为正向耦合端口；所述自适应抵消无源互调信号的装置的抵消器电路(B)在所述模拟无线收发设备内新增，且其射频端口和耦合器(A)的耦合端口直接连接；所述自适应抵消无源互调信号的装置的天馈组件(A2)和天线(A1)即为所述模拟无线收发设备的天线链路上的对应组件和天线；
    当模拟无线收发设备有多个收发链路时，所述每一收发链路中双工器的每个天线口后 均紧邻一个耦合器(A)，以及抵消器电路(B)。
  22. 一种塔顶放大装置，其特征在于：包括如上述权利要求1-20所述的自适应抵消无源互调信号的装置，自适应抵消无源互调信号的装置的双工器(A0)即为塔顶放大装置的双工器(A0)；自适应抵消无源互调信号的装置的接收单元(C)复用塔顶放大装置的接收单元(C)，自适应抵消无源互调信号的装置的无源互调检测电路(D)需在所述塔顶放大装置内新增，自适应抵消无源互调信号的装置的发射电路单元(F)复用塔顶放大装置的发射电路单元(F)，所述发射电路单元(F)由鉴频耦合器(F1)以及双工器(A0)发射端口和收发模块(G)之间的电缆构成，其中鉴频耦合器(F1)的耦合端口和发射信号鉴频电路(E1)的射频输入端口连接，鉴频耦合器(F1)相对于发射信号为正向耦合端口，鉴频耦合器(F1)的一个主通路端口连接双工器(A0)发射端口，另一个主通路端口连接收发模块(G)的发射端口；自适应抵消无源互调信号的装置的数字处理单元(E)复用塔顶放大装置的数字处理单元(E)，自适应抵消无源互调信号的装置的耦合器(A)需在所述塔顶放大装置内新增，所述耦合器(A)的一个主通路端口和无线收发设备的双工器(A0)的天线口直接连接，耦合器(A)的耦合端口相对于所述塔顶放大装置的发射信号为正向耦合端口；自适应抵消无源互调信号的装置的抵消器电路(B)需在所述塔顶放大装置内新增，所述抵消器电路(B)的射频端口和耦合器(A)的耦合端口直接连接，自适应抵消无源互调信号的装置的天馈组件(A2)和天线(A1)即为所述塔顶放大装置的天线链路上的对应组件和天线。
  23. 一种自适应抵消无源互调信号的方法，其特征在于，包括以下步骤：
    S1：获取发射信号带宽和频段、接收信号带宽和频段、无源互调信号中的主要干扰分量的阶次和频段信息、期望的无源互调预设值以及随时间变化的曲线、幅度和相位的初始经验数据、最大抵消次数信息，并转换成相应的配置参数；
    S2：依据步骤S1中有关发射信号的配置参数求得无源互调信号的频点，并转换成相应数字滤波参数存储入参量配置表中；
    S3：依据步骤S1中有关接收信号、无源互调信号的配置参数以及由步骤S2中获取的无源互调信号的数字滤波参数，对采样信号进行数字滤波，滤除除无源互调信号以外的其他信号分量，求得落入到接收频段的无源互调信号的幅度值；
    S4：判断当前工作状态；所述工作状态的状态标识默认值是：“初始工作模式”；如果工作状态的状态标识值是“初始工作模式”则继续步骤S5-1，否则继续步骤S5-2；
    S5-1：将步骤S3获取的无源互调信号幅度值与步骤S1中的无源互调预设值进行对比，以判断无源互调信号幅度是否小于等于的无源互调预设值；
    S6：如果步骤S5-1的判断结果为“是”，则保持互调信号发生器与耦合器(A)之间链路高隔离度状态；并返回步骤S2；
    S7：如果步骤S5-1的判断结果为“否”，则)切换到互调信号发生器与耦合器(A)之间链路低隔离度状态；且将工作状态的状态标识值并设置为“抵消工作状态”；继续执行步骤S8；
    S5-2：将步骤S3获取的无源互调信号幅度值与步骤S1中的无源互调预设值进行对比，以判断无源互调信号幅度是否小于等于的无源互调预设值；如果步骤S5-2的判断结果为“是”，则保持状态，并返回步骤S2；如果步骤S5-2的判断结果为“否”，则执行步骤S8；
    S8：依据步骤S3的无源互调信号的幅度值推算抵消器电路的幅度、相位调整值；并配送给抵消器电路中的调幅器、调相器，实施抵消；在完成当前一轮抵消处理后，将继续回到步骤S2继续下一轮的抵消处理。
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