WO2019129291A1 - 一种提高反激式谐振开关电源ccm模式转换效率的方法 - Google Patents

一种提高反激式谐振开关电源ccm模式转换效率的方法 Download PDF

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Publication number
WO2019129291A1
WO2019129291A1 PCT/CN2018/125730 CN2018125730W WO2019129291A1 WO 2019129291 A1 WO2019129291 A1 WO 2019129291A1 CN 2018125730 W CN2018125730 W CN 2018125730W WO 2019129291 A1 WO2019129291 A1 WO 2019129291A1
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Prior art keywords
signal
state
output
time
mos transistor
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PCT/CN2018/125730
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English (en)
French (fr)
Inventor
孙伟锋
陶蓉蓉
王浩
肖金玉
苏巍
徐申
时龙兴
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Southeast University
CSMC Technologies Fab2 Co Ltd
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Southeast University
CSMC Technologies Fab2 Co Ltd
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Priority to US16/959,001 priority Critical patent/US11323039B2/en
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    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03K—PULSE TECHNIQUE
    • H03K5/00—Manipulating of pulses not covered by one of the other main groups of this subclass
    • H03K5/22—Circuits having more than one input and one output for comparing pulses or pulse trains with each other according to input signal characteristics, e.g. slope, integral
    • H03K5/24—Circuits having more than one input and one output for comparing pulses or pulse trains with each other according to input signal characteristics, e.g. slope, integral the characteristic being amplitude
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/22—Conversion of DC power input into DC power output with intermediate conversion into AC
    • H02M3/24—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters
    • H02M3/28—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC
    • H02M3/325—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33507—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters
    • H02M3/33523—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters with galvanic isolation between input and output of both the power stage and the feedback loop
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/22—Conversion of DC power input into DC power output with intermediate conversion into AC
    • H02M3/24—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters
    • H02M3/28—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC
    • H02M3/325—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H02M3/33576—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0003—Details of control, feedback or regulation circuits
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0003—Details of control, feedback or regulation circuits
    • H02M1/0009—Devices or circuits for detecting current in a converter
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0003—Details of control, feedback or regulation circuits
    • H02M1/0025—Arrangements for modifying reference values, feedback values or error values in the control loop of a converter
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0048—Circuits or arrangements for reducing losses
    • H02M1/0054—Transistor switching losses
    • H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/22—Conversion of DC power input into DC power output with intermediate conversion into AC
    • H02M3/24—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters
    • H02M3/28—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC
    • H02M3/325—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33507—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters
    • H02M3/33515—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters with digital control
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/22—Conversion of DC power input into DC power output with intermediate conversion into AC
    • H02M3/24—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters
    • H02M3/28—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC
    • H02M3/325—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H02M3/33576—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
    • H02M3/33592—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer having a synchronous rectifier circuit or a synchronous freewheeling circuit at the secondary side of an isolation transformer
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Definitions

  • the present invention relates to the field of switching power supplies, and in particular, to a method for improving the conversion efficiency of a CCM (Continuous Conduction Mode) mode of a flyback resonant switching power supply, a resonant switching power supply control method, and a control system thereof.
  • CCM Continuous Conduction Mode
  • Switching power supplies have been moving in the direction of miniaturization, high frequency, modularization, and light weight. As the operating frequency of switching power supplies continues to rise, switching losses due to increased switching frequency have become a serious problem. Therefore, in the design of the switching power supply, it is necessary to carefully analyze and deal with the switching loss problem.
  • the switching device In the resonant soft-switching circuit, the switching device can be switched between turn-on and turn-off under zero voltage or zero current under ideal conditions, and the switching loss is zero.
  • ZCS Zero Current Switching
  • ZVS Zero Voltage Switching
  • the present application proposes a method for improving the conversion efficiency of a flyback resonant switching power supply CCM mode, a resonant switching power supply control method and a control system thereof, which are accurate in a CCM mode flyback resonant switching power supply.
  • ZCS zero current turn-off
  • quasi-ZVS zero voltage turn-on
  • a method for improving the conversion efficiency of a flyback resonant switching power supply CCM mode, based on a control system of a soft switching flyback resonant circuit comprising: a current detecting module, a state detecting module, a PWM (Pulse Width Modulation) module, and an output
  • the feedback module and the control system formed by the drive module are connected with the controlled switching power supply to form a closed loop.
  • the control system controls the switching power supply in a soft start state or an ON-OFF state based on the ON-OFF control method, wherein:
  • the current detection module is used to collect the basic parameters of the constant voltage algorithm, including a comparator COMP1 and a D flip-flop D1.
  • the positive terminal of the comparator COMP1 is connected to the primary side sampling resistor voltage Vs, the negative terminal is grounded, and the comparator COMP1 outputs the signal VCOMP1.
  • Connect the D input terminal of the D flip-flop D1 the clock terminal of the D flip-flop D1 is connected to the clock signal CLK, as the operating clock CK of the system, the output terminal Q of the D flip-flop D1 outputs the signal VCOMP1', and the comparison signals VCOMP1 and VCOMP1' are both output.
  • the state detecting module is configured to determine whether the operating state of the control system is a soft start state or an ON-OFF state, and includes a counter Counter1 and a D flip-flop D2.
  • the input signal of the state detecting module is a comparison signal VCOMP1, VCOMP1' output by the current detecting module.
  • the input terminal D of the D flip-flop D2 is connected to the switch control signal duty outputted by the drive module, the clock input CLK signal is used as the operating clock CK of the system, and the output terminal Q of the D flip-flop D2 outputs the signal dutyy current detection module output.
  • the comparison signal VCOMP1, VCOMP1' and the switch control signal duty outputted by the driving module and the output signal duty of the D flip-flop D2 are both input signals of the counter Counter1, and the counter Counter1 outputs the working state signal State;
  • the output feedback module is configured to control the ripple of the output voltage Vo of the switching power supply in the ON-OFF state, and the input signal of the output feedback module is the secondary output voltage Vo and the working state signal State output by the state detecting module, including two comparators. COMP2 and COMP3 and an SR latch latch1, the comparator COMP2 compares the output voltage Vo with the output voltage upper limit Vmax, and the output VCOMP2 is connected to the R terminal of the SR latch latch1; the comparator COMP3 sets the output voltage lower limit Vmin and the output voltage Vo.
  • the comparison output VCOMP3 is connected to the S terminal of the SR latch latch1, the positive terminal of the comparator COMP2 is connected to Vo, the negative terminal is connected to the output voltage upper limit Vmax, the output is VCOMP2, the positive terminal of the comparator COMP3 is connected to the output voltage lower limit Vmin, and the negative terminal is connected.
  • Vo the output is VCOMP3, the Q terminal output signal of the SR latch latch1 and the state control signal State are two input signals of the AND gate and1, and the output of the AND gate is the ON-OFF enable signal Enable_ON-OFF output to the drive.
  • Module and PWM module are two input signals of the AND gate and1, and the output of the AND gate is the ON-OFF enable signal Enable_ON-OFF output to the drive.
  • the PWM module is used to control the on-time and off-time of the MOS transistor of the switching power supply, accurately realize the zero-current ZCS turn-off of the primary MOS transistor and the quasi-zero voltage ZVS turn-on, maximizing the switching loss of the primary MOS transistor;
  • PWM module The input signal is the ON-OFF enable signal Enable_ON-OFF outputted by the output feedback module, the operating state signal State output by the state detecting module, the comparison signals VCOMP1, VCOMP1' output by the current detecting module, and the switch control signal duty outputted by the driving module
  • the output signal of the PWM module is a MOS transistor turn-off signal Flag_off and a MOS transistor turn-on signal Flag_on input to the driving module, so as to realize modulation of the switch control signal duty according to two different working states of soft start and ON-OFF;
  • the input of the driving module is the MOS transistor turn-off signal Flag_off and the MOS transistor turn-on signal Flag_on outputted by the PWM module, the working state signal State outputted by the state detecting module, and the ON-OFF enable signal Enable_ON-OFF outputted by the output feedback module, and the driving module outputs
  • the modulated duty cycle switch control signal duty is used to control the turn-on and turn-off of the switching power supply power tube to improve the efficiency of the switching power supply.
  • a resonant switching power supply control method includes:
  • Sampling sampling the primary side resistance voltage of the switching power supply and processing to generate a first signal
  • State detection acquiring the first signal and the switch control signal and determining an operating state of the switching power supply, wherein the working state is a soft start state or a switch switching state;
  • Switching control preset threshold Tset, when the working state is the switch switching state, execute:
  • a first shutdown control acquiring the first signal and the switch control signal, and calculating a time interval Ttap between the zero points of the adjacent primary currents of the switching power supply during the current opening time, and outputting at the zero point a regulation signal and the first regulation signal is a shutdown signal;
  • First opening control comparing the time interval Ttap with a preset threshold Tset, when Ttap>Tset, controlling the current off time to be less than the off time of the previous cycle, outputting the first regulation signal and the first
  • the control signal is an on signal.
  • Driving output generating the switch control signal according to the first regulation signal, when the first regulation signal is an on signal, the switch control signal is an on signal, and when the first regulation signal is a shutdown signal, The switch control signal is a turn-off signal.
  • a resonant switching power supply control system includes:
  • a current detecting module configured to sample a primary side sampling resistance voltage of the switching power supply, and process the primary side sampling resistance voltage to output a first signal
  • a state detecting module is connected to the current detecting module to acquire the first signal, is connected to the driving module to obtain a switch control signal, and is used to determine an operating state of the switching power source, and generate a working state signal, where the working state signal Is a soft start status signal or an ON-OFF status signal;
  • a PWM module configured to be connected to the current detecting module to acquire the first signal, and connected to the state detecting module to obtain the working state signal, where the PWM module is configured to acquire a preset on time and a threshold Tset, And when the working state signal is an ON-OFF state signal, performing a first shutdown control and a first opening control, wherein
  • the first turn-off control includes: acquiring the first signal and the switch control signal, and calculating a time interval Ttap between the zero points of the adjacent primary currents of the switching power supply during the current turn-on time, at and at the zero point Outputting a first control signal and the first control signal is a turn-off signal;
  • the first turn-on control includes: comparing the time interval Ttap with a preset threshold Tset, and when Ttap>Tset, controlling the current off time to be less than the off time of the previous cycle, outputting the first control signal and The first control signal is an on signal.
  • a driving module connected to the PWM module to acquire the first control signal, and generate the switch control signal, when the first control signal is an open signal, the switch control signal is an open signal, when the first When a regulation signal is a shutdown signal, the switch control signal is a shutdown signal.
  • FIG. 1 is a flow chart showing the steps of a method for controlling a resonant switch according to an embodiment of the present application
  • FIG. 2 is a block diagram showing the system structure of a resonant switching power supply control system according to an embodiment of the present application
  • FIG. 3 is a structural block diagram of a current detecting module according to an embodiment of the present application.
  • 4a is a flow chart of state detection in an embodiment of the present application.
  • 4b is a structural diagram of a state detection module according to an embodiment of the present application.
  • 5a is a structural block diagram of an output feedback module according to an embodiment of the present application.
  • FIG. 5b is a flow chart of ripple adjustment according to an embodiment of the present application.
  • 6a is a flowchart of a soft start state algorithm of a PWM module according to an embodiment of the present application
  • 6b is a flowchart of an algorithm in an ON-OFF state according to an embodiment of the present application.
  • 6c is a waveform diagram of an ON-OFF state in an embodiment of the present application.
  • 6d is a waveform diagram of an ON-OFF state in an embodiment of the present application.
  • FIG. 7a is a structural block diagram of a driving module according to an embodiment of the present application.
  • 7b is a flow chart of driving output according to an embodiment of the present application.
  • FIG. 8 is a structural diagram of a closed loop circuit of a CCM mode flyback resonant switching power supply according to an embodiment of the present application.
  • the resonant switching power supply control method includes the following steps.
  • Step S100 sampling the primary side resistance voltage of the switching power supply and processing to generate a first signal.
  • a current detecting module is connected to the primary side of the switching power supply to sample and process the primary side resistance voltage of the switching power supply.
  • a comparator COMP1 and a D flip-flop D1 can be arranged in the current detecting module.
  • the positive input end of the comparator COMP1 is connected with the switching power supply to obtain the primary side sampling resistance voltage Vs of the switching power supply, and the negative input terminal is connected to the ground, and the output signal is The signal VCOMP1, when the primary current IL changes from a positive value to a negative value, the signal VCOMP1 output by the comparator COMP1 changes from 1 to 0; the input signal of the D input terminal of the D flip-flop D1 is VCOMP1, and the input clock signal CLK is The control circuit operates the clock CK, the output signal of the output terminal Q is the signal VCOMP1', and the first signal includes the signal VCOMP1 and the signal VCOMP1'.
  • Step S200 Acquire a first signal and a switch control signal and determine an operating state of the switching power supply, and the working state is a soft start state or an ON-OFF state.
  • the switching power supply has a zero point in the ON time of the continuous n switching cycles, and when there is a zero point, the working state is an ON-OFF state, when not If there is a zero point, the working state is a soft start state, wherein 5 ⁇ n ⁇ 20.
  • the switching power supply includes an ON-OFF state and a soft-start state.
  • the switching power supply includes a MOS transistor, and the switching power supply is turned on and off by controlling the opening and closing of the MOS transistor, the first signal And the switch control signals are level signals.
  • the primary current of the switching power supply has a negative value, that is, there is a zero point, and whether it appears in the opening time of the n switching cycles
  • the switching power supply has a zero point in the ON time of the continuous n switching cycles, and the working state is an ON-OFF state.
  • Step S300 Switching control: preset threshold value Tset, when the working state is ON-OFF state, execute:
  • the first turn-off control acquiring the first signal and the switch control signal, calculating a time interval Ttap between the zero points of the adjacent primary currents of the switching power supply during the current turn-on time, and outputting the first control signal at the zero point and first
  • the control signal is a shutdown signal;
  • the first turn-on control the comparison time interval Ttap and the preset threshold Tset, when Ttap>Tset, the current off time is controlled to be less than the off time of the previous cycle, and the first control signal is output and the first A control signal is an on signal.
  • the preset on-time and the threshold Ttap threshold Tset are executed.
  • the first shutdown control is performed: acquiring the first signal and the switch control signal, and calculating the switching power supply.
  • the signal and the first control signal is a shutdown signal; and the first turn-on control: obtaining the first signal and the switch control signal, calculating the number of zeros of the primary current of the switching power supply during the current off time, and the comparison time interval Ttap
  • counter Counter2, counter Counter3, counter Counter4 and a time counting unit are provided.
  • the first control signal includes an enable signal Flag_on and a turn-off signal Flag_off.
  • the signal Flag_on is turned on, and the signal Flag_off is turned off.
  • the first control signal is an on signal
  • the control system is set to soft start, and when the first regulation signal is the shutdown signal, the shutdown signal Flag_off is set.
  • Figure 6c shows a small Ttap case.
  • the MOS transistor turn-off signal Flag_off 1, zero current shutdown, and the MOS transistor at the 4th zero point of the primary current after the MOS transistor is turned off.
  • the MOS transistor turn-on signal Flag_on is set to 1, and the primary current is pulled down as a whole during the next duty cycle, so that the next duty cycle circuit works.
  • 6d illustrates the case where the drain-source voltage Vds of the MOS transistor is turned on at the second valley and switched on at the first valley.
  • the PWM module outputs the MOS tube off signal Flag_off and the off MOS tube on signal Flag_on to the driving module to implement control of the switching tube duty cycle signal duty.
  • Step S400 Generate a switch control signal according to the first control signal.
  • the switch control signal is an open signal
  • the switch control signal is a closed signal
  • the switch control signal is a turn-off signal.
  • the method further includes ripple adjustment: a preset output voltage upper limit Vmax and an output voltage lower limit Vmin, and an output voltage Vo of the switching power supply is obtained, and when the working state is an ON-OFF state, the output voltage Vo and the output are compared.
  • Vo>Vmax the second control signal is a turn-off signal
  • Vo ⁇ Vmin the second control signal is an open signal.
  • the second regulation signal needs to be acquired, and when the second regulation signal is the on signal, the first shutdown control is performed.
  • the second control signal is an enable signal Enable_ON-OFF.
  • the method for improving the conversion efficiency of a flyback resonant switching power supply in a CCM mode is based on a control system comprising a current detecting module, a state detecting module, an output feedback module, a PWM module and a driving module, the control system and the controlled switching power supply Connected to form a closed loop.
  • the utility model has the advantages of accurately implementing the zero current or zero voltage switching of the switch tube, effectively reducing the power switch loss, improving the power supply efficiency, and effectively stabilizing the output voltage in a certain ripple range, thereby realizing effective control of the output voltage, and at the same time,
  • the solution can be applied to isolated or non-isolated switching power supply circuit structures with versatility, reusability and portability. Repeat the above process to cycle control of the switching power supply power tube on and off to make the system more stable, thus achieving higher efficiency.
  • the application also relates to a resonant switching power supply control system, as shown in FIG. 2, the system includes a current detecting module, a state detecting module, a PWM module and a driving module, wherein:
  • the current detecting module is configured to sample the primary side sampling resistance voltage of the switching power supply, and process the primary side sampling resistance voltage to output a first signal.
  • the current detecting module includes a comparator COMP1 and a D flip-flop D1.
  • the positive input terminal of the comparator COMP1 is connected to the switching power supply to obtain the primary side sampling resistance voltage Vs of the switching power supply, and the negative input terminal is connected. Ground, the output signal is the signal VCOMP1.
  • the signal VCOMP1 output by the comparator COMP1 changes from 1 to 0;
  • the input signal of the D input of the D flip-flop D1 is VCOMP1
  • the input clock signal CLK is the control circuit operating clock CK
  • the output signal of the output terminal Q is the signal VCOMP1'
  • the first signal includes the signal VCOMP1 and the signal VCOMP1'.
  • the state detecting module is connected with the current detecting module to obtain the first signal, is connected with the driving module to obtain the switch control signal, and is used for determining the working state of the switching power source, generating a working state signal, and the working state signal is a soft start state signal or ON- OFF status signal.
  • the state detecting module includes a counter Counter1 and a D flip-flop D2.
  • the D input terminal of the D flip-flop D2 is connected to the output end of the driving module to obtain the output of the driving module.
  • the switch control signal duty, the output signal of the D flip-flop D2 is duty '
  • the input end of the counter Counter1 is connected with the output end of the D flip-flop D2 to obtain the output signal duty '
  • the output of the counter Counter1 is also respectively connected with the driving module.
  • the switch control signal duty and the current detection module output signals VCOMP1 and VCOMP1' satisfy the logical relationship:
  • the switching power supply includes a MOS tube (Metal-Oxide-Semiconductor Field-Effect Transistor, metal oxide semiconductor field) The effect tube) realizes the on and off of the switching power supply by controlling the on and off of the MOS tube.
  • MOS tube Metal-Oxide-Semiconductor Field-Effect Transistor, metal oxide semiconductor field
  • the primary current has a zero crossing
  • the circuit has been stable, can enter the ON-OFF state, so here through a D trigger D2 introduces a temporary variable counter_Temp with an initial value of 0 to determine whether counter1 is increased in a continuous period.
  • the D input of D flip-flop D2 is connected to the switch control signal duty, and the input clock signal CLK is the operating clock of the control circuit.
  • the output signal of the CK, Q output is duty'.
  • the circuit structure is shown in Figure 4b, and the counter1 part is implemented by the algorithm.
  • the primary current IL is always greater than 0 in the conduction phase. As the switching time increases, the primary current IL is stable. Negative current indicates that the system has stabilized and can enter the ON-OFF state.
  • the PWM module is connected to the current detecting module to obtain the first signal, and is connected to the state detecting module to obtain the working state signal, and the PWM module is configured to acquire the preset on-time and the threshold Tset, and the working state signal is ON-OFF state.
  • the first turn-off control includes acquiring the first signal and the switch control signal, and calculating the adjacent primary side of the switching power supply during a current turn-on time a time interval Ttap between the zero points of the current, and outputting the first control signal at the zero point and the first control signal is a turn-off signal, specifically, calculating that the switching power supply is currently turned on according to the first signal and the switch control signal The number of zeros of the primary current in the time counter2, and the time interval Ttap between the adjacent zeros are calculated.
  • the first control signal is output and
  • the first regulation signal is a shutdown signal;
  • the first opening control includes comparing the time interval Ttap with a preset threshold Tset, and when Ttap>Tset, controlling the current shutdown The time is less than the off time of the previous cycle, the first regulation signal is output and the first regulation signal is an on signal.
  • the first control signal and the first control signal are an on signal.
  • the first control signal is an open signal, and specifically, according to the first signal and the switch control signal, calculate the number of zeros of the primary current of the switching power supply during the current off time, and the comparison time interval Ttap and the preset threshold.
  • the PWM module includes a counter Counter2, a counter Counter3, a counter Counter4, and a time counting unit.
  • the driving module is connected with the PWM module to obtain the first control signal, and generates a switch control signal.
  • the switch control signal is an open signal
  • the switch control signal is Turn off the signal.
  • the system further includes: an output feedback module: connected to the state detecting module to obtain an operating state signal, and configured to obtain an output voltage upper limit Vmax and an output voltage lower limit Vmin and a switching power supply output voltage Vo when the working state
  • the output voltage Vo is compared with the preset output voltage upper limit Vmax and the preset output voltage lower limit Vmin, and the second control signal is output.
  • Vo>Vmax the second control signal is a shutdown signal.
  • Vo ⁇ Vmin the second regulation signal is an on signal.
  • the output feedback module includes two comparators COMP2 and COMP3 and an SR latch latch1.
  • the positive input terminal of COMP2 is connected with the switching power supply to obtain the output voltage Vo of the switching power supply, and the negative input terminal is connected to the upper limit of the output voltage of the switching power supply Vmax.
  • the positive input terminal of COMP3 is connected to the output voltage lower limit Vmin of the switching power supply, and the negative input terminal is connected with the switching power supply to obtain the output voltage of the switching power supply Vo.
  • the workflow is roughly as shown in Figure 5b.
  • the output feedback module outputs an ON-OFF enable signal Enable_ON-OFF to the drive module and the PWM module.
  • the driving module includes an SR latch latch2, an AND gate and an AND gate, an inverter inverter1, and an inverter inverter2, and an S input terminal of the SR latch latch2.
  • the in-pass signal Flag_on the R input of the SR latch latch2 is connected to the off signal Flag_off, the output of the SR latch latch2 is connected to the input of the AND gate and the input of the inverter inverter1 is enabled.
  • the signal Enable_ON-OFF, the input of the AND gate and the third is connected to the working state signal State and is connected to the output of the inverter inverter1, and the inverter inverter2 is connected between the input of the AND gate and the output of the AND gate and 3.

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Abstract

一种高反激式谐振开关电源CCM模式转换效率的方法，包括：预设临界值Tset，计算当前开通时间内相邻零点之间的时间间距Ttap，在零点输出关断信号，并比对时间间隔Ttap与预设临界值Tset，当Ttap>Tset，控制当前关断时间小于前一周期的关断时间，输出开启信号，当Ttap＝0，则控制当前关断之间大于前一周期的关断时间，输出开启信号，当0<Ttap<＝Tset，控制当前关断时间与前一开关周期的关断时间相同，输出开启信号。

Description

一种提高反激式谐振开关电源CCM模式转换效率的方法 技术领域
本申请涉及开关电源领域，尤其涉及一种提高反激式谐振开关电源CCM(Continuous Conduction Mode，连续导通模式)模式转换效率的方法、谐振开关电源控制方法及其控制系统。
背景技术
开关电源一直朝着小型化、高频化、模块化、轻量化的方向发展。随着开关电源工作频率的不断上升，由于开关频率增大造成的开关损耗逐渐成为了一个严重的问题。因此，在开关电源的设计中，而需要仔细分析和处理开关损耗问题。
在谐振软开关电路中，理想状态下开关器件可以实现在零电压或零电流条件下进行开通与关断的切换，开关损耗为零。而在准谐振开关电源电路中，如何精确实现开关器件的ZCS(Zero Current Switching，零电流关断)或者准ZVS(Zero Voltage Switching，零电压开启)，最大化降低开关损耗，便是设计的难点所在。
发明内容
为克服传统技术的局限和不足，本申请提出了一种提高反激式谐振开关电源CCM模式转换效率的方法、谐振开关电源控制方法及其控制系统，在CCM模式反激式谐振开关电源中精确实现原边MOS管的ZCS(零电流关断)以及准ZVS(零电压开启)，最大化降低原边MOS管的开关损耗，达到电源效率的提高。
一种提高反激式谐振开关电源CCM模式转换效率的方法，基于软开关反激谐振电路的控制系统，其中：包括电流检测模块、状态检测模块、PWM(Pulse Width Modulation脉冲宽度调制)模块、输出反馈模块以及驱动模块构成的控制系统与受控的开关电源连接起来构成闭环，该控制系统基于ON-OFF控制方法，在软启动状态或ON-OFF状态下对开关电源进行控制，其中：
电流检测模块用于采集实现恒压算法的基本参数，包括一个比较器COMP1和一个D触发器D1，比较器COMP1的正端连接原边采样电阻电压Vs，负端接地，比较器COMP1输出信号VCOMP1连接D触发器D1的D输入端，D触发器D1的时钟端连接时钟信号CLK，作为系统的工作时钟CK，D触发器D1的输出端Q输出信号VCOMP1’，比较信号VCOMP1和VCOMP1’均输出给状态检测模块和PWM模块；
状态检测模块用于判断控制系统的工作状态是软启动状态还是ON-OFF状态，包括一个计数器Counter1和一个D触发器D2，状态检测模块的输入信号为电流检测模块输出的比较信号VCOMP1、VCOMP1’和驱动模块输出的开关控制信号duty，状态检测模块的输出信号为输出给输出反馈模块、PWM模块和驱动模块的工作状态信号State；定义State＝0为软启动状态，State＝1为ON-OFF状态；D触发器D2的输入端D连接驱动模块输出的开关控制信号duty，时钟端输入时钟信号CLK作为系统的工作时钟CK，D触发器D2的输出端Q输出信号duty’电流检测模块输出的比较信号VCOMP1、VCOMP1’和驱动模块输出的开关控制信号duty以及D触发器D2的 输出信号duty’均作为计数器Counter1的输入信号，计数器Counter1输出工作状态信号State；
输出反馈模块用于实现ON-OFF状态下控制开关电源输出电压Vo的纹波大小，输出反馈模块的输入信号为副边输出电压Vo和状态检测模块输出的工作状态信号State，包括两个比较器COMP2和COMP3以及一个SR锁存器latch1，比较器COMP2将输出电压Vo与输出电压上限Vmax比较后输出VCOMP2连接至SR锁存器latch1的R端；比较器COMP3将输出电压下限Vmin与输出电压Vo比较输出VCOMP3连接至SR锁存器latch1的S端，比较器COMP2的正端接Vo，负端接输出电压上限Vmax，输出为VCOMP2，比较器COMP3的正端接输出电压下限Vmin，负端接Vo，输出为VCOMP3，SR锁存器latch1的Q端输出信号与状态控制信号State为一个与门and1的两个输入信号，与门的输出即为ON-OFF使能信号Enable_ON-OFF输出给驱动模块和PWM模块；
PWM模块用于控制开关电源的MOS管导通时间和关断时间，精确实现原边MOS管的零电流ZCS关断和准零电压ZVS开启，最大化降低原边MOS管的开关损耗；PWM模块的输入信号为输出反馈模块输出的ON-OFF使能信号Enable_ON-OFF、状态检测模块输出的工作状态信号State、电流检测模块输出的比较信号VCOMP1、VCOMP1’和驱动模块输出的开关控制信号duty，PWM模块的输出信号为输入到驱动模块的MOS管关断信号Flag_off和MOS管开启信号Flag_on，以实现基于软启动及ON-OFF两个不同的工作状态对开关控制信号duty进行调制；
驱动模块的输入为PWM模块输出的MOS管关断信号Flag_off和MOS管开启信号Flag_on以及状态检测模块输出的工作状态信号State和输出反馈模块输出的ON-OFF使能信号Enable_ON-OFF，驱动模块输出调制后的相应占空比开关控制信号duty，对开关电源功率管的开通和关断进行控制，实现开关电源效率的提升。
一种谐振开关电源控制方法，包括：
采样：采样所述开关电源的原边电阻电压并进行处理，生成第一信号；
状态检测：获取所述第一信号和开关控制信号并判断所述开关电源的工作状态，所述工作状态为软启动状态或开关切换状态；
切换控制：预设临界值Tset，当所述工作状态为开关切换状态时，执行：
第一关断控制：获取所述第一信号和所述开关控制信号，计算所述开关电源在当前开通时间内相邻原边电流的零点之间的时间间隔Ttap，在并在零点处输出第一调控信号且所述第一调控信号为关断信号；及
第一开通控制：比对所述时间间隔Ttap与预设临界值Tset，当Ttap>Tset，控制当前关断时间小于前一周期的关断时间，输出所述第一调控信号且所述第一调控信号为开启信号，当Ttap＝0，则控制当前关断之间大于前一周期的关断时间，输出所述第一调控信号且所述第一调控信号为开启信号，当0<Ttap<＝Tset，控制当前关断时间与前一开关周期的关断时间相同，输出所述第一调控信号且所述第一调控信号为开启信号；及
驱动输出：根据所述第一调控信号生成所述开关控制信号，当所述第一调控信号为开启信号时，所述开关控制信号为开启信号，当所述第一调控信号为关闭信号时，所述开关控制信号为关断信号。
一种谐振开关电源控制系统，包括：
电流检测模块，用于采样所述开关电源的原边采样电阻电压，并对所述原边采样电阻电压进行处理输出第一信号；
状态检测模块，与所述电流检测模块连接以获取所述第一信号，与驱动模块连接以获取开关控制信号，并用于判断所述开关电源的工作状态，生成工作状态信号，所述工作状态信号为软启动状态信号或ON-OFF状态信号；
PWM模块，与所述电流检测模块连接以获取所述第一信号，与所述状态检测模块连接以获取所述工作状态信号，所述PWM模块用于获取预设导通时间和临界值Tset，并在所述工作状态信号为ON-OFF状态信号时，执行第一关断控制和第一开启控制，其中，
所述第一关断控制包括：获取所述第一信号和所述开关控制信号，计算所述开关电源在当前开通时间内相邻原边电流的零点之间的时间间隔Ttap，在并在零点处输出第一调控信号且所述第一调控信号为关断信号；
所述第一开通控制包括：比对所述时间间隔Ttap与预设临界值Tset，当Ttap>Tset，控制当前关断时间小于前一周期的关断时间，输出所述第一调控信号且所述第一调控信号为开启信号，当Ttap＝0，则控制当前关断之间大于前一周期的关断时间，输出所述第一调控信号且所述第一调控信号为开启信号，当0<Ttap<＝Tset，控制当前关断时间与前一开关周期的关断时间相同，输出所述第一调控信号且所述第一调控信号为开启信号；及
驱动模块，与所述PWM模块连接以获取所述第一调控信号，生成所述开关控制信号，当所述第一调控信号为开启信号时，所述开关控制信号为开启信号，当所述第一调控信号为关闭信号时，所述开关控制信号为关断信号。
本申请的一个或多个实施例的细节在下面的附图和描述中提出。本申请的其他特征、目的和优点将从说明书、附图以及权利要求书变得明显。
附图说明
为了更好地描述和说明这里公开的那些发明的实施例和/或示例，可以参考一幅或多幅附图。用于描述附图的附加细节或示例不应当被认为是对所公开的发明、目前描述的实施例和/或示例以及目前理解的这些发明的最佳模式中的任何一者的范围的限制。
图1为本申请一实施例中谐振开关控制方法的步骤流程图；
图2为本申请一实施例中谐振开关电源控制系统的系统结构框图；
图3为本申请一实施例中电流检测模块的结构框图；
图4a为本申请一实施例中状态检测流程图；
图4b为本申请一实施例中状态检测模块结构图；
图5a为本申请一实施例中输出反馈模块的结构框图；
图5b为本申请一实施例中纹波调节流程图；
图6a为本申请一实施例中PWM模块软启动状态算法流程图；
图6b为本申请一实施例中ON-OFF状态时的算法流程图；
图6c为本申请一实施例中ON-OFF状态时波形图；
图6d为本申请一实施例中ON-OFF状态时波形图；
图7a为本申请一实施例中驱动模块的结构框图；
图7b为本申请一实施例中驱动输出流程图；
图8为本申请一实施例中的CCM模式反激式谐振开关电源的闭环电路结构图。
具体实施方式
在一实施例中，如图1所示，谐振开关电源控制方法包括以下步骤。
步骤S100：采样开关电源的原边电阻电压并进行处理，生成第一信号。
在一具体的实施例中，利用一电流检测模块与开关电源的原边连接以采样开关电源的原边电阻电压并进行处理。电流检测模块内可设置一个比较器COMP1以及一个D触发器D1，比较器COMP1的正输入端与开关电源连接，以获取开关电源的原边采样电阻电压Vs，负输入端连接地，输出信号为信号VCOMP1，当原边电流IL从正值变为负值时，比较器COMP1输出的信号VCOMP1则会从1变到0；D触发器D1的D输入端的输入信号为VCOMP1，输入时钟信号CLK为控制电路工作时钟CK，输出端Q的输出信号为信号VCOMP1’，第一信号包括信号VCOMP1和信号VCOMP1’。由
Figure PCTCN2018125730-appb-000001
即可判断原边电流的零点，其中，逻辑运算符
Figure PCTCN2018125730-appb-000002
表示亦或的逻辑关系。
步骤S200：获取第一信号和开关控制信号并判断开关电源的工作状态，工作状态为软启动状态或ON-OFF状态。
在一具体实施例中，根据第一信号和开关控制信号判断开关电源在连续n个开关周期的开通时间内是否均存在零点，当是均存在零点，则工作状态为ON-OFF状态，当不是均存在零点，则工作状态为软启动状态，其中，5≤n≤20。
开关电源包括ON-OFF状态和软启动状态，在一具体实施例中，开关电源包括MOS管，通过控制所述MOS管的开启和关断控制所述开关电源的开启和关断，第一信号和开关控制信号均为电平信号。获取信号VCOMP1和信号VCOMP1’以及开关控制信号duty，由于根据
Figure PCTCN2018125730-appb-000003
即可判断原边电流的零点，当开关控制信号duty和信号VCOMP1、信号VCOMP1’满足逻辑关系：
Figure PCTCN2018125730-appb-000004
时，说明在开关导通阶段，开关电源的原边电流存在负值，即存在零点，当在n个开关周期的开通时间内是否均出现
Figure PCTCN2018125730-appb-000005
Figure PCTCN2018125730-appb-000006
时，则判断所述开关电源在连续n个开关周期的开通时间内均存在零点，所述工作状态为ON-OFF状态。在一具体实施例中，判断工作状态后输出工作状态信号State，工作状态信号也为电平信号，State＝0为软启动状态，State＝1为ON-OFF状态。
步骤S300：切换控制：预设临界值Tset，当工作状态为ON-OFF状态时，执行：
第一关断控制：获取第一信号和开关控制信号，计算开关电源在当前开通时间内相邻原边电流的零点之间的时间间隔Ttap，在并在零点处输出第一调控信号且第一调控信号为关断信号；第一开通控制：比对时间间隔Ttap与预设临界值Tset，当Ttap>Tset，控制当前关断时间小于前一周期的关断时间，输出第一调控信号且第一调控信号为开启信号，当Ttap＝0，则控制当前关断之间大于前一周期的关断时间，输出第一调控信号且第一调控信号为开启信号，当0<Ttap<＝Tset，控制当前关断时间与前一开关周期的关断时间相同，输出第一调控信号且第一调控信号为开启信号。
在一实施例中，预设导通时间和临界值Ttap临界值Tset，当工作状态为ON-OFF状态时，执行：第一关断控制：获取第一信号和开关控制信号，计算开关电源在当前开通时间内原边电流的零点的个数counter2，以及计算相邻零点之间的时间间隔Ttap，在counter2＝2时，或者counter2＝0 且开通时间达到预设导通时间时，输出第一调控信号且第一调控信号为关断信号；及第一开通控制：获取第一信号和开关控制信号，计算开关电源在当前关断时间内原边电流的零点的个数counter3，以及比对时间间隔Ttap与预设临界值Tset，当Ttap>Tset，则当counter3＝2时，输出第一调控信号且第一调控信号为开启信号，当Ttap＝0，则当counter3＝4时，输出第一调控信号且第一调控信号为开启信号，当0<Ttap<＝Tset，则当counter3＝N时，输出第一调控信号且第一调控信号为开启信号，其中，N为上一开关周期中counter3的取值；重复执行第一关断控制。
在一具体实施例中，设置计数器Counter2，计数器Counter3，计数器Counter4和一个时间计数单元。时间计数单元用于计数State＝1状态下的counter2>＝1且counter2<＝2时的时间长度Ttap；计数器Counter2是用来计数MOS管导通阶段的原边电流零点个数counter2，当duty＝1，
Figure PCTCN2018125730-appb-000007
时，Counter2开始计数；当duty＝0时，Counter2清零。计数器Counter3用来计数MOS管关闭阶段的原边电流零点个数counter3，当
Figure PCTCN2018125730-appb-000008
时，计数器Counter3开始计数；当duty＝1时，计数器Counter3清零。计数器Counter4用于控制软启动状态下MOS管导通时间以及ON-OFF状态下原边电流在MOS管导通阶段恒大于零(即Ttap＝0)时的MOS管关断，当duty＝1时，计数器Counter4开始计数；当duty＝0时，Counter4清零。
在一实施例中，第一调控信号包括开启信号Flag_on，关断信号Flag_off，当第一调控信号为开启信号时，开启信号Flag_on，关断信号Flag_off，当第一调控信号为开启信号时，当控制系统处于软启动置1，当第一调控信号为关断信号时，关断信号Flag_off置1。当控制系统处于软启动状态，即State＝0，控制原边MOS管固定导通时间为Tonmax，当计数器Counter4计数到系统给定导通时间Tonmax时，MOS管关断信号Flag_off置为1并输入到驱动模块；然后由计数器Counter3计数原边MOS管关断后原边电流零点，当counter3＝4时，即对应MOS管漏源电压Vds的第二个谷底，此时将MOS管开启信号Flag_on置为1并输入到驱动模块。图6a所示即为软启动状态下PWM模块工作流程。
当控制系统处于ON-OFF状态即State＝1时，如图6b所示为ON-OFF状态下PWM模块工作流程。由计数器Counter2计数MOS管导通阶段原边电流零点达到2时或者counter2＝0，计数器Counter4计数到系统给定导通时间Tonmax时，MOS管关断信号Flag_off置为1。如图6c所示为计数器Counter2计数MOS管导通阶段原边电流零点达到2时，MOS管关断信号Flag_off置为1。对于MOS管开启信号Flag_on何时置1，首先需要讨论最佳工作点的问题：在MOS管导通阶段，由时间计算单元计算counter2>＝1且counter2<＝2时的时间长度Ttap，当Ttap较小或者原边电流在MOS管导通时刚刚大于零时，电路的开关损耗较小且返回电源的能量较小，为电路的最佳工作点，电路整体效率较高。图6c示意了Ttap较小的情况，此时counter2＝2时，MOS管关断信号Flag_off＝1，实现零电流关断，并在MOS管关断后原边电流的第4个零点将MOS管开启信号Flag_on置为1，此时对应MOS管漏源电压Vds的第二个谷底，实现准零电压开启。所以，为保证电路始终工作在最佳工作点附近，系统给定一个Ttap的临界值Tset，在ON-OFF使能信号Enable_ON-OFF＝1前提下，如图6b所示，当Ttap>Tset，说明当前工作点远离最佳工作点，则本工作周期在原边MOS管关闭后漏源电压Vds谐振时的第一个谷底处将MOS管导通，即counter3＝2时，MOS管开启信号Flag_on置为1，这样保证了准零电压开启的同时减小了MOS管关断时间，整体拉高下一工作周期原边电流，减小Ttap，使下一工作周期电路工作点靠近最佳工作点；当Ttap＝0，当前工作周期原边电流在MOS管导通阶段(此时的MOS管导通时间由Tonmax限制)恒大于零，即没有过零点，则本工作周期在原边MOS管关闭后漏源电压Vds谐 振时的第二个谷底处将MOS管导通，即counter3＝4时，MOS管开启信号Flag_on置为1，下一工作周期整体拉低原边电流，使下一工作周期电路工作点靠近最佳工作点；当0<Ttap<＝Tset，当前工作周期电路工作点较为理想，逼近最佳工作点，仍维持上一周期的工作状态，即counter3＝N时(N对应着上一工作周期的工作状态，当上一工作周期，MOS管在关闭后漏源电压Vds谐振时的第二个谷底处导通，则N＝4；当上一工作周期，MOS管在关闭后漏源电压Vds谐振时的第一个谷底处导通，则N＝2)，MOS管开启信号Flag_on置为1。图6d示意了MOS管漏源电压Vds在第二个谷底导通和在第一个谷底导通相互切换的情况。PWM模块将MOS管关断信号Flag_off以及关MOS管开启信号Flag_on输出到驱动模块，以实现对开关管占空比信号duty的控制。
步骤S400：根据第一调控信号生成开关控制信号，当第一调控信号为开启信号时，开关控制信号为开启信号，当第一调控信号为关闭信号时，开关控制信号为关断信号。
在一实施例中，该方法还包括纹波调节：预设输出电压上限Vmax和输出电压下限Vmin，获取开关电源的输出电压Vo，当工作状态为ON-OFF状态时，对比输出电压Vo、输出电压上限Vmax和输出电压下限Vmin，并输出第二调控信号，当Vo＞Vmax时，第二调控信号为关断信号，当Vo＜Vmin时，第二调控信号为开启信号。此时，在步骤S300中，需获取第二调控信号，当第二调控信号为开启信号时，执行第一关断控制。在一具体实施例中，第二调控信号为使能信号Enable_ON-OFF，当State＝0时，ON-OFF使能信号Enable_ON-OFF置零；当State＝1时，即在ON-OFF状态下，输出电压Vo超过上限Vmax，ON-OFF使能信号Enable_ON-OFF＝0，电路进入OFF状态，MOS管关断，初级绕组不会再向次级绕组传递能量，输出电压Vo开始下降，直至输出电压Vo低于下限Vmin，ON-OFF使能信号Enable_ON-OFF＝1，电路进入ON状态。如此循环将输出电压稳定在一定的纹波范围内。此时，步骤S400中，工作状态信号State＝0时，即软启动状态下，开关控制信号duty在MOS管开启信号Flag_on＝1时置1，在MOS管关断信号Flag_off＝1时duty置0。当工作状态信号State＝1，即ON-OFF状态下，ON-OFF使能信号Enable_ON-OFF＝0时，电路处于OFF状态，开关管占空比信号duty置0；ON-OFF使能信号Enable_ON-OFF＝1时，电路处于ON状态，开关控制信号duty在MOS管开启信号Flag_on＝1时置1，在MOS管关断信号Flag_off＝1时duty置0，其工作流程如图7b所示。本申请提高CCM模式下反激式谐振开关电源转换效率的方法，基于包括电流检测模块、状态检测模块、输出反馈模块、PWM模块以及驱动模块构成的控制系统，该控制系统与受控的开关电源连接起来构成一个闭环。
本申请的优点在于：精确实现开关管零电流或者零电压切换，有效减少电源开关损耗，提高电源效率，且将输出电压有效稳定在一定纹波范围，实现对输出电压的有效控制，同时，本方案能适用于隔离式或者非隔离开关电源电路结构，具备通用性，可复用性和可移植性。重复上述过程进行循环控制开关电源功率管的开通和关断，以使系统更加稳定，从而获得更高的工作效率。
本申请还涉及一种谐振开关电源控制系统，如图2所示，该系统包括电流检测模块、状态检测模块、PWM模块和驱动模块，其中：
电流检测模块，用于采样所述开关电源的原边采样电阻电压，并对所述原边采样电阻电压进行处理输出第一信号。
在一具体实施例中，电流检测模块包括一个比较器COMP1以及一个D触发器D1，比较器COMP1的正输入端与开关电源连接，以获取开关电源的原边采样电阻电压Vs，负输入端连接地，输出信号为信号VCOMP1，当原边电流IL从正值变为负值时，比较器COMP1输出的信号 VCOMP1则会从1变到0；D触发器D1的D输入端的输入信号为VCOMP1，输入时钟信号CLK为控制电路工作时钟CK，输出端Q的输出信号为信号VCOMP1’，第一信号包括信号VCOMP1和信号VCOMP1’。由
Figure PCTCN2018125730-appb-000009
即可判断原边电流的零点，其中，逻辑运算符
Figure PCTCN2018125730-appb-000010
表示亦或的逻辑关系。
状态检测模块，与电流检测模块连接以获取第一信号，与驱动模块连接以获取开关控制信号，并用于判断开关电源的工作状态，生成工作状态信号，工作状态信号为软启动状态信号或ON-OFF状态信号。
在一具体实施例中，如图4b所示，状态检测模块包括一个计数器Counter1和一个D触发器D2，D触发器D2的D输入端与驱动模块的输出端连接，以获取驱动模块的输出的开关控制信号duty，D触发器D2的输出信号为duty’，计数器Counter1的输入端与D触发器D2的输出端连接，以获取输出信号duty’，且计数器Counter1的输出端还分别与驱动模块连接以获取开关控制信号duty、与电流检测模块连接以获取信号VCOMP1和信号VCOMP1’。系统上电后，状态检测模块的初始状态为State＝0，当开关控制信号duty和电流检测模块输出信号VCOMP1、VCOMP1’满足逻辑关系：
Figure PCTCN2018125730-appb-000011
时，说明在开关导通阶段，开关电源的原边电流存在负值，计数器Counter1开始计数counter1＝counter1+1；开关电源包括MOS管(Metal-Oxide-Semiconductor Field-Effect Transistor，金属氧化物半导体场效应管)，通过控制MOS管的通断实现开关电源的导通与关断。如果在连续n(5<＝n<＝20)个开关周期MOS管导通阶段，原边电流均有过零点，则可说明电路已经稳定，可进入ON-OFF状态，所以这里通过一个D触发器D2并引入一个初始值赋为0的临时变量counter_Temp，来判断counter1是否是在连续周期内增加，D触发器D2的D输入端接入开关控制信号duty，输入时钟信号CLK为控制电路工作时钟CK，Q输出端的输出信号为duty’。其电路结构如图4b所示，counter1部分由算法实现，当duty＝0，
Figure PCTCN2018125730-appb-000012
且counter_Temp<counter1时，将计数器Counter1的值赋给counter_Temp，即counter_Temp＝counter1；当duty＝0，
Figure PCTCN2018125730-appb-000013
且counter1＝counter_Temp时，计数器Counter1和counter_Temp全部清零。当counter1达到n(5<＝n<＝20)时，即连续n(5<＝n<＝20)个开关周期MOS管导通阶段，开关电源的原边连接IL均存在负值，则判断该开关电源电路已经稳定，则状态检测模块输出的工作状态信号State＝1，即跳出软启动状态，进入到ON-OFF状态。状态检测模块工作流程可以由图4a概括，软启动初期，由于开关电源的输出电压Vo较低，导致原边电流IL在导通阶段始终大于0，随着开关时间增加，原边电流IL稳定存在负电流时，说明系统已经稳定可以进入ON-OFF状态。
PWM模块，与电流检测模块连接以获取第一信号，与状态检测模块连接以获取工作状态信号，PWM模块用于获取预设导通时间和临界值Tset，并在工作状态信号为ON-OFF状态信号时，执行第一关断控制和第一开启控制，其中，第一关断控制包括获取所述第一信号和所述开关控制信号，计算所述开关电源在当前开通时间内相邻原边电流的零点之间的时间间隔Ttap，在并在零点处输出第一调控信号且所述第一调控信号为关断信号，具体可为根据第一信号和开关控制信号，计算开关电源在当前开通时间内原边电流的零点的个数counter2，以及计算相邻零点之间的时间间隔Ttap，在counter2＝2时，或者counter2＝0且开通时间达到预设导通时间时，输出第一调控信号且第一调控信号为关断信号；第一开通控制包括比对所述时间间隔Ttap与预设临界值Tset，当Ttap>Tset，控制当前关断时间小于前一周期的关断时间，输出所述第一调控信号且所述第一调控信号为开启信号，当Ttap＝0，则控制当前关断之间大于前一周期的关断时间，输出所述第一 调控信号且所述第一调控信号为开启信号，当0<Ttap<＝Tset，控制当前关断时间与前一开关周期的关断时间相同，输出所述第一调控信号且所述第一调控信号为开启信号，具体可为根据第一信号和开关控制信号，计算开关电源在当前关断时间内原边电流的零点的个数counter3，以及比对时间间隔Ttap与预设临界值Tset的关系，当Ttap>Tset，则在counter3＝2时，输出第一调控信号且第一调控信号为开启信号，或者当Ttap＝0，则在counter3＝4时输出第一调控信号且第一调控信号为开启信号，或者当0<Ttap<＝Tset，则在counter3＝N时输出第一调控信号且第一调控信号为开启信号，其中，N为上一开关周期中counter3的取值。
在一具体实施例中，PWM模块包括计数器Counter2、计数器Counter3、计数器Counter4和一个时间计数单元。时间计数单元用于计数State＝1状态下的counter2>＝1且counter2<＝2时的时间长度Ttap；计数器Counter2是用来计数MOS管导通阶段的原边电流零点个数，当duty＝1，
Figure PCTCN2018125730-appb-000014
时，Counter2开始计数；当duty＝0时，Counter2清零。计数器Counter3用来计数MOS管关闭阶段的原边电流零点个数，当duty＝0，
Figure PCTCN2018125730-appb-000015
时，Counter3开始计数；当duty＝1时，Counter3清零。计数器Counter4用于控制软启动状态下MOS管导通时间以及ON-OFF状态下原边电流在MOS管导通阶段恒大于零(即Ttap＝0)时的MOS管关断，当duty＝1时，Counter4开始计数；当duty＝0时，Counter4清零。
驱动模块，与PWM模块连接以获取第一调控信号，生成开关控制信号，当第一调控信号为开启信号时，开关控制信号为开启信号，当第一调控信号为关闭信号时，开关控制信号为关断信号。
在一具体实施例中，该系统还包括：输出反馈模块：与状态检测模块连接以获取工作状态信号，并用于获取输出电压上限Vmax和输出电压下限Vmin以及开关电源的输出电压Vo，当工作状态信号为ON-OFF状态信号时，对比输出电压Vo与预设输出电压上限Vmax和预设输出电压下限Vmin，并输出第二调控信号，当Vo＞Vmax，则第二调控信号为关断信号，当Vo＜Vmin，则第二调控信号为开启信号。在一具体实施例中，如图5a所示，输出反馈模块包括两个比较器COMP2和COMP3以及一个SR锁存器latch1。COMP2的正输入端与开关电源连接以获取开关电源的输出电压Vo，负输入端接开关电源输出电压上限Vmax，当输出电压Vo超过上限Vmax，比较器COMP2输出信号VCOMP2＝1，并接入到SR锁存器latch1的R端，将SR锁存器latch1输出信号Q1置零；COMP3的正输入端接开关电源的输出电压下限Vmin，负输入端与开关电源连接以获取开关电源的输出电压Vo，当输出电压Vo低于下限Vmin，比较器COMP3输出信号VCOMP3＝1，并接入到SR锁存器latch1的S端，将输出信号Q1置1。SR锁存器latch1的输出信号Q1与状态控制信号State输入到与门and1中，与门and1输出ON-OFF使能信号Enable_ON-OFF，即可实现当State＝0时，ON-OFF使能信号Enable_ON-OFF置零；当State＝1时，即在ON-OFF状态下，输出电压Vo超过上限Vmax，ON-OFF使能信号Enable_ON-OFF＝0，电路进入OFF状态，MOS管关断，初级绕组不会再向次级绕组传递能量，输出电压Vo开始下降，直至输出电压Vo低于下限Vmin，ON-OFF使能信号Enable_ON-OFF＝1，电路进入ON状态。如此循环将输出电压稳定在一定的纹波范围内。其工作流程大致如图5b所示。输出反馈模块将ON-OFF使能信号Enable_ON-OFF输出给驱动模块和PWM模块。
在一具体实施例中，如图7a所示，驱动模块包括SR锁存器latch2、与门and2、与门and3、反相器inverter1和反相器inverter2，SR锁存器latch2的S输入端接入导通信号Flag_on，SR锁存器latch2的R输入端接入关断信号Flag_off，SR锁存器latch2的输出端与与门and2的输入端 连接，反相器inverter1的输入端接入使能信号Enable_ON-OFF，与门and3的输入端接入工作状态信号State并与反相器inverter1的输出端连接，反相器inverter2连接于与门and2的输入端与与门and3的输出端之间。其工作流程如图7b所示，工作状态信号State＝0时，即软启动状态下，开关控制信号duty在MOS管开启信号Flag_on＝1时置1，在MOS管关断信号Flag_off＝1时duty置0。当工作状态信号State＝1，即ON-OFF状态下，ON-OFF使能信号Enable_ON-OFF＝0时，电路处于OFF状态，开关管占空比信号duty置0；ON-OFF使能信号Enable_ON-OFF＝1时，电路处于ON状态，开关控制信号duty在MOS管开启信号Flag_on＝1时置1，在MOS管关断信号Flag_off＝1时duty置0。
重复上述过程进行循环控制开关电源功率管的开通和关断，以使系统更加稳定，从而获得更高的工作效率。
本申请已经通过上述实施例进行了说明，但应当理解的是，上述实施例只是用于举例和说明的目的，而非意在将本申请限制于所描述的实施例范围内。此外本领域技术人员可以理解的是，本申请并不局限于上述实施例，根据本申请的教导还可以做出更多种的变型和修改，这些变型和修改均落在本申请所要求保护的范围以内。本申请的保护范围由附属的权利要求书及其等效范围所界定。

Claims (20)

  1. 一种提高反激式谐振开关电源CCM模式转换效率的方法，基于软开关反激谐振电路的控制系统，其中：包括电流检测模块、状态检测模块、PWM模块、输出反馈模块以及驱动模块构成的控制系统与受控的开关电源连接起来构成闭环，该控制系统基于ON-OFF控制方法，在软启动状态或ON-OFF状态下对开关电源进行控制，其中：
    电流检测模块用于采集实现恒压算法的基本参数，包括一个比较器COMP1和一个D触发器D1，比较器COMP1的正端连接原边采样电阻电压Vs，负端接地，比较器COMP1输出信号VCOMP1连接D触发器D1的D输入端，D触发器D1的时钟端连接时钟信号CLK，作为系统的工作时钟CK，D触发器D1的输出端Q输出信号VCOMP1’，比较信号VCOMP1和VCOMP1’均输出给状态检测模块和PWM模块；
    状态检测模块用于判断控制系统的工作状态是软启动状态还是ON-OFF状态，包括一个计数器Counter1和一个D触发器D2，状态检测模块的输入信号为电流检测模块输出的比较信号VCOMP1、VCOMP1’和驱动模块输出的开关控制信号duty，状态检测模块的输出信号为输出给输出反馈模块、PWM模块和驱动模块的工作状态信号State；定义State＝0为软启动状态，State＝1为ON-OFF状态；D触发器D2的输入端D连接驱动模块输出的开关控制信号duty，时钟端输入时钟信号CLK作为系统的工作时钟CK，D触发器D2的输出端Q输出信号duty’电流检测模块输出的比较信号VCOMP1、VCOMP1’和驱动模块输出的开关控制信号duty以及D触发器D2的输出信号duty’均作为计数器Counter1的输入信号，计数器Counter1输出工作状态信号State；
    输出反馈模块用于实现ON-OFF状态下控制开关电源输出电压Vo的纹波大小，输出反馈模块的输入信号为副边输出电压Vo和状态检测模块输出的工作状态信号State，包括两个比较器COMP2和COMP3以及一个SR锁存器latch1，比较器COMP2将输出电压Vo与输出电压上限Vmax比较后输出VCOMP2连接至SR锁存器latch1的R端；比较器COMP3将输出电压下限Vmin与输出电压Vo比较输出VCOMP3连接至SR锁存器latch1的S端，比较器COMP2的正端接Vo，负端接输出电压上限Vmax，输出为VCOMP2，比较器COMP3的正端接输出电压下限Vmin，负端接Vo，输出为VCOMP3，SR锁存器latch1的Q端输出信号与状态控制信号State为一个与门and1的两个输入信号，与门的输出即为ON-OFF使能信号Enable_ON-OFF输出给驱动模块和PWM模块；
    PWM模块用于控制开关电源的MOS管导通时间和关断时间，精确实现原边MOS管的零电流ZCS关断和准零电压ZVS开启，最大化降低原边MOS管的开关损耗；PWM模块的输入信号为输出反馈模块输出的ON-OFF使能信号Enable_ON-OFF、状态检测模块输出的工作状态信号State、电流检测模块输出的比较信号VCOMP1、VCOMP1’和驱动模块输出的开关控制信号duty，PWM模块的输出信号为输入到驱动模块的MOS管关断信号Flag_off和MOS管开启信号Flag_on，以实现基于软启动及ON-OFF两个不同的工作状态对开关控制信号duty进行调制；
    驱动模块的输入为PWM模块输出的MOS管关断信号Flag_off和MOS管开启信号Flag_on以及状态检测模块输出的工作状态信号State和输出反馈模块输出的ON-OFF使能信号Enable_ON-OFF，驱动模块输出调制后的相应占空比开关控制信号duty，对开关电源功率管的开通和关断进行控制，实现开关电源效率的提升。
  2. 根据权利要求1所述的提高反激式谐振开关电源CCM模式转换效率的方法，其中：所 述状态检测模块在系统上电后初始状态为State＝0，当开关控制信号duty和电流检测模块输出信号VCOMP1、VCOMP1’满足：
    Figure PCTCN2018125730-appb-100001
    时，计数器开始计数counter1＝counter1+1；当duty＝0，
    Figure PCTCN2018125730-appb-100002
    且counter_Temp<counter1时，将计数器Counter1的值赋给初始值赋为0的临时变量counter_Temp，即counter_Temp＝counter1；当duty＝0，
    Figure PCTCN2018125730-appb-100003
    且counter1＝counter_Temp时，计数器Counter1和counter_Temp全部清零；当counter1达到n时，5<＝n<＝20，即连续n个开关周期，原边电流在MOS管导通阶段均存在负电流，说明电路状态已经稳定，则输出工作状态信号State＝1，即跳出软启动状态，进入ON-OFF状态，逻辑运算符
    Figure PCTCN2018125730-appb-100004
    表示亦或的逻辑关系。
  3. 根据权利要求1所述的提高反激式谐振开关电源CCM模式转换效率的方法，其中：所述输出反馈模块在系统处于State＝0即软启动状态时，ON-OFF使能信号Enable_ON-OFF置零；当系统处于State＝1即ON-OFF状态、且VCOMP2＝1时ON-OFF使能信号Enable_ON-OFF＝0，系统进入OFF状态，MOS管关断，初级绕组不会再向次级绕组传递能量，次级输出电压Vo开始下降，直至VCOMP3＝1，ON-OFF使能信号Enable_ON-OFF＝1，系统进入ON状态，MOS管开启，输出反馈模块将ON-OFF使能信号Enable_ON-OFF输出给驱动模块和PWM模块。
  4. 根据权利要求1所述的提高反激式谐振开关电源CCM模式转换效率的方法，其中：所述PWM模块包括三个计数器Counter2、counter3、counter4和一个时间计数单元。计数器Counter2是用来计数State＝1即ON-OFF状态下MOS管导通时原边电流零点个数，其输入信号为状态信号State、ON-OFF使能信号Enable_ON-OFF、占空比信号duty以及电流检测模块输出信号VCOMP1和VCOMP1’，输出为MOS管关断信号Flag_off，在State＝1、Enable_ON-OFF＝1的情况下，当duty＝1，VCOMP1⊕COMP1’＝1时，计数器Counter2开始计数；当duty＝0时，计数器Counter2清零，当计数器Counter2＝2时即输出MOS管关断信号Flag_off；计数器Counter3用来计数State＝0即软启动状态下MOS管导通时间以及State＝1即ON-OFF状态下()MOS管关闭时原边电流零点，其输入信号为状态信号State、ON-OFF使能信号Enable_ON-OFF、占空比信号duty以及电流检测模块输出信号VCOMP1和VCOMP1’，输出为MOS管开启信号Flag_on，当duty＝0，VCOMP1⊕COMP1’＝1时，计数器Counter3开始计数；当duty＝1时，计数器Counter3清零，当counter3计数达到要求即可输出MOS管开启信号Flag_on。计数器Counter4用于控制State＝0即软启动状态下MOS管导通时间以及State＝1即ON-OFF状态下原边电流在MOS管导通阶段恒大于零，即时间长度Ttap＝0时的MOS管关断，其输入信号为占空比信号duty，输出为MOS管关断信号Flag_off，当duty＝1时，计数器Counter4开始计数；当duty＝0时，计数器Counter4清零；时间计数单元用于计数State＝1即ON-OFF状态下的计数器Counter2>＝1且计数器Counter2<＝2时的时间长度Ttap，所以时间计数单元的输入信号是counter2和状态信号State，输出信号是时间长度Ttap，简单的说，计数器Counter4和counter3分别用于控制State＝0状态下的MOS管导通时间和MOS管关断时间；在State＝1状态下，ON-OFF使能信号Enable_ON-OFF＝1的前提下，由counter2和counter4共同控制MOS管导通时间，counter3控制MOS管关断时间，时间计数单元也是在State＝1状态下工作；
    当工作状态信号State＝0，即系统处于软启动状态，系统给定导通时间Tonmax，此时一个开关周期内原边MOS管导通时间即为Tonmax，当计数器Counter4计数到系统给定导通时间Tonmax时，MOS管关断信号Flag_off置为1并输入到驱动模块；当计数器Counter3计数到4时，即为原边MOS管关闭后，原边电流的第四个零点，根据电容电压与电流的关系，此时对应 原边MOS管关闭后漏源电压Vds谐振时的第二个谷底，即在这个时候导通MOS管可将开关损耗降到最低，此时将MOS管开启信号Flag_on置为1并输入到驱动模块；
    当工作状态信号State＝1，即系统处于ON-OFF状态，当ON-OFF使能信号Enable_ON-OFF＝1，计数器Counter2＝2或者Enable_ON-OFF＝1，计数器Counter2＝0，计数器Counter4计数到系统给定导通时间Tonmax时，MOS管关断信号Flag_off置为1，并由时间计算单元计算计数器Counter2>＝1且计数器Counter2<＝2时的时间长度Ttap，当Ttap较大时，原边电流在MOS管导通阶段的负电流较大，并且负电流时间较长，返回电源的能量较大，传递给副边绕组的能量较少，系统整体效率较低，故当Ttap较小或者原边电流在MOS管导通时刚刚大于零时，即为最佳工作点，当系统工作点靠近最佳工作点时，系统整体效率较高，基于上述理论，系统给定一个Ttap的临界值Tset，当Ttap>Tset，当前工作点远离最佳工作点，则本工作周期在原边MOS管关闭后漏源电压Vds谐振时的第一个谷底处导通MOS管，即减小了MOS管关闭时间的同时也保证了在谷底导通，MOS管关断时间减小，则副边电流下降就减少，相应的下一工作周期原边电流整体被拉高，Ttap也就随之减小，使下一工作周期系统工作点靠近最佳工作点，即当ON-OFF使能信号Enable_ON-OFF＝1，计数器Counter3＝2时，MOS管开启信号Flag_on置为1；当Ttap＝0，当前工作周期原边电流在MOS管导通阶段恒大于零，即没有过零点，则本工作周期在原边MOS管关闭后漏源电压Vds谐振时的第二个谷底处，MOS管导通，下一工作周期整体拉低原边电流，使下一工作周期系统工作点靠近最佳工作点，即当ON-OFF使能信号Enable_ON-OFF＝1，计数器Counter3＝4时，MOS管开启信号Flag_on置为1；当0<Ttap<＝Tset，当前工作周期系统工作点较为理想，逼近最佳工作点，仍维持上一周期的工作状态，即当ON-OFF使能信号Enable_ON-OFF＝1，计数器Counter3＝N时，N对应着上一工作周期的工作状态，当上一工作周期，MOS管在关闭后漏源电压Vds谐振时的第二个谷底处导通，则N＝4；当上一工作周期，MOS管在关闭后漏源电压Vds谐振时的第一个谷底处导通，则N＝2，MOS管开启信号Flag_on置为1；PWM模块将MOS管关断信号Flag_off以及MOS管开启信号Flag_on输出到驱动模块，以实现对开关管占空比信号duty的控制。
  5. 根据权利要求1所述的提高反激式谐振开关电源CCM模式转换效率的方法，其中：所述驱动模块包括一个SR锁存器latch2、两个反相器inverter1和inverter2及两个与门and2和and3，SR锁存器latch2的S端接MOS管导通信号Flag_on，R端接MOS管关断信号Flag_off，SR锁存器latch2的输出端Q端连接与门and2的一个输入端，状态控制信号State连接与门and3的一个输入端，ON-OFF使能信号Enable_ON-OFF经反相器inverter1后连接与门and3的另一个输入端，与门and3的输出经反相器inverter2后连接与门and2的另一个输入端，与门and2输出控制开关控制信号duty；
    当工作状态信号State＝0时，驱动模块在MOS管开启信号Flag_on＝1时，将开关管占空比信号duty置1，即将原边MOS管导通，在MOS管关断信号Flag_off＝1时，将开关管占空比信号duty置0，即将原边MOS管关断；当工作状态信号State＝1，ON-OFF使能信号Enable_ON-OFF＝0时，电路处于OFF状态，驱动模块将开关管占空比信号duty置0；当工作状态信号State＝1，ON-OFF使能信号Enable_ON-OFF＝1时，系统处于ON状态，驱动模块在MOS管开启信号Flag_on＝1时，将开关管占空比信号duty置1，即将原边MOS管导通，在MOS管关断信号Flag_off＝1时，将开关管占空比信号duty置0，即将原边MOS管关断；重复上述过程进行循环控制开关电源功率管的开通和关断，以使系统更加稳定，从而获得更高的工作效率。
  6. 一种谐振开关电源控制方法，包括：
    采样：采样所述开关电源的原边电阻电压并进行处理，生成第一信号；
    状态检测：获取所述第一信号和开关控制信号并判断所述开关电源的工作状态，所述工作状态为软启动状态或ON-OFF状态；
    切换控制：预设临界值Tset，当所述工作状态为ON-OFF状态时，执行：
    第一关断控制：获取所述第一信号和所述开关控制信号，计算所述开关电源在当前开通时间内相邻原边电流的零点之间的时间间隔Ttap，在并在零点处输出第一调控信号且所述第一调控信号为关断信号；
    第一开通控制：比对所述时间间隔Ttap与预设临界值Tset，当Ttap>Tset，控制当前关断时间小于前一周期的关断时间，输出所述第一调控信号且所述第一调控信号为开启信号，当Ttap＝0，则控制当前关断之间大于前一周期的关断时间，输出所述第一调控信号且所述第一调控信号为开启信号，当0<Ttap<＝Tset，控制当前关断时间与前一开关周期的关断时间相同，输出所述第一调控信号且所述第一调控信号为开启信号；及
    驱动输出：根据所述第一调控信号生成所述开关控制信号，当所述第一调控信号为开启信号时，所述开关控制信号为开启信号，当所述第一调控信号为关闭信号时，所述开关控制信号为关断信号。
  7. 根据权利要求6所述的控制方法，所述切换控制还包括预设导通时间，其中
    所述第一关断控制具体包括：获取所述第一信号和所述开关控制信号，计算所述开关电源在当前开通时间内原边电流的零点的个数counter2，以及计算相邻所述零点之间的时间间隔Ttap，在counter2＝2时，或者counter2＝0且所述开通时间达到所述预设导通时间时，输出第一调控信号且所述第一调控信号为关断信号；
    所述第一开通控制具体包括：获取所述第一信号和所述开关控制信号，计算所述开关电源在当前关断时间内原边电流的零点的个数counter3，以及比对所述时间间隔Ttap与预设临界值Tset，当Ttap>Tset，则当counter3＝2时，输出所述第一调控信号且所述第一调控信号为开启信号，当Ttap＝0，则当counter3＝4时，输出所述第一调控信号且所述第一调控信号为开启信号，当0<Ttap<＝Tset，则当counter3＝N时，输出所述第一调控信号且所述第一调控信号为开启信号，其中，N为上一开关周期中counter3的取值；重复执行所述第一关断控制。
  8. 根据权利要求6所述的控制方法，还包括：
    纹波调节：预设输出电压上限Vmax和输出电压下限Vmin，获取所述开关电源的输出电压Vo，当所述工作状态为ON-OFF状态时，对比所述输出电压Vo、所述输出电压上限Vmax和所述输出电压下限Vmin，并输出第二调控信号，当Vo＞Vmax时，所述第二调控信号为关断信号，当Vo＜Vmin时，所述第二调控信号为开启信号；
    所述切换控制的步骤还包括：获取所述第二调控信号，当所述第二调控信号为开启信号时，执行所述第一关断控制；
    所述驱动输出的步骤具体包括：根据所述第一调控信号、所述第二调控信号和所述工作状态生成所述开关控制信号，其中，当所述工作状态为ON-OFF状态时，当所述第一调控信号和所述第二调控信号均为开启信号，所述开关控制信号为开启信号，当第一调控信号为关断信号或第二调控信号为关断信号，所述开关控制信号为关断信号。
  9. 根据权利要求6所述的控制方法，其中，所述采样所述开关电源的原边电阻电压并进行 处理的步骤包括：
    设置比较器COMP1和D触发器D1，所述比较器COMP1的正输入端接入所述原边电阻电压，所述比较器COMP1的负输入端接地，所述比较器COMP1的输出端输出信号VCOMP1，且所述比较器COMP1的输出单与所述D触发器D1的输入端连接，所述D触发器D1的输出端输出信号VCOMP1’，所述第一信号包括所述信号VCOMP1和所述信号VCOMP1’。
  10. 根据权利要求9所述的控制方法，其中，所述判断所述开关电源的工作状态的步骤具体包括：根据所述第一信号和所述开关控制信号判断所述开关电源在连续n个开关周期的开通时间内是否均存在零点，当是均存在零点，则所述工作状态为ON-OFF状态，当不是均存在零点，则所述工作状态为软启动状态，其中，5≤n≤20。
  11. 根据权利要求10所述的控制方法，其中，所述开关电源包括MOS管，通过控制所述MOS管的开启和关断控制所述开关电源的开启和关断，所述开启信号为高电平，所述关断信号为低电平。
  12. 根据权利要求11所述的控制方法，其中，所述根据所述第一信号和所述开关控制信号判断所述开关电源在连续n个开关周期的开通时间内是否均存在零点的步骤具体包括：
    在n个开关周期的开通时间内均执行逻辑运算
    Figure PCTCN2018125730-appb-100005
    其中，duty为所述开关控制信号，当在n个开关周期的开通时间内是否均出现
    Figure PCTCN2018125730-appb-100006
    Figure PCTCN2018125730-appb-100007
    则判断所述开关电源在连续n个开关周期的开通时间内均存在零点，所述工作状态为ON-OFF状态，逻辑运算符
    Figure PCTCN2018125730-appb-100008
    表示亦或的逻辑关系。
  13. 根据权利要求12所述的控制方法，其中，判断所述工作状态后输出工作状态信号，所述工作状态信号为电平信号，所述工作状态信号为高电平时表示所述ON-OFF状态信号，所述工作状态信号为低电平时表示所述软启动状态信号。
  14. 根据权利要求6所述的控制方法，其中，
    所述切换控制步骤还包括：
    当所述工作状态为软启动状态时，执行：
    第二关断控制：计算所述开通时间并当所述开通时间达到所述预设导通时间时，输出所述第一调控信号且所述第一调控信号为关断信号；
    第二开启控制：获取所述第一信号和所述开关控制信号，计算所述开关电源在当前关断时间内原边电流的零点的个数counter3，当counter3＝4时，输出所述第一调控信号且所述第一调控信号为开启信号；
    所述驱动输出还包括：
    当所述工作状态为软启动时，所述开关控制信号与所述第一调控信号一致。
  15. 一种谐振开关电源控制系统，包括：
    电流检测模块，用于采样所述开关电源的原边采样电阻电压，并对所述原边采样电阻电压进行处理输出第一信号；
    状态检测模块，与所述电流检测模块连接以获取所述第一信号，与驱动模块连接以获取开关控制信号，并用于判断所述开关电源的工作状态，生成工作状态信号，所述工作状态信号为软启动状态信号或ON-OFF状态信号；
    PWM模块，与所述电流检测模块连接以获取所述第一信号，与所述状态检测模块连接以获取所述工作状态信号，所述PWM模块用于获取预设导通时间和临界值Tset，并在所述工作状态 信号为ON-OFF状态信号时，执行第一关断控制和第一开启控制，其中，
    所述第一关断控制包括：获取所述第一信号和所述开关控制信号，计算所述开关电源在当前开通时间内相邻原边电流的零点之间的时间间隔Ttap，在并在零点处输出第一调控信号且所述第一调控信号为关断信号；
    所述第一开通控制包括：比对所述时间间隔Ttap与预设临界值Tset，当Ttap>Tset，控制当前关断时间小于前一周期的关断时间，输出所述第一调控信号且所述第一调控信号为开启信号，当Ttap＝0，则控制当前关断之间大于前一周期的关断时间，输出所述第一调控信号且所述第一调控信号为开启信号，当0<Ttap<＝Tset，控制当前关断时间与前一开关周期的关断时间相同，输出所述第一调控信号且所述第一调控信号为开启信号；及
    驱动模块，与所述PWM模块连接以获取所述第一调控信号，生成所述开关控制信号，当所述第一调控信号为开启信号时，所述开关控制信号为开启信号，当所述第一调控信号为关闭信号时，所述开关控制信号为关断信号。
  16. 根据权利要求15所述的控制系统，还包括：
    输出反馈模块：与所述状态检测模块连接以获取所述工作状态信号，并用于获取输出电压上限Vmax和输出电压下限Vmin以及所述开关电源的输出电压Vo，当所述工作状态信号为ON-OFF状态信号时，对比所述输出电压Vo与所述预设输出电压上限Vmax和所述预设输出电压下限Vmin，并输出第二调控信号，当Vo＞Vmax，则所述第二调控信号为关断信号，当Vo＜Vmin，则所述第二调控信号为开启信号。
    所述PWM模块还与所述输出反馈模块连接以获取所述第二调控信号，并用于当所述第二调控信号为开启信号时，执行所述第一关断控制；
    所述驱动模块还与所述输出反馈模块连接以获取所述第二调控信号，以及与所述状态检测模块连接以获取所述工作状态信号，生成所述开关控制信号，其中，当所述工作状态信号为ON-OFF状态信号时，当所述第一调控信号和所述第二调控信号均为开启信号时，所述开关控制信号为开启信号，当第一调控信号为关断信号或第二调控信号为关断信号，所述开关控制信号为关断信号。
  17. 根据权利要求16所述的控制系统，其中，所述开关电源包括MOS管，通过控制所述MOS管的开启和关断控制所述开关电源的开启和关断，所述开启信号为高电平，所述关断信号为低电平。
  18. 根据权利要求17所述的控制系统，其中，所述PWM模块包括：比较器COMP2、比较器COMP3、SR锁存器latch1以及与门and1，所述比较器COMP2的负输入端接入所述预设输出电压上限Vmax，所述比较器COMP2的正输入端和所述比较器COMP3的负输入端均接入所述输出电压Vo，所述比较器COMP3的正输入端接所述输出电压下限Vmin，所述比较器COMP2的输出端接所述SR锁存器latch1的R输入端，所述比较器COMP3的输出端接所述SR锁存器latch1的S输入端，所述SR锁存器latch1的输出端和所述工作状态信号均与所述与门and1的输入端连接，所述与门and1的输出端输出所述第二调控信号，所述第二调控信号为使能信号。
  19. 根据权利要求18所述的控制系统，其中，所述驱动模块包括SR锁存器latch2、与门and2、与门and3、反相器inverter1和反相器inverter2，所述SR锁存器latch2的S输入端接入所述第一调控信号，所述第一调控信号经反相后输入所述SR锁存器latch2的R输入端，所述SR锁存器latch2的输出端与所述与门and2的输入端连接，所述反相器inverter1的输入端接入所述使能信号，所述与门and3的输入端接入所述工作状态信号并与所述反相器inverter1的输出端连接，所 述反相器inverter2连接于所述与门and2的输入端与所述与门and3的输出端之间。
  20. 根据权利要求15所述的控制系统，其中，所述电流检测模块包括比较器COMP1和D触发器D1，所述比较器COMP1的正输入端接入所述原边电阻电压，所述比较器COMP1的负输入端接地，所述比较器COMP1的输出端输出信号VCOMP1，且所述比较器COMP1的输出单与所述D触发器D1的输入端连接，所述D触发器D1的输出端输出信号VCOMP1’，所述第一信号包括所述信号VCOMP1和所述信号VCOMP1’。
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