WO2019120126A1 - 信号处理方法、装置及系统 - Google Patents

信号处理方法、装置及系统 Download PDF

Info

Publication number
WO2019120126A1
WO2019120126A1 PCT/CN2018/120708 CN2018120708W WO2019120126A1 WO 2019120126 A1 WO2019120126 A1 WO 2019120126A1 CN 2018120708 W CN2018120708 W CN 2018120708W WO 2019120126 A1 WO2019120126 A1 WO 2019120126A1
Authority
WO
WIPO (PCT)
Prior art keywords
signal
frequency band
matrix
communication system
spreading
Prior art date
Application number
PCT/CN2018/120708
Other languages
English (en)
French (fr)
Inventor
王新征
Original Assignee
华为技术有限公司
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by 华为技术有限公司 filed Critical 华为技术有限公司
Publication of WO2019120126A1 publication Critical patent/WO2019120126A1/zh

Links

Images

Classifications

    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04W—WIRELESS COMMUNICATION NETWORKS
    • H04W16/00—Network planning, e.g. coverage or traffic planning tools; Network deployment, e.g. resource partitioning or cells structures
    • H04W16/14—Spectrum sharing arrangements between different networks
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04W—WIRELESS COMMUNICATION NETWORKS
    • H04W28/00—Network traffic management; Network resource management
    • H04W28/02—Traffic management, e.g. flow control or congestion control
    • H04W28/04—Error control

Definitions

  • the present application relates to the field of communications, and in particular, to a signal processing method, apparatus, and system.
  • the 3G mobile communication system generally includes a Universal Mobile Telecommunications System (UMTS), and the 4G mobile communication system is generally a Long-Term Evolution (LTE) system.
  • UMTS Universal Mobile Telecommunications System
  • LTE Long-Term Evolution
  • a spectrum sharing method is generally adopted to improve utilization of spectrum resources. For example, when the base station of the UMTS system detects that its traffic is low for a certain period of time and the traffic of the LTE system is high, the base station of the UMTS can deactivate the idle frequency band in the UMTS system, and the deactivated idle frequency band. Can be used by LTE systems.
  • the present application provides a signal processing method, device and system, which can solve the problem of signal interference when a communication system of two systems in the related art shares a spectrum, and the technical solution is as follows:
  • a signal processing method which can be applied to a base station in a first-standard communication system, and the method can include:
  • the communication system of the first system and the communication system of the second system share the target frequency band, acquire at least one signal to be transmitted in the communication system of the first system, and a spreading code corresponding to each signal to be transmitted; determine at least one channel plus a scrambling signal, and a spreading code corresponding to each scrambling signal; then, a spreading code corresponding to each signal to be transmitted may be used to spread the signal to be transmitted for each path, and the corresponding spreading signal may be used.
  • the frequency code is used for spreading each scrambled signal; finally, at least one of the to-be-transmitted signal after spreading and the at least one scrambled signal after spreading are processed to obtain a transmitted signal, and the transmitted signal is transmitted.
  • the processing may include superimposing and scrambling, and the power of the transmitted signal obtained in the target frequency band is smaller than the original power, and the original power is obtained by processing only the at least one signal to be transmitted after the spread spectrum.
  • the power of the signal in the target frequency band which belongs to a preset frequency band shared by the communication systems of the two systems.
  • the base station in the communication system of the first standard transmits the signal to be transmitted, by adding at least one scrambling signal, the power transmitted by the base station in the target frequency band is less than the original power, thereby The interference of the transmitted signal to the signal in the communication system of the second system can be effectively reduced.
  • the determining, by the base station in the first-standard communication system, the at least one scrambling signal, and the spreading code corresponding to each scrambling signal may include:
  • the number N of the scrambled signals is less than or equal to the number of the idle spreading codes, and the idle spreading code does not include the to-be-sent in the system. a spreading code corresponding to the signal;
  • N spreading codes corresponding to the N scrambling signals may be selected from the idle spreading codes in the code table.
  • the base station may randomly select N spreading codes, or may sequentially select N.
  • the unit time may be a duration of each symbol in the communication system of the second system, and the unit time may be a reciprocal of the subcarrier spacing in the communication system of the second standard;
  • the N-channel scrambled signal may make the power of the power model in the target frequency band smaller than the original power.
  • the process of determining, by the base station, the N-channel scrambled signal according to the power model may include:
  • the first power threshold may be less than or equal to a difference between a maximum transmit power of the base station and a total power of the at least one signal to be transmitted in the communication system of the first mode.
  • the processing may include superimposing and scrambling, and acquiring L chips that the transmission signal can include in a unit time, and the L can satisfy: T 0 is the unit time, T c is the chip period of the communication system of the first system, and INT () indicates rounding the value in the parentheses, for example, it can be rounded up, rounded down, rounded, rounded, etc.
  • the base station can determine that the signal model is a column vector f of L ⁇ 1 according to the type of operation included in the processing and the number L of chips included in the unit time of the transmitted signal, and the column vector f can satisfy:
  • S is a L ⁇ L scrambling code matrix
  • the scrambling code matrix is a diagonal matrix
  • a diagonal element of the lth row in the scrambling code matrix is a scrambling code corresponding to the lth chip in the L chips.
  • l is a positive integer not greater than L
  • g is an L ⁇ 1 column vector composed of L chips included in the unit time after superimposing at least one signal to be transmitted after spreading.
  • W i is a spreading matrix of L ⁇ (k i ⁇ N i ) composed of spreading codes corresponding to the i-th scrambling signal group, and i is a positive integer not greater than w, and W i meets: Indicates direct product, a unit matrix of k i order, W′ i is a matrix of l i ⁇ N i , and l i is a spreading factor of a spreading code corresponding to each scrambling signal in the i-th scrambled signal group, k i is the The number of symbols transmitted by each scrambled signal in the i-th scrambled signal group in the unit time, and the y-th column element in the matrix W' i is
  • the base station determines, according to the signal model, a power model of the transmitted signal in the target frequency band, which may include:
  • a scrambling signal matrix x' composed of the N-channel scrambled signals the scrambling signal matrix x' can satisfy:
  • P' is the first power threshold
  • the processing performed by the base station on the at least one to-be-transmitted signal and the at least one scrambled signal after the spreading may further include: filtering by using a transmit shaping filter, and oversampling according to an oversampling factor R, where R is positive Integer; at this time, the transmitted signal includes L ⁇ R chips in unit time, and L satisfies: T 0 is the unit time, T c is the chip period of the communication system of the first system, and INT () means rounding the value in the brackets.
  • R positive Integer
  • the base station determines the column vector f' whose signal model is (L ⁇ R) ⁇ 1 according to the type of operation included in the processing and the number of chips L ⁇ R included in the unit time of the transmission signal, and the column vector f′ satisfies:
  • S is an L ⁇ L scrambling code matrix
  • the scrambling code matrix is a diagonal matrix
  • the diagonal element of the i-th row in the scrambling code matrix is a scrambling code corresponding to the i-th chip in the L chips.
  • g is an L ⁇ 1 column vector composed of L chips included in a unit time after superimposing at least one channel to be transmitted after spreading
  • w is a group included in the N channel scrambling signal
  • the spreading factor of the spreading code corresponding to at least one scrambling signal included in each group of scrambling signal groups is equal, and the spreading factors of the spreading codes corresponding to each group of scrambling signal groups are not equal
  • W i is A spreading matrix of L ⁇ (k i ⁇ N i ) composed of spreading codes corresponding to the i-group scrambling signal group, i is a positive integer not greater than w, and W i satisfies: Indicates direct product, a unit matrix of k i order, W′ i is a matrix of l i ⁇ N i , and l i is a spreading factor of a spreading code corresponding to each scrambling signal in the i-th scrambled signal group, k i is the first The number of symbols transmitted by each
  • x' is a set of w groups of scrambled signal groups arranged in columns
  • H is a filter matrix of (L ⁇ R) ⁇ L, and the element H mn of the mth row and the nth column in the filter matrix H satisfies:
  • RC 0 (t) is the unit impulse response function of the emission shaping filter
  • m is a positive integer not greater than (L ⁇ R)
  • n is a positive integer not greater than L.
  • a power model of the transmitted signal in the target frequency band is determined according to the signal model, including:
  • the power model P of the transmitted signal in the target frequency band is determined, and the power model P can satisfy:
  • a scrambling signal matrix x' composed of the N-channel scrambled signals the scrambling signal matrix x' can satisfy:
  • P' is the first power threshold
  • the base station may further detect whether the first sampling frequency of the baseband signal in the first-standard communication system is smaller than a second sampling frequency of the baseband signal in the second system of communication systems;
  • the base station may determine that the oversampling factor R is an integer greater than or equal to 2, for example, the oversampling factor R may satisfy: The product of the first sampling frequency and the oversampling factor R is equal to the second sampling frequency.
  • the base station may determine that the oversampling factor R is 1, that is, there is no need to oversample the baseband signal.
  • the base station determines, when the diagonal element of the diagonal element is 0 or 1, the row of the diagonal element of the value of 1, the center of the first frequency band occupied by the communication system of the first standard may be determined first. a frequency f0, and determining a lower limit frequency f1 of the target frequency band, an upper limit frequency f2 of the target frequency band, and a center frequency f0 of the first frequency band;
  • the center frequency f0 satisfies: f1 ⁇ f0 ⁇ f2, it can be determined that the diagonal element of the value 1 includes the first row to the first row Line, and Going to the L'th row, where fs is the sampling frequency of the first-standard communication system, where L' is the total number of rows included in the diagonal matrix;
  • the row of the diagonal elements having a value of 1 may further include: Go to the first Line, and / or, the first Go to the first Row;
  • the row of the diagonal element having a value of 1 may further include: Go to the first Line, and / or, the first Go to the first Row;
  • the row of the diagonal element having a value of 1 may further include Go to the first Line, and / or, the first Go to the first Row;
  • ⁇ 1, ⁇ 2, ⁇ 3, ⁇ 4, ⁇ 5, and ⁇ 6 are all positive integers.
  • the base station may further detect whether the target frequency band is a continuous frequency band;
  • the target frequency band is a continuous frequency band, determine the lower limit frequency f1 of the target frequency band, the upper limit frequency f2 of the target frequency band, and the center frequency f0 of the first frequency band;
  • the base station may first determine, according to the foregoing method, the row of the diagonal element corresponding to each sub-band in the target frequency band;
  • the combination of the rows of the diagonal elements corresponding to each sub-band corresponding to the target frequency band may be determined as the diagonal element of the diagonal matrix having the diagonal element of 0 or 1. .
  • the signal processing method may further include:
  • the signal of the communication system of the second system is processed by using the transmission shaping filter of the communication system of the first system After sending.
  • the emission shaping filter in the communication system of the first system has less influence on the signal of the communication system of the second system, so the emission shaping filter can be used.
  • the signal of the second-standard communication system is processed and transmitted, thereby effectively improving the efficiency of signal processing and transmission, and reducing the cost.
  • the frequency band shared by the first-standard communication system and the second-standard communication system may be a preset frequency band
  • the base station may acquire the scheduling information of the second-standard communication system before determining the at least one scrambling signal.
  • the scheduling information may include a scheduling frequency band of the communication system of the second system; afterwards, the base station may determine the overlapping frequency band between the scheduling frequency band and the preset frequency band as the target frequency band.
  • the base station can determine the target frequency band according to the scheduling frequency band actually used by the communication system of the second standard, and reduce the power of the transmitted signal in the target frequency band, thereby effectively reducing the interference of the signal in the second standard communication system. Under the premise, avoid excessive increase in transmit power.
  • the base station may further filter and transmit the transmit signal by using a narrow bandwidth filter, where the narrow bandwidth filter may include a band pass filter, a band stop filter, a high pass filter, and a low Any of the pass filters;
  • the base station may further acquire scheduling information of the communication system of the second system before determining at least one scrambling signal, where the scheduling information may include a scheduling frequency band of the communication system of the second standard; afterwards, the base station may perform the scheduling A portion of the frequency band that overlaps with the passband of the narrow bandwidth filter is determined as the target frequency band.
  • the base station can use the narrow bandwidth filter to suppress the power of the transmitted signal in a part of the frequency band, and for the frequency band that is not suppressed by the narrow bandwidth filter, the method of adding at least one scrambled signal may be adopted.
  • the adjustment of the power of the target frequency band not only effectively reduces the interference of the signal of the communication system of the second standard, but also improves the flexibility of signal processing.
  • the method may further include:
  • each chip sequence is a sequence of a plurality of chips obtained by spreading a symbol
  • the spreading code used by the symbol indicated by the first chip sequence transmitted by the signal of the first path in the signal group of the first path signal includes: the spreading code corresponding to the signal of the any path n 0 +1 to the l'th element, the spreading code used by the symbol indicated by the last chip sequence transmitted by the any path signal in the duration includes: the first of the spreading codes corresponding to the any path signal Up to (L'+n 0 )%l' elements, l' is a spreading factor of the spreading code corresponding to the first path signal, and L' is the number of chips included in the unit time of the transmitting signal , % means taking the remainder.
  • the signal processing method provided by the present application may determine each path according to the time difference between the initial transmission time of each symbol in the communication system of the second system and the initial transmission time of the corresponding chip sequence in the communication system of the first system.
  • the spreading code actually used by the signal during the duration of the symbol so that the power of the transmitted signal during the duration can be accurately calculated, thereby accurately reducing the communication system of the first system in the communication system of the second system.
  • Signal interference improves the accuracy of signal processing.
  • the process of determining, by the base station, the spreading code used by each channel in the duration of the signal group to which the first path signal belongs according to the number n 0 of the chip may include:
  • the diagonal element of the value 1 includes the (n 0 +1)th to the (n 0 +L') rows, and k' i is the first signal.
  • the number of symbols transmitted during the duration of the first symbol, l' is a spreading factor of the spreading code corresponding to the first path signal;
  • V' i is a matrix of l' ⁇ N' i
  • the yth column element of the matrix V' i is the N' i channel signal included in the signal group to which the first path signal belongs 'signals corresponding to the column vector composed of a spreading code
  • y' of y is not greater than N 'i is a positive integer.
  • the method may further include:
  • the indication may be sent to the base station of the second-standard communication system.
  • the indication information may be used to indicate that the base station of the communication system of the second system is allowed to be scheduled in a preset frequency band shared by the communication systems of the two systems, or the indication information may be used to indicate the second standard
  • the base station of the communication system stops transmitting signals for a preset period of time.
  • the bandwidth of the allowed scheduling frequency band may be smaller than the bandwidth of the preset frequency band, thereby avoiding the communication system of the second standard communication system of the first standard when the traffic volume of the communication system of the first standard is large.
  • the signal transmission and reception has an impact, ensuring that the communication system of the first standard can work normally.
  • a signal processing apparatus which can be applied to a base station of a first-standard communication system, the apparatus can include: at least one module, the at least one module can be used to implement the foregoing first aspect Signal processing method.
  • a signal processing apparatus which can be applied to a base station of a first-standard communication system, the apparatus can include: a processor, a transceiver, and a memory; the processor, the transceiver, and the memory can be used for The signal processing method provided by the above first aspect is implemented.
  • a computer readable storage medium having instructions stored therein that, when executed on a computer, cause the computer to perform the signals provided by the first aspect above Approach.
  • a computer program product comprising instructions for causing a computer to perform the signal processing method provided by the first aspect described above is provided when the computer program product runs on a computer.
  • a chip is provided, the chip being configurable in a base station of a communication system of a first standard, the chip comprising programmable logic circuits and/or program instructions for implementing the first aspect when the chip is in operation
  • the signal processing method provided.
  • a signal processing system may include: a base station and at least one terminal device;
  • the base station may include the signal processing apparatus provided in the second aspect or the third aspect described above.
  • a base station in a first-standard communication system can determine at least one scrambling signal when sharing a target frequency band with a communication system of another standard, and The scrambled signal and the signal to be transmitted in the system are processed and sent to the terminal device. Since the scrambled signal can make the power of the transmitted signal sent by the base station in the target frequency band smaller than the original power, the transmit signal pair can be effectively reduced. Interference of signals in the second standard communication system.
  • FIG. 1 is a block diagram of a signal processing system according to an embodiment of the present invention.
  • FIG. 2 is a structural diagram of another signal processing system according to an embodiment of the present invention.
  • FIG. 3 is a schematic diagram of a code tree of an orthogonal variable spreading factor code according to an embodiment of the present invention.
  • FIG. 4 is a flowchart of a signal processing method according to an embodiment of the present invention.
  • FIG. 5 is a schematic diagram of a code channel used in a UMTS system according to an embodiment of the present invention.
  • FIG. 6 is a flowchart of a method for determining at least one scrambling signal and a spreading code corresponding to each scrambling signal according to an embodiment of the present invention
  • FIG. 7 is a schematic diagram of a code channel used in another UMTS system according to an embodiment of the present invention.
  • FIG. 8 is a schematic diagram of another code channel used in a UMTS system according to an embodiment of the present invention.
  • FIG. 9 is a schematic diagram of a frequency band occupied by a UMTS system and an LTE system according to an embodiment of the present invention.
  • FIG. 10 is a schematic diagram of power spectral density of a transmitted signal transmitted by a base station in a UMTS according to an embodiment of the present invention
  • FIG. 11 is a schematic diagram of another UMTS system and a frequency band occupied by an LTE system according to an embodiment of the present invention.
  • FIG. 12 is a schematic diagram of still another UMTS system and a frequency band occupied by an LTE system according to an embodiment of the present invention.
  • FIG. 13 is a schematic diagram of power spectral density of a transmitted signal transmitted by a base station in another UMTS according to an embodiment of the present invention
  • FIG. 14 is a schematic diagram of still another UMTS system and a frequency band occupied by an LTE system according to an embodiment of the present invention.
  • FIG. 15 is a flowchart of another signal processing method according to an embodiment of the present invention.
  • 16 is a schematic diagram of power spectral density of a transmitted signal in a UMTS system and an LTE system according to an embodiment of the present invention
  • FIG. 17 is a schematic diagram of a target frequency band according to an embodiment of the present invention.
  • FIG. 18 is a schematic diagram of correspondence between a OFDM symbol in an LTE system and a chip sequence in a UMTS system in a time domain according to an embodiment of the present disclosure
  • 19 is a flowchart of a method for determining a spreading code actually used by each channel signal according to an embodiment of the present invention.
  • 20 is a schematic diagram of correspondence between different symbols in a LTE system and a chip sequence in a UMTS system in a time domain according to an embodiment of the present invention
  • 21 is a schematic structural diagram of a signal processing apparatus according to an embodiment of the present invention.
  • FIG. 22 is a schematic structural diagram of a first determining module according to an embodiment of the present disclosure.
  • FIG. 23 is a schematic structural diagram of another signal processing apparatus according to an embodiment of the present invention.
  • FIG. 24 is a schematic structural diagram of still another signal processing apparatus according to an embodiment of the present invention.
  • FIG. 25 is a schematic structural diagram of hardware of a signal processing apparatus according to an embodiment of the present invention.
  • the system may include a base station 01 and a plurality of terminal devices 02, which may also be referred to as user equipment (UE).
  • a communication connection is established between each terminal device 02 and the base station 01.
  • Terminal Equipment The base station 01 can support the transmission and reception of signals of at least two modes.
  • the base station 01 can support transmission and reception of UMTS signals, and can also support transmission and reception of LTE signals.
  • the plurality of terminal devices 02 may also include terminal devices of at least two standards, and the terminal devices of each standard may interact with the base station 01 to perform signals corresponding to the system.
  • FIG. 2 is a schematic structural diagram of another signal processing system according to an embodiment of the present invention.
  • the system may include at least two base stations (two base stations 011 and 012 are shown in FIG. 2) and multiple The terminal device 02, wherein each base station can support transmission and reception of a standard signal, and each base station can communicate through a preset interface.
  • the base station 011 can support the transmission and reception of signals of the first standard (for example, UMTS), and the base station 012 can support the transmission and reception of signals of the second system (for example, LTE); each of the plurality of terminal devices 02 can be the same as the same System base station communication.
  • the first standard for example, UMTS
  • the base station 012 can support the transmission and reception of signals of the second system (for example, LTE)
  • each of the plurality of terminal devices 02 can be the same as the same System base station communication.
  • any base station shown in FIG. 1 and FIG. 2 may be referred to as a Node B (NodeB, NB), an evolved Node B (eNB), depending on the wireless communication technology used by the communication system. Access Point (AP), etc.
  • the base station can be further divided into a macro base station for providing a macro cell, a micro base station for providing a pico cell, and a femtocell for providing Femto cell) Femto base station, etc.
  • future base stations may use other names.
  • any of the terminal devices shown in FIG. 1 and FIG. 2 may be various wireless communication devices having wireless communication functions, such as mobile cellular phones, cordless phones, Session Initiation Protocol (SIP) phones, and individuals.
  • Digital Assistant (PDA) smart phone, laptop, tablet, wireless data card, Modulator demodulator (Modem), wearable device (such as smart watch), in-vehicle device, etc., or the terminal device It can be a wireless terminal in machine to machine (M2M) communication, such as a sensor, a meter that can be remotely metered, or some other intelligent hardware.
  • M2M machine to machine
  • the spectrum resources thereof are relatively idle (ie, in a light load state), and the traffic of the second-standard communication system is
  • the communication system of the second standard can share a relatively idle preset frequency band in the communication system of the first standard, that is, the communication systems of the two systems can simultaneously pass the The idle preset frequency band transmits and receives signals.
  • the base station can directly trigger the spectrum sharing according to the traffic volume of the obtained two communication systems.
  • the base stations of the communication systems of the two systems are set independently of each other (that is, the scenario shown in FIG. 2), the two base stations can exchange scheduling information through a preset interface (for example, an X2 interface), and the scheduling sent by each base station.
  • the information may include parameters for indicating the current traffic status of the base station, such that the base station of the communication system of the first system may trigger spectrum sharing according to the scheduling information of the interaction.
  • the two base stations may separately report the scheduling information to the control network element of the third party, and the control network element of the third party may trigger the spectrum sharing according to the received scheduling information.
  • the triggering manner of the spectrum sharing is not limited in the embodiment of the present invention.
  • the parameter used to measure the traffic volume of each communication system may include: the power of the transmitted signal.
  • the communication system of the first standard may be a communication system using a spread spectrum modulation technology, for example, may be a UMTS system, a Code Division Multiple Access (CDMA) 2000 system, or a time division synchronization code. Time Division-Synchronous Code Division Multiple Access (TD-SCDMA) system.
  • the first-standard communication system can transmit and receive signals by using a Frequency Division Duplex (FDD) technology, and can also transmit and receive signals by using a Time Division Duplex (TDD) technology. limited.
  • FDD Frequency Division Duplex
  • TDD Time Division Duplex
  • the base station when the base station sends a signal to the terminal device, it is necessary to use different spreading codes to spread the signals to be transmitted on different physical channels, and then perform the spread of the multiple signals. Superimpose and use the specific scrambling code to scramble the superimposed signal and send it.
  • the communication system of the first system is a UMTS system in a 3G communication system.
  • the UMTS system uses FDD technology to transmit and receive signals, that is, the uplink signal and the downlink signal use different spectrums.
  • the base station unit (BBU) in the base station can perform the functions of spreading, superimposing and scrambling on the signal to be transmitted, and can pass the processed signal through the common public radio.
  • the Common Public Radio Interface (CPRI) is transmitted to a Radio Remote Unit (RRU).
  • the CPRI interface can sample the baseband signal sent by the BBU.
  • the sampling frequency is generally 3.84 megahertz (MHz).
  • the RRU can The received signal is converted (for example, up-converted) into a radio frequency signal and transmitted through an antenna.
  • the spreading code used in the UMTS system is generally an Orthogonal Variable Spreading Factor (OVSF) code.
  • OVSF Orthogonal Variable Spreading Factor
  • the OVSF code used for the signal on each physical channel can be selected from the code tree shown in FIG. As shown in FIG. 3, each OVSF code may include at least one element, and each element has a value of 1 or -1. And, each OVSF code can be symbolized Indicates that m 1 represents a spreading factor (SF) of the OVSF code, and the SF may be used to indicate the length of the OVSF code, that is, the number of elements included in the OVSF code.
  • SF spreading factor
  • n 1 may be used to indicate SF OVSF codes for the plurality of m 1 in the OVSF codes of n 1, n 1 and satisfying: 0 ⁇ n1 ⁇ m 1.
  • C 2,0 may represent the 0th OVSF code of the two OVSF codes whose SF is 2
  • C 4,2 may represent the 2nd OVSF code of the 4 OVSF codes whose SF is 4.
  • any two OVSF codes of the same SF are orthogonal to each other, and each OVSF code as a parent node can derive two OVSF codes of two SFs, and each OVSF with SF greater than 1
  • the two SFs obtained after the code division are half of the spreading code, and the OVSF codes corresponding to the parent node are not orthogonal, but are orthogonal to other OVSF codes whose SF is half of the code tree.
  • two spreading codes (1, 1) and (-1, -1) with SF 2 can be obtained, and the two spreading codes are
  • the OVSF code C 2,0 corresponding to the parent node of the OVSF code C 4,1 is not orthogonal, but is orthogonal to the other OVSF code C 2,1 whose SF is 2. It can be seen that when a spreading code is selected for the signal on each physical channel, if an OVSF code in the code tree has been selected, the other SF larger OVSF code derived from the OVSF code is used as the parent node. Can not be selected again; similarly, if an OVSF code has been selected, the OVSF code corresponding to the parent node of the OVSF code can no longer be selected.
  • each physical channel may also be referred to as a code channel, as the signal on each physical channel needs to be spread by using a unique spreading code.
  • the communication system of the second system may be a global system for mobile communication (GSM) system, an LTE system, or a new radio (NR) system, etc., without using spread spectrum modulation technology. system.
  • GSM global system for mobile communication
  • LTE long term evolution
  • NR new radio
  • the system bandwidth selection of the LTE system is flexible, and generally includes various optional bandwidths such as 3 MHz, 5 MHz, and 10 MHz.
  • Table 1 is a correspondence between system bandwidth and sampling frequency in an LTE system according to an embodiment of the present invention. It can be seen from Table 1 that LTE systems with different system bandwidths have different CPRI sampling frequencies. For example, an LTE system with a system bandwidth of 3 MHz may have a sampling frequency of 3.84 MHz, and an LTE system with a system bandwidth of 5 MHz may have a sampling frequency of 7.68 MHz.
  • the duration T 0 of each symbol in the LTE system can satisfy: Microseconds ( ⁇ s).
  • the symbol in the LTE system may be an Orthogonal Frequency Division Multiplexing (OFDM) symbol, and the duration T 0 may refer to a duration of an OFDM symbol (ie, a useful OFDM symbol) that does not consider a cyclic prefix. .
  • OFDM Orthogonal Frequency Division Multiplexing
  • the duration (ie, chip period) T c of each chip in the UMTS system satisfies: Seconds, therefore the number of chips L that the UMTS system is capable of transmitting within the duration T 0 of each symbol in the LTE system satisfies:
  • the INT() indicates that the value in the parentheses is rounded up, and the rounding may be rounded up, rounded down, or rounded off, which is not limited in the embodiment of the present invention.
  • the symbols used by the downlink signals may also be OFDM symbols, and the subcarrier spacing in the NR system may be other values than the 15 kHz, for example, 3.75 kHz or 30 kHz.
  • the number of chips that the UMTS system can transmit varies during the duration of each symbol in the NR system. For example, when the subcarrier spacing of the NR system is 30 kHz, the number L of chips transmitted by the UMTS system during the duration of each useful OFDM symbol can be:
  • the method may be applied to the base station 01 of the first-standard communication system shown in FIG. 1, or may be applied to the first shown in FIG. 2.
  • the method may include:
  • Step 101 When the communication system of the first standard and the communication system of the second standard share the target frequency band, acquire at least one signal to be transmitted in the communication system of the first standard, and a spreading code corresponding to each signal to be transmitted.
  • the base stations of the two communication systems can transmit signals by using a shared preset frequency band, and the target frequency band can be the preset frequency band. It can be part of the frequency band in the preset frequency band.
  • the at least one to-be-sent signal in the first-standard communication system refers to a signal that the base station is to send to the terminal device, so that the terminal device receives and demodulates.
  • the spreading code corresponding to each of the to-be-transmitted signals may be selected by the base station of the first-standard communication system from the code table or the code tree, and the spreading codes corresponding to any two of the signals to be transmitted are orthogonal to each other.
  • the downlink signal may include signals on multiple common channels, as well as signals on multiple traffic channels.
  • the common channel may include a Synchronization Channel (SCH), a Primary Common Control Physical Channel (P-CCPCH), and a Primary Common Pilot Channel (P-CPICH);
  • the channel may include a Dedicated Physical Channel (DPCH), which may be used to transmit R99 service data such as Adaptive Multi Rate (AMR) voice. Since the signal on the SCH in the common channel does not need to be spread, the signal on the SCH may not need to be considered in the embodiment of the present invention.
  • DPCH Dedicated Physical Channel
  • FIG. 5 is a schematic diagram of a code channel used by a UMTS system according to an embodiment of the present invention.
  • a signal that a base station needs to transmit to a terminal device includes two common channels (P-CCPCH).
  • P-CCPCH common channels
  • the signal to be transmitted on the P-CPICH and the signal to be transmitted on the H' way traffic channel, that is, the (H'+2) way to be transmitted signal is included in the UMTS system.
  • the length of the spreading code corresponding to the to-be-transmitted signal on the common channel P-CCPCH and the P-CPICH is 256 (that is, the spreading factor SF is 256), and the extension corresponding to the to-be-transmitted signal on the H' way traffic channel
  • the spreading factor of the frequency code is 128.
  • each channel to be transmitted in the UMTS system can transmit 256 chips in the unit time in units of duration of each symbol in the LTE system.
  • the 256 chips included in the to-be-transmitted signal on the common channel are obtained by spreading a symbol by using a spreading code of length 256, and 256 codes included in the to-be-transmitted signal on each traffic channel.
  • the slice is obtained by spreading two symbols using a spreading code of length 128.
  • the symbol of the to-be-transmitted signal on the common channel P-CPICH transmitted in the unit time may include the symbol a
  • the symbol of the to-be-transmitted signal on the common channel P-CCPCH transmitted in the unit time may include
  • the signal to be transmitted on each traffic channel in the symbol b, H' traffic channel can transmit two symbols in the unit time.
  • the signal to be transmitted on the first traffic channel can transmit the symbol c in the unit time. symbols 11 and c 12, the first H 'road traffic channel signal to be transmitted in the unit time symbols and transmission symbols c H'1 c H'2. It can be seen from FIG.
  • the spreading code corresponding to the to-be-transmitted signal on the common channel P-CCPCH may be C 256,0 , that is, among the plurality of spreading codes with a spreading factor of 256, the 0th expansion
  • the frequency code; the spreading code corresponding to the signal to be transmitted on the common channel P-CPICH may be C 256,1 .
  • the spreading code corresponding to the first to-be-transmitted signal may be C 128, h1
  • the spreading code corresponding to the to-be-transmitted signal of the hi road may be C 128,hi , where hi is less than or equal to A positive integer of H'.
  • Step 102 Determine at least one scrambled signal, and a spreading code corresponding to each scrambled signal.
  • the base station in the first-standard communication system may first determine the number of channels of the scrambled signal, and the spreading code corresponding to each scrambled signal, and then calculate the power of the transmitted signal in the target frequency band per unit time.
  • the unit time may refer to the duration of each symbol in the communication system of the second system.
  • the transmitting signal may be that the signal to be transmitted of each of the at least one to-be-transmitted signal is spread, and each scrambled signal of the at least one scrambled signal is spread, and then spread.
  • the target frequency band belongs to a preset frequency band shared by the two communication systems, that is, the target frequency band may be part of the frequency band in the preset frequency band, or may be the preset frequency band.
  • the base station may determine, according to the power of the transmit signal in the target frequency band, the transmitted symbol of each scrambled signal in the unit time, and the determined scrambled signal may cause the transmit signal to be in the
  • the power in the target band is less than the original power.
  • the original power may be the power of the signal obtained by performing corresponding processing (for example, superimposition and scrambling) on the spread signal of at least one channel to be transmitted in the target frequency band. That is, by adding at least one scrambled signal, the power of the transmitted signal transmitted by the base station to the terminal device in the target frequency band can be reduced, thereby reducing interference with signals in the second-standard communication system.
  • the base station in the communication system of the first system can obtain the scheduling information of the communication system of the second system in real time or periodically, the scheduling The information may include the scheduling frequency band actually used by the communication system of the second system.
  • the base station in the first-standard communication system may determine the overlapping frequency band between the scheduled frequency band and the preset frequency band as the target frequency band. That is, in the process of sharing the spectrum, the first-standard communication system can select an appropriate scrambling signal according to the scheduling frequency band actually used by the communication system of the second system, so as to accurately reduce the communication system in the second system. Signal interference.
  • FIG. 6 is a flowchart of a method for determining at least one scrambling signal and a spreading code corresponding to each scrambling signal according to an embodiment of the present invention.
  • the method may include:
  • Step 1021 Determine the number N of the scrambled signals according to the number of idle spreading codes in the code table.
  • the number N of the scrambled signals may be less than or equal to the number of idle spreading codes remaining in the system.
  • the idle spreading code may be an available spreading code other than the spreading code corresponding to the signal to be transmitted in the code table. If the spreading code stored in the code table is an OVSF code as shown in FIG. 3, when one of the OVSF codes is selected as the spreading code of the signal to be transmitted, the SF derived from the OVSF code is used as the parent node. Larger OVSF codes will not be available.
  • the spreading factor of the spreading code corresponding to the signal to be transmitted on the two common channels is 256, and the spreading signal corresponding to the to-be-transmitted signal on the H' channel is transmitted.
  • the spreading factor of the code is 128.
  • the base station can determine that the number of idle spreading codes is 126, and the number of idle spreading codes is (128-H). '-1).
  • the base station can determine that the number N of the scrambled signals satisfies: N ⁇ (128-H'-1).
  • the base station may determine that when the at least one scrambled signal uses a spreading code with a spreading factor of 128, the number N of the scrambled signal should be less than or equal to 117; when the at least one scrambled signal is used When the spreading factor of the spreading factor is 256, the number N of the scrambled signals should be less than or equal to 234.
  • the at least one scrambling signal may also be divided into multiple groups, and different scrambling signal groups may use spreading codes of different spreading factors.
  • the number of scrambled signals included in each group of scrambled signal groups It should be less than the number of corresponding idle spreading codes.
  • Step 1022 Select N spreading codes that are in one-to-one correspondence with the N-channel scrambled signals from the idle spreading codes in the code table.
  • the base station may select a corresponding spreading code for each scrambling signal from the idle spreading code.
  • the base station may randomly select from the idle spreading code, or may also be selected from the idle spreading code in sequence, which is not limited in this embodiment of the present invention.
  • FIG. 7 is a schematic diagram of a code channel used in another UMTS system according to an embodiment of the present invention.
  • a spreading factor of a spreading code selected by a base station for the N-channel scrambled signal may be 128, and the nth (n' is a positive integer not greater than N) of the N-channel scrambled signal, the spreading code corresponding to the scrambling signal may be
  • the spreading code corresponding to the first scrambling signal is
  • the spreading code corresponding to the Nth scrambling signal is
  • Step 1023 Acquire a signal model of the transmitted signal in a unit time.
  • the base station in the first-standard communication system when transmitting a signal, needs to spread the frequency of each channel according to the spreading code corresponding to each channel signal, and then perform the multi-channel after the spreading.
  • the signal is processed to obtain a transmitted signal, which may include superposition and scrambling. Since it is necessary to consider the interference caused by the signal transmitted by the base station in the communication system of the first system to the signal in the communication system of the second system, the duration of each symbol in the communication system of the second system can be used as the unit time. Determine the symbol value of each scramble signal in the unit time.
  • the base station may determine that the number L of chips that can be transmitted in the unit time T 0 of each of the at least one to-be-transmitted signal satisfies:
  • the at least one signal to be transmitted may be divided into M groups of to-be-transmitted signal groups, wherein a spreading factor of the at least one channel to be transmitted signal included in each group of the to-be-transmitted signal group has equal spreading factors, and each group of signals to be transmitted corresponds to a signal group to be transmitted.
  • the spreading factors of the spreading codes are not equal.
  • ⁇ () represents the summation of the parameters in the parentheses
  • the column vector of L ⁇ 1 may refer to the column vector including the L row elements
  • V j is the L ⁇ composed of the spreading codes corresponding to the jth group of signals to be transmitted.
  • the yth column element in the matrix V' j is the spreading code corresponding to the y' way to be transmitted signal in the N j way to be transmitted signal included in the jth group to be transmitted signal group, and y' is not greater than N j Positive integer.
  • c j is a column vector of (k j ⁇ N j ) ⁇ 1 composed of the N j way to be transmitted signals included in the jth group to be transmitted signal group, and the column vector of (k j ⁇ N j ) ⁇ 1 includes k sequentially arranged in columns j-th sub-vector, each sub-vector may comprise elements N j, N j elements that may each be a symbol in the transmission signal path for the N j.
  • the number of chips L included in the transmission signal per unit time is 256
  • the UMTS system includes (H'+2) road to be transmitted signals. Since the spreading factor of the spreading code corresponding to the signal to be transmitted on the two common channels is 256, and the spreading factor of the spreading code corresponding to the signal to be transmitted on the H' channel is 128, the The H'+2) road to be transmitted signal can be divided into two groups, wherein the first group of to-be-transmitted signal groups includes two signals to be transmitted on the common channel, and the second group of to-be-transmitted signal groups includes the to-be-transmitted signal channel.
  • the spreading code corresponding to the to-be-transmitted signal on the common channel P-CCPCH, C 256,0 , and the spreading signal corresponding to the to-be-transmitted signal on the common channel P-CPICH The code is C 256,1 , and the two spreading codes can form a 256 ⁇ 2 matrix V′ 1 , and the first column element in the matrix V′ 1 can be 256 ⁇ which is composed of a spreading code C 256,0 .
  • the symbol a and the symbol b transmitted by the two signals to be transmitted included in the first group of signals to be transmitted in the unit time may constitute a 2 ⁇ 1 column vector c 1 , and the column vector c 1 satisfies:
  • T represents the transpose of the matrix
  • the spreading codes corresponding to the signals to be transmitted on the H' way traffic channel are respectively to
  • the H' spreading codes can form a 128 x H' matrix V' 2 .
  • the first column element in the matrix V' 2 may be a spreading code corresponding to the first path to be transmitted signal in the H' way to be transmitted signal.
  • each of the to-be-transmitted signals can transmit two symbols in the unit time, and then the H' way to be transmitted signals is composed of
  • the column vector c 2 of 2 ⁇ H') ⁇ 1 can satisfy:
  • the column vector c 2 may include two sub-vectors arranged in columns: [c 11 c 21 ... c H'1 ] T and [c 12 c 22 ... c H'2 ] T , wherein each of the H' elements included in each sub-vector may be one of the signals of the H' way to be transmitted.
  • the H' elements in the sub-vector [c 11 c 21 ... c H'1 ] T are in turn the first symbol transmitted by the signal to be transmitted in the H' way to be transmitted in the unit time.
  • the H' elements in T are in turn the second symbol transmitted by the signal to be transmitted in the H' way to be transmitted in the unit time.
  • V 1 c 1 + V 2 c 2 au 0 + bu 1 + V 2 c 2 Equation (6)
  • the base station may according to the type included in the processing, and the chips included in the unit time of the transmitting signal.
  • the number L determines that the signal model of the transmitted signal in the unit time may be an L ⁇ 1 column vector f, and the column vector f can satisfy:
  • S is a L ⁇ L scrambling code matrix
  • the scrambling code matrix is a diagonal matrix
  • a diagonal element of the lth row in the scrambling code matrix is a scrambling code corresponding to a lth chip in the L chips.
  • l is a positive integer not greater than L
  • the scrambling code may be predetermined by the base station.
  • g is an L ⁇ 1 column vector composed of L chips included in a unit time after superimposing at least one signal to be transmitted after spreading, and the expression can refer to the above formula (1).
  • w is the number of groups included in the N-channel scrambling signal, the spreading factor of the spreading code corresponding to at least one scrambling signal included in each group of scrambling signal groups is equal, and the spreading code corresponding to each group of scrambling signal groups The spreading factors are not equal.
  • W i is a L ⁇ (k i ⁇ N i ) spreading matrix composed of spreading codes corresponding to the i-th scrambling signal group, i is a positive integer not greater than w, and W i can satisfy: Indicates direct product, a unit matrix of k i order, W′ i is a matrix of l i ⁇ N i , and l i is a spreading factor of a spreading code corresponding to each scrambling signal in the i-th scrambled signal group, k i is the first The number of symbols transmitted by each scrambled signal in the i-group scrambled signal group per unit time.
  • the yth column element in the matrix W' i is a column vector composed of a spreading code corresponding to the y-channel scrambled signal in the N i channel scrambled signal included in the ith scrambling signal group, and y is not greater than N A positive integer of i .
  • (k i ⁇ N i) column vector x i is the i-th group comprising a group of scrambling signals
  • Luke scrambled signal N i ⁇ 1 is composed of, (k i ⁇ N i) ⁇ 1 column vector comprises a K i
  • the sub-vectors arranged in columns, the N i elements included in each sub-vector may respectively indicate one symbol in the N i way scrambled signal.
  • W' is a row of a total of w spread spectrum matrices corresponding to the sc group of scrambled signals.
  • the scrambling signal matrix, the scrambling signal matrix x' can be expressed as:
  • the spreading factor of the spreading code corresponding to the additional N-channel scrambling signal in the UMTS system is 128, and the number of symbols transmitted by each scrambling signal in unit time is 2,
  • the spreading codes corresponding to the N-channel scrambling signals are respectively to
  • the N spreading codes may form a 128 ⁇ N matrix W′ 1
  • the first column element in the matrix W′ 1 may be a spreading code corresponding to the first scrambling signal in the N channel scrambled signals.
  • the yth column element may be a spreading code corresponding to the y (the y is a positive integer not greater than N) path scrambling signal in the N-channel scrambled signal.
  • each scrambled signal can transmit two symbols in the unit time, and the (2 ⁇ N) ⁇ 1 column vector x 1 composed of the N-channel scrambled signal can be Satisfy:
  • the base station can determine that the signal model f of the transmitted signal in unit time satisfies according to the above formula (7):
  • FIG. 8 is a schematic diagram of another code channel used in a UMTS system according to an embodiment of the present invention.
  • a signal transmitted by a base station to a terminal device in a communication system of a first standard includes a signal to be transmitted on two common channels, and (H'+H") the signal to be transmitted on the traffic channel of the road, wherein the spreading factor of the to-be-transmitted signal on the two common channels has a spreading factor of 256, and the traffic channel on the H' channel is to be transmitted.
  • the spreading factor of the spreading code used by the signal is 128, and the spreading factor of the to-be-transmitted signal on the H" traffic channel is 64.
  • the spreading matrix V 1 corresponding to the first group of signals to be transmitted may refer to the above formula (2), and the spreading matrix V 2 corresponding to the second group of signals to be transmitted may refer to the above formula (4).
  • each spreading code can form a 128 ⁇ 1 column vector
  • the H” spreading codes can further form a 128 ⁇ H” matrix V′ 3 .
  • the L ⁇ (4 ⁇ H”) spreading matrix V 3 composed of the spreading codes corresponding to the third group of to-be-transmitted signal groups can satisfy:
  • each of the to-be-transmitted signals can transmit four symbols in the unit time, and the H” road is to be sent by the signal (4) ⁇ H") ⁇ 1 column vector c 3 can satisfy:
  • the H" elements included in each of the sub-vectors may be one of the symbols of the H" way to be transmitted, for example, the H' elements in the sub-vector [d 11 d 21 ...
  • the signal obtained by superimposing the spread signal (H'+H"+2) to be transmitted signal is composed of L chips included in the unit time.
  • the L ⁇ 1 column vector g can be expressed as:
  • the N-channel scrambling signals may also be divided into multiple groups.
  • the L ⁇ (2 ⁇ N′) spreading matrix W 1 composed of the spreading codes corresponding to the first group of scrambling signal groups can satisfy:
  • Each scrambling signal in the first set of scrambling signal groups can transmit two symbols in the unit time, and the (2 ⁇ N′) ⁇ 1 column vector x 1 composed of the first group of scrambled signal groups can be Satisfy:
  • the L ⁇ (4 ⁇ N”) spreading matrix W 2 composed of the spreading codes corresponding to the second set of scrambling signal groups can satisfy:
  • Each of the scrambled signals in the second set of scrambled signals can transmit four symbols at the unit time, and the (4 ⁇ N") ⁇ 1 column vector x 2 composed of the second set of scrambled signal groups can satisfy :
  • the column vector x 2 may include four sub-vectors arranged in columns: [e 11 e 21 ... e N"1 ] T , [e 12 e 22 ... e N" 2 ] T , [ e 13 e 23 ... e N" 3 ] T and [e 14 e 24 ... e N" 4 ] T .
  • the N" elements included in each of the sub-vectors may be one of the N" way scrambled signals, respectively.
  • the N" elements in the sub-vector [e 11 e 21 ... e N"1 ] T are, in turn, the first symbol transmitted by each scrambled signal in the N-channel scrambled signal in the unit time.
  • the N" elements in T are, in turn, the third symbol transmitted by each scrambled signal in the N" way scrambled signal within the unit time.
  • the base station can determine that the signal model f of the transmitted signal in the unit time satisfies according to the above formula (7):
  • the processing may further include: adopting The transmit shaping filter filters and oversamples based on the oversampling factor R, which is a positive integer.
  • the transmitted signal may include (L ⁇ R) chips in a unit time, and since the L ⁇ R chips are obtained by oversampling the L chips, the L ⁇ R after the oversampling is performed.
  • the chips can also be referred to as L x R sample values.
  • the base station can determine, according to the type of operation included in the processing, and the number of chips L ⁇ R included in the unit time of the transmission signal, the signal model of the transmitted signal in the unit time is (L ⁇ R) ⁇ 1.
  • Vector f', and the column vector f' satisfies:
  • H is a filter matrix of (L ⁇ R) ⁇ L, and other parameters in the formula (19) have the same meanings as corresponding parameters in the above formula (7), and are not described herein again.
  • the element H mn of the mth row and the nth column in the filter matrix H can satisfy:
  • RC 0 (t) is the unit impulse response function of the emission shaping filter used in the communication system of the first system
  • m is a positive integer not greater than (L ⁇ R)
  • n is a positive value not greater than L Integer.
  • the emission shaping filter may be a root-raised cosine (RRC) filter, and the unit impulse response function RC 0 (t) of the RRC filter can satisfy:
  • T c is the duration of each chip in the communication system of the first system
  • ⁇ is a preset roll-off coefficient.
  • the duration T c of each chip can satisfy: And the value of ⁇ can be 0.22.
  • the oversampling factor R when the oversampling factor R is equal to 1, it means that the chip sequence in the communication system of the first system is not oversampled, that is, the time domain signal in the communication system of the first system at this time.
  • the sampling interval ⁇ t is the duration T c of one chip.
  • the oversampling factor R is greater than 1, it is equivalent to sampling R times for each chip in the communication system of the first system, and the sampling interval ⁇ t is:
  • the unitary impulse response h(n) of the digital filter obtained after discretization of the transmit shaping filter satisfies:
  • the unit impulse response h(n) has a significant non-zero value only for a limited length.
  • the length of the unit impulse response h(n) can be truncated to 2L+1. Then, in the L chip sequences included in the transmission signal of the unit time, (R-1) 0s are added between each adjacent two chips, and then the unit impulse response is h(n). Filter, you can get A sample sequence that samples the sample interval.
  • the sampled value can constitute the column vector f' shown in the above formula (19).
  • Step 1024 Determine, according to the signal model, a power model of the transmitted signal in the target frequency band.
  • the base station may determine a power model of the transmitted signal in the target frequency band per unit time according to the signal model.
  • the process of determining the power model can include:
  • Step S1 Converting the signal model of the transmitted signal in a unit time to the frequency domain.
  • the base station may multiply the signal model by a preset frequency domain conversion matrix to convert the signal model from the time domain to the frequency domain.
  • the frequency domain conversion matrix F 1 may be an L ⁇ L matrix in which the matrix F 1 is converted.
  • the element of the m 2nd n 2 column may be Wherein m 2 satisfies: 1 ⁇ m 2 ⁇ L, and n 2 satisfies: 1 ⁇ n 2 ⁇ L.
  • the frequency domain conversion matrix F 2 may be L ⁇ R for both the number of rows and the number of columns (L ⁇ R) a matrix of ⁇ (L ⁇ R), in the frequency domain conversion matrix F 2 , the elements of the n 3th column of the m 3th row may be Wherein m 3 satisfies: 1 ⁇ m 3 ⁇ (L ⁇ R), and n 3 satisfies: 1 ⁇ n 3 ⁇ (L ⁇ R).
  • Step S2 Determine, according to the target frequency band, a row of a diagonal element having a value of 1 in a diagonal matrix of L' ⁇ L' whose diagonal element is 0 or 1.
  • the diagonal element having a value of 1 may be used to indicate a frequency domain sampling point located in the target frequency band among the frequency bands occupied by the transmission signal in the unit time.
  • L' may be the number of chips or sample values included in the transmitted signal in the unit time.
  • the base station when the base station determines the row of the diagonal element with the value of 1 in the diagonal matrix of the L′ ⁇ L′, the base station may first determine the first frequency band occupied by the communication system of the first standard.
  • the center frequency f0 is then determined by the lower limit frequency f1 of the target frequency band, the upper limit frequency f2 of the target frequency band, and the center frequency f0 of the first frequency band.
  • the center frequency f0 satisfies: f1 ⁇ f0 ⁇ f2, it can be determined that the diagonal element of the value 1 includes the first row to the first row Line, and Go to line L', where fs is the sampling frequency of the communication system of the first system.
  • the first-standard communication system is a UMTS system
  • the second-standard communication system is an LTE system.
  • the first frequency band occupied by the UMTS system is a frequency band of 0 to 5 MHz
  • the second frequency band occupied by the LTE system is a frequency band of 1 MHz to 4 MHz.
  • the second frequency band is also the preset frequency band shared by the UMTS system and the LTE system.
  • the center frequencies of the first frequency band and the second frequency band are equal, both being 2.5 MHz.
  • the base station may determine that the 256 ⁇ 256 diagonal matrix ⁇ 1, the value of the row diagonal elements comprising a row of first to Line (ie lines 1 to 91), and Go to line 256 (ie lines 167 to 256).
  • the L may be appropriately expanded.
  • the row of the diagonal elements having a value of 1 may further include: Go to the first Line, and / or, the first Go to the first Row.
  • the row of the diagonal element having a value of 1 may further include: Go to the first Line, and / or, the first Go to the first Row.
  • the row of the diagonal element having a value of 1 may further include Go to the first Line, and / or, the first Go to the first Row.
  • ⁇ 1, ⁇ 2, ⁇ 3, ⁇ 4, ⁇ 5, and ⁇ 6 are all positive integers, and ⁇ 1 to ⁇ 6 may be fixed values set in advance, or may be performed according to actual number of rows in the diagonal matrix of L′ ⁇ L′ Adjustment.
  • the row of diagonal elements having a value of 1 may include the first row to the first row.
  • Line ie lines 1 to 96
  • Go to line 256 ie lines 162 to 256).
  • the base station may first detect whether the target frequency band is a continuous frequency band, and if the target frequency band is detected, In the continuous frequency band, the row of the diagonal element having a value of 1 in the diagonal matrix can be determined directly according to the size of the lower limit frequency f1, the center frequency f0 and the upper limit frequency f2.
  • the base station may determine that the diagonal element is 0 or 1 according to each sub-band included in the target frequency band.
  • the base station can determine the behavior of the diagonal elements with a value of 1 in the diagonal matrix: the collection of the diagonal elements of each sub-band corresponding to the value of 1.
  • Step S3 Removing the line of the diagonal element of the L' ⁇ L' diagonal matrix, taking a value of 0, and generating a frequency band extraction matrix.
  • the generated band extraction matrix ⁇ may be a J ⁇ L matrix.
  • J is a positive integer not greater than L.
  • the generated band extraction matrix ⁇ 1 may be a matrix of J′ ⁇ (L ⁇ R). Where J' is a positive integer not greater than (L x R).
  • the diagonal matrix is a 256 ⁇ 256 matrix
  • the diagonal elements of the value 1 determined according to the target frequency band are in the first to 91st rows, and the 167th to 256th rows. Then, after removing the diagonal elements of the 256 ⁇ 256 diagonal matrix with a value of 0, a 181 ⁇ 256 band extraction matrix ⁇ can be obtained.
  • Step S4 determining a power model P of the transmitted signal in the target frequency band.
  • the base station may multiply the frequency band extraction matrix by the signal model converted to the frequency domain, so that the frequency domain sampling points located in the target frequency band may be extracted from the signal model of the transmitted signal.
  • the extracted frequency domain sampling point can satisfy:
  • the extracted frequency domain sampling point can satisfy:
  • the base station can calculate the power model P of the transmitted signal in the target frequency band in the unit time band according to the above formula (22) or (23).
  • the power model P can be expressed as:
  • the power model P can be expressed as:
  • Step 1025 Determine an N-channel scrambled signal according to the power model.
  • the base station When determining the N-channel scrambled signal, the base station tries to reduce the interference of the signal in the first-standard communication system to the signal in the second-standard communication system in order to ensure that the power of the transmitted signal in the target frequency band is as small as possible.
  • the symbol value of the scrambled signal can be adjusted to minimize the power of the power model P of the transmitted signal within the target frequency band for that unit of time.
  • the base station may calculate, when the total power of the N-channel scrambled signal is less than the first power threshold, the power of the power model is a minimum value, and each of the N-channel scrambled signals is in the unit time. The symbol value inside, so that the N-channel scrambled signal can be determined.
  • the first power threshold may be less than or equal to a difference between a maximum transmit power of the base station in the communication system of the first format and a total power of the at least one transmit signal to be transmitted.
  • the N-channel scrambled signal when transmitting the N-channel scrambled signal, it is necessary to ensure that the sum of the total power of the N-channel scrambled signal and the total power of at least one of the signals to be transmitted is not greater than the maximum transmit power of the base station in the UMTS system.
  • a constraint condition needs to be set to ensure that the total power of the N-channel scrambled signal in the unit time is less than The first power threshold P'.
  • the constraint can be expressed as:
  • the first power threshold P' may be less than or equal to a difference between a maximum transmit power of the base station and a total power of the at least one signal to be transmitted in the communication system of the first system. That is, when transmitting the N-channel scrambled signal, it is required to ensure that the sum of the total power of the N-channel scrambled signal and the total power of at least one of the signals to be transmitted is not greater than the maximum transmission of the base station in the communication system of the first standard. power.
  • the scrambling signal matrix composed of the N-channel scrambled signal determined by minimizing the above formula (24) can be expressed as:
  • the scrambling signal matrix composed of the N-channel scrambled signal determined by minimizing the above formula (25) can be expressed as:
  • argmin represents the value of the independent variable x' when the power model P takes the smallest value.
  • KKT Karush-Kuhn-Tucker
  • a H represents the conjugate matrix of matrix A
  • ⁇ is a Lagrangian multiplier
  • ⁇ 0 is a parameter value such that x' satisfies the constraint condition shown by the formula (26), and I is an identity matrix.
  • ⁇ 0 is a parameter value such that x' satisfies the constraint condition shown by the formula (26)
  • I is an identity matrix.
  • the best ⁇ 0 can be found by the dichotomy.
  • x' is the solution of the above formula (33) and x' is the least squares solution of the above formula (34). Therefore, the scrambling signal matrix composed of the N-channel scrambled signals can be known. x' may be the least squares solution of the above formula (34).
  • the power of the power model P may be reduced by a certain ratio with respect to the original power, for example, It can be reduced to 80% of the original power, or 90% of the original power, etc., as long as the power of the power model P is less than the original power, which is not limited by the embodiment of the present invention.
  • Step 103 Perform spreading on each of the to-be-transmitted signals by using a spreading code corresponding to each of the to-be-transmitted signals in the at least one to-be-transmitted signal.
  • the base station may multiply each of the to-be-transmitted signals by its corresponding spreading code, thereby implementing spreading of the signal to be transmitted for each channel.
  • Step 104 Perform spreading on each scrambled signal by using a spreading code corresponding to each scrambled signal in the at least one scrambled signal.
  • the base station After determining, by the base station, the symbol value of each scrambled signal in the unit time and the spreading code corresponding to each scrambled signal, the base station can respectively spread each scrambled signal with its corresponding spread spectrum The codes are multiplied, thereby achieving spreading of each scrambled signal.
  • Step 105 Process at least one channel to be transmitted after spreading and at least one channel of scrambled signal after spreading to obtain a transmission signal.
  • the base station may process the spread spectrum of at least one to-be-transmitted signal and the spread-timed at least one scrambled signal to obtain a transmit signal, and the column vector formed by the chip included in the unit time It can be as shown in the above formula (7).
  • the processing may include superposition and scrambling.
  • the base station may further detect, before processing the spread signal signal, whether the first sampling frequency of the baseband signal in the communication system of the first standard is smaller than the second sampling frequency of the baseband signal in the communication system of the second standard. .
  • the base station may also determine The sampling factor R, which may be greater than or equal to two. For example, the product of the oversampling factor R and the first sampling frequency can be equal to the second sampling frequency.
  • the base station may determine that the oversampling factor R is equal to 1, that is, the baseband signal may not need to be oversampled.
  • the process of processing the spreaded at least one to-be-transmitted signal and the at least one scrambled signal may further include: filtering by using a transmit shaping filter, and oversampling according to the oversampling factor R.
  • the column vector composed of the L ⁇ R sample values included in the unit time obtained by the processed transmission signal may be as shown in the above formula (19).
  • Step 106 Send the transmission signal.
  • the first system of communication systems can transmit the transmitted signal to the terminal device. Since the value of the transmitted signal in the target frequency band is smaller than the original power, the interference to the signal in the communication system of the second standard can be effectively reduced.
  • the terminal device may perform descrambling and despreading the transmitting signal to obtain the at least one signal to be transmitted. Since the scrambled signal in the transmitted signal is used to adjust power, but is not used to transmit information to the terminal device, the terminal device may not need to process the scrambled signal.
  • the communication system of the first standard is a UMTS system
  • the communication system of the second standard is an LTE system
  • the frequency bands occupied by the communication systems of the two standards are as shown in the figure.
  • the preset frequency band shared by the communication systems of the two systems is a frequency band of 3 MHz from 1 MHz to 4 MHz.
  • the scheduling frequency band actually used by the LTE system is a frequency band of 1.15 MHz to 3.85 MHz
  • the target frequency band is also a frequency band of 1.7 MHz from 1.15 MHz to 3.85 MHz, that is, the target frequency band is centered in the first frequency band occupied by UMTS. 2.7MHz band.
  • the transmitting signal sent by the base station in the UMTS system to the terminal device includes 127 scrambling signals, and the spreading factor of the spreading code used by the 127 channel scrambling signals is 128, the transmitting signal sent by the base station in the UMTS
  • the power spectral density (PSD) can be as shown in FIG.
  • the power spectral density shown in FIG. 10 is obtained by transforming the spectrum of the signal into a low-pass frequency band.
  • the frequency point 0 is equivalent to the center frequency f0 of the first frequency band
  • the frequency band is -1.35. MHz to 1.35MHz is equivalent to the target frequency band. Comparing the two curves shown in FIG. 10, it can be seen that after adding at least one scramble signal, the total power of the transmitted signal transmitted by the base station is increased, but the power on the target frequency band is significantly reduced.
  • the amplitude of the transmitted signal in the target frequency band and the number of the scrambled signal, the spreading factor of the spreading code used for scrambling the signal, and the pre-determination can be determined. It is related to parameters such as power threshold. Since the scheduling frequency band of the LTE system includes the target frequency band, the power of the target frequency band is reduced, which reduces the interference of the transmitted signal sent by the base station in the UMTS system to the signal in the LTE system.
  • the communication system of the first standard is a UMTS system
  • the communication system of the second standard is an LTE system
  • the frequency bands occupied by the communication systems of the two standards are as follows: As shown in FIG. 11, the second frequency band occupied by the LTE system is located in the first frequency band occupied by the UMTS system, that is, the preset frequency band shared by the communication systems of the two systems is part of the first frequency band. However, the center frequency of the preset frequency band is not equal to the center frequency of the first frequency band. If the target frequency band is 0.65MHz to 3.35MHz, a total of 2.7MHz frequency band.
  • the base station may determine, according to the method shown in the foregoing step S2, the row of the diagonal element with the value of 1 according to the target frequency band, and further determine the frequency band extraction matrix.
  • the process of determining the at least one scrambled signal reference may be made to the foregoing embodiment, and details are not described herein again.
  • the communication system of the first system is a UMTS system
  • the communication system of the second system is an LTE or NR system
  • the frequency bands occupied by the communication systems of the two systems are as shown in the figure. 12, as can be seen from FIG. 12, after the communication systems of the two systems share the spectrum, the frequency bands occupied by the communication systems of the two systems partially overlap, and the second frequency band occupied by the communication system of the second system
  • the bandwidth may be greater than the bandwidth of the first frequency band occupied by the communication system of the first standard.
  • the bandwidth of the first frequency band is 5 MHz
  • the bandwidth of the second frequency band may be 5 MHz, or may be 10 MHz or 20 MHz.
  • the base station in the UMTS system can determine that the diagonal element of the value 1 includes the first row to the first row. Line (ie line 1 to line 153), and Go to line 256 (ie line 196 to line 256). Then, after the base station removes the diagonal elements in the diagonal matrix with a value of 0, the band extraction matrix can be obtained. Finally, the base station can calculate the scrambled signal matrix with reference to equation (27) above.
  • FIG. 13 is a schematic diagram of power spectral density of a transmitted signal transmitted by a base station in another UMTS according to an embodiment of the present invention. Also shown in FIG. 13 is the power spectral density when the scrambled signal is not included in the transmitted signal transmitted by the base station. Similarly, the power spectral density shown in FIG. 13 is also obtained by transforming the spectrum of the signal into the low-pass band, that is, in the spectrum shown in FIG. 13, the frequency point 0 is equivalent to the center frequency f0 of the first frequency band, and the frequency band is -0.915MHz to 2.28MHz is equivalent to the target frequency band. Comparing the two curves shown in Fig.
  • the operator can deploy a larger bandwidth non-UMTS system (such as an LTE system or an NR system, etc.).
  • a single-path channel is used between a base station and a terminal device in a UMTS system, the performance of the UMTS system is not affected by changes in its power spectral density.
  • the UMTS system is a multipath channel between the base station and the terminal equipment, the inter-path interference of the UMTS system will increase due to the change of its power spectral density, but has little effect on the overall performance of the UMTS system.
  • the communication system of the first standard is a UMTS system
  • the communication system of the second standard is an LTE system or an NR system
  • the communication systems of the two systems share the spectrum.
  • the frequency band is shown in Figure 14. It can be seen from FIG. 14 that the bandwidth of the first frequency band occupied by the communication system of the first standard and the bandwidth of the second frequency band occupied by the communication system of the second standard are both 5 MHz, and the communication systems of the two standards are The occupied frequency bands coincide, that is, the first-standard communication system shares the first frequency band occupied by it as a preset frequency band to the communication system of the second standard.
  • the transmitting end of the signal in the UMTS system can filter the signal through the RRC transmit shaping filter, the spectrum of the transmitted signal transmitted by the base station drops rapidly, and the base station can sample the baseband at a sampling frequency of 3.84 MHz.
  • the transmitting end of the signal adopts a rectangular shaping filter, and the spectrum of the signal transmitted by the base station drops slowly.
  • the sampling frequency of the baseband signal of the LTE system or the NR system with a system bandwidth of 5 MHz is generally 7.68 MHz.
  • the base station of the UMTS system can oversample the baseband signal so that its sampling frequency also reaches 7.68 MHz.
  • the base station can determine a diagonal element having a value of 1 in a diagonal matrix of (L ⁇ R) ⁇ (L ⁇ R) according to the above step S2.
  • the line includes: Line 1 to Line (ie line 1 to line 37), and Go to line 512 (ie lines 477 to 512).
  • the range of the diagonal element of the value of 1 can be appropriately expanded, so that the UMTS system can make more bandwidth to the subcarrier of the LTE system.
  • the row of diagonal elements having a value of 1 may include the first row to the first row.
  • Line (ie lines 1 to 41), and By line 256 (i.e., lines 473 to 512) the UMTS system can be allowed to give up the bandwidth of 4 subcarriers on both the left and right sides of the scheduling band.
  • the base station removes the diagonal elements in the diagonal matrix with a value of 0, the band extraction matrix can be obtained.
  • the base station can calculate the scrambled signal matrix with reference to equation (27) above.
  • the second-standard communication system in which the operator deploys the 5 MHz system bandwidth can utilize the first system more effectively than the system in which only the 3 MHz system is deployed.
  • the signal processing method provided by the embodiment of the present invention may further include:
  • Step 107 Determine a first frequency band occupied by the communication system of the first standard, and a second frequency band occupied by the communication system of the second standard.
  • the bandwidth of the first frequency band occupied by the communication system of the first standard may be 5 MHz, which is occupied by the communication system of the second standard.
  • the bandwidth of the second frequency band can be 3 MHz.
  • Step 108 If the second frequency band is located in the first frequency band, when transmitting the signal of the communication system of the second standard, the transmission shaping filter of the communication system of the first standard is used for the communication system of the second standard The signal is processed and sent.
  • the signal when the base station in the first-standard communication system transmits a signal, the signal may be filtered by using a transmit shaping filter, and the power spectral density of the filtered signal is faster at the edge of the spectrum. .
  • the emission shaping filter When the second frequency band is located in the first frequency band, the emission shaping filter has less influence on the signal of the communication system of the second system, so the second generation of the transmission system of the communication system of the first system can be used for the second
  • the signals of the standard communication system are processed and transmitted, so that the efficiency of signal processing and transmission can be effectively improved, and the cost can be reduced.
  • FIG. 16 is a schematic diagram of power spectral density of a transmitted signal in a UMTS system and an LTE system according to an embodiment of the present invention.
  • the square of the amplitude-frequency response of the transmit shaping filter (or receive filter) used in the UMTS system has the same shape as the power spectral density of the transmitted signal transmitted by the base station in the UMTS system.
  • the power spectral density of the transmitted signal in the LTE system has dropped by about 30 decibels (dB). Therefore, if the signal in the LTE system is filtered by the transmit shaping filter or the receive filter in the UMTS system, the influence on the LTE signal of the 3 MHz system bandwidth is small.
  • the transmit filter in the base station is generally implemented in the RRU, the signal of the second-standard communication system is also transmitted through a transmit shaping filter, meaning that the baseband signal of the second-standard communication system can be It is superimposed with the baseband signal of the first-standard communication system, and then transmitted through the same RRU, thereby effectively reducing the cost of signal processing.
  • the base station may further filter the transmit signal by using a narrow bandwidth filter, and then send the filtered transmit signal.
  • the narrow bandwidth filter may include any one of a band pass filter, a band rejection filter, a high pass filter, and a low pass filter.
  • the narrow bandwidth filter can suppress the power of the transmitted signal transmitted by the base station in the stop band portion of the narrow bandwidth filter. Since the power of the transmitted signal transmitted by the base station is smaller in the stop band portion of the narrow bandwidth filter, the frequency band of the stop band portion of the narrow bandwidth filter can be used as the scheduling frequency band of the communication system of the second standard.
  • the base station of the communication system of the first standard can acquire the scheduling frequency band of the communication system of the second standard, and can determine the part of the scheduling frequency band that overlaps with the passband of the narrow bandwidth filter. For this target band. That is, for the frequency band that is not suppressed by the narrow bandwidth filter, the power of the target frequency band can be adjusted by adding at least one scrambling signal, thereby effectively reducing the interference of the signal of the second standard communication system. .
  • the second-standard communication system is an LTE system
  • the downlink signals of the LTE system generally include a cell-specific reference signal (CRS) and a physical HARQ (hybrid automatic repeat request) indicating channel.
  • CRS cell-specific reference signal
  • HARQ hybrid automatic repeat request
  • PHICH Physical Hybrid-ARQ Indicator Channel
  • PCFICH Physical Control Format Indicator Channel
  • CSI-RS Channel State Information Reference Signal
  • the power spectral density of the UMTS signal is adjusted by adding at least one scrambling signal, so that the transmit signal transmitted by the base station in the UMTS system is in the CRS, PHICH, PCFICH or CSI-RS of the LTE.
  • the power in the scheduling band is smaller, so that interference can be effectively reduced.
  • the base station in the UMTS system can determine the overlapping frequency band and the passband overlap portion as the target frequency band.
  • the target frequency band can include a plurality of dispersed sub-bands.
  • the base station of the UMTS system may refer to the method shown in the foregoing step S2, and calculate, according to the multiple sub-bands included in the target frequency band, the row of the diagonal elements corresponding to each sub-band corresponding to the value of 1 in the diagonal matrix. And determining, in the respective sub-bands, the collection of the diagonal elements of the diagonal value of 1 corresponding to the row of the diagonal elements in the diagonal matrix.
  • the base station determines a diagonal element with a value of 1 according to the method shown in the foregoing step S2, and the 12 In the sub-band, the line spacing of the diagonal elements determined by the adjacent two sub-bands is 1 and the line spacing is 3.
  • the diagonal element of the value 1 determined according to the first sub-band may be the second row, and the diagonal element of the value determined by the second sub-band may be the fifth row.
  • the collection of the diagonal elements of the value determined by the 12 sub-bands may be expressed as: ⁇
  • ⁇ 2+3 ⁇ , ⁇ is an integer, and 0 ⁇ 11 ⁇ .
  • the base station can transmit 7 OFDM symbols per slot, of which only the first and fifth OFDM symbols have CRS. If the base station in the UMTS system does not need to always send a scrambled signal, the base station may send the CRS when the CRS is sent in the LTE system according to the acquired scheduling information of the LTE system. The signal is scrambled all the way to avoid excessively increasing the transmit power of the UMTS system.
  • the process of protecting the PCIFICH, the PHICH, and the CSI-RS in the LTE system by adding at least one scrambling signal is similar to the above process of protecting the CRS, and details are not described herein again.
  • the flexibility of the signal processing method is improved, and the communication system of the second system can be accurately protected.
  • the single or a few subcarriers in the system effectively improve the performance of the communication system of the two systems.
  • each symbol may further include a Cyclic Prefix (CP), and when calculating the duration of each symbol in the communication system of the second system, It is generally the duration of each useful symbol (ie, the symbol that does not consider the CP). Therefore, in the duration of a useful symbol in the communication system of the second system, there may be a start transmission time of the useful symbol and a start of the first chip sequence of a certain signal in the communication system of the first system.
  • CP Cyclic Prefix
  • the transmission timings are inconsistent, in order to accurately calculate the power of the transmitted signal during the duration of each symbol, thereby accurately reducing the interference of the communication system of the first system to the signal in the communication system of the second system, it may be considered The case where the initial transmission time is inconsistent.
  • the communication system of the first system is a UMTS system
  • the communication system of the second system is an LTE system or an NR system
  • the communication system of the second system includes a CP in each OFDM symbol, regardless of the second standard.
  • FIG. 18 is a schematic diagram of correspondence between OFDM symbols in an LTE system and a chip sequence in a UMTS system in a time domain according to an embodiment of the present invention.
  • a CP is added to each OFDM symbol, and the CP is added.
  • the correspondence between the OFDM symbol and the chip sequence in UMTS i.e., a sequence composed of a plurality of chips obtained by spreading one symbol
  • Each chip sequence shown in Figure 18 may include 256 chips or 128 chips.
  • the chip sequence of length 256 is obtained by spreading a symbol by using a spreading code with a spreading factor of 256.
  • the chip sequence of length 128 is a spreading code with a spreading factor of 128 for one symbol. After the spread spectrum is obtained.
  • the base station after determining, by using the method shown in the foregoing step 1021, the base station determines the spreading code corresponding to each channel scrambling signal, and when acquiring the transmission signal in the unit time, the base station may also perform the communication system according to the second standard.
  • the duration of each symbol determines the spreading code that is actually used by each scrambled signal and each of the signals to be transmitted when the duration of the symbol is in units of time.
  • the process of determining the spreading code actually used by each channel signal may be as shown in FIG. 19, and the method may include:
  • Step 1023a Obtain a starting transmission time of each symbol in the communication system of the second system.
  • the base station of the communication system of the first system can obtain the initial transmission time of one symbol in the communication system of the second system through a preset interface. For example, the base station can acquire the synchronization information of the communication system of the second system synchronously. The initial transmission time of a symbol in the communication system of the second system. And, the base station can determine the initial transmission time of each symbol according to the CP length of each symbol and the duration of the useful symbol in the communication system of the second system.
  • Step 1023b Detecting a start transmission time of the first symbol in the communication system of the second system, and a start transmission time of the first chip sequence transmitted by each of the spread signals in the duration of the first symbol. The first time difference.
  • the first symbol may be any symbol in the communication system of the second system, and each chip sequence is a sequence consisting of multiple chips obtained by spreading one symbol.
  • the first chip sequence may refer to a chip sequence corresponding to the first symbol transmitted by each signal during the duration of the first symbol.
  • the initial transmission time of the first symbol refers to the initial transmission time when the first symbol does not consider the CP.
  • FIG. 20 is a schematic diagram of correspondence between different symbols in a LTE system and a chip sequence in a UMTS system in a time domain according to an embodiment of the present invention.
  • the first symbol in the LTE system is the symbol A
  • the signal to be transmitted on the two common channels in the UMTS system is within the unit time when the duration of the symbol A is in unit time.
  • a chip sequence of length 256 may be separately transmitted, and each of the to-be-transmitted signal and the N-channel scrambled signal on the H' way traffic channel may respectively transmit two chip sequences of length 128 in the unit time.
  • the initial transmission time of the first chip sequence transmitted by each channel in the unit time coincides with the initial transmission time of the symbol A. Therefore, the base station of the UMTS system can determine the symbol A and each channel signal. The first time difference between them is zero.
  • the base station of the UMTS system can determine that the first time difference between the symbol C and the signal to be transmitted on each traffic channel is 0, and between each of the symbol C and the N channel scrambled signal The first time difference is zero.
  • the signals to be transmitted on the two common channels can respectively transmit two chip sequences within the duration of the symbol C, but only half of the chips can be transmitted per chip sequence. That is, the initial transmission time of the first chip sequence transmitted by the to-be-transmitted signal on the two common channels during the duration is inconsistent with the initial transmission time of the symbol C. Therefore, the base station of the UMTS system can It is determined that the first time difference between the symbol C and the signal to be transmitted on each common channel is not zero.
  • Step 1023c If the first time difference between the initial transmission time of the first symbol and the initial transmission time of the first chip sequence in the first path signal is not equal to 0, calculate the first one transmitted in the first time difference.
  • the number of chips of the chip sequence is n 0 .
  • the base station may calculate, according to the first time difference ⁇ t and the chip period t c in the UMTS system, the number of chips n 0 that the first path signal can transmit in the first time difference,
  • the number of chips n 0 can satisfy:
  • the base station may determine that the number of chips n 0 in the first chip sequence transmitted by the to-be-transmitted signal on each common channel within the first time difference ⁇ t is:
  • n if the value that is found is not an integer, it can also be used as the number of chips n 0 of the value after rounding.
  • the rounding may be rounded up or down, which is not limited by the embodiment of the present invention.
  • Step 1023d Determine, according to the number of chips n 0 , a spreading code used by each channel in the signal group to which the first path signal belongs.
  • the base station may determine, according to the number n 0 of the chip, a symbol indicated by the first chip sequence transmitted by the signal of the first path in the duration of the signal.
  • the spreading code includes: the n 0 +1 to the 1st element in the spreading code corresponding to the any of the signals, and can determine the symbol indicated by the last chip sequence of the any signal transmitted during the duration
  • the spreading code used includes: 1st to (L'+n 0 )%l' elements in the spreading code corresponding to any one of the signals, and l' is an extension of the spreading code corresponding to the first path signal
  • the frequency factor, L' is the number of chips that the transmitted signal includes in the unit time, and % indicates the remainder.
  • the base station may determine that the spreading code corresponding to the symbol indicated by the other chip sequence is the spreading code corresponding to the any channel signal.
  • the spreading factor corresponding to the to-be-transmitted signal on the common channel P-CCPCH and the P-CPICH in the first group of to-be-transmitted signal groups has a spreading factor of 256
  • the signal to be transmitted on each common channel is The number of chips n 0 of the first chip sequence transmitted in the first time difference ⁇ t is 128.
  • the symbol indicated by the first chip sequence transmitted by the to-be-transmitted signal on the common channel P-CCPCH during the duration of the symbol C is the symbol b 1
  • the base station can determine that the symbol b 1 is in the symbol C.
  • the spreading code used for the duration is the 129th to 256th elements of the spreading code C 256,0
  • the spreading code used by the symbol b 2 for the duration of the symbol C is the spreading code C 256 1 , the first to the (256+128)% 256 elements (ie, the first to the 128th elements); similarly, the base station can determine the signal to be transmitted on the common channel P-CPICH, where the symbol a 1 is
  • the spreading code used for the duration of the symbol C is the 129th to 256th elements of the spreading code C 256,1
  • the spreading code used by the symbol a 2 for the duration of the symbol C is the spreading code.
  • C 256 1st to 128th elements.
  • the signal obtained by superimposing the spread (H'+2) path to be transmitted signal represented by the above formula (7) is composed of L chips included in the duration of the symbol C.
  • the L ⁇ 1 column vector g can be expressed as:
  • u i (m 4 :n 4 ) in the formula (36) may represent a column vector composed of elements of the m 4th to nth 4th rows in the column vector u i , and the value of i in the formula (36) is 0 or 1.
  • the process of determining the spreading code used by the first path signal in the duration according to the number of chips n 0 in the foregoing step 1023c may also be implemented by the following method. :
  • Step C1 Determine (k' i ⁇ l') ⁇ (k' i ⁇ ) that the diagonal element is 0 or 1 according to the number of chips L′ included in the unit time and the number of chips n 0 of the transmitted signal.
  • the diagonal element with a value of 1 is in the (n 0 +1)th to the (n 0 +L')th row.
  • k' i is the number of symbols transmitted by the first path signal during the duration of the first symbol
  • l' is a spreading factor of the spreading code corresponding to the first path signal
  • the first symbol is the symbol B shown in FIG. 20, and the signals to be transmitted on the two common channels can respectively transmit two chip sequences during the duration of the symbol B, on the H' way traffic channel.
  • Each of the to-be-transmitted signal and the N-channel scrambled signal may respectively transmit three chip sequences.
  • each of the multi-path to-be-transmitted signal and the multi-channel scrambled signal, the initial transmission time of the first chip sequence transmitted during the duration of the symbol B and the initial transmission time of the symbol B The first time difference between the two is equal, and the number of chips transmitted by each channel in the first time difference is n 0 .
  • Step C2 removing the diagonal matrix of the (k' i ⁇ l') ⁇ (k' i ⁇ l'), taking the diagonal element of the value 0, generating L' ⁇ (k' i ⁇ l' The chip extraction matrix K.
  • the base station removes the first to 128th lines of the diagonal elements with a value of 0, and after the 385th to the 512th lines, A 256 x 512 chip extraction matrix K.
  • Step C3 Determine a spreading matrix W' i composed of a spreading code corresponding to the signal group to which the first path signal belongs.
  • the spreading matrix W 'i satisfy:
  • V′ i is a matrix of l′ ⁇ N′ i
  • the y′ column element of the matrix V′ i is the N′ i channel signal included in the signal group to which the first path signal belongs.
  • the y 'signals corresponding to the spreading code, y' is not greater than N 'i is a positive integer.
  • each group of to-be-transmitted signal groups can be determined by using the above formula (37) and A spreading matrix corresponding to each set of scrambled signal groups.
  • the base station can determine the composition of the spreading code corresponding to the first group of signals to be transmitted.
  • spreading matrix W 'i satisfies:
  • the chip extraction matrix K is a matrix of 256 ⁇ 512.
  • the base station can determine that the diagonal matrix of the diagonal element is 0 or 1 has a dimension of (3 ⁇ 128) ⁇ (3 ⁇ 128), that is, The diagonal matrix has a dimension of 384 x 384. And the base station can determine that the diagonal element with the value of 1 in the diagonal matrix is in the (n 0 +1)th to the (n 0 +256)th row. Further, the base station removes the first to 128th lines of the diagonal elements having a value of 0 in the diagonal matrix of 384 ⁇ 384, and after the 385th to the 512th lines, a 256 ⁇ 384 chip extraction matrix K can be obtained.
  • the base station may determine that the spreading matrix W′ i composed of the spreading codes corresponding to the second group of to-be-transmitted signal groups satisfies:
  • the chip extraction matrix K is a matrix of 256 ⁇ 384.
  • the spreading factor l' of the corresponding spreading code is 128, so the base station can determine that the diagonal matrix of the diagonal element is 0 or 1 has a dimension of (3 ⁇ 128) ⁇ (3 ⁇ 128), and can determine the diagonal In the matrix, the diagonal element with a value of 1 is in the (n 0 +1)th to the (n 0 +256)th row. Further, the base station removes the first to 128th lines of the diagonal elements having a value of 0 in the diagonal matrix of 384 ⁇ 384, and after the 385th to the 512th lines, a 256 ⁇ 384 chip extraction matrix K can be obtained.
  • the base station may determine the scrambling signal corresponding to the group consisting of a spreading code spreading matrix W 'i satisfies:
  • the chip extraction matrix K is a matrix of 256 ⁇ 384.
  • the base station can calculate the column vector formed by the chip included in the transmission signal in the unit time according to the above formula (7) or formula (19), and then calculate the transmission of each scramble signal in the unit time. Symbol value.
  • the spreading code used for calculating the duration of the symbol D in the duration of the symbol D can be referred to the foregoing embodiment, and details are not described herein again.
  • the base station of the first-standard communication system can detect the traffic volume in real time during the process of sending a signal, for example, the number of idle spreading codes in the system and the signal to be sent can be detected. Power.
  • the base station detects that the number of idle spreading codes in the communication system of the first standard is less than a preset threshold, or detects that the power of the to-be-transmitted signal is greater than the second power threshold, the base station may be configured to the base station of the second-standard communication system.
  • the indication information is used to indicate that the base station of the communication system of the second mode allows the frequency band to be scheduled in the preset frequency band, and the bandwidth of the allowed scheduling frequency band may be smaller than the bandwidth of the preset frequency band, or the indication information may also be
  • the base station for indicating the communication system of the second system stops transmitting signals during the preset time period.
  • the first-standard communication system can directly stop spectrum sharing. Thereby, it is possible to avoid affecting the normal transmission of signals in the communication system of the first system.
  • a base station in a UMTS system wants to page a terminal device, the base station needs to send a signal through a Paging Indicator Channel (PICH) (the SF of the spreading code corresponding to the PICH may be 256).
  • PICH Paging Indicator Channel
  • AICH Acquisition Indicator Channel
  • the base station also needs to pass an E-DCH (Enhanced Dedicated Channel) absolute grant channel (E-DCH Absolute Grant).
  • E-DCH Enhanced Dedicated Channel
  • E-DCH Absolute Grant E-DCH Absolute Grant
  • E-HICH transmits a signal, where the SF of the spreading code corresponding to the E-AGCH may be 256, and the SF of the spreading code corresponding to the E-RGCH and the E-HICH may be 128.
  • the base station of the UMTS system may stop spectrum sharing; or may send through the physical channel.
  • the communication system of the second system is instructed to stop transmitting the signal by the system information.
  • the embodiment of the present invention provides a signal processing method, in which a base station in a first-standard communication system can determine at least one scrambling signal when sharing a preset frequency band with another standard communication system, and The scrambled signal and the to-be-transmitted signal in the system are processed and sent to the terminal device.
  • the scrambled signal can cause the transmit signal sent by the base station to be less than the original power in the target frequency band (the target frequency band belongs to the preset frequency band). Therefore, on the basis of improving the spectrum utilization rate, the interference of the transmission signal transmitted by the communication system of the first system to the signal in the communication system of the second system can be effectively reduced.
  • FIG. 21 is a schematic structural diagram of a signal processing apparatus according to an embodiment of the present invention.
  • the signal processing apparatus may be configured in any base station in the implementation environment shown in FIG. 1 or FIG. 2, and may implement the foregoing embodiments.
  • Signal processing method. As shown in FIG. 21, the apparatus may include:
  • the first obtaining module 201 can be used to implement the method shown in step 101 in the embodiment shown in FIG. 4 above.
  • the first determining module 202 can be used to implement the method shown in step 102 in the embodiment shown in FIG. 4 above.
  • the first spreading module 203 can be used to implement the method shown in step 103 in the embodiment shown in FIG. 4 above.
  • the second spreading module 204 can be used to implement the method shown in step 104 of the embodiment shown in FIG. 4 above.
  • the processing module 205 can be used to implement the method shown in step 105 in the embodiment shown in FIG. 4 above.
  • the first sending module 206 can be used to implement the method shown in step 106 in the embodiment shown in FIG. 4 above.
  • FIG. 22 is a schematic structural diagram of a first determining module according to an embodiment of the present invention. As shown in FIG. 22, the first determining module 202 may include:
  • the first determining sub-module 2021 can be used to implement the method shown in step 1021 in the embodiment shown in FIG. 6 above.
  • the sub-module 2022 can be used to implement the method shown in step 1022 in the embodiment shown in FIG. 6 above.
  • the obtaining sub-module 2023 can be used to implement the method shown in step 1023 in the embodiment shown in FIG. 6 above.
  • the second determining sub-module 2024 can be used to implement the method shown in step 1024 in the embodiment shown in FIG. 6 above.
  • the third determining sub-module 2025 can be used to implement the method shown in step 1025 in the embodiment shown in FIG. 6 above.
  • the third determining submodule 2025 can be used to:
  • each scrambled signal in the N-channel scrambled signal is in the unit time Symbol value.
  • FIG. 23 is a schematic structural diagram of another signal processing apparatus according to an embodiment of the present invention. As shown in FIG. 23, the apparatus may further include:
  • the first detecting module 207 is configured to detect whether the first sampling frequency of the baseband signal in the communication system of the first system is smaller than the second sampling frequency of the baseband signal in the communication system of the second system.
  • the second determining module 208 is configured to determine that the oversampling factor R is an integer greater than or equal to 2 when the first sampling frequency is less than the second sampling frequency.
  • the third determining module 209 is configured to determine that the oversampling factor R is 1 when the first sampling frequency is not less than the second sampling frequency.
  • the second determining sub-module 2024 determines, in the diagonal matrix that the diagonal element is 0 or 1, the row of the diagonal elements having a value of 1 may include:
  • the center frequency f0 satisfies: f1 ⁇ f0 ⁇ f2, it is determined that the diagonal element of the value 1 includes the first row to the first row Line, and Going to the L'th row, where fs is the sampling frequency of the first-standard communication system, where L' is the total number of rows included in the diagonal matrix;
  • the second determining submodule 2024 is further configured to:
  • determining the row of the diagonal element having a value of 1 further includes: Go to the first Line, and / or, the first Go to the first Row;
  • determining the row of the diagonal element having a value of 1 further includes: Go to the first Line, and / or, the first Go to the first Row;
  • determining the row of the diagonal element having a value of 1 further includes Go to the first Line, and / or, the first Go to the first Row; wherein ⁇ 1, ⁇ 2, ⁇ 3, ⁇ 4, ⁇ 5, and ⁇ 6 are all positive integers.
  • the second determining submodule 2024 can be used to:
  • the second determining sub-module 2024 determines the lower limit frequency f1 of the target frequency band, the upper limit frequency f2 of the target frequency band, and the center frequency f0 of the first frequency band, including:
  • the target frequency band is a continuous frequency band, determining a lower limit frequency f1 of the target frequency band, an upper limit frequency f2 of the target frequency band, and a center frequency f0 of the first frequency band;
  • the second determining sub-module 2024 can also be used to:
  • the combination of the rows of the diagonal elements corresponding to each sub-band in the target frequency band is determined to be the row of the diagonal elements with the value of 1 in the diagonal matrix of which the diagonal element is 0 or 1.
  • the base station of the first-standard communication system is further configured to send a signal of the second-standard communication system, as shown in FIG. 23, the device may further include:
  • the fourth determining module 210 is configured to determine, when sharing the preset frequency band, the first frequency band occupied by the communication system of the first standard and the second frequency band occupied by the communication system of the second standard when the communication system of the two standards is shared .
  • the first sending module 206 is further configured to: if the second frequency band is located in the first frequency band, when transmitting the signal of the second standard communication system, adopting a transmit shaping filter of the communication system of the first standard The signal of the communication system of the second system is processed and transmitted.
  • FIG. 24 is a schematic structural diagram of still another signal processing apparatus according to an embodiment of the present invention. As shown in FIG. 24, the apparatus may further include:
  • the second obtaining module 211 is configured to acquire scheduling information of the communications system of the second system, where the scheduling information includes a scheduling frequency band of the communications system of the second standard.
  • the fifth determining module 212 is configured to determine the target frequency band according to the scheduling frequency band and the preset frequency band, where the target frequency band includes an overlapping frequency band between the scheduling frequency band and the preset frequency band.
  • the first sending module 206 can be used to:
  • the transmitted signal is filtered and transmitted using a narrow bandwidth filter including any one of a band pass filter, a band stop filter, a high pass filter, and a low pass filter.
  • the apparatus may further include:
  • the sixth determining module 213 is configured to determine, in the scheduling frequency band, a portion overlapping the passband of the narrow bandwidth filter as the target frequency band.
  • the obtaining sub-module 2023 is further configured to implement the method shown in step 1023a to step 1023d in the foregoing embodiment shown in FIG.
  • the apparatus may further include:
  • the second sending module 214 is configured to: when the number of idle spreading codes in the communication system of the first mode is less than a preset threshold, or the power of the to-be-transmitted signal is greater than the second power threshold, to the second system
  • the base station of the communication system sends the indication information
  • the indication information is used to indicate that the base station of the communication system of the second system is within the preset frequency band, or the indication information is used to indicate that the base station of the second system of the communication system stops within a preset time period. Send a signal.
  • the embodiment of the present invention provides a signal processing apparatus, where a base station in a first-standard communication system can determine at least one scrambled signal when sharing a preset frequency band with another standard communication system, and The scrambled signal and the to-be-transmitted signal in the system are processed and sent to the terminal device.
  • the scrambled signal can cause the transmit signal sent by the base station to be less than the original power in the target frequency band (the target frequency band belongs to the preset frequency band). Therefore, on the basis of improving the spectrum utilization rate, the interference of the transmission signal transmitted by the communication system of the first system to the signal in the communication system of the second system can be effectively reduced.
  • FIG. 25 is a schematic diagram showing the hardware structure of a signal processing apparatus according to an embodiment of the present application.
  • the signal processing device can be configured in any of the base stations in the implementation environment shown in FIG. 1 or 2.
  • the apparatus can include a processor 402, a transceiver 404, a plurality of antennas 406, a memory 408, an I/O (Input/Output) interface 410, and a bus 412.
  • Memory 408 can be used to store instructions 4082 and data 4084.
  • processor 402, transceiver 404, memory 408, and I/O interface 410 are communicatively coupled to one another via a bus 412, and a plurality of antennas 406 are coupled to transceiver 404.
  • connection manner between the processor 402, the transceiver 404, the memory 408, and the I/O interface 410 shown in FIG. 25 is merely exemplary.
  • the processor 402, the transceiver 404, Memory 408 and I/O interface 410 may also be communicatively coupled to each other using other connections than bus 412.
  • the processor 402 can be a general purpose processor, which can be a processor that performs specific steps and/or operations by reading and executing instructions (eg, instructions 4082) stored in a memory (eg, memory 408), general processing Data (e.g., data 4084) stored in a memory (e.g., memory 408) may be used in performing the above steps and/or operations.
  • a general purpose processor may be, for example but not limited to, a Central Processing Unit (CPU).
  • processor 402 may also be a special purpose processor, which may be a specially designed processor for performing specific steps and/or operations, such as, but not limited to, a digital signal processor ( Digital Signal Processor (DSP), Application Specific Integrated Circuit (ASIC), and Field Programmable Gate Array (FPGA).
  • DSP Digital Signal Processor
  • ASIC Application Specific Integrated Circuit
  • FPGA Field Programmable Gate Array
  • processor 402 can also be a combination of multiple processors, such as a multi-core processor.
  • the processor 402 can include at least one circuit to perform the steps of the signal processing method in the above embodiments.
  • the transceiver 404 is configured to transceive signals.
  • the transceiver 404 transmits and receives signals through at least one of the plurality of antennas 406.
  • the memory 408 may be various types of storage media, such as random access memory (RAM), ROM, non-volatile RAM (NVRAM), programmable ROM (Programmable ROM, PROM), Erasable PROM (EPROM), electrically erasable PROM (EEPROM), flash memory, optical memory, and registers.
  • RAM random access memory
  • ROM read-only memory
  • NVRAM non-volatile RAM
  • PROM programmable ROM
  • EPROM Erasable PROM
  • EEPROM electrically erasable PROM
  • flash memory optical memory
  • registers optical memory
  • the memory 408 is specifically configured to store instructions 4082 and data 4084.
  • the processor 402 is a general purpose processor, the processor 402 can perform specific steps and/or operations by reading and executing the instructions 4082 stored in the memory 408.
  • Data 4084 may be required during the above steps and/or operations.
  • the I/O interface 410 is for receiving instructions and/or data from peripheral devices and outputting instructions and/or data to
  • the processor 402 can be used to perform, for example, without limitation, baseband related processing, and the transceiver 404 can be used to perform, for example, without limitation, radio frequency transceiving.
  • the above devices may be respectively disposed on chips independent of each other, or may be disposed at least partially or entirely on the same chip.
  • the processor 402 can be further divided into an analog baseband processor and a digital baseband processor, wherein the analog baseband processor can be integrated on the same chip as the transceiver 404, and the digital baseband processor can be disposed on a separate chip. With the continuous development of integrated circuit technology, more and more devices can be integrated on the same chip.
  • a digital baseband processor can be combined with a variety of application processors (such as but not limited to graphics processors, multimedia processors, etc.) Integrated on the same chip.
  • application processors such as but not limited to graphics processors, multimedia processors, etc.
  • Such a chip can be referred to as a system on chip. Separate devices on different chips or integrated on one or more chips often depends on the specific needs of the product design.
  • the embodiment of the invention further provides a computer readable storage medium, wherein the computer readable storage medium stores instructions, when the computer readable storage medium is run on a computer, causing the computer to execute the signal processing method in the above embodiment A step of.
  • the embodiment of the present invention further provides a computer program product comprising instructions, when the computer program product is run on a computer, causing the computer to perform the steps of the signal processing method in the above embodiment.
  • the embodiment of the present invention further provides a chip, which can be configured in a base station of a communication system of a first standard, the chip includes programmable logic circuits and/or program instructions, and is used to implement the above embodiment when the chip is running. Signal processing method.
  • the embodiment of the present invention further provides a signal processing system.
  • the system may include: a base station and at least one terminal device 02.
  • the base station may include the signal processing device shown in any of FIG. 21 and FIG. 23 to FIG. 25, and the signal processing device may further include the first determining module shown in FIG.

Landscapes

  • Engineering & Computer Science (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Signal Processing (AREA)
  • Mobile Radio Communication Systems (AREA)

Abstract

本申请提供了一种信号处理方法、装置及系统，属于通信领域，该方法包括：在第一制式的通信系统与第二制式的通信系统共享目标频段时，第一制式的通信系统的基站获取第一制式的通信系统中至少一路待发送信号，以及每一路待发送信号对应的扩频码；确定至少一路加扰信号，以及每一路加扰信号对应的扩频码；根据至少一路待发送信号和至少一路加扰信号中每一路信号对应的扩频码，对每一路信号进行扩频；对扩频后的多路信号进行处理得到发射信号并发送，该发射信号在该目标频段内的功率小于仅对扩频后的至少一路待发送信号进行所述处理后得到的信号在该目标频段内的功率，因此可以有效降低该发射信号对该第二制式的通信系统中的信号的干扰。

Description

信号处理方法、装置及系统
本申请要求于2017年12月20日提交的申请号为201711387988.1、发明名称为“信号处理方法、装置及系统”的中国专利申请的优先权，其全部内容通过引用结合在本申请中。
技术领域
本申请涉及通信领域，特别涉及一种信号处理方法、装置及系统。
背景技术
随着移动通信产业的快速发展，传统的3G移动通信系统的用户逐渐向4G乃至5G移动通信系统迁移，由此使得传统通信系统的频谱越来越空闲，而新部署的通信系统(例如4G移动通信系统)的频谱越来越紧张，导致频谱资源不能合理有效的利用。其中，3G移动通信系统一般包括通用移动通信系统(Universal Mobile Telecommunications System，UMTS)，4G移动通信系统一般为长期演进(Long-Term Evolution，LTE)系统。
相关技术中，一般采用频谱共享的方法来提高频谱资源的利用率。例如，当UMTS系统的基站检测到某段时间内其业务量较低，而LTE系统的业务量较高时，则该UMTS的基站可以去激活UMTS系统中的空闲频段，该去激活的空闲频段可以供LTE系统使用。
但是，当UMTS系统中不存在空闲频段时，将无法实现频谱共享；若将该UMTS系统非空闲的频段与LTE系统共享，该UMTS系统通过该非空闲的频段发送的信号将会对LTE系统中的信号造成干扰。
发明内容
本申请提供了一种信号处理方法、装置及系统，可以解决相关技术中两种制式的通信系统共享频谱时存在信号干扰的问题，技术方案如下：
第一方面，提供了一种信号处理方法，该方法可以应用于第一制式的通信系统中的基站，该方法可以包括：
在第一制式的通信系统与第二制式的通信系统共享目标频段时，获取该第一制式的通信系统中至少一路待发送信号，以及每一路待发送信号对应的扩频码；确定至少一路加扰信号，以及每一路加扰信号对应的扩频码；之后可以采用每一路待发送信号对应的扩频码，对每一路待发送信号进行扩频，并可以采用每一路加扰信号对应的扩频码，对每一路加扰信号进行扩频；最后对扩频后的至少一路待发送信号和扩频后的至少一路加扰信号进行处理得到发射信号，并发送该发射信号。其中，该处理可以包括叠加和加扰，且该处理后得到的发射信号在该目标频段内的功率小于原始功率，该原始功率为仅对扩频后的至少一路待发送信号进行处理后得到的信号在该目标频段内的功率，该目标频段属于该两种制式的通信系统所共享的预设频段。
本申请提供的信号处理方法中，第一制式的通信系统中的基站在发送待发送信号时，通过增加至少一路加扰信号，使得基站发送的发射信号在目标频段内的功率小于原始功率，从而可以有效降低该发射信号对该第二制式的通信系统中的信号的干扰。
可选的，第一制式的通信系统中的基站确定至少一路加扰信号，以及每一路加扰信号对应的扩频码的过程可以包括：
根据码表中空闲扩频码的数量，确定加扰信号的路数N，该加扰信号的路数N小于或等于该空闲扩频码的数量，该空闲扩频码不包括系统中待发送信号所对应的扩频码；
之后，即可从码表中的空闲扩频码中选取与N路加扰信号一一对应的N个扩频码，例如，基站可以随机选取N个扩频码，或者也可以顺序选取N个扩频码；
获取发射信号在单位时间内的信号模型，该单位时间可以为该第二制式的通信系统中每个符号的持续时间，且该单位时间可以为第二制式的通信系统中子载波间隔的倒数；
确定该信号模型在该目标频段内的功率功率，并根据该功率模型确定该N路加扰信号，该N路加扰信号可以使得该功率模型在该目标频段内的功率小于该原始功率。
可选的，基站根据该功率模型确定N路加扰信号的过程可以包括：
在该N路加扰信号在该单位时间内的总功率小于第一功率阈值的前提下，计算该功率模型的功率为最小值时，该N路加扰信号中每一路加扰信号在该单位时间内的符号值。其中，该第一功率阈值可以小于或等于第一制式的通信系统中，基站的最大发射功率与该至少一路待发送信号的总功率之间的差值。
可选的，该处理可以包括叠加和加扰，获取该的该发射信号在单位时间内可以包括的L个码片，该L可以满足：
Figure PCTCN2018120708-appb-000001
T 0为该单位时间，T c为该第一制式的通信系统的码片周期，INT()表示对括号内的数值取整，例如可以是向上取整、向下取整或者四舍五入取整等；基站根据处理包括的操作类型，以及发射信号在单位时间内包括的码片个数L，可以确定该信号模型为L×1的列向量f，该列向量f可以满足：
Figure PCTCN2018120708-appb-000002
其中，S为L×L的扰码矩阵，该扰码矩阵为对角矩阵，且该扰码矩阵中第l行的对角元素为该L个码片中第l个码片对应的扰码，l为不大于L的正整数，g为对扩频后的至少一路待发送信号进行叠加后得到的信号在该单位时间内所包括的L个码片所组成的L×1的列向量，w为N路该加扰信号所包括的组数，每组加扰信号组所包括的至少一路加扰信号对应的扩频码的扩频因子相等，各组加扰信号组对应的扩频码的扩频因子的不相等，W i为第i组加扰信号组对应的扩频码组成的L×(k i×N i)的扩频矩阵，i为不大于w的正整数，且W i满足：
Figure PCTCN2018120708-appb-000003
表示直积，
Figure PCTCN2018120708-appb-000004
为k i阶单位矩阵，W' i为l i×N i的矩阵，l i为第i组加扰信号组中每一路加扰信号所对应的扩频码的扩频因子，k i为该第i组加扰信号组中每一路加扰信号在该单位时间内所传输的符号的个数，矩阵W' i中的第y列元素为该第i组加扰信号组所包括的N i路加扰信号中，第y路加扰信号对应的扩频码组成的列向量，y为不大于N i的正整数，x i为第i组加扰信号组包括的N i路加扰信号所组成的(k i×N i)×1的列向量，该(k i×N i)×1的列向量包括k i个按列排列的子向量，每个子向量包括的N i个元素分别指示该N i路加扰信号中的一个符号，W'为w组加扰信号组对应的共w个扩频矩阵按行排列所组成的
Figure PCTCN2018120708-appb-000005
的组合扩频矩阵，x'为w组加扰信号组按列排列所组成的
Figure PCTCN2018120708-appb-000006
的加扰信号矩阵；
相应的，基站根据信号模型，确定发射信号在该目标频段内的功率模型可以包括：
根据该目标频段，确定对角元素为0或1的L×L的对角矩阵中，取值为1的对角元素所在行；
去除该对角矩阵中，取值为0的对角元素所在行，生成J×L的频段提取矩阵Λ，J为不大于L的正整数；
根据信号模型，确定发射信号在该目标频段内的功率模型P，该功率模型P满足：
P＝||ΛF 1f|| 2＝||ΛF 1SW′x′+ΛF 1Sg|| 2，其中，F 1为L×L的频域转换矩阵，||·||表示向量的欧式范数；
计算N路加扰信号中每一路加扰信号在该单位时间内的符号值的过程可以包括：
根据该功率模型P，确定该N路加扰信号组成的加扰信号矩阵x'，该加扰信号矩阵x'可以满足：
Figure PCTCN2018120708-appb-000007
其中，P'为该第一功率阈值。
可选的，基站对扩频后的至少一路待发送信号以及至少一路加扰信号所进行的处理还可以包括：采用发射成型形滤波器滤波，以及根据过采样因子R进行过采样，R为正整数；此时，发射信号在单位时间内包括L×R个码片，L满足：
Figure PCTCN2018120708-appb-000008
T 0为单位时间，T c为第一制式的通信系统的码片周期，INT()表示对括号内的数值取整。
基站根据处理包括的操作类型，以及发射信号在单位时间内包括的码片个数L×R，确定信号模型为(L×R)×1的列向量f'，该列向量f'满足：
Figure PCTCN2018120708-appb-000009
其中，S为L×L的扰码矩阵，该扰码矩阵为对角矩阵，且该扰码矩阵中第i行的对角元素为L个码片中第i个码片对应的扰码，g为对扩频后的至少一路待发送信号进行叠加后得到的信号在单位时间内所包括的L个码片所组成的L×1的列向量，w为N路加扰信号所包括的组数，每组加扰信号组所包括的至少一路加扰信号对应的扩频码的扩频因子相等，各组加扰信号组对应的扩频码的扩频因子的不相等，W i为第i组加扰信号组对应的扩频码组成的L×(k i×N i)的扩频矩阵，i为不大于w的正整数，且W i满足：
Figure PCTCN2018120708-appb-000010
表示直积，
Figure PCTCN2018120708-appb-000011
为k i阶单位矩阵，W' i为l i×N i的矩阵，l i为第i组加扰信号组中每一路加扰信号所对应的扩频码的扩频因子，k i为第i组加扰信号组中每一路加扰信号在单位时间内所传输的符号的个数，矩阵W' i中的第y列元素为第i组加扰信号组所包括的N i路加扰信号中，第y路加扰信号对应的扩频码组成的列向量，y为不大于N i的正整数，x i为第i组加扰信号组包括的N i路加扰信号所组成的(k i×N i)×1的列向量，(k i×N i)×1的列向量包括k i个按列排列的子向量，每个子向量包括的N i个元素分别指示N i路加扰信号中的一个符号，W'为w组加扰信号组对应的共w个扩频矩阵按行排列所组成的
Figure PCTCN2018120708-appb-000012
的组合扩频矩阵，x'为w组加扰信号组按列排列所组成的
Figure PCTCN2018120708-appb-000013
的加扰信号矩阵；H为(L×R)×L的滤波矩阵，滤波矩阵H中的第m行第n列的元素H mn满足：
Figure PCTCN2018120708-appb-000014
其中，RC 0(t)为发射成型滤波器的单位冲激响应函数，m为不大于(L×R)的正整数，n为不大于L的正整数。
根据信号模型，确定发射信号在该目标频段内的功率模型，包括：
根据目标频段，确定对角元素为0或1的(L×R)×(L×R)的对角矩阵中，取值为1的对角元素所在行；
去除(L×R)×(L×R)的对角矩阵中，取值为0的对角元素所在行，生成J'×(L×R)的频段提取矩阵Λ 1，J'为不大于(L×R)的正整数；
根据信号模型，确定发射信号在该目标频段内的功率模型P，功率模型P可以满足：
P＝||Λ 1F 2f'|| 2＝||Λ 1F 2HSW'x'+Λ 1F 2HSg|| 2，其中，F 2为(L×R)×(L×R)的频域转换矩阵，||·||表示向量的欧式范数；
计算N路加扰信号中每一路加扰信号在单位时间内的符号值的过程可以包括：
根据该功率模型P，确定该N路加扰信号组成的加扰信号矩阵x'，该加扰信号矩阵x'可以满足：
Figure PCTCN2018120708-appb-000015
其中，P'为第一功率阈值。
可选的，基站在对扩频后的至少一路待发送信号以及扩频后的至少一路加扰信号进行处理之前，还可以检测该第一制式的通信系统中基带信号的第一采样频率是否小于该第二制式的通信系统中基带信号的第二采样频率；
当该第一采样频率小于该第二采样频率时，为了更好的匹配该第二采样频率，基站可以确定该过采样因子R为大于或等于2的整数，例如该过采样因子R可以满足：第一采样频率与过采样因子R的乘积等于该第二采样频率。
当该第一采样频率不小于该第二采样频率时，基站可以确定该过采样因子R为1，也即是无需对基带信号进行过采样。
可选的，基站在确定对角元素为0或1的对角矩阵中，取值为1的对角元素所在行时，可以先确定该第一制式的通信系统所占用的第一频段的中心频率f0，并判断该目标频段的下限频率f1、该目标频段的上限频率f2和该第一频段的中心频率f0三者的大小；
当该中心频率f0满足：f1＜f0≤f2时，可以确定取值为1的对角元素所在行包括第1行至第
Figure PCTCN2018120708-appb-000016
行，以及第
Figure PCTCN2018120708-appb-000017
行至第L'行，其中fs为该第一制式的通信系统的采样频率，其中，L'为该对角矩阵所包括的总行数；
当该中心频率f0满足：f0＞f2时，可以确定取值为1的对角元素所在行包括第
Figure PCTCN2018120708-appb-000018
Figure PCTCN2018120708-appb-000019
行至第
Figure PCTCN2018120708-appb-000020
行；
当该中心频率f0满足：f0≤f1时，可以确定取值为1的对角元素所在行包括第
Figure PCTCN2018120708-appb-000021
Figure PCTCN2018120708-appb-000022
行至第
Figure PCTCN2018120708-appb-000023
行。
进一步的，当该中心频率f0满足：f1＜f0≤f2时，取值为1的对角元素所在行还可以包括：第
Figure PCTCN2018120708-appb-000024
行至第
Figure PCTCN2018120708-appb-000025
行，和/或，第
Figure PCTCN2018120708-appb-000026
Figure PCTCN2018120708-appb-000027
行至第
Figure PCTCN2018120708-appb-000028
行；
当该中心频率f0满足：f0＞f2时，取值为1的对角元素所在行还可以包括：第
Figure PCTCN2018120708-appb-000029
Figure PCTCN2018120708-appb-000030
行至第
Figure PCTCN2018120708-appb-000031
行，和/或，第
Figure PCTCN2018120708-appb-000032
行至第
Figure PCTCN2018120708-appb-000033
行；
当该中心频率f0满足：f0≤f1时，取值为1的对角元素所在行还可以包括第
Figure PCTCN2018120708-appb-000034
Figure PCTCN2018120708-appb-000035
行至第
Figure PCTCN2018120708-appb-000036
行，和/或，第
Figure PCTCN2018120708-appb-000037
行至第
Figure PCTCN2018120708-appb-000038
Figure PCTCN2018120708-appb-000039
行；
其中，Δ1、Δ2、Δ3、Δ4、Δ5和Δ6均为正整数。
可选的，基站在判断该目标频段的下限频率f1、该目标频段的上限频率f2和该第一频段的中心频率f0三者的大小之前，还可以检测该目标频段是否为连续频段；
当该目标频段为连续频段时，再判断该目标频段的下限频率f1、该目标频段的上限频率f2和该第一频段的中心频率f0三者的大小；
当该目标频段不为连续频段时，即当该目标频段包括多个子频段时，基站可以先参考上述方法分别确定该目标频段中每个子频段对应的取值为1的对角元素所在行；然后可以将该目标频段中各个子频段对应的取值为1的对角元素所在行的合集，确定为该对角元素为0或 1的对角矩阵中，取值为1的对角元素所在行。
可选的，如果该第一制式的通信系统的基站还用于发送该第二制式的通信系统的信号，则该信号处理方法还可以包括：
确定该第一制式的通信系统所占用的第一频段，以及该第二制式的通信系统所占用的第二频段；
若该第二频段位于该第一频段内，在发送该第二制式的通信系统的信号时，采用该第一制式的通信系统的发射成型滤波器对该第二制式的通信系统的信号进行处理后发送。
由于当第二频段位于该第一频段内，该第一制式的通信系统中的发射成型滤波器对该第二制式的通信系统的信号的影响较小，因此可以采用该发射成型滤波器对该第二制式的通信系统的信号进行处理后发送，从而可以有效提高信号处理和发送的效率，降低成本。
可选的，第一制式的通信系统与第二制式的通信系统共享的频段可以为预设频段，基站在确定至少一路加扰信号之前，还可以先获取该第二制式的通信系统的调度信息，该调度信息可以包括该第二制式的通信系统的调度频段；之后，基站可以将该调度频段和该预设频段之间的重叠频段确定为该目标频段。
也即是，基站可以根据第二制式的通信系统实际使用的调度频段确定目标频段，并降低发射信号在该目标频段内的功率，从而可以在有效降低对第二制式的通信系统中信号的干扰的前提下，避免过多增加发射功率。
可选的，基站在发送该发射信号时，还可以采用窄带宽滤波器对该发射信号进行滤波后发送，该窄带宽滤波器可以包括带通滤波器、带阻滤波器、高通滤波器和低通滤波器中的任一种；
相应的，基站在确定至少一路加扰信号之前，还可以获取该第二制式的通信系统的调度信息，该调度信息可以包括该第二制式的通信系统的调度频段；之后，基站可以将该调度频段中与该窄带宽滤波器的通带重叠的部分确定为该目标频段。
在该信号处理方法中，基站可以采用该窄带宽滤波器对发射信号在部分频段的功率进行抑制，对于该窄带宽滤波器没有抑制的频段，可以采用增加至少一路加扰信号的方式，对该目标频段的功率进行调整，不仅可以有效降低对第二制式的通信系统的信号的干扰，并且提高了信号处理的灵活性。
可选的，该方法还可以包括：
获取该第二制式的通信系统中每个符号的起始传输时刻；
检测该第二制式的通信系统中第一符号的起始传输时刻，与扩频后的每一路信号在该第一符号的持续时间内传输的首个码片序列的起始传输时刻的第一时间差，其中每个码片序列是对一个符号进行扩频后得到的多个码片所组成的序列；
若该第一符号的起始传输时刻与第一路信号中首个码片序列的起始传输时刻的第一时间差不等于0，计算在该第一时间差内所传输的该首个码片序列的码片个数n 0；
根据该码片个数n 0，确定该第一路信号所属的信号组中，每一路信号在该持续时间内采用的扩频码；
其中，该第一路信号所属的信号组中，任一路信号在该持续时间内传输的首个码片序列指示的符号所采用的扩频码包括：该任一路信号对应的扩频码中第n 0+1至第l'个元素，该任一路信号在该持续时间内传输的最后一个码片序列指示的符号所采用的扩频码包括：该任一路信号对应的扩频码中第1至第(L'+n 0)％l'个元素，l'为该第一路信号对应的扩频码的扩频因子，L'为该发射信号在该单位时间内包括的码片个数，％表示取余数。
本申请提供的信号处理方法，可以根据该第二制式的通信系统中每个符号的起始传输时刻与该第一制式的通信系统中对应码片序列的起始传输时刻的时间差，确定每一路信号在该符号的持续时间内实际采用的扩频码，从而可以精确计算得到发射信号在该持续时间内的功率，进而可以精准降低第一制式的通信系统对该第二制式的通信系统中的信号的干扰，提高了信号处理的精度。
其中，基站根据该码片个数n 0，确定该第一路信号所属的信号组中，每一路信号在该持续时间内采用的扩频码的过程可以包括：
根据该发射信号在该单位时间内包括的码片个数L'，以及该码片个数n 0，确定对角元素为0或1的(k' i×l')×(k' i×l')的对角矩阵中，取值为1的对角元素所在行包括第(n 0+1)行至第(n 0+L')行，k' i为该第一路信号在该第一符号的持续时间内所传输的符号的个数，l'为该第一路信号对应的扩频码的扩频因子；
去除该(k' i×l')×(k' i×l')的对角矩阵中，取值为0的对角元素所在行，生成L'×(k' i×l')的码片提取矩阵K；
确定该第一路信号所属的信号组对应的扩频码组成的扩频矩阵W' i满足：
Figure PCTCN2018120708-appb-000040
Figure PCTCN2018120708-appb-000041
其中，
Figure PCTCN2018120708-appb-000042
为k' i阶单位矩阵，V' i为l'×N' i的矩阵，且矩阵V' i中第y'列元素为该第一路信号所属的信号组包括的N' i路信号中，第y'路信号对应的扩频码组成的列向量，y'为不大于N' i的正整数。
可选的，该方法还可以包括：
当检测到该第一制式的通信系统中空闲扩频码的数量小于预设个数阈值，或者待发送信号的功率大于第二功率阈值时，可以向该第二制式的通信系统的基站发送指示信息，该指示信息可以用于指示该第二制式的通信系统的基站在两种制式的通信系统所共享的预设频段内的允许调度频段，或者，该指示信息可以用于指示该第二制式的通信系统的基站在预设时间段内停止发送信号。
其中，该允许调度频段的带宽可以小于该预设频段的带宽，由此可以避免在第一制式的通信系统的业务量较大时，第二制式的通信系统对该第一制式的通信系统的信号收发造成影响，保证该第一制式的通信系统能够正常工作。
第二方面，提供了一种信号处理装置，该装置可以应用于第一制式的通信系统的基站，该装置可以包括：至少一个模块，该至少一个模块可以用于实现上述第一方面所提供的信号处理方法。
第三方面，提供了一种信号处理装置，该装置可以应用于第一制式的通信系统的基站，该装置可以包括：处理器、收发器以及存储器；该处理器、收发器以及存储器可以用于实现上述第一方面所提供的信号处理方法。
第四方面，提供了一种计算机可读存储介质，该计算机可读存储介质中存储有指令，当该计算机可读存储介质在计算机上运行时，可以使得计算机执行上述第一方面所提供的信号处理方法。
第五方面，提供了一种包含指令的计算机程序产品，当该计算机程序产品在计算机上运 行时，可以使得计算机执行上述第一方面所提供的信号处理方法。
第六方面，提供了一种芯片，该芯片可以配置于第一制式的通信系统的基站中，该芯片包括可编程逻辑电路和/或程序指令，当该芯片运行时用于实现上述第一方面所提供的信号处理方法。
第七方面，提供了一种信号处理系统，该系统可以包括：基站和至少一个终端设备；
该基站可以包括上述第二方面或第三方面所提供的信号处理装置。
综上所述，本申请提供了一种信号处理方法、装置及系统，第一制式的通信系统中的基站可以在与其他制式的通信系统共享目标频段时，确定至少一路加扰信号，并对该加扰信号和系统中的待发送信号进行处理后发送至终端设备，由于该加扰信号可以使得基站发送的发射信号在该目标频段内的功率小于原始功率，因此可以有效降低该发射信号对该第二制式的通信系统中的信号的干扰。
附图说明
图1是本发明实施例提供的一种信号处理系统的架构图；
图2是本发明实施例提供的另一种信号处理系统的架构图；
图3是本发明实施例提供的一种正交可变扩频因子码的码树示意图；
图4是本发明实施例提供的一种信号处理方法的流程图；
图5是本发明实施例提供的一种UMTS系统所使用的码道的示意图；
图6是本发明实施例提供的一种确定至少一路加扰信号，以及每一路加扰信号对应的扩频码的方法流程图；
图7是本发明实施例提供的另一种UMTS系统中使用的码道的示意图；
图8是本发明实施例提供的又一种UMTS系统中使用的码道的示意图；
图9是本发明实施例提供的一种UMTS系统以及LTE系统所占用的频段的示意图；
图10是本发明实施例提供的一种UMTS中基站发送的发射信号的功率谱密度的示意图；
图11是本发明实施例提供的另一种UMTS系统以及LTE系统所占用的频段的示意图；
图12是本发明实施例提供的又一种UMTS系统以及LTE系统所占用的频段的示意图；
图13是本发明实施例提供的另一种UMTS中基站发送的发射信号的功率谱密度的示意图；
图14是本发明实施例提供的再一种UMTS系统以及LTE系统所占用的频段的示意图；
图15是本发明实施例提供的另一种信号处理方法的流程图；
图16是本发明实施例提供的一种UMTS系统以及LTE系统中发射信号的功率谱密度的示意图；
图17是本发明实施例提供的一种目标频段的示意图；
图18是本发明实施例提供的一种LTE系统中的OFDM符号与UMTS系统中的码片序列在时域内的对应关系示意图；
图19是本发明实施例提供的一种确定每一路信号实际使用的扩频码的方法流程图；
图20是本发明实施例提供的一种LTE系统中不同符号与UMTS系统中码片序列在时域内的对应关系示意图；
图21是本发明实施例提供的一种信号处理装置的结构示意图；
图22是本发明实施例提供的一种第一确定模块的结构示意图；
图23是本发明实施例提供的另一种信号处理装置的结构示意图；
图24是本发明实施例提供的又一种信号处理装置的结构示意图；
图25是本发明实施例提供的一种信号处理装置的硬件结构示意图。
具体实施方式
图1是本发明实施例提供的一种信号处理系统的架构图，参考图1，该系统可以包括基站01和多个终端设备02，该终端设备也可以称为用户设备(User Equipment，UE)，每个终端设备02与该基站01之间均建立有通信连接。终端设备该基站01可以支持至少两种制式的信号的收发。例如，该基站01即可以支持UMTS信号的收发，也可以支持LTE信号的收发。相应的，该多个终端设备02中也可以包括至少两种制式的终端设备，每种制式的终端设备可以与该基站01交互相应制式的信号。
图2是本发明实施例提供的另一种信号处理系统的架构图，如图2所示，该系统可以包括至少两个基站(图2中示出了两个基站011和012)以及多个终端设备02，其中每个基站可以支持一种制式的信号的收发，且各个基站之间可以通过预设接口通信。例如，基站011可以支持第一制式(例如UMTS)的信号的收发，基站012可以支持第二制式(例如LTE)的信号的收发；该多个终端设备02中，每个终端设备02可以与相同制式的基站通信。
需要说明的是，依赖于通信系统所使用的无线通信技术，图1和图2中所示的任一基站又可以称为节点B(NodeB，NB)，演进节点B(evolved NodeB,eNB)、接入点(Access Point，AP)等。此外，根据所提供的服务覆盖区域的大小，基站又可以分为用于提供宏蜂窝(Macro cell)的宏基站、用于提供微蜂窝(Pico cell)的微基站和用于提供毫微微蜂窝(Femto cell)的毫微微基站等。随着无线通信技术的不断演进，未来的基站也可以采用其他的名称。
图1和图2中所示的任一终端设备可以是具备无线通信功能的各种无线通信设备，例如可以为移动蜂窝电话、无绳电话、会话启动通信协议(Session Initiation Protocol，SIP)电话、个人数字助理(Personal Digital Assistant，PDA)、智能电话、笔记本电脑、平板电脑、无线数据卡、无线调制解调器(Modulator demodulator，Modem)、可穿戴设备(如智能手表)、车载设备等，或者该终端设备也可以为机器对机器(machine to machine，M2M)通信中的无线终端，例如传感器，能远程抄表的仪表，或其他一些智能硬件等等。
在图1和图2所示的系统中，当第一制式的通信系统的业务量较低，导致其频谱资源较为空闲(即处于轻载状态时)，而第二制式的通信系统的业务量较高，导致其频谱资源较为紧张时，该第二制式的通信系统可以共享该第一制式的通信系统中较为空闲的预设频段，也即是，该两种制式的通信系统可以同时通过该较为空闲的预设频段收发信号。
示例的，若该两种制式的通信系统共用一个基站(即图1所示的共站发射的场景)，则该基站可以直接根据获取到的两种制式的通信系统的业务量，触发频谱共享。若该两种制式的通信系统的基站相互独立设置(即图2所示的场景)，则该两个基站之间可以通过预设接口(例如X2接口)交互调度信息，每个基站发送的调度信息中可以包括用于指示该基站当前业务量状况的参数，从而使得该第一制式的通信系统的基站可以根据交互的调度信息，触发频谱共享。或者，该两个基站还可以分别向第三方的控制网元上报调度信息，该第三方的控制网元可以根据接收到的调度信息，触发该频谱共享。本发明实施例对该频谱共享的触发方式不做限定。其中，用于衡量每个通信系统的业务量的参数可以包括：发射信号的功率。
在本发明实施例中，该第一制式的通信系统可以为采用扩频调制技术的通信系统，例如 可以为UMTS系统、码分多址(Code Division Multiple Access，CDMA)2000系统或者时分同步码分多址(Time Division-Synchronous Code Division Multiple Access，TD-SCDMA)系统等。且该第一制式的通信系统可以采用频分双工(Frequency Division Duplex，FDD)技术收发信号，也可以采用时分双工(Time Division Duplex，TDD)技术收发信号，本发明实施例对此不做限定。在该采用扩频调制技术的通信系统中，基站向终端设备发送信号时，需要采用不同的扩频码对不同物理信道上的待发送信号进行扩频，然后将扩频后的多路信号进行叠加，并采用特定的扰码对该叠加后的信号进行加扰后发送。
假设该第一制式的通信系统为3G通信系统中的UMTS系统。该UMTS系统采用FDD技术收发信号，即上行信号和下行信号使用不同的频谱。基站向终端设备发送下行信号时，基站中的基站处理单元(Base band Unit，BBU)可以对待发送的信号依次进行扩频、叠加和加扰等处理，并可以将处理后的信号通过通用公共无线电接口(Common Public Radio Interface，CPRI)传输至射频拉远单元(Radio Remote Unit，RRU)，该CPRI接口可以对BBU发送的基带信号进行采样，采样频率一般为3.84兆赫兹(MHz)，RRU可以将接收到的信号转换(例如进行上变频转换)为射频信号，并通过天线发射出去。
UMTS系统中所采用的扩频码一般为正交可变扩频因子(Orthogonal Variable Spreading Factor，OVSF)码。其中每一路物理信道上的信号所采用的OVSF码可以从如图3所示的码树中选取。如图3所示，每个OVSF码可以包括至少一个元素，每个元素的取值为1或者-1。并且，每个OVSF码可以由符号
Figure PCTCN2018120708-appb-000043
表示，其中m 1表示该OVSF码的扩频因子(spreading factor，SF)，SF可以用于指示该OVSF码的长度，即该OVSF码中所包括的元素的个数。n 1可以用于指示SF为m 1的多个OVSF码中的第n 1个OVSF码，且n 1满足：0≤n1＜m 1。例如，C 2,0可以表示SF为2的两个OVSF码中的第0个OVSF码，C 4,2可以表示SF为4的四个OVSF码中的第2个OVSF码。
从图3还可以看出，SF相同的任意两个OVSF码相互正交，每个OVSF码作为父节点可以衍生出两个SF为其两倍的OVSF码，并且，每个SF大于1的OVSF码等分后得到的两个SF为其一半的扩频码，与其父节点对应的OVSF码均不正交，但与码树中SF为其一半的其他OVSF码均正交。例如，将SF为4的OVSF码C 4,1进行等分后，可以得到两个SF为2的扩频码(1,1)和(-1,-1)，该两个扩频码与OVSF码C 4,1的父节点对应的OVSF码C 2,0均不正交，但与SF为2的另一个OVSF码C 2,1均正交。由此可知，在为每一路物理信道上的信号选取扩频码时，若码树中的某个OVSF码已经被选取，则以该OVSF码作为父节点衍生出的其他SF更大的OVSF码均不能再被选取；同理，若某个OVSF码已经被选取，则该OVSF码的父节点对应的OVSF码也不能再被选取。
由于每一路物理信道上的信号需要采用唯一的扩频码进行扩频，因此在本发明实施例中，每一路物理信道也可以称为一个码道。
在本发明实施例中，该第二制式的通信系统可以为全球移动通信系统(Global System for Mobile Communication，GSM)系统、LTE系统或者新无线(New Radio，NR)系统等不采用扩频调制技术的系统。其中，在LTE系统中，基站向终端设备发送信号时，需要将不同频率的子载波上的信号进行叠加后发送。并且，LTE系统的系统带宽选择较为灵活，一般可以包括3MHz、5MHz和10MHz等多种可选带宽。表1是本发明实施例提供的一种LTE系统中系统带宽与采样频率的对应关系，从表1可以看出，不同系统带宽的LTE系统具有不同的CPRI采样频率。例如，系统带宽为3MHz的LTE系统的采样频率可以为3.84MHz，而系统带宽为5MHz的LTE系统的采样频率可以为7.68MHz。
表1
系统带宽/MHz 1.4 3 5 10 15 20
采样频率/MHz 1.92 3.84 7.68 15.36 23.04 30.72
此外，在LTE系统中，由于子载波间隔Δf为15千赫兹(kHz)，因此LTE系统中每个符号的持续时间T 0可以满足：
Figure PCTCN2018120708-appb-000044
微秒(μs)。其中，LTE系统中的符号可以为正交频分复用(Orthogonal Frequency Division Multiplexing，OFDM)符号，且该持续时间T 0可以是指不考虑循环前缀的OFDM符号(即有用OFDM符号)的持续时间。又由于UMTS系统中的采样频率为3.84MHz，该UMTS系统中每个码片的持续时间(即码片周期)T c满足：
Figure PCTCN2018120708-appb-000045
秒，因此在LTE系统中每个符号的持续时间T 0内，该UMTS系统能够传输的码片个数L满足：
Figure PCTCN2018120708-appb-000046
其中，INT()表示对括号内的数值取整，该取整可以是向上取整，也可以是向下取整，还可以是四舍五入，本发明实施例对此不做限定。
在NR系统中，下行信号使用的符号也可以为OFDM符号，且NR系统中子载波间隔除了15kHz之外，还可以选取其他值，例如还可以为3.75kHz或者30kHz等。相应的，在该NR系统中每个符号的持续时间内，该UMTS系统可以传输的码片个数也有所不同。例如，当该NR系统的子载波间隔为30kHz时，在每个有用OFDM符号的持续时间内，UMTS系统传输的码片个数L可以为：
Figure PCTCN2018120708-appb-000047
图4是本发明实施例提供的一种信号处理方法的流程图，该方法可以应用于图1所示的第一制式的通信系统的基站01中，或者可以应用于图2所示的第一制式的通信系统的基站011中，参考图4，该方法可以包括：
步骤101、在第一制式的通信系统与第二制式的通信系统共享目标频段时，获取该第一制式的通信系统中至少一路待发送信号，以及每一路待发送信号对应的扩频码。
在本发明实施例中，两种制式的通信系统在触发频谱共享后，该两种制式的通信系统的基站可以均采用共享的预设频段发送信号，该目标频段可以为该预设频段，也可以为该预设频段中的部分频段。其中，该第一制式的通信系统中的至少一路待发送信号是指基站待发送至终端设备，以便终端设备接收并解调的信号。每一路待发送信号对应的扩频码可以是该第一制式的通信系统的基站预先从码表或者码树中选取的，并且任意两路待发送信号对应的扩频码相互正交。
示例的，假设第一制式的通信系统为UMTS系统，第二制式的通信系统为LTE系统。该UMTS系统中，下行信号可以包括多路公共信道上的信号，以及多路业务信道上的信号。其中，公共信道可以包括同步信道(Synchronization Channel，SCH)、主公共控制物理信道(Primary Common Control Physical Channel，P-CCPCH)和主公共导频信道(Primary Common Pilot Channel，P-CPICH)等；业务信道可以包括专用物理信道(Dedicated Physical Channel，DPCH)，该DPCH可以用于传输自适应多速率(Adaptive Multi Rate，AMR)语音等R99业务数据。由于公共信道中的SCH上的信号无需扩频，因此在本发明实施例中可以无需考虑该SCH上的信号。
图5是本发明实施例提供的一种UMTS系统所使用的码道的示意图，如图5所示，假设在UMTS系统中，基站需要向终端设备发送的信号包括两路公共信道(P-CCPCH和P-CPICH)上的待发送信号，以及H'路业务信道上的待发送信号，即UMTS系统中共包括(H'+2)路待发送信号。其中，公共信道P-CCPCH和P-CPICH上的待发送信号对应的扩频码的长度均为 256(即扩频因子SF为256)，H'路业务信道上的待发送信号所对应的扩频码的扩频因子均为128。如图5所示，以该LTE系统中每个符号的持续时间为单位时间，该UMTS系统中的每一路待发送信号在该单位时间内可以传输256个码片。其中，公共信道上的待发送信号所包括的256个码片是采用长度为256的扩频码对一个符号进行扩频得到的，而每个业务信道上的待发送信号所包括的256个码片则是采用长度为128的扩频码对两个符号进行扩频得到的。
如图5所示，该公共信道P-CPICH上的待发送信号在该单位时间内传输的符号可以包括符号a，公共信道P-CCPCH上的待发送信号在该单位时间内传输的符号可以包括符号b，H'路业务信道中每一路业务信道上的待发送信号在该单位时间内可以传输两个符号，例如，第一路业务信道上的待发送信号在该单位时间内可以传输符号c 11和符号c 12，第H'路业务信道上的待发送信号在该单位时间内可以传输符号c H'1和符号c H'2。从图5还可以看出，该公共信道P-CCPCH上的待发送信号所对应的扩频码可以为C 256,0，即扩频因子为256的多个扩频码中，第0个扩频码；该公共信道P-CPICH上的待发送信号所对应的扩频码可以为C 256,1。该H'路业务信道中，第一路待发送信号对应的扩频码可以为C 128,h1，第hi路待发送信号对应的扩频码可以为C 128,hi，其中，hi为小于等于H'的正整数。
步骤102、确定至少一路加扰信号，以及每一路加扰信号对应的扩频码。
进一步的，第一制式的通信系统中的基站可以先确定加扰信号的路数，以及每一路加扰信号对应的扩频码，然后可以计算单位时间内的发射信号在目标频段内的功率。该单位时间可以是指第二制式的通信系统中每个符号的持续时间。该发射信号可以是指对该至少一路待发送信号中的每一路待发送信号进行扩频，并对该至少一路加扰信号中的每一路加扰信号进行扩频，然后再对扩频后的至少一路待发送信号以及扩频后的至少一路加扰信号进行叠加和加扰等处理后得到的信号。该目标频段属于该两种制式的通信系统所共享的预设频段，即该目标频段可以为该预设频段内的部分频段，或者也可以为该预设频段。
之后，基站可以根据该单位时间内的发射信号在该目标频段内的功率大小，确定每一路加扰信号在该单位时间内的所传输的符号，该确定的加扰信号可以使得该发射信号在该目标频段内的功率小于原始功率。其中，该原始功率可以是指仅对该扩频后的至少一路待发送信号进行相应处理(例如叠加和加扰)后得到的信号在该目标频段内的功率。也即是，通过增加至少一路加扰信号，可以降低基站向终端设备发送的发射信号在该目标频段内的功率，从而可以降低对第二制式的通信系统中的信号的干扰。
作为一种可选的实现方式，当两种制式的通信系统共享频谱时，该第一制式的通信系统中的基站可以实时或者周期性的获取该第二制式的通信系统的调度信息，该调度信息中可以包括该第二制式的通信系统实际使用的调度频段。该第一制式的通信系统中的基站可以将该调度频段与该预设频段之间的重叠频段确定为该目标频段。也即是，在共享频谱的过程中，第一制式的通信系统可以根据第二制式的通信系统实际使用的调度频段，选择合适的加扰信号，以精准降低对该第二制式的通信系统中信号的干扰。
图6是本发明实施例提供的一种确定至少一路加扰信号，以及每一路加扰信号对应的扩频码的方法流程图，参考图6，该方法可以包括：
步骤1021、根据码表中空闲扩频码的数量，确定加扰信号的路数N。
在本发明实施例中，该加扰信号的路数N可以小于或等于系统中剩余的空闲扩频码的数量。其中，该空闲扩频码可以是指码表中除了待发送信号对应的扩频码之外的可用扩频码。若码表中存储的扩频码为如图3所示的OVSF码，则当其中某个OVSF码被选取为待发送信 号的扩频码后，以该OVSF码为父节点所衍生出的SF更大的OVSF码将均不可用。
示例的，假设在UMTS系统中，如图5所示，两路公共信道上的待发送信号对应的扩频码的扩频因子为256，H'路业务信道上的待发送信号对应的扩频码的扩频因子为128。结合图3可知，图5中的两个SF为256的扩频码被选取后，该两个SF为256的扩频码的父节点所对应的一个SF为128的扩频码将不可用，因此若基站为该至少一路加扰信号分配的扩频码均为SF为128的扩频码，则该基站可以确定SF为128的扩频码中，空闲扩频码的数量为(128-H'-1)。相应的，基站可以确定加扰信号的路数N满足：N≤(128-H'-1)。
假设H'＝10，则基站可以确定码表中剩余的空闲扩频码可以包括117(117＝128-10-1)个扩频因子为128的扩频码，或者234(256-2-2×10)个扩频因子为256的扩频码。相应的，基站可以确定，当该至少一路加扰信号均采用扩频因子为128的扩频码时，该加扰信号的路数N应当小于或等于117；当该至少一路加扰信号均采用扩频因子为256的扩频码时，该加扰信号的路数N应当小于或等于234。当然，该至少一路加扰信号也可以划分为多组，不同的加扰信号组可以采用不同扩频因子的扩频码，此时，每组加扰信号组所包括的加扰信号的路数应当小于对应的空闲扩频码的数量。
步骤1022、从码表中的空闲扩频码中选取与N路加扰信号一一对应的N个扩频码。
进一步的，基站可以从空闲扩频码中为每一路加扰信号选取对应的一个扩频码。在选取每一路加扰信号对应的扩频码时，基站可以从空闲扩频码中随机选取，或者也可以从该空闲扩频码中顺序选取，本发明实施例对此不做限定。
示例的，图7是本发明实施例提供的另一种UMTS系统中使用的码道的示意图，如图7所示，基站为该N路加扰信号选取的扩频码的扩频因子可以均为128，且该N路加扰信号中的第n'(n'为不大于N的正整数)路加扰信号对应的扩频码可以为
Figure PCTCN2018120708-appb-000048
例如第一路加扰信号对应的扩频码为
Figure PCTCN2018120708-appb-000049
第N路加扰信号对应的扩频码为
Figure PCTCN2018120708-appb-000050
步骤1023、获取发射信号在单位时间内的信号模型。
在本发明实施例中，第一制式的通信系统中的基站在发送信号时，需要先根据每一路信号对应的扩频码，对每一路信号进行扩频，然后再对扩频后的多路信号进行处理得到发射信号，该处理可以包括叠加和加扰。由于需要考虑该第一制式的通信系统中的基站发送的信号对第二制式的通信系统中的信号造成的干扰，因此可以以该第二制式的通信系统中每个符号的持续时间为单位时间，确定每一路加扰信号在该单位时间内的符号值。
在本发明实施例一种可选的实现方式中，假设该单位时间为T 0，该第一制式的通信系统的码片周期为T c，该码片周期T c可以为第一制式的通信系统中基带信号的采样频率fs的倒数，即
Figure PCTCN2018120708-appb-000051
则基站可以确定该至少一路待发送信号中的每一路待发送信号在该单位时间T 0内所能够传输的码片个数L满足：
Figure PCTCN2018120708-appb-000052
若该至少一路待发送信号可以划分为M组待发送信号组，其中每组待发送信号组包括的至少一路待发送信号对应的扩频码的扩频因子相等，各组待发送信号组对应的扩频码的扩频因子的不相等。则对扩频后的至少一路待发送信号进行叠加后得到的信号，在该单位时间内所包括的L个码片所组成的L×1的列向量g可以表示为：
Figure PCTCN2018120708-appb-000053
其中，∑()表示对括号内的参数求和，L×1的列向量可以是指包括L行元素的列向量，V j为第j组待发送信号组对应的扩频码组成的L×(k j×N j)的扩频矩阵(即扩频矩阵的行数为L，列数为k j×N j)，j为不大于M的正整数，且V j满足：
Figure PCTCN2018120708-appb-000054
表示直积(也称为Kronecker积)，
Figure PCTCN2018120708-appb-000055
为k j阶单位矩阵，V' j为l j×N j的矩阵，l j为该第j组待发送信号组中每一 路待发送信号所对应的扩频码的扩频因子，k j为该第j组待发送信号组中每一路待发送信号在该单位时间内所传输的符号的个数，且k j可以满足l j×k j＝L。矩阵V' j中第y'列元素为该第j组待发送信号组所包括的N j路待发送信号中，第y'路待发送信号对应的扩频码，y'为不大于N j的正整数。c j为该第j组待发送信号组包括的N j路待发送信号所组成的(k j×N j)×1的列向量，该(k j×N j)×1的列向量包括k j个依次按列排列的子向量，每个子向量可以包括N j个元素，该N j个元素可以分别为该N j路待发送信号中的一个符号。
示例的，假设如图5所示，UMTS系统中，单位时间内的发射信号包括的码片个数L为256，该UMTS系统中包括(H'+2)路待发送信号。由于其中两路公共信道上的待发送信号所对应的扩频码的扩频因子为256，H'路业务信道上的待发送信号对应的扩频码的扩频因子均为128，则该(H'+2)路待发送信号可以划分为两组，其中第一组待发送信号组包括两路公共信道上的待发送信号，第二组待发送信号组包括H'路公共信道上的待发送信号。也即是，M＝2，l 1＝256，l 2＝128，N 1＝2，N 2＝H'，k 1＝1，k 1＝2。
根据图5可知，第一组待发送信号组中，公共信道P-CCPCH上的待发送信号所对应的扩频码C 256,0，公共信道P-CPICH上的待发送信号所对应的扩频码为C 256,1，该两个扩频码可以构成一个256×2的矩阵V' 1，该矩阵V' 1中的第一列元素可以为扩频码C 256,0所组成的256×1的列向量u 0，该矩阵V' 1中的第二列元素可以为扩频码C 256,1所组成的256×2的列向量u 1。由于k 1＝1，因此基站可以确定该第一组待发送信号组对应的扩频码组成的256×2的扩频矩阵V 1满足：
V 1＝V' 1＝[u 0 u 1]   公式(2)
相应的，该第一组待发送信号组所包括的两路待发送信号在该单位时间内所传输的符号a和符号b可以组成2×1的列向量c 1，该列向量c 1满足：
c 1＝[a b] T   公式(3)
其中，T表示矩阵的转置。
继续参考图5，在第二组待发送信号组中，H'路业务信道上的待发送信号所对应的扩频码分别为
Figure PCTCN2018120708-appb-000056
至
Figure PCTCN2018120708-appb-000057
该H'个扩频码可以构成一个128×H'的矩阵V' 2。该矩阵V' 2中的第一列元素可以为该H'路待发送信号中第一路待发送信号对应的扩频码
Figure PCTCN2018120708-appb-000058
组成的128×1的列向量
Figure PCTCN2018120708-appb-000059
第y'列元素可以为该H'路待发送信号中，第y'路待发送信号对应的扩频码
Figure PCTCN2018120708-appb-000060
组成的128×1的列向量
Figure PCTCN2018120708-appb-000061
y'为不大于H'的正整数，第H'列元素可以为第H'路待发送信号对应的扩频码
Figure PCTCN2018120708-appb-000062
组成的128×1的列向量
Figure PCTCN2018120708-appb-000063
由于k 2＝2，因此可以确定该第二组待发送信号组对应的扩频码组成的L×(2×H')的扩频矩阵V 2满足：
Figure PCTCN2018120708-appb-000064
相应的，该第二组待发送信号组所包括的H'路待发送信号中，每一路待发送信号在该单位时间内可以传输两个符号，则该H'路待发送信号所组成的(2×H')×1的列向量c 2可以满足：
c 2＝[c 11 c 21 … c H'1 c 12 c 22 … c H'2] T   公式(5)
从该公式(5)可以看出，该列向量c 2可以包括两个按列排列的子向量：[c 11 c 21 … c H'1] T和[c 12 c 22 … c H'2] T，其中每个子向量所包括的H'个元素可以分别为该H'路待发送信号中的一个符号。例如子向量[c 11 c 21 … c H'1] T中的H'个元素依次为该H'路待发送信号中每一路待发送信号在该单位时间内所传输的第一个符号，子向量[c 12 c 22 … c H'2] T中的H'个元素依次为该H'路待发送信号中每一路待发送信号在该单位时间内所传输的第二个符号。
最后，根据上述公式(1)可知，对扩频后的(H'+2)路待发送信号进行叠加后得到的信号，在该单位时间内所包括的L个码片所组成的L×1的列向量g可以表示为：
g＝V 1c 1+V 2c 2＝au 0+bu 1+V 2c 2   公式(6)
进一步的，当该第一制式的通信系统中的基站所发送的发射信号中还包括N路加扰信号时，基站可以根据处理所包括的类型，以及发射信号在单位时间内包括的码片个数L，确定该发射信号在该单位时间内的信号模型可以为L×1的列向量f，该列向量f可以满足：
Figure PCTCN2018120708-appb-000065
其中，S为L×L的扰码矩阵，该扰码矩阵为对角矩阵，且该扰码矩阵中第l行的对角元素为L个码片中第l个码片对应的扰码，l为不大于L的正整数，该扰码可以为基站预先确定的。g为对扩频后的至少一路待发送信号进行叠加后得到的信号在单位时间内所包括的L个码片所组成的L×1的列向量，其表达式可以参考上述公式(1)。w为该N路加扰信号所包括的组数，每组加扰信号组所包括的至少一路加扰信号对应的扩频码的扩频因子相等，各组加扰信号组对应的扩频码的扩频因子的不相等。W i为第i组加扰信号组对应的扩频码组成的L×(k i×N i)的扩频矩阵，i为不大于w的正整数，且W i可以满足：
Figure PCTCN2018120708-appb-000066
表示直积，
Figure PCTCN2018120708-appb-000067
为k i阶单位矩阵，W' i为l i×N i的矩阵，l i为第i组加扰信号组中每一路加扰信号所对应的扩频码的扩频因子，k i为第i组加扰信号组中每一路加扰信号在单位时间内所传输的符号的个数。矩阵W' i中的第y列元素为第i组加扰信号组所包括的N i路加扰信号中，第y路加扰信号对应的扩频码组成的列向量，y为不大于N i的正整数。x i为第i组加扰信号组包括的N i路加扰信号所组成的(k i×N i)×1的列向量，(k i×N i)×1的列向量包括k i个按列排列的子向量，每个子向量包括的N i个元素可以分别指示N i路加扰信号中的一个符号。W'为该w组加扰信号组对应的共w个扩频矩阵按行排列所组成的
Figure PCTCN2018120708-appb-000068
的组合扩频矩阵，该组合扩频矩阵W'可以表示为：W'＝[W 1 … W w]；x'为该w组加扰信号组按列排列所组成的
Figure PCTCN2018120708-appb-000069
的加扰信号矩阵，该加扰信号矩阵x'可以表示为：
Figure PCTCN2018120708-appb-000070
假设如图7所示，该UMTS系统中额外增加的N路加扰信号所对应的扩频码的扩频因子均为128，每一路加扰信号在单位时间内传输的符号数为2，则基站可以确定该N路加扰信号可以划分为一组，即w＝1，并且k 1＝2，l 1＝128。
根据图7可知，N路加扰信号所对应的扩频码分别为
Figure PCTCN2018120708-appb-000071
至
Figure PCTCN2018120708-appb-000072
该N个扩频码可以构成一个128×N的矩阵W' 1，该矩阵W' 1中的第一列元素可以为该N路加扰信号中第一路加扰信号对应的扩频码
Figure PCTCN2018120708-appb-000073
组成的128×1的列向量
Figure PCTCN2018120708-appb-000074
第y列元素可以为该N路加扰信号中，第y(y为不大于N的正整数)路加扰信号对应的扩频码
Figure PCTCN2018120708-appb-000075
组成的128×1的列向量
Figure PCTCN2018120708-appb-000076
第N列元素可以为第N路加扰信号对应的扩频码
Figure PCTCN2018120708-appb-000077
组成的列向量
Figure PCTCN2018120708-appb-000078
由于k 1＝2，因此基站可以确定该N路加扰信号对应的扩频码所组成的L×(2×N)的扩频矩阵W 1满足：
Figure PCTCN2018120708-appb-000079
相应的，该N路加扰信号中，每一路加扰信号在该单位时间内可以传输两个符号，则该N路加扰信号所组成的(2×N)×1的列向量x 1可以满足：
x 1＝[x 11 x 21 … x N1 x 12 x 22 … x N2] T  公式(9)
从该公式(9)可以看出，该列向量c 1可以划分为两个(k 1＝2)按列排列的子向量：[x 11 x 21 … x N1] T和[x 12 x 22 … x H2] T，其中每个子向量所包括的N个元素可以分别为该N路加扰信号中的一个符号，例如子向量[x 11 x 21 … x N1] T中的N个元素依次为该N路加扰信号中每一路加扰信号在该单位时间内所传输的第一个符号，子向量[x 12 x 22 … x H2] T中的N个元素依次为该N路加扰信号中每一路加扰信号在该单位时间内所传输的第二个符号。
最后，基站即可根据上述公式(7)确定发射信号在单位时间内的信号模型f满足：
f＝S(g+W 1x 1)＝Sg+SW 1x 1    公式(10)
由于w＝1，结合该公式(10)可知，组合扩频矩阵W'满足：W'＝W 1；该加扰信号矩阵x'满足：x'＝x 1。
图8是本发明实施例提供的又一种UMTS系统中使用的码道的示意图，若第一制式的通信系统中基站需要向终端设备发送的信号包括两路公共信道上的待发送信号，以及(H'+H”)路业务信道上的待发送信号，其中，该两路公共信道上的待发送信号所采用的扩频码的扩频因子为256，H'路业务信道上的待发送信号采用的扩频码的扩频因子为128，H”路业务信道上的待发送信号采用的扩频码的扩频因子为64。则该(H'+H”+2)路待发送信号根据扩频因子的不同可以划分为3组，即M＝3；并且基站可以确定上述公式(1)中的其他参数满足：l 1＝256，l 2＝128，l 3＝64，N 1＝2，N 2＝H'，N 3＝H”，k 1＝1，k 1＝2，k 3＝4。
其中，该第一组待发送信号组对应的扩频矩阵V 1可以参考上述公式(2)，第二组待发送信号组对应的扩频矩阵V 2可以参考上述公式(4)。
对于该第三组待发送信号组，如图8所示，H”路业务信道上的待发送信号所对应的扩频码分别为
Figure PCTCN2018120708-appb-000080
至
Figure PCTCN2018120708-appb-000081
该H”个扩频码中，每个扩频码可以构成一个128×1的列向量，该H”个扩频码进而可以构成一个128×H”的矩阵V' 3。参考上述公式(4)，该第三组待发送信号组对应的扩频码所组成的L×(4×H”)的扩频矩阵V 3可以满足：
Figure PCTCN2018120708-appb-000082
相应的，该第三组待发送信号组所包括的H”路待发送信号中，每一路待发送信号在该单位时间内可以传输四个符号，该H”路待发送信号所组成的(4×H”)×1的列向量c 3可以满足：
c 3＝[d 11 d 21 … d H”1 d 12 d 22 … d H”2 d 13 d 23 … d H”3 d 14 d 24 … d H”4] T 公式(12)
从该公式(12)可以看出，该列向量c 3可以包括四个(k 3＝4)按列排列的子向量：[d 11 d 21 … d H”1] T、[d 12 d 22 … d H”2] T、[d 13 d 23 … d H”3] T以及[d 14 d 24 … d H”4] T。其中每个子向量所包括的H”个元素可以分别为该H”路待发送信号中的一个符号，例如子向量[d 11 d 21 … d H”1] T中的H'个元素依次为该H”路待发送信号中每一路待发送信号在该单位时间内所传输的第一个符号，子向量[d 14 d 24 … d H”4] T中的H”个元素依次为该H”路待发送信号中每一路待发送信号在该单位时间内所传输的第四个符号。
根据上述公式(1)可知，此时，对扩频后的(H'+H”+2)路待发送信号进行叠加后得到的信号，在该单位时间内所包括的L个码片所组成的L×1的列向量g可以表示为：
g＝au 0+bu 1+V 2c 2+V 3c 3  公式(13)
进一步的，当该N路加扰信号对应的扩频码的扩频因子不完全相等时，该N路加扰信号也可以划分为多组。例如在图8所示的示例中，该N路加扰信号可以划分为两组(即w＝2)，其中第一组加扰信号组中，每一路加扰信号所对应的扩频码的扩频因子为128，第二组加扰信号组中，每一路加扰信号所对应的扩频码的扩频因子为64，上述公式(7)中的其他参数可以满足：k 1＝2，k 2＝4，l 1＝128，l 2＝64。
其中，第一组加扰信号组对应的扩频码所组成的L×(2×N')的扩频矩阵W 1可以满足：
Figure PCTCN2018120708-appb-000083
该第一组加扰信号组中每一路加扰信号在该单位时间内可以传输两个符号，该第一组加扰信号组所组成的(2×N')×1的列向量x 1可以满足：
x 1＝[x 11 x 21 … x N'1 x 12 x 22 … x N'2] T  公式(15)
第二组加扰信号组对应的扩频码所组成的L×(4×N”)的扩频矩阵W 2可以满足：
Figure PCTCN2018120708-appb-000084
该第二组加扰信号组中每一路加扰信号在该单位时间可以传输四个符号，该第二组加扰信号组所组成的(4×N”)×1的列向量x 2可以满足：
x 2＝[e 11 e 21 … e N”1 e 12 e 22 … e N”2 e 13 e 23 … e N”3 e 14 e 24 … e N”4] T  公式(17)
从该公式(17)可以看出，该列向量x 2可以包括4个按列排列的子向量：[e 11 e 21 … e N”1] T、[e 12 e 22 … e N”2] T、[e 13 e 23 … e N”3] T以及[e 14 e 24 … e N”4] T。其中每个子向量所包括的N”个元素可以分别为该N”路加扰信号中的一个符号。例如子向量[e 11 e 21 … e N”1] T中的N”个元素依次为该N”路加扰信号中每一路加扰信号在该单位时间内所传输的第一个符号，子向量[e 13 e 23 … e N”3] T中的N”个元素依次为该N”路加扰信号中每一路加扰信号在该单位时间内所传输的第三个符号。
最后，基站即可根据上述公式(7)确定发射信号在该单位时间内的信号模型f满足：
f＝S(g+W 1x 1+W 2x 2)＝S(au 0+bu 1+V 2c 2+V 3c 3)+SW 1x 1+SW 2x 2  公式(18)
由于w＝2，结合该公式(17)可知，组合扩频矩阵W'可以满足：W'＝[W 1 W 2]；该加扰信号矩阵x'可以满足：
Figure PCTCN2018120708-appb-000085
在本发明实施例另一种可选的实现方式中，第一制式的通信系统的基站对扩频后的至少一路待发送信号以及至少一路加扰信号进行处理时，该处理还可以包括：采用发射成型滤波器进行滤波，以及根据过采样因子R进行过采样，R为正整数。此时，发射信号在单位时间内可以包括(L×R)个码片，由于该L×R个码片是对L个码片进行过采样后得到的，因此该过采样后的L×R个码片也可以称为L×R个采样值。
此时，基站根据处理包括的操作类型，以及发射信号在单位时间内包括的码片个数L×R，可以确定该发射信号在单位时间内的信号模型为(L×R)×1的列向量f'，且该列向量f'满足：
Figure PCTCN2018120708-appb-000086
其中，H为(L×R)×L的滤波矩阵，公式(19)中的其他参数与上述公式(7)中对应参数的含义相同，此处不再赘述。该滤波矩阵H中的第m行第n列的元素H mn可以满足：
Figure PCTCN2018120708-appb-000087
其中，RC 0(t)为该第一制式的通信系统中所采用的发射成型滤波器的单位冲激响应函数，m为不大于(L×R)的正整数，n为不大于L的正整数。该发射成型滤波器可以为根升余弦(root-raised cosine，RRC)滤波器，该RRC滤波器的单位冲激响应函数RC 0(t)可以满足：
Figure PCTCN2018120708-appb-000088
该公式(21)中T c为第一制式的通信系统中每个码片的持续时间，α为预设的滚降系数。在UMTS系统中，每个码片的持续时间T c可以满足：
Figure PCTCN2018120708-appb-000089
且α的取值可以为0.22。
在上述公式(20)中，当过采样因子R等于1时，表示未对第一制式的通信系统中的码片序列进行过采样，即此时该第一制式的通信系统中时域信号的采样间隔Δt即为一个码片的持续时间T c。当过采样因子R大于1时，相当于对该第一制式的通信系统中的每个码片采样了R次，此时采样间隔Δt为：
Figure PCTCN2018120708-appb-000090
对于过采样因子R大于1的场景，发射成型滤波器离散化后得到数字滤波器的单位脉冲响应h(n)满足：
Figure PCTCN2018120708-appb-000091
该单位脉冲响应h(n)仅在有限的长度内有显著非0的取值。为了简化计算，降低复杂度，可以将单位脉冲响应h(n)的长度截短为2L+1。之后，可以在该单位时间内的发射信号所包括的L个码片序列中，每相邻两个码片之间添加(R-1)个0，然后再经过单位脉冲响应为h(n)的滤波器，即可得到以
Figure PCTCN2018120708-appb-000092
为采样间隔进行采样的采样序列。最后，可以去除该采样序列的前L个数值，保留从第(L+1)个数值至第(L×R+L)个数值，即可得到L×R个采样值，该L×R个采样值即可构成上述公式(19)所示的列向量f'。
步骤1024、根据信号模型，确定发射信号在该目标频段内的功率模型。
进一步的，基站可以根据信号模型，确定单位时间内的发射信号在目标频段内的功率模型。该确定功率模型的过程可以包括：
步骤S1、将发射信号在单位时间内的信号模型转换至频域。
在本发明实施例中，基站可以将该信号模型与预设的频域转换矩阵相乘，从而将该信号模型从时域转换至频域。
对于上述公式(7)所示的信号模型(即未进行滤波和过采样的发射信号的信号模型)，该频域转换矩阵F 1可以为L×L的矩阵，在该频域转换矩阵F 1中，第m 2第n 2列的元素可以为
Figure PCTCN2018120708-appb-000093
其中，m 2满足：1≤m 2≤L，n 2满足：1≤n 2≤L。
对于上述公式(19)所示的信号模型(即经过滤波和过采样的发射信号的信号模型)，该频域转换矩阵F 2可以为行数和列数均为L×R的(L×R)×(L×R)的矩阵，在该频域转换矩阵F 2中，第m 3行第n 3列的元素可以为
Figure PCTCN2018120708-appb-000094
其中，m 3满足：1≤m 3≤(L×R)，n 3满足：1≤n 3≤(L×R)。
步骤S2、根据目标频段，确定对角元素为0或1的L'×L'的对角矩阵中，取值为1的对角元素所在行。
该取值为1的对角元素可以用于指示在该单位时间内的发射信号所占的频段中，位于该目标频段内的频域采样点。其中，L'可以为该单位时间内的发射信号所包括的码片或采样值的个数。根据上述分析可知，对于上述公式(7)所示的发射信号，L'＝L；对于上述公式(19)所示的发射信号，L'＝L×R。
在本发明实施例中，基站在确定L'×L'的对角矩阵中，取值为1的对角元素所在行时，可以先确定该第一制式的通信系统所占用的第一频段的中心频率f0，然后再判断该目标频段的 下限频率f1、该目标频段的上限频率f2和该第一频段的中心频率f0三者的大小。
当该中心频率f0满足：f1＜f0≤f2时，可以确定取值为1的对角元素所在行包括第1行至第
Figure PCTCN2018120708-appb-000095
行，以及第
Figure PCTCN2018120708-appb-000096
行至第L'行，其中fs为该第一制式的通信系统的采样频率。
当该中心频率f0满足：f0＞f2时，可以确定取值为1的对角元素所在行包括第
Figure PCTCN2018120708-appb-000097
Figure PCTCN2018120708-appb-000098
行至第
Figure PCTCN2018120708-appb-000099
行。
当该中心频率f0满足：f0≤f1时，可以确定取值为1的对角元素所在行包括第
Figure PCTCN2018120708-appb-000100
Figure PCTCN2018120708-appb-000101
行至第
Figure PCTCN2018120708-appb-000102
行。
示例的，假设该第一制式的通信系统为UMTS系统，该第二制式的通信系统为LTE系统。当该两个通信系统共享频谱时，如图9所示，该UMTS系统所占的第一频段为0至5MHz的频段，该LTE系统所占的第二频段为1MHz至4MHz的频段，该第二频段也即是该UMTS系统与该LTE系统共享的预设频段。从图9可以看出，该第一频段和第二频段的中心频率相等，均为2.5MHz。若该LTE系统实际使用的调度频段为1.15MHz至3.85MHz共2.7MHz的频段，则该UMTS系统的基站即可确定待处理的目标频段可以该1.15MHz至3.85MHz共2.7MHz的频段。也即是，该UMTS系统的基站可以确定：f0＝2.5MHz，f1＝1.15MHz，f2＝3.85MHz。由于中心频率f0满足：f1＜f0≤f2。若L'＝L＝256，则该基站可以确定该256×256的对角矩阵Λ 1中，取值为1的对角元素所在行包括第1行至第
Figure PCTCN2018120708-appb-000103
行(即第1至第91行)，以及第
Figure PCTCN2018120708-appb-000104
行至第256行(即第167至第256行)。
可选的，由于信号的频谱在带宽边缘存在滚降，为了有效降低第一制式的通信系统中基站向终端设备发送的信号对第二制式的通信系统中的信号的干扰，可以适当扩大该L'×L'的对角矩阵中取值为1的对角元素所在行的范围。
例如，当该中心频率f0满足：f1＜f0≤f2时，取值为1的对角元素所在行还可以包括：第
Figure PCTCN2018120708-appb-000105
行至第
Figure PCTCN2018120708-appb-000106
行，和/或，第
Figure PCTCN2018120708-appb-000107
Figure PCTCN2018120708-appb-000108
行至第
Figure PCTCN2018120708-appb-000109
行。
当该中心频率f0满足：f0＞f2时，取值为1的对角元素所在行还可以包括：第
Figure PCTCN2018120708-appb-000110
Figure PCTCN2018120708-appb-000111
行至第
Figure PCTCN2018120708-appb-000112
行，和/或，第
Figure PCTCN2018120708-appb-000113
行至第
Figure PCTCN2018120708-appb-000114
行。
当该中心频率f0满足：f0≤f1时，取值为1的对角元素所在行还可以包括第
Figure PCTCN2018120708-appb-000115
Figure PCTCN2018120708-appb-000116
行至第
Figure PCTCN2018120708-appb-000117
行，和/或，第
Figure PCTCN2018120708-appb-000118
行至第
Figure PCTCN2018120708-appb-000119
Figure PCTCN2018120708-appb-000120
行。
其中，Δ1、Δ2、Δ3、Δ4、Δ5和Δ6均为正整数，且Δ1至Δ6可以为预先设置的固定值，也可以根据L'×L'的对角矩阵中的实际可选行数进行调整。
示例的，假设Δ1和Δ2均等于5，则在该256×256的对角矩阵中，取值为1的对角元素所在行可以包括第1行至第
Figure PCTCN2018120708-appb-000121
行(即第1至第96行)，以及第
Figure PCTCN2018120708-appb-000122
Figure PCTCN2018120708-appb-000123
行至第256行(即第162至第256行)。
需要说明的是，在上述步骤S2中，基站在判断下限频率f1、中心频率f0和上限频率f2三者的大小之前，还可以先检测该目标频段是否为连续频段，若检测到该目标频段为连续频段时，则可以直接根据该下限频率f1、中心频率f0和上限频率f2三者的大小，确定对角矩阵中取值为1的对角元素所在行。
当基站检测到该目标频段不为连续频段时，也即是，当检测到该目标频段包括多个子频段时，基站可以根据该目标频段包括的各个子频段，确定对角元素为0或1的对角矩阵中，取值为1的对角元素所在行。例如，对于每个子频段，基站可以判断该子频段的下限频率、该子频段的上限频率和该第一频段的中心频率f0三者的大小，并确定与该子频段对应的取值为1的对角元素所在行。最后，基站可以确定对角矩阵中，取值为1的对角元素所在行为：各个子频段对应的取值为1的对角元素所在行的合集。
步骤S3、去除该L'×L'对角矩阵中，取值为0的对角元素所在行，生成频段提取矩阵。
当L'＝L时，去除取值为0的对角元素所在行之后，生成的频段提取矩阵Λ可以为J×L的矩阵。其中，J为不大于L的正整数。
当L'＝L×R时，去除取值为0的对角元素所在行之后，生成的频段提取矩阵Λ 1可以为J'×(L×R)的矩阵。其中，J'为不大于(L×R)的正整数。
示例的，假设对角矩阵为256×256的矩阵，根据目标频段所确定的取值为1的对角元素所在行为第1至第91行，以及第167至第256行。则去除该256×256的对角矩阵中取值为0的对角元素后，可以得到181×256的频段提取矩阵Λ。
步骤S4、确定发射信号在该目标频段内的功率模型P。
在本发明实施例中，基站可以将频段提取矩阵与转换至频域的信号模型相乘，从而可以从该发射信号的信号模型中提取出位于该目标频段内的频域采样点。对于上述公式(7)所示的发射信号的信号模型，该提取出的频域采样点可以满足：
r＝ΛF 1f  公式(22)
对于上述公式(19)所示的发射信号的信号模型，该提取出的频域采样点可以满足：
r'＝Λ 1F 2f'   公式(23)
进一步的，基站即可根据上述公式(22)或(23)计算得到该单位时间内的发射信号在该目标频段内的功率模型P。对于上述公式(7)所示的发射信号的信号模型，该功率模型P可以表示为：
P＝||r|| 2＝||ΛF 1SW′x′+ΛF 1Sg|| 2   公式(24)
对于上述公式(19)所示的发射信号的信号模型，该功率模型P可以表示为：
P＝||r'|| 2＝||Λ 1F 2HSW'x'+Λ 1F 2HSg|| 2  公式(25)
公式(24)和公式(25)中的||·||表示向量的欧式范数。
步骤1025、根据该功率模型确定N路加扰信号。
基站在确定该N路加扰信号时，为了保证发射信号在目标频段内的功率尽可能的小，尽量降低第一制式的通信系统中的信号对第二制式的通信系统中的信号的干扰，可以调整加扰信号的符号值，从而最小化该单位时间内的发射信号在该目标频段内的功率模型P的功率。
例如，基站可以在该N路加扰信号的总功率小于第一功率阈值的前提下，计算该功率模型的功率为最小值时，该N路加扰信号中每一路加扰信号在该单位时间内的符号值，从而即可确定该N路加扰信号。其中，该第一功率阈值可以小于或等于第一制式的通信系统中基站的最大发射功率与该至少一路待发送信号的总功率之间的差值。也即是，在发送该N路加扰信号时，需要保证N路加扰信号的总功率与至少一路待发送信号的总功率之和，不大于该UMTS系统中基站的最大发射功率。
在本发明实施例中，在最小化上述公式(24)或者公式(25)所示的功率模型P时，需要设定约束条件，以保证N路加扰信号在该单位时间内的总功率小于第一功率阈值P'。该约束条件可以表示为：
||x'|| 2≤P'   公式(26)
在本发明实施例中，该第一功率阈值P'可以小于或等于第一制式的通信系统中，基站的最大发射功率与该至少一路待发送信号的总功率之间的差值。也即是，在发送该N路加扰信号时，需要保证N路加扰信号的总功率与至少一路待发送信号的总功率之和，不大于该第一制式的通信系统中基站的最大发射功率。
在满足上述公式(26)所示条件的前提下，通过最小化上述公式(24)所确定的N路加扰信号组成的加扰信号矩阵可以表示为：
Figure PCTCN2018120708-appb-000124
在满足上述公式(26)所示条件的前提下，通过最小化上述公式(25)所确定的N路加扰信号组成的加扰信号矩阵可以表示为：
Figure PCTCN2018120708-appb-000125
上述公式(27)和公式(28)中，argmin表示功率模型P取值最小时的自变量x'的取值。
在求解上述公式(27)时，可以令A＝ΛF 1SW'，b＝-ΛF 1Sg，则上述公式(27)可以进一步简化为：
Figure PCTCN2018120708-appb-000126
在求解如公式(29)所示的约束优化问题时，可以采用库恩塔克(Karush-Kuhn-Tucker，KKT)条件进行求解，根据KKT条件可以得到：
Figure PCTCN2018120708-appb-000127
其中，A H表示矩阵A的共轭矩阵，λ为拉格朗日乘子。
一方面，如果λ＞0，那么||x'|| 2＝P'，根据上述公式(30)可以推导出：
(A HA+λI)x'＝A Hb   公式(31)
求解公式(31)可以得到该N路加扰信号组成的加扰信号矩阵x'满足：
x'＝(A HA+λ 0I) -1A Hb   公式(32)
其中，λ 0为使得x'满足公式(26)所示的约束条件的参数值，I为单位矩阵。一般λ 0越大，x'的范数就越小。在本发明实施例中，通过二分法可以查找到最佳的λ 0。
另一方面，如果λ＝0，根据上述公式(30)可以推导出：
A HAx'＝A Hb   公式(33)
该公式(33)可以进一步简化为：
Ax'＝b   公式(34)
根据矩阵论可知，x'为上述公式(33)的解与x'是上述公式(34)的最小二乘解互为充要条件，由此可知该N路加扰信号组成的加扰信号矩阵x'可以为上述公式(34)的最小二乘解。
同理，在求解上述公式(28)时，也可以采用上述KKT条件进行计算，本发明实施例对此不再赘述。
需要说明的是，基站在根据功率模型P确定N路加扰信号时，除了可以在约束条件下最小化该功率模型P，还可以使得该功率模型P的功率相对于原始功率降低一定比例，例如可以降低为原始功率80％，或者原始功率的90％等，只要保证该功率模型P的功率小于原始功率即可，本发明实施例对此不做限定。
步骤103、采用该至少一路待发送信号中每一路待发送信号对应的扩频码，对每一路待发送信号进行扩频。
基站可以将该每一路待发送信号与其对应的扩频码相乘，从而实现对该每一路待发送信号的扩频。
步骤104、采用该至少一路加扰信号中每一路加扰信号对应的扩频码，对每一路加扰信号进行扩频。
基站在确定该至少一路加扰信号中每一路加扰信号在该单位时间内的符号值，以及每一路加扰信号对应的扩频码之后，即可将每一路加扰信号与其对应的扩频码相乘，由此实现对每一路加扰信号的扩频。
步骤105、对扩频后的至少一路待发送信号以及扩频后的至少一路加扰信号进行处理得到发射信号。
进一步的，基站可以对该扩频后的至少一路待发送信号，以及扩频后的至少一路加扰信号进行处理，得到发射信号，该发射信号在单位时间内包括的码片所组成的列向量可以如上述公式(7)所示。其中，该处理可以包括叠加和加扰。
或者，基站在对该扩频后的路信号进行处理之前，还可以检测该第一制式的通信系统中基带信号的第一采样频率是否小于第二制式的通信系统中基带信号的第二采样频率。当该第一采样频率小于该第二采样频率时，为了更好的匹配该第二制式的通信系统的采样频率，有效降低对第二制式的通信系统中信号的干扰，该基站还可以确定过采样因子R，该过采样因子R可以大于或等于2。例如，该过采样因子R与第一采样频率的乘积可以等于该第二采样频率。当该第一采样频率不小于该第二采样频率时，该基站可以确定过采样因子R等于1，也即是，可以无需对基带信号进行过采样。
相应的，对该扩频后的至少一路待发送信号以及至少一路加扰信号进行处理的过程还可以包括：采用发射成型滤波器进行滤波，以及根据该过采样因子R进行过采样。此时，处理后得到的发射信号在单位时间内包括的L×R个采样值所组成的列向量可以如上述公式(19)所示。
示例的，假设第一制式的通信系统中，基带信号的第一采样频率为3.84MHz，该第二制式的通信系统中，基带信号的第二采样频率为7.68MHz，则该第一制式的通信系统的基站可以确定过采样因子R＝2，并可以对该扩频后的信号进行两倍过采样，此时该单位时间内的发射信号所包括的采样值的个数可以为L×R。
步骤106、发送该发射信号。
最后，第一制式的通信系统即可将该发射信号发射至终端设备。由于该发射信号在该目标频段内的取值小于原始功率，因此可以有效降低对第二制式的通信系统中的信号的干扰。终端设备接收到该发射信号之后，可以对该发射信号进行解扰和解扩，以获取该至少一路待发送信号。由于该发射信号中的加扰信号是用于调整功率的，而并未是用于向终端设备传输信息的，因此终端设备可以无需对该加扰信号进行处理。
在本发明实施例一种可选的实现方式中，假设第一制式的通信系统为UMTS系统，第二制式的通信系统为LTE系统，两种制式的通信系统共享频谱后所占的频段如图9所示，两种制式的通信系统共享的预设频段为1MHz至4MHz共3MHz的频段。但LTE系统实际使用的调度频段为1.15MHz至3.85MHz的频段，该目标频段也为该1.15MHz至3.85MHz共2.7MHz的频段，即该目标频段为UMTS所占的第一频段中位于中心的2.7MHz的频段。若该UMTS系统中的基站向终端设备发送的信号中包括127路加扰信号，且该127路加扰信号所采用的扩频码的扩频因子均为128，则UMTS中基站发送的发射信号的功率谱密度(power spectral density,PSD)可以如图10所示。
图10中还示出了基站发送的信号中不包括加扰信号时的功率谱密度。图10所示的功率谱密度是将信号的频谱变换到低通频段后仿真得到的，即图10所示的频谱中，频点0即相当于该第一频段的中心频率f0，频段-1.35MHz至1.35MHz即相当于该目标频段。对比图10所示的两条曲线可以看出，在增加至少一路加扰信号后，基站发送的发射信号的总功率增加了，但是在该目标频段上的功率却明显降低了。根据上述公式(27)和公式(28)可以确定，发射信号的功率在该目标频段内降低的幅度与加扰信号的路数，加扰信号所采用的扩频码的扩频因子，以及预设的功率阈值等参数有关。由于LTE系统的调度频段包括该目标频段，将该目标频段的功率降低，也就降低了UMTS系统中基站发送的发射信号对LTE系统中的信号的干扰。
在本发明实施例另一种可选的实现方式中，假设第一制式的通信系统为UMTS系统，第二制式的通信系统为LTE系统，两种制式的通信系统共享频谱后所占的频段如图11所示，该LTE系统所占的第二频段位于该UMTS系统所占用的第一频段内，也即是，该两种制式的通信系统所共享的预设频段为该第一频段的一部分，但该预设频段的中心频率与该第一频段的中心频率不相等。若目标频段为0.65MHz至3.35MHz共2.7MHz的频段。则基站可以根据上述步骤S2所示的方法，根据该目标频段确定取值为1的对角元素所在行，进而确定该频段提取矩阵。后续确定至少一路加扰信号的过程可以参考上述实施例，此处不再赘述。
在本发明实施例又一种可选的实现方式中，假设第一制式的通信系统为UMTS系统，第二制式的通信系统为LTE或者NR系统，两种制式的通信系统所占的频段如图12所示，从图12可以看出，该两种制式的通信系统共享频谱后，该两种制式的通信系统所占的频段部分重叠，且该第二制式的通信系统所占的第二频段的带宽可以大于该第一制式的通信系统所占的第一频段的带宽。例如，该第一频段的带宽为5MHz，该第二频段的带宽可以为5MHz，也可以为10MHz或者20MHz。
若该第一频段的中心频率f0为2.5MHz，两种制式的系统共享的预设频段为1.585MHz至4.78MHz的频段，且目标频段即为该预设频段。假设L＝256，则由于该中心频率f0满足：f1＜f0≤f2，参考上述步骤S2可知，UMTS系统中的基站可以确定取值为1的对角元素所在行包括第1行至第
Figure PCTCN2018120708-appb-000128
行(即第1行至第153行)，以及第
Figure PCTCN2018120708-appb-000129
Figure PCTCN2018120708-appb-000130
行至第256行(即第196行至第256行)。之后，基站去除该对角矩阵中取值为0的对角元素后，即可得到频段提取矩阵。最后，基站可以参考上述公式(27)计算该加扰 信号矩阵。
图13是本发明实施例提供的另一种UMTS中基站发送的发射信号的功率谱密度的示意图。图13中还示出了基站发送的发射信号中不包括加扰信号时的功率谱密度。同样，图13所示的功率谱密度也是将信号的频谱变换到低通频段后仿真得到的，即图13所示的频谱中，频点0即相当于该第一频段的中心频率f0，频段-0.915MHz至2.28MHz即相当于该目标频段。对比图13所示的两条曲线可以看出，在增加至少一路加扰信号后，基站发送的信号的总功率增加了，但是在该目标频段内的功率却明显降低了。通过降低UMTS系统中基站发送的发射信号在该目标频段内的功率，使得运营商可以部署更大带宽的非UMTS系统(例如LTE系统或者NR系统等)。并且，当UMTS系统中基站与终端设备之间为单径信道时，UMTS系统的性能不会因为其功率谱密度的变化而受到影响。当UMTS系统中基站与终端设备之间为多径信道时，UMTS系统的径间干扰会因为其功率谱密度的变化而增加，但对UMTS系统整体性能的影响不大。
在本发明实施例再一种可选的实现方式中，假设第一制式的通信系统为UMTS系统，第二制式的通信系统为LTE系统或者NR系统，两种制式的通信系统共享频谱后所占的频段如图14所示。从图14可以看出，该第一制式的通信系统所占的第一频段的带宽，以及该第二制式的通信系统所占的第二频段的带宽均为5MHz，并且两种制式的通信系统所占的频段重合，也即是，该第一制式的通信系统将其所占的第一频段均作为预设频段共享至了第二制式的通信系统。由于UMTS系统中信号的发射端可以通过RRC发射成型滤波器对信号进行滤波，因此基站发送的发射信号的频谱下降较快，基站能够以3.84MHz的采样频率对基带进行采样。而在LTE系统或者NR系统中，信号的发射端采用的是矩形成型滤波器，基站发送的信号的频谱下降慢。为了满足采样定理，系统带宽为5MHz的LTE系统或者NR系统对基带信号的采样频率一般为7.68MHz。
为了更好地匹配第二制式的通信系统的采样频率，UMTS系统的基站可以对基带信号进行过采样，使得其采样频率也达到7.68MHz。相应的，该过采样因子R可以满足：R＝2，该过采样后的信号在单位时间内所传输的码片个数即为L×R，其中L可以满足：L＝256。若LTE系统仅调度了6个资源块(Resource Block，RB)，且其调度频段为1.96MHz至3.04MHz共1.08MHz的频段，则UMTS系统的基站可以确定目标频段即为该1.96MHz至3.04MHz共1.08MHz的频段。
由于第一频段的中心频率f0满足：f1＜f0≤f2，则根据上述步骤S2，基站可以确定(L×R)×(L×R)的对角矩阵中，取值为1的对角元素所在行包括：第1行至第
Figure PCTCN2018120708-appb-000131
行(即第1行至第37行)，以及第
Figure PCTCN2018120708-appb-000132
行至第512行(即第477至第512行)。
进一步的，考虑到频谱边缘的过渡问题，可以适当扩大该取值为1的对角元素所在行的范围，以使得UMTS系统可以让出更多的带宽给LTE系统的子载波。例如，可以使得Δ1和Δ2均等于4，则在该512×512的对角矩阵中，取值为1的对角元素所在行可以包括第1行至第
Figure PCTCN2018120708-appb-000133
行(即第1至第41行)，以及第
Figure PCTCN2018120708-appb-000134
行至第256行(即第473至第512行)，由此可以使得UMTS系统在该调度频段的左右两边各多让出4个子载波的带宽。之后，基站去除该对角矩阵中取值为0的对角元素后，即可得到频段提取矩阵。最后，基站可以参考上述公式(27)计算该加扰信号矩阵。
第一制式的通信系统通过上述方法与第二制式的通信系统共享频谱时，可以使得运营商部署5MHz系统带宽的第二制式的通信系统比仅仅部署3MHz的系统能够更有效地利用该第 一制式的通信系统的频谱。
可选的，在本发明实施例中，当该第一制式的通信系统的基站还用于发送该第二制式的通信系统的信号(也即是图1所示的共站发射的场景)时，如图15所示，本发明实施例所提供的信号处理方法还可以包括：
步骤107、确定第一制式的通信系统所占用的第一频段，以及第二制式的通信系统所占用的第二频段。
示例的，如图9所示，两种制式的通信系统在共享预设频段时，该第一制式的通信系统所占用的第一频段的带宽可以为5MHz，该第二制式的通信系统所占用的第二频段的带宽可以为3MHz。
步骤108、若该第二频段位于该第一频段内，在发送该第二制式的通信系统的信号时，采用该第一制式的通信系统的发射成型滤波器对该第二制式的通信系统的信号进行处理后发送。
在本发明实施例中，第一制式的通信系统中的基站在发送信号时，可以采用发射成型滤波器对信号进行滤波，该滤波后的信号的功率谱密度在其频谱边缘的下降速度较快。当第二频段位于该第一频段内，该发射成型滤波器对该第二制式的通信系统的信号的影响较小，因此可以采用该第一制式的通信系统的发射成型滤波器对该第二制式的通信系统的信号进行处理后发送，从而可以有效提高信号处理和发送的效率，降低成本。
示例的，图16是本发明实施例提供的一种UMTS系统以及LTE系统中发射信号的功率谱密度的示意图。UMTS系统中所使用的发射成型滤波器(或接收滤波器)的幅频响应的模的平方与该UMTS系统中基站发送的发射信号的功率谱密度有相同的形状。从图16可以看出，UMTS系统中的发射成型滤波器的幅频响应开始下降的频点(例如1.8MHz)处，LTE系统中发射信号的功率谱密度已经下降了大约30分贝(dB)，因此如果采用该UMTS系统中的发射成型滤波器或者接收滤波器对LTE系统中的信号进行滤波，对3MHz系统带宽的LTE信号的影响较小。
在实际应用中，由于基站中的发射滤波器一般在RRU中实现，将第二制式的通信系统的信号也通过一个发射成型滤波器进行发送，意味着该第二制式的通信系统的基带信号可以先与第一制式的通信系统的基带信号进行叠加，然后再经过同一个RRU发射出去，从而可以有效降低信号处理的成本。
可选的，在上述步骤106中，基站还可以采用窄带宽滤波器对该发射信号进行滤波，然后再发送该滤波后的发射信号。
其中，该窄带宽滤波器可以包括带通滤波器、带阻滤波器、高通滤波器和低通滤波器中的任一种。该窄带宽滤波器可以抑制基站发送的发射信号在该窄带宽滤波器的阻带部分的功率。由于基站发送的发射信号的功率在该窄带宽滤波器的阻带部分的功率值较小，因此可以将该窄带宽滤波器的阻带部分的频段用作第二制式的通信系统的调度频段。
相应的，在上述步骤102中，第一制式的通信系统的基站可以获取该第二制式的通信系统的调度频段，并且可以将该调度频段中与该窄带宽滤波器的通带重叠的部分确定为该目标频段。也即是，对于该窄带宽滤波器没有抑制的频段，可以采用增加至少一路加扰信号的方式，对该目标频段的功率进行调整，从而可以有效降低对第二制式的通信系统的信号的干扰。
假设第二制式的通信系统为LTE系统，该LTE系统的下行信号一般包括小区特定的参考信号(Cell-specific Reference Signal，CRS)、物理HARQ(混合自动重传请求，Hybrid Automatic  Repeat Request)指示信道(Physical Hybrid-ARQ Indicator Channel，PHICH)、物理控制格式指示信道(Physical Control Format Indicator Channel，PCFICH)、信道状态信息参考信号(Channel State Information Reference Signal，CSI-RS)，上述信号和信道分散在LTE系统的整个系统带宽上。如果单纯采用窄带宽滤波器对该UMTS系统的信号进行滤波，以降低干扰，则需要采用阻带较小(例如15kHz)的滤波器对UMTS系统的信号进行滤波。但采用阻带较窄的滤波器会造成滤波器的阶数过高，UMTS系统的性能严重下降。而在本发明实施例中，通过增加至少一路加扰信号对该UMTS信号的功率谱密度进行调整，使得该UMTS系统中基站发射的发射信号的在LTE的CRS、PHICH、PCFICH或CSI-RS的调度频段内的功率中较小，从而可以有效降低干扰。
示例的，假设在LTE系统发送CRS时，为了避免对LTE系统中CRS的干扰，可以将CRS的调度频段中与窄带宽滤波器的通带重叠的部分确定为该目标频段。如图17所示，假设UMTS系统所占的第一频段的带宽为5MHz，该CRS的调度频段均匀分散在该5MHz的频段内，其中窄带宽滤波器的阻带(即频率响应曲线下凹的部分)与部分调度频段重叠。因此，UMTS系统中的基站可以将该调度频段与通带重叠部分确定为目标频段。从图17可以看出，该目标频段可以包括多个分散的子频段。
进一步的，UMTS系统的基站可以参考上述步骤S2所示的方法，根据该目标频段所包括的多个子频段，计算对角矩阵中，每个子频段所对应的取值为1的对角元素所在行，并将该各个子频段对应的取值为1的对角元素所在行的合集，确定为该对角矩阵中取值为1的对角元素所在行。
示例的，假设该目标频段中包括12个子频段，每个子频段的带宽为15kHz，基站参考上述步骤S2所示的方法，根据每个子频段确定了一行取值为1的对角元素，且该12个子频段中，相邻两个子频段所确定的取值为1的对角元素所在行的行间距为3。例如，根据第一个子频段所确定的取值为1的对角元素所在行可以为第2行，根据第二个子频段所确定的取值为1的对角元素所在行可以为第5行。则根据该12个子频段所确定的取值为1的对角元素所在行的合集可以表示为：{γ|γ＝2+3β，β为整数，0≤β≤11}。
此外，由于在LTE系统中，基站每个时隙可以传输7个OFDM符号，其中只有第1个和第5个OFDM符号上有CRS。如果是为了降低UMTS系统对该CRS的干扰，则UMTS系统中的基站无需始终发送加扰信号，该基站可以根据获取到的LTE系统的调度信息，在该LTE系统中发送CRS时再发送该至少一路加扰信号，从而可以避免过多增加UMTS系统的发射功率。通过增加至少一路加扰信号保护LTE系统中PCIFICH、PHICH和CSI-RS的过程与上述保护CRS的过程类似，这里不再赘述。
在本发明实施例中，通过将窄带宽滤波器滤波的方法与增加至少一路加扰信号的方法相结合，不仅提高了该信号处理方法的灵活性，还可以精准地保护第二制式的通信系统中单个或少数几个子载波，有效提高了两种制式的通信系统的性能。
可选的，由于第二制式的通信系统在发送信号时，每个符号还可以包括循环前缀(Cyclic Prefix，CP)，而在计算该第二制式的通信系统中每个符号的持续时间时，一般是计算每个有用符号(也即是不考虑CP的符号)的持续时间。因此在该第二制式的通信系统中某个有用符号的持续时间内，可能存在该有用符号的起始传输时刻与该第一制式的通信系统中某一路信号的首个码片序列的起始传输时刻不一致的情况，为了精确计算得到发射信号在该每个符号的持续时间内的功率，进而精准降低第一制式的通信系统对该第二制式的通信系统中的 信号的干扰，可以考虑该起始传输时刻不一致的情况。
示例的，假设第一制式的通信系统为UMTS系统，第二制式的通信系统为LTE系统或者NR系统，该第二制式的通信系统中每个OFDM符号中均包括CP，则不论该第二制式的通信系统中首个有用OFDM符号的起始传输时刻与该UMTS系统中每一路信号的首个符号的起始传输时刻是否相同，随着时间的推移，LTE系统中的有用OFDM符号与UMTS系统中的符号(不论该符号被扩频成多少码片)必然会出现起始传输时刻不一致的情况。
图18是本发明实施例提供的一种LTE系统中的OFDM符号与UMTS系统中的码片序列在时域内的对应关系示意图，如图18所示，每个OFDM符号中添加有CP，该CP打乱了OFDM符号与UMTS中码片序列(即对一个符号扩频后得到的多个码片组成的序列)的对应关系。图18中示出的每个码片序列可以包括256个码片或者128个码片。其中长度为256的码片序列是采用扩频因子为256的扩频码对一个符号进行扩频后得到的，长度为128的码片序列是采用扩频因子为128的扩频码对一个符号进行扩频后得到的。从图18可以看出，即使第一个有用OFDM符号(即不考虑CP的OFDM符号0)的起始传输时刻与该UMTS系统中的每个码片序列的起始传输时刻一致，但由于CP的存在，随着时间的推移，后续多个有用OFDM符号的起始传输时刻与该UMTS系统中的码片序列的起始传输时刻并不对齐。
在本发明实施例中，基站通过上述步骤1021所示的方法确定每一路加扰信号对应的扩频码后，在获取单位时间内的发射信号时，还可以根据第二制式的通信系统中每个符号的持续时间段，确定以该符号的持续时间段为单位时间时，每一路加扰信号和每一路待发送信号实际使用的扩频码。其中，确定每一路信号实际使用的扩频码的过程可以如图19所示，该方法可以包括：
步骤1023a、获取该第二制式的通信系统中每个符号的起始传输时刻。
第一制式的通信系统的基站可以通过预设接口获取该第二制式的通信系统中一个符号的起始传输时刻，例如，该基站可以在获取第二制式的通信系统的调度信息时，同步获取该第二制式的通信系统中一个符号的起始传输时刻。并且，基站可以根据该第二制式的通信系统中，每个符号的CP长度，以及有用符号的持续时间，确定每个符号的起始传输时刻。
步骤1023b、检测第二制式的通信系统中第一符号的起始传输时刻，与扩频后的每一路信号在该第一符号的持续时间内传输的首个码片序列的起始传输时刻的第一时间差。
在本发明实施例中，该第一符号可以为该第二制式的通信系统中的任一符号，每个码片序列是对一个符号进行扩频后得到的多个码片所组成的序列。该首个码片序列可以是指在该第一符号的持续时间内，每一路信号所传输的第一个符号对应的码片序列。并且，该第一符号的起始传输时刻是指该第一符号不考虑CP时的起始传输时刻。
示例的，图20是本发明实施例提供的一种LTE系统中不同符号与UMTS系统中码片序列在时域内的对应关系示意图。如图20所示，假设LTE系统中的第一符号为符号A，当以该符号A的持续时间段为单位时间时，UMTS系统中的两路公共信道上的待发送信号在该单位时间内可以分别传输一个长度为256的码片序列，H'路业务信道上的待发送信号和N路加扰信号中的每一路信号在该单位时间内可以分别传输两个长度为128的码片序列。并且，每一路信号在该单位时间内传输的首个码片序列的起始传输时刻与该符号A的起始传输时刻均一致，因此，该UMTS系统的基站可以确定该符号A与每一路信号之间的第一时间差为0。
若该第一符号为符号C，则从图20可以看出，当以该符号C的持续时间段为单位时间时，H'路业务信道上的待发送信号和N路加扰信号中的每一路信号，恰好可以分别传输两个长度为128的码片序列。也即是，每一路业务信道上的待发送信号以及每一路加扰信号，在该符 号C的持续时间内传输的首个码片序列的起始传输时刻与该符号C的起始传输时刻均一致，因此，该UMTS系统的基站可以确定该符号C与每一路业务信道上的待发送信号之间的第一时间差为0，且该符号C与N路加扰信号中的每一路信号之间的第一时间差为0。而两路公共信道上的待发送信号在该符号C的持续时间内可以分别传输两个码片序列，但每个码片序列只能传输一半的码片。也即是，该两路公共信道上的待发送信号在该持续时间内传输的首个码片序列的起始传输时刻与该符号C的起始传输时刻不一致，因此，该UMTS系统的基站可以确定该符号C与每一路公共信道上的待发送信号之间的第一时间差不为0。
步骤1023c、若该第一符号的起始传输时刻与第一路信号中首个码片序列的起始传输时刻的第一时间差不等于0，计算在该第一时间差内所传输的该首个码片序列的码片个数n 0。
进一步的，当该至少一路待发送信号和至少一路加扰信号中，第一路信号中首个码片序列的起始传输时刻与该第一符号与该第一符号的起始传输时刻的第一时间差不等于0时，基站可以根据该第一时间差Δt以及UMTS系统中的码片周期t c，计算得到该第一路信号在该第一时间差内所能够传输的码片个数n 0，该码片个数n 0可以满足：
Figure PCTCN2018120708-appb-000135
示例的，假设该符号C与每一路公共信道上的待发送信号之间的第一时间差Δt为33.33μs，而UMTS系统中的码片周期
Figure PCTCN2018120708-appb-000136
则基站可以确定每一路公共信道上的待发送信号在该第一时间差Δt内所传输的首个码片序列中的码片个数n 0为：
Figure PCTCN2018120708-appb-000137
需要说明的是，在根据该公式(35)计算码片个数n 0时，若计算得到的数值不为整数，则还可以对该数值进行取整后作为该码片个数n 0。其中，取整可以包括向上取整或者向下取整，本发明实施例对此不做限定。
步骤1023d、根据该码片个数n 0，确定该第一路信号所属的信号组中，每一路信号在该持续时间内采用的扩频码。
在本发明实施例中，基站可以根据该码片个数n 0，确定该第一路信号所属的信号组中，任一路信号在该持续时间内传输的首个码片序列指示的符号所采用的扩频码包括：该任一路信号对应的扩频码中第n 0+1至第l'个元素，并可以确定该任一路信号在该持续时间内传输的最后一个码片序列指示的符号所采用的扩频码包括：该任一路信号对应的扩频码中第1至第(L'+n 0)％l'个元素，l'为该第一路信号对应的扩频码的扩频因子，L'为该发射信号在该单位时间内包括的码片个数，％表示取余数。
此外，对于首个码片序列和最后一个码片序列之间的其他码片序列，基站可以确定该其他码片序列指示的符号对应的扩频码即为该任一路信号对应的扩频码。
示例的，假设第一组待发送信号组中，公共信道P-CCPCH和P-CPICH上的待发送信号对应的扩频码的扩频因子为256，并且每一路公共信道上的待发送信号在第一时间差Δt内所传输的首个码片序列的码片个数n 0为128。根据图20可知，公共信道P-CCPCH上的待发送信号在符号C的持续时间内所传输的首个码片序列指示的符号为符号b 1，则基站可以确定该符号b 1在该符号C的持续时间内所采用的扩频码为扩频码C 256,0中第129至第256个元素，符号b 2在该符号C的持续时间内所采用的扩频码为扩频码C 256,0中第1至第(256+128)％256个元素(即第1至第128个元素)；同理，基站可以确定公共信道P-CPICH上的待发送信号中，符号a 1在该符号C的持续时间内所采用的扩频码为扩频码C 256,1中第129至第256个元素，符号a 2在该符号C的持续时间内所采用的扩频码为扩频码C 256,1中第1至第128个元素。
相应的，上述公式(7)所示的，对扩频后的(H'+2)路待发送信号进行叠加得到的信号， 在该符号C的持续时间内所包括的L个码片所组成的L×1的列向量g可以表示为：
Figure PCTCN2018120708-appb-000138
其中，公式(36)中的u i(m 4:n 4)可以表示由列向量u i中第m 4至第n 4行的元素所构成的列向量，公式(36)中i取值为0或1。
在本发明实施例一种可选的实现方式中，上述步骤1023c中根据码片个数n 0，确定该第一路信号在该持续时间内采用的扩频码的过程还可以通过如下方法实现：
步骤C1、根据发射信号在单位时间内包括的码片个数L'，以及码片个数n 0，确定对角元素为0或1的(k' i×l')×(k' i×l')的对角矩阵中，取值为1的对角元素所在行为第(n 0+1)行至第(n 0+L')行。
其中，k' i为该第一路信号在该第一符号的持续时间内所传输的符号的个数，l'为该第一路信号对应的扩频码的扩频因子。
示例的，假设该第一符号为图20所示的符号B，在该符号B的持续时间内，两路公共信道上的待发送信号可以分别传输两个码片序列，H'路业务信道上的待发送信号和N路加扰信号中的每一路信号，可以分别传输三个码片序列。并且，该多路待发送信号和多路加扰信号中的每一路信号，在该符号B的持续时间内传输的首个码片序列的起始传输时刻与该符号B的起始传输时刻之间的第一时间差相等，且每一路信号在该第一时间差内所传输的码片个数均为n 0。若该第一路信号为该公共信道P-CCPCH上的待发送信号，则由于UMTS系统中，发射信号在单位时间内所包括的码片个数L'为256，该公共信道P-CCPCH上的待发送信号对应的扩频码的扩频因子l'为256，第一路信号在该符号B的持续时间内所传输的符号的个数k' i＝2。因此基站可以确定对角元素为0或1的对角矩阵的维度为(2×256)×(2×256)，并且可以确定该对角矩阵中，取值为1的对角元素所在行为第(n 0+1)行至第(n 0+256)行。例如，当n 0＝128时，基站可以确定该取值为1的对角元素所在行为第129行至第384行。
步骤C2、去除该(k' i×l')×(k' i×l')的对角矩阵中，取值为0的对角元素所在行，生成L'×(k' i×l')的码片提取矩阵K。
示例的，基站去除(2×256)×(2×256)的对角矩阵中，取值为0的对角元素所在的第1至第128行，以及第385至第512行之后，可以得到256×512的码片提取矩阵K。
步骤C3、确定该第一路信号所属的信号组对应的扩频码组成的扩频矩阵W' i。
该扩频矩阵W' i可以满足：
Figure PCTCN2018120708-appb-000139
其中，
Figure PCTCN2018120708-appb-000140
为k′ i阶单位矩阵，V' i为l'×N' i的矩阵，且矩阵V' i中第y'列元素为该第一路信号所属的信号组包括的N' i路信号中，第y'路信号对应的扩频码，y'为不大于N' i的正整数。
相应的，在通过上述公式(7)或公式(19)计算该单位时间内的发射信号包括的码片所组成的列向量时，可以采用上述公式(37)确定每一组待发送信号组以及每一组加扰信号组对应的扩频矩阵。
示例的，若该第一路信号为该公共信道P-CCPCH上的待发送信号，则由于第一路信号在该符号B的持续时间内所传输的符号的个数k' i＝2，该第一路信号所属的第一组待发送信号组所包括的信号的路数N' i＝2。并且该第一组待发送信号组中，公共信道P-CCPCH上的待发送信号对应的扩频码C 256,0可以组成的256×1的列向量u 0，公共信道P-CPICH上的待发送信号所对应的扩频码为C 256,1可以组成的256×1的列向量u 1，因此根据上述公式(37)，基站可以确定该第一组待发送信号组对应的扩频码组成的扩频矩阵W' i满足：
Figure PCTCN2018120708-appb-000141
其中，码片提取矩阵K为256×512的矩阵。
若该第一路信号为该图20所示的一路业务信道上的待发送信号，则由于该第一路信号在该符号B的持续时间内所传输的符号的个数k' i＝3，该第一路信号对应的扩频码的扩频因子l'为128，因此基站可以确定对角元素为0或1的对角矩阵的维度为(3×128)×(3×128)，即该对角矩阵的维度为384×384。并且基站可以确定该对角矩阵中，取值为1的对角元素所在行为第(n 0+1)行至第(n 0+256)行。进一步的，基站去除384×384的对角矩阵中取值为0的对角元素所在第1至第128行，以及第385至第512行之后，可以得到256×384的码片提取矩阵K。
又由于该第一路信号所属的第二组待发送信号组所包括的信号的路数N' i＝H'，并且该第二组待发送信号组中，第y'(y'为不大于H'的正整数)路待发送信号对应的扩频码
Figure PCTCN2018120708-appb-000142
可以组成的128×1的列向量
Figure PCTCN2018120708-appb-000143
因此根据上述公式(37)，基站可以确定该第二组待发送信号组对应的扩频码组成的扩频矩阵W' i满足：
Figure PCTCN2018120708-appb-000144
其中，码片提取矩阵K为256×384的矩阵。
若该第一路信号为该图20所示的一路加扰信号，则由于第一路信号在该符号B的持续时间内所传输的符号的个数K' i＝3，该第一路信号对应的扩频码的扩频因子l'为128，因此基站可以确定对角元素为0或1的对角矩阵的维度为(3×128)×(3×128)，并且可以确定该对角矩阵中，取值为1的对角元素所在行为第(n 0+1)行至第(n 0+256)行。进一步的，基站去除384×384的对角矩阵中取值为0的对角元素所在第1至第128行，以及第385至第512行之后，可以得到256×384的码片提取矩阵K。
又由于该第一路信号所属的加扰信号组所包括的信号的路数N' i＝N。并且该加扰信号组中，第y(y为不大于N的正整数)路加扰信号对应的扩频码
Figure PCTCN2018120708-appb-000145
可以组成的128×1的列向量
Figure PCTCN2018120708-appb-000146
因此根据上述公式(37)，基站可以确定该加扰信号组对应的扩频码组成的扩频矩阵W' i满足：
Figure PCTCN2018120708-appb-000147
其中，码片提取矩阵K为256×384的矩阵。
之后，基站即可根据上述公式(7)或公式(19)计算该单位时间内的发射信号包括的码片所构成的列向量，进而再计算每一路加扰信号在该单位时间内所传输的符号值。
此外，当该第一符号为图20所示的符号D时，计算每一路信号在该符号D的持续时间内采用的扩频码可以参考上述实施例，本发明实施例对此不再赘述。
可选的，在本发明实施例中，该第一制式的通信系统的基站在发送信号的过程中，还可以实时检测其业务量，例如可以检测系统中空闲扩频码的数量以及待发送信号的功率。当基站检测到该第一制式的通信系统中空闲扩频码的数量小于预设个数阈值，或者检测到待发送信号的功率大于第二功率阈值时，可以向第二制式的通信系统的基站发送指示信息，该指示信息可以用于指示第二制式的通信系统的基站在该预设频段内允许调度频段，该允许调度频 段的带宽可以小于该预设频段的带宽，或者该指示信息还可以用于指示该第二制式的通信系统的基站在该预设时间段内停止发送信号。又或者，该第一制式的通信系统还可以直接停止频谱共享。从而可以避免对第一制式的通信系统中信号的正常发送造成影响。
示例的，在实际应用中，如果UMTS系统中的基站要寻呼终端设备，则该基站需要通过寻呼指示信道(Paging Indicator Channel，PICH)发送信号(该PICH对应的扩频码的SF可以为256)。如果终端设备向基站发起随机接入，那么该基站还要通过捕获指示信道(Acquisition Indicator Channel，AICH)发送信号(该AICH对应的扩频码的SF可以为256)。当UMTS的终端设备有高速上行链路分组接入(high speed uplink packet access，HSUPA)业务时，基站还需要通过E-DCH(增强专用信道，Enhanced Dedicated Channel)绝对授权信道(E-DCH Absolute Grant Channel，E-AGCH)、E-DCH相对授权信道(E-DCH Relative Grant Channel，E-RGCH)、以及E-DCH混合ARQ(自动重传请求，Automatic Repeat Request)指示信道(E-DCH Hybrid ARQ Indicator Channel，E-HICH)发送信号，其中该E-AGCH对应的扩频码的SF可以为256，该E-RGCH和E-HICH对应的扩频码的SF可以为128。当UMTS系统中的基站需要通过上述物理信道同时发送信号，且基站待发送的信号占据了较多的码道资源时，则该UMTS系统的基站可以停止频谱共享；或者可以在通过上述物理信道发送信号的过程中，通过该制式信息指示第二制式的通信系统停止发送信号。
综上所述，本发明实施例提供了一种信号处理方法，第一制式的通信系统中的基站可以在与其他制式的通信系统共享预设频段时，确定至少一路加扰信号，并对该加扰信号和系统中的待发送信号进行处理后发送至终端设备，由于该加扰信号可以使得基站发送的发射信号在目标频段(该目标频段属于该预设频段)内的功率小于原始功率，因此可以在提高频谱利用率的基础上，有效降低该第一制式的通信系统发送的发射信号对该第二制式的通信系统中的信号的干扰。
图21是本发明实施例提供的一种信号处理装置的结构示意图，该信号处理装置可以配置在图1或图2所示实施环境中的任一基站中，并且可以实现上述实施例所提供的信号处理方法。如图21所示，该装置可以包括：
第一获取模块201，可以用于实现上述图4所示实施例中步骤101所示的方法。
第一确定模块202，可以用于实现上述图4所示实施例中步骤102所示的方法。
第一扩频模块203，可以用于实现上述图4所示实施例中步骤103所示的方法。
第二扩频模块204，可以用于实现上述图4所示实施例中步骤104所示的方法。
处理模块205，可以用于实现上述图4所示实施例中步骤105所示的方法。
第一发送模块206，可以用于实现上述图4所示实施例中步骤106所示的方法。
图22是本发明实施例提供的一种第一确定模块的结构示意图，如图22所示，该第一确定模块202可以包括：
第一确定子模块2021，可以用于实现上述图6所示实施例中步骤1021所示的方法。
选取子模块2022，可以用于实现上述图6所示实施例中步骤1022所示的方法。
获取子模块2023，可以用于实现上述图6所示实施例中步骤1023所示的方法。
第二确定子模块2024，可以用于实现上述图6所示实施例中步骤1024所示的方法。
第三确定子模块2025，可以用于实现上述图6所示实施例中步骤1025所示的方法。
可选的，该第三确定子模块2025可以用于：
在N路加扰信号在该单位时间内的总功率小于第一功率阈值的前提下，计算功率模型的 功率为最小值时，该N路加扰信号中每一路加扰信号在该单位时间内的符号值。
可选的，图23是本发明实施例提供的另一种信号处理装置的结构示意图，如图23所示，该装置还可以包括：
第一检测模块207，用于检测该第一制式的通信系统中基带信号的第一采样频率是否小于该第二制式的通信系统中基带信号的第二采样频率。
第二确定模块208，用于当该第一采样频率小于该第二采样频率时，确定该过采样因子R为大于或等于2的整数。
第三确定模块209，用于当该第一采样频率不小于该第二采样频率时，确定该过采样因子R为1。
可选的，该第二确定子模块2024确定对角元素为0或1的对角矩阵中，取值为1的对角元素所在行可以包括：
确定该第一制式的通信系统所占用的第一频段的中心频率f0；
判断该目标频段的下限频率f1、该目标频段的上限频率f2和该第一频段的中心频率f0三者的大小；
当该中心频率f0满足：f1＜f0≤f2时，确定取值为1的对角元素所在行包括第1行至第
Figure PCTCN2018120708-appb-000148
行，以及第
Figure PCTCN2018120708-appb-000149
行至第L'行，其中fs为该第一制式的通信系统的采样频率，其中，L'为该对角矩阵所包括的总行数；
当该中心频率f0满足：f0＞f2时，确定取值为1的对角元素所在行包括第
Figure PCTCN2018120708-appb-000150
Figure PCTCN2018120708-appb-000151
行至第
Figure PCTCN2018120708-appb-000152
行；
当该中心频率f0满足：f0≤f1时，确定取值为1的对角元素所在行包括第
Figure PCTCN2018120708-appb-000153
Figure PCTCN2018120708-appb-000154
行至第
Figure PCTCN2018120708-appb-000155
行。
可选的，该第二确定子模块2024还可以用于：
当该中心频率f0满足：f1＜f0≤f2时，确定取值为1的对角元素所在行还包括：第
Figure PCTCN2018120708-appb-000156
行至第
Figure PCTCN2018120708-appb-000157
行，和/或，第
Figure PCTCN2018120708-appb-000158
Figure PCTCN2018120708-appb-000159
行至第
Figure PCTCN2018120708-appb-000160
行；
当该中心频率f0满足：f0＞f2时，确定取值为1的对角元素所在行还包括：第
Figure PCTCN2018120708-appb-000161
Figure PCTCN2018120708-appb-000162
行至第
Figure PCTCN2018120708-appb-000163
行，和/或，第
Figure PCTCN2018120708-appb-000164
行至第
Figure PCTCN2018120708-appb-000165
行；
当该中心频率f0满足：f0≤f1时，确定取值为1的对角元素所在行还包括第
Figure PCTCN2018120708-appb-000166
Figure PCTCN2018120708-appb-000167
行至第
Figure PCTCN2018120708-appb-000168
行，和/或，第
Figure PCTCN2018120708-appb-000169
行至第
Figure PCTCN2018120708-appb-000170
Figure PCTCN2018120708-appb-000171
行；其中，Δ1、Δ2、Δ3、Δ4、Δ5和Δ6均为正整数。
可选的，该第二确定子模块2024可以用于：
检测该目标频段是否为连续频段；
该第二确定子模块2024判断该目标频段的下限频率f1、该目标频段的上限频率f2和该第一频段的中心频率f0三者的大小，包括：
当该目标频段为连续频段时，判断该目标频段的下限频率f1、该目标频段的上限频率f2和该第一频段的中心频率f0三者的大小；
当该目标频段不为连续频段时，该第二确定子模块2024，还可以用于：
分别确定所述目标频段中每个子频段对应的取值为1的对角元素所在行；
将该目标频段中各个子频段对应的取值为1的对角元素所在行的合集，确定为该对角元素为0或1的对角矩阵中，取值为1的对角元素所在行。
可选的，该第一制式的通信系统的基站还用于发送该第二制式的通信系统的信号，如图23所示，该装置还可以包括：
第四确定模块210，用于确定两种制式的通信系统在共享预设频段时，该第一制式的通信系统所占用的第一频段，以及该第二制式的通信系统所占用的第二频段。
该第一发送模块206，还可以用于：若该第二频段位于该第一频段内，在发送该第二制式的通信系统的信号时，采用该第一制式的通信系统的发射成型滤波器对该第二制式的通信系统的信号进行处理后发送。
图24是本发明实施例提供的又一种信号处理装置的结构示意图，如图24所示，该装置还可以包括：
第二获取模块211，用于获取该第二制式的通信系统的调度信息，该调度信息包括该第二制式的通信系统的调度频段。
第五确定模块212，用于根据该调度频段和该预设频段，确定该目标频段，该目标频段包括该调度频段与该预设频段之间的重叠频段。
可选的，该第一发送模块206可以用于：
采用窄带宽滤波器对该发射信号进行滤波后发送，该窄带宽滤波器包括带通滤波器、带阻滤波器、高通滤波器和低通滤波器中的任一种。
相应的，如图24所示，该装置还可以包括：
第六确定模块213，用于将该调度频段中与该窄带宽滤波器的通带重叠的部分确定为该目标频段。
可选的，该获取子模块2023，还可以用于实现上述图19所示实施例中步骤1023a至步骤1023d所示的方法。
可选的，如图23和图24所示，该装置还可以包括：
第二发送模块214，用于当检测到该第一制式的通信系统中空闲扩频码的数量小于预设个数阈值，或者待发送信号的功率大于第二功率阈值时，向该第二制式的通信系统的基站发送指示信息；
该指示信息用于指示该第二制式的通信系统的基站在该预设频段内的允许调度频段，或者，该指示信息用于指示该第二制式的通信系统的基站在预设时间段内停止发送信号。
综上所述，本发明实施例提供了一种信号处理装置，第一制式的通信系统中的基站可以在与其他制式的通信系统共享预设频段时，确定至少一路加扰信号，并对该加扰信号和系统中的待发送信号进行处理后发送至终端设备，由于该加扰信号可以使得基站发送的发射信号在目标频段(该目标频段属于该预设频段)内的功率小于原始功率，因此可以在提高频谱利用率的基础上，有效降低该第一制式的通信系统发送的发射信号对该第二制式的通信系统中 的信号的干扰。
请参考图25，其示出了本申请实施例提供的一种信号处理装置的硬件结构示意图。该信号处理装置可以配置在图1或图2所示实施环境中的任一基站中。参见图25，该装置可以包括处理器402、收发器404、多根天线406，存储器408、I/O(输入/输出，Input/Output)接口410和总线412。存储器408可以用于存储指令4082和数据4084。此外，处理器402、收发器404、存储器408和I/O接口410通过总线412彼此通信连接，多根天线406与收发器404相连。需要说明的是，图25所示的处理器402、收发器404、存储器408和I/O接口410之间的连接方式仅仅是示例性的，在实现过程中，处理器402、收发器404、存储器408和I/O接口410也可以采用除了总线412之外的其他连接方式彼此通信连接。
其中，处理器402可以是通用处理器，通用处理器可以是通过读取并执行存储器(例如存储器408)中存储的指令(例如指令4082)来执行特定步骤和/或操作的处理器，通用处理器在执行上述步骤和/或操作的过程中可能用到存储在存储器(例如存储器408)中的数据(例如数据4084)。通用处理器可以是，例如但不限于，中央处理器(Central Processing Unit，CPU)。此外，处理器402也可以是专用处理器，专用处理器可以是专门设计的用于执行特定步骤和/或操作的处理器，该专用处理器可以是，例如但不限于，数字信号处理器(Digital Signal Processor，DSP)、应用专用集成电路(Application Specific Integrated Circuit，ASIC)和现场可编程门阵列(Field Programmable Gate Array，FPGA)等。此外，处理器402还可以是多个处理器的组合，例如多核处理器。处理器402可以包括至少一个电路，以执行上述实施例中的信号处理方法的步骤。
收发器404用于收发信号。可选地，收发器404其通过多根天线406之中的至少一根天线来收发信号。
存储器408可以是各种类型的存储介质，例如随机存取存储器(Random Access Memory，RAM)、ROM、非易失性RAM(Non-Volatile RAM，NVRAM)、可编程ROM(Programmable ROM，PROM)、可擦除PROM(Erasable PROM，EPROM)、电可擦除PROM(Electrically Erasable PROM，EEPROM)、闪存、光存储器和寄存器等。存储器408具体用于存储指令4082和数据4084，当处理器402为通用处理器时，处理器402可以通过读取并执行存储器408中存储的指令4082，来执行特定步骤和/或操作，在执行上述步骤和/或操作的过程中可能需要用到数据4084。I/O接口410用于接收来自外围设备的指令和/或数据，以及向外围设备输出指令和/或数据。
在实现过程中，处理器402可以用于进行，例如但不限于，基带相关处理，收发器404可以用于进行，例如但不限于，射频收发。上述器件可以分别设置在彼此独立的芯片上，也可以至少部分的或者全部的设置在同一块芯片上。例如，处理器402可以进一步划分为模拟基带处理器和数字基带处理器，其中模拟基带处理器可以与收发器404集成在同一块芯片上，数字基带处理器可以设置在独立的芯片上。随着集成电路技术的不断发展，可以在同一块芯片上集成的器件越来越多，例如，数字基带处理器可以与多种应用处理器(例如但不限于图形处理器，多媒体处理器等)集成在同一块芯片之上。这样的芯片可以称为系统芯片(System on Chip)。将各个器件独立设置在不同的芯片上，还是整合设置在一个或者多个芯片上，往往取决于产品设计的具体需要。
此外，本申请中的术语“和/或”，仅仅是一种描述关联对象的关联关系，表示可以存在三种关系，例如，A和/或B，可以表示：单独存在A，同时存在A和B，单独存在B这三种 情况。
本发明实施例还提供了一种计算机可读存储介质，该计算机可读存储介质中存储有指令，当该计算机可读存储介质在计算机上运行时，使得计算机执行上述实施例中的信号处理方法的步骤。
本发明实施例还提供了一种包含指令的计算机程序产品，当该计算机程序产品在计算机上运行时，使得计算机执行上述实施例中的信号处理方法的步骤。
本发明实施例还提供了一种芯片，该芯片可以配置于第一制式的通信系统的基站中，该芯片包括可编程逻辑电路和/或程序指令，当该芯片运行时用于实现上述实施例中的信号处理方法。
本发明实施例还提供了一种信号处理系统，如图1或图2所示，该系统可以包括：基站和至少一个终端设备02。
该基站可以包括图21，以及图23至图25任一所示的信号处理装置，该信号处理装置中还可以包括图22所示的第一确定模块。
以上所述仅为本申请的示例性实施方式，并不用于限定本申请实施例的保护范围，凡在本申请实施例的技术方案的基础之上，所做的任何修改、等同替换、改进等，均应包括在本申请实施例的保护范围之内。

Claims (33)

  1. 一种信号处理方法，其特征在于，应用于第一制式的通信系统的基站，所述方法包括：
    在所述第一制式的通信系统与第二制式的通信系统共享目标频段时，获取所述第一制式的通信系统中至少一路待发送信号，以及每一路所述待发送信号对应的扩频码；
    确定至少一路加扰信号，以及每一路所述加扰信号对应的扩频码；
    采用每一路所述待发送信号对应的扩频码，对每一路所述待发送信号进行扩频；
    采用每一路所述加扰信号对应的扩频码，对每一路所述加扰信号进行扩频；
    对扩频后的至少一路所述待发送信号以及扩频后的至少一路所述加扰信号进行处理得到发射信号，所述发射信号在所述目标频段内的功率小于原始功率，所述原始功率为仅对扩频后的至少一路所述待发送信号进行所述处理后得到的信号在所述目标频段内的功率；
    发送所述发射信号。
  2. 根据权利要求1所述的方法，其特征在于，所述确定至少一路加扰信号，以及每一路所述加扰信号对应的扩频码，包括：
    根据码表中空闲扩频码的数量，确定所述加扰信号的路数N；
    从所述码表中的空闲扩频码中选取与N路所述加扰信号一一对应的N个扩频码，所述空闲扩频码不包括所述待发送信号对应的扩频码；
    获取所述发射信号在单位时间内的信号模型，所述单位时间为所述第二制式的通信系统中每个符号的持续时间；
    根据所述信号模型，确定所述发射信号在所述目标频段内的功率模型；
    根据所述功率模型确定N路所述加扰信号。
  3. 根据权利要求2所述的方法，其特征在于，所述根据所述功率模型确定N路所述加扰信号，包括：
    在N路所述加扰信号在所述单位时间内的总功率小于第一功率阈值的前提下，计算所述功率模型的功率为最小值时，N路所述加扰信号中每一路所述加扰信号在所述单位时间内的符号值。
  4. 根据权利要求3所述的方法，其特征在于，所述处理包括叠加和加扰，所述发射信号在所述单位时间内包括L个码片，所述L满足：
    Figure PCTCN2018120708-appb-100001
    T 0为所述单位时间，T c为所述第一制式的通信系统的码片周期，INT()表示对括号内的数值取整，所述获取所述发射信号在单位时间内的信号模型，包括：
    根据所述处理包括的操作类型，以及所述发射信号在所述单位时间内包括的码片个数L，确定所述信号模型为L×1的列向量f，所述列向量f满足：
    Figure PCTCN2018120708-appb-100002
    其中，S为L×L的扰码矩阵，所述扰码矩阵为对角矩阵，且所述扰码矩阵中第l行的对角元素为所述L个码片中第l个码片对应的扰码，l为不大于L的正整数，g为对扩频后的至少一路所述待发送信号进行叠加后得到的信号在所述单位时间内所包括的L个码片所组成的L×1的列向量，w为N路所述加扰信号所包括的组数，每组加扰信号组所包括的至少一路所述加扰信号对应的扩频码的扩频因子相等，各组加扰信号组对应的扩频码的扩频因子的不相等，W i为第i组加扰信号组对应的扩频码组成的L×(k i×N i)的扩频矩阵，i为不大于w的 正整数，且W i满足：
    Figure PCTCN2018120708-appb-100003
    表示直积，
    Figure PCTCN2018120708-appb-100004
    为k i阶单位矩阵，W' i为l i×N i的矩阵，l i为所述第i组加扰信号组中每一路所述加扰信号所对应的扩频码的扩频因子，k i为所述第i组加扰信号组中每一路所述加扰信号在所述单位时间内所传输的符号的个数，矩阵W' i中的第y列元素为所述第i组加扰信号组所包括的N i路所述加扰信号中，第y路所述加扰信号对应的扩频码组成的列向量，y为不大于N i的正整数，x i为第i组加扰信号组包括的N i路所述加扰信号所组成的(k i×N i)×1的列向量，所述(k i×N i)×1的列向量包括k i个按列排列的子向量，每个子向量包括的N i个元素分别指示N i路所述加扰信号中的一个符号，W'为w组加扰信号组对应的共w个扩频矩阵按行排列所组成的
    Figure PCTCN2018120708-appb-100005
    的组合扩频矩阵，x'为w组加扰信号组按列排列所组成的
    Figure PCTCN2018120708-appb-100006
    的加扰信号矩阵；
    所述根据所述信号模型，确定所述发射信号在所述目标频段内的功率模型，包括：
    根据所述目标频段，确定对角元素为0或1的L×L的对角矩阵中，取值为1的对角元素所在行；
    去除所述对角矩阵中，取值为0的对角元素所在行，生成J×L的频段提取矩阵Λ，J为不大于L的正整数；
    根据所述信号模型，确定所述发射信号在所述目标频段内的功率模型P，所述功率模型P满足：
    P＝||ΛF 1f|| 2＝||ΛF 1SW′x′+ΛF 1Sg|| 2，其中，F 1为l×L的频域转换矩阵，||·||表示向量的欧式范数；
    计算N路所述加扰信号中每一路所述加扰信号在所述单位时间内的符号值，包括：
    根据所述功率模型P，确定N路所述加扰信号组成的加扰信号矩阵x'，所述加扰信号矩阵x'满足：
    Figure PCTCN2018120708-appb-100007
    其中，P'为所述第一功率阈值。
  5. 根据权利要求3所述的方法，其特征在于，所述处理包括叠加、加扰、采用发射成型形滤波器滤波以及根据过采样因子R进行过采样，R为正整数；所述发射信号在所述单位时间内包括L×R个码片，所述L满足：
    Figure PCTCN2018120708-appb-100008
    T 0为所述单位时间，T c为所述第一制式的通信系统的码片周期，INT()表示对括号内的数值取整，所述获取所述发射信号在单位时间内的信号模型，包括：
    根据所述处理包括的操作类型，以及所述发射信号在所述单位时间内包括的码片个数L×R，确定所述信号模型为(L×R)×1的列向量f'，所述列向量f'满足：
    Figure PCTCN2018120708-appb-100009
    其中，S为L×L的扰码矩阵，所述扰码矩阵为对角矩阵，且所述扰码矩阵中第i行的对角元素为所述L个码片中第i个码片对应的扰码，g为对扩频后的至少一路所述待发送信号进行叠加后得到的信号在所述单位时间内所包括的L个码片所组成的L×1的列向量，w为N路所述加扰信号所包括的组数，每组加扰信号组所包括的至少一路所述加扰信号对应的扩频码的扩频因子相等，各组加扰信号组对应的扩频码的扩频因子的不相等，W i为第i组加扰信号组对应的扩频码组成的L×(k i×N i)的扩频矩阵，i为不大于w的正整数，且W i满足：
    Figure PCTCN2018120708-appb-100010
    Figure PCTCN2018120708-appb-100011
    表示直积，
    Figure PCTCN2018120708-appb-100012
    为k i阶单位矩阵，W' i为l i×N i的矩阵，l i为所述第i组加扰信号组中每一路所述加扰信号所对应的扩频码的扩频因子，k i为所述第i组加扰信号组中每一路所述加扰信号在所述单位时间内所传输的符号的个数，矩阵W' i中的第y列元素为所述第i组加扰信号组所包括的N i路所述加扰信号中，第y路所述加扰信号对应的扩频码组成的列向量，y为不大于N i的正整数，x i为第i组加扰信号组包括的N i路所述加扰信号所组成的(k i×N i)×1的列向量，所述(k i×N i)×1的列向量包括k i个按列排列的子向量，每个子向量包括的N i个元 素分别指示N i路所述加扰信号中的一个符号，W'为w组加扰信号组对应的共w个扩频矩阵按行排列所组成的
    Figure PCTCN2018120708-appb-100013
    的组合扩频矩阵，x'为w组加扰信号组按列排列所组成的
    Figure PCTCN2018120708-appb-100014
    的加扰信号矩阵；H为(L×R)×L的滤波矩阵，所述滤波矩阵H中的第m行第n列的元素H mn满足：
    Figure PCTCN2018120708-appb-100015
    其中，RC 0(t)为所述发射成型滤波器的单位冲激响应函数，m为不大于(L×R)的正整数，n为不大于L的正整数。
    所述根据所述信号模型，确定所述发射信号在所述目标频段内的功率模型，包括：
    根据所述目标频段，确定对角元素为0或1的(L×R)×(L×R)的对角矩阵中，取值为1的对角元素所在行；
    去除所述(L×R)×(L×R)的对角矩阵中，取值为0的对角元素所在行，生成J'×(L×R)的频段提取矩阵Λ 1，J'为不大于(L×R)的正整数；
    根据所述信号模型，确定所述发射信号在所述目标频段内的功率模型P，所述功率模型P满足：
    P＝||Λ 1F 2f'|| 2＝||Λ 1F 2HSW'x'+Λ 1F 2HSg|| 2，其中，F 2为(L×R)×(L×R)的频域转换矩阵，||·||表示向量的欧式范数；
    计算N路所述加扰信号中每一路所述加扰信号在所述单位时间内的符号值，包括：
    根据所述功率模型P，确定N路所述加扰信号组成的加扰信号矩阵x'，所述加扰信号矩阵x'满足：
    Figure PCTCN2018120708-appb-100016
    其中，P'为所述第一功率阈值。
  6. 根据权利要求5所述的方法，其特征在于，在对扩频后的至少一路所述待发送信号以及扩频后的至少一路所述加扰信号进行处理之前，所述方法还包括：
    检测所述第一制式的通信系统中基带信号的第一采样频率是否小于所述第二制式的通信系统中基带信号的第二采样频率；
    当所述第一采样频率小于所述第二采样频率时，确定所述过采样因子R为大于或等于2的整数；
    当所述第一采样频率不小于所述第二采样频率时，确定所述过采样因子R为1。
  7. 根据权利要求4至6任一所述的方法，其特征在于，确定对角元素为0或1的对角矩阵中，取值为1的对角元素所在行，包括：
    确定所述第一制式的通信系统所占用的第一频段的中心频率f0；
    判断所述目标频段的下限频率f1、所述目标频段的上限频率f2和所述第一频段的中心频率f0三者的大小；
    当所述中心频率f0满足：f1＜f0≤f2时，确定取值为1的对角元素所在行包括第1行至第
    Figure PCTCN2018120708-appb-100017
    行，以及第
    Figure PCTCN2018120708-appb-100018
    行至第L'行，其中fs为所述第一制式的通信系统的采样频率，其中，L'为所述对角矩阵所包括的总行数；
    当所述中心频率f0满足：f0＞f2时，确定取值为1的对角元素所在行包括第
    Figure PCTCN2018120708-appb-100019
    Figure PCTCN2018120708-appb-100020
    行至第
    Figure PCTCN2018120708-appb-100021
    行；
    当所述中心频率f0满足：f0≤f1时，确定取值为1的对角元素所在行包括第
    Figure PCTCN2018120708-appb-100022
    Figure PCTCN2018120708-appb-100023
    行至第
    Figure PCTCN2018120708-appb-100024
    行。
  8. 根据权利要求7所述的方法，其特征在于，
    当所述中心频率f0满足：f1＜f0≤f2时，取值为1的对角元素所在行还包括：第
    Figure PCTCN2018120708-appb-100025
    行至第
    Figure PCTCN2018120708-appb-100026
    行，和/或，第
    Figure PCTCN2018120708-appb-100027
    Figure PCTCN2018120708-appb-100028
    行至第
    Figure PCTCN2018120708-appb-100029
    行；
    当所述中心频率f0满足：f0＞f2时，取值为1的对角元素所在行还包括：第
    Figure PCTCN2018120708-appb-100030
    Figure PCTCN2018120708-appb-100031
    行至第
    Figure PCTCN2018120708-appb-100032
    行，和/或，第
    Figure PCTCN2018120708-appb-100033
    行至第
    Figure PCTCN2018120708-appb-100034
    行；
    当所述中心频率f0满足：f0≤f1时，取值为1的对角元素所在行还包括第
    Figure PCTCN2018120708-appb-100035
    Figure PCTCN2018120708-appb-100036
    行至第
    Figure PCTCN2018120708-appb-100037
    行，和/或，第
    Figure PCTCN2018120708-appb-100038
    行至第
    Figure PCTCN2018120708-appb-100039
    Figure PCTCN2018120708-appb-100040
    行；
    其中，Δ1、Δ2、Δ3、Δ4、Δ5和Δ6均为正整数。
  9. 根据权利要求7所述的方法，其特征在于，在判断所述目标频段的下限频率f1、所述目标频段的上限频率f2和所述第一频段的中心频率f0三者的大小之前，所述方法还包括：
    检测所述目标频段是否为连续频段；
    所述判断所述目标频段的下限频率f1、所述目标频段的上限频率f2和所述第一频段的中心频率f0三者的大小，包括：
    当所述目标频段为连续频段时，判断所述目标频段的下限频率f1、所述目标频段的上限频率f2和所述第一频段的中心频率f0三者的大小；
    当所述目标频段不为连续频段时，所述方法还包括：
    分别确定所述目标频段中每个子频段对应的取值为1的对角元素所在行；
    将所述目标频段中各个子频段对应的取值为1的对角元素所在行的合集，确定为所述对角元素为0或1的对角矩阵中，取值为1的对角元素所在行。
  10. 根据权利要求1至6任一所述的方法，其特征在于，所述第一制式的通信系统的基站还用于发送所述第二制式的通信系统的信号，所述方法还包括：
    确定所述第一制式的通信系统所占用的第一频段，以及所述第二制式的通信系统所占用的第二频段；
    若所述第二频段位于所述第一频段内，在发送所述第二制式的通信系统的信号时，采用所述第一制式的通信系统的发射成型滤波器对所述第二制式的通信系统的信号进行处理后发送。
  11. 根据权利要求1至6任一所述的方法，其特征在于，所述第一制式的通信系统与所 述第二制式的通信系统共享的频段为预设频段，在所述确定至少一路加扰信号之前，所述方法还包括：
    获取所述第二制式的通信系统的调度信息，所述调度信息包括所述第二制式的通信系统的调度频段；
    将所述调度频段和所述预设频段之间的重叠频段确定为所述目标频段。
  12. 根据权利要求1至6任一所述的方法，其特征在于，所述发送所述发射信号，包括：
    采用窄带宽滤波器对所述发射信号进行滤波后发送，所述窄带宽滤波器包括带通滤波器、带阻滤波器、高通滤波器和低通滤波器中的任一种；
    所述第一制式的通信系统与所述第二制式的通信系统共享的频段为预设频段，在所述确定至少一路加扰信号之前，所述方法还包括：
    获取所述第二制式的通信系统的调度信息，所述调度信息包括所述第二制式的通信系统的调度频段；
    将所述调度频段中与所述窄带宽滤波器的通带重叠的部分确定为所述目标频段。
  13. 根据权利要求4至6任一所述的方法，其特征在于，所述方法还包括：
    获取所述第二制式的通信系统中每个符号的起始传输时刻；
    检测所述第二制式的通信系统中第一符号的起始传输时刻，与扩频后的每一路信号在所述第一符号的持续时间内传输的首个码片序列的起始传输时刻的第一时间差，其中码片序列是对一个符号进行扩频后得到的多个码片所组成的序列；
    若所述第一符号的起始传输时刻与第一路信号中首个码片序列的起始传输时刻的第一时间差不等于0，计算在所述第一时间差内所传输的所述首个码片序列的码片个数n 0；
    根据所述码片个数n 0，确定所述第一路信号所属的信号组中，每一路信号在所述持续时间内采用的扩频码；
    其中，所述第一路信号所属的信号组中，任一路信号在所述持续时间内传输的首个码片序列指示的符号所采用的扩频码包括：所述任一路信号对应的扩频码中第n 0+1至第l'个元素，所述任一路信号在所述持续时间内传输的最后一个码片序列指示的符号所采用的扩频码包括：所述任一路信号对应的扩频码中第1至第(L'+n 0)％l'个元素，l'为所述第一路信号对应的扩频码的扩频因子，L'为所述发射信号在所述单位时间内包括的码片个数，％表示取余数。
  14. 根据权利要求13所述的方法，其特征在于，所述根据所述码片个数n 0，确定所述第一路信号所属的信号组中，每一路信号在所述持续时间内采用的扩频码，包括：
    根据所述发射信号在所述单位时间内包括的码片个数L'，以及所述码片个数n 0，确定对角元素为0或1的(k' i×l')×(k' i×l')的对角矩阵中，取值为1的对角元素所在行包括第(n 0+1)行至第(n 0+L')行，k' i为所述第一路信号在所述第一符号的持续时间内所传输的符号的个数，l'为所述第一路信号对应的扩频码的扩频因子；
    去除所述(k' i×l')×(k' i×l')的对角矩阵中，取值为0的对角元素所在行，生成L'×(k' i×l')的码片提取矩阵K；
    确定所述第一路信号所属的信号组对应的扩频码组成的扩频矩阵W' i满足：
    Figure PCTCN2018120708-appb-100041
    其中，
    Figure PCTCN2018120708-appb-100042
    为k' i阶单位矩阵，V' i为l′×N' i的矩阵，且矩阵V' i中第y'列元素为所述第一路信 号所属的信号组包括的N' i路信号中，第y'路信号对应的扩频码组成的列向量，y'为不大于N' i的正整数。
  15. 根据权利要求1至6任一所述的方法，其特征在于，所述方法还包括：
    当检测到所述第一制式的通信系统中空闲扩频码的数量小于预设个数阈值，或者所述待发送信号的功率大于第二功率阈值时，向所述第二制式的通信系统的基站发送指示信息，所述指示信息用于指示所述第二制式的通信系统的基站在共享的预设频段内的允许调度频段，或者，所述指示信息用于指示所述第二制式的通信系统的基站在预设时间段内停止发送信号。
  16. 一种信号处理装置，其特征在于，应用于第一制式的通信系统的基站，所述装置包括：
    第一获取模块，用于在所述第一制式的通信系统与第二制式的通信系统共享目标频段时，获取所述第一制式的通信系统中至少一路待发送信号，以及每一路所述待发送信号对应的扩频码；
    第一确定模块，用于确定至少一路加扰信号，以及每一路所述加扰信号对应的扩频码；
    第一扩频模块，用于采用每一路所述待发送信号对应的扩频码，对每一路所述待发送信号进行扩频；
    第二扩频模块，用于采用每一路所述加扰信号对应的扩频码，对每一路所述加扰信号进行扩频；
    处理模块，用于对扩频后的至少一路所述待发送信号以及扩频后的至少一路所述加扰信号进行处理得到发射信号，所述发射信号在所述目标频段内的功率小于原始功率，所述原始功率为仅对扩频后的至少一路所述待发送信号进行所述处理后得到的信号在所述目标频段内的功率；
    第一发送模块，用于发送所述发射信号。
  17. 根据权利要求16所述的装置，其特征在于，所述第一确定模块，包括：
    第一确定子模块，用于根据码表中空闲扩频码的数量，确定所述加扰信号的路数N；
    选取子模块，用于从所述码表中的空闲扩频码中选取与N路所述加扰信号一一对应的N个扩频码，所述空闲扩频码不包括所述待发送信号对应的扩频码；
    获取子模块，用于获取所述发射信号在单位时间内的信号模型，所述单位时间为所述第二制式的通信系统中每个符号的持续时间；
    第二确定子模块，用于根据所述信号模型，确定所述发射信号在所述目标频段内的功率模型；
    第三确定子模块，用于根据所述功率模型确定N路所述加扰信号。
  18. 根据权利要求17所述的装置，其特征在于，所述第三确定子模块，用于：
    在N路所述加扰信号在所述单位时间内的总功率小于第一功率阈值的前提下，计算所述功率模型的功率为最小值时，N路所述加扰信号中每一路所述加扰信号在所述单位时间内的符号值。
  19. 根据权利要求18所述的装置，其特征在于，所述处理包括叠加和加扰，所述发射信 号在所述单位时间内包括L个码片，所述L满足：
    Figure PCTCN2018120708-appb-100043
    T 0为所述单位时间，T c为所述第一制式的通信系统的码片周期，INT()表示对括号内的数值取整，所述获取子模块，用于：
    根据所述处理包括的操作类型，以及所述发射信号在所述单位时间内包括的码片个数L，确定所述信号模型为L×1的列向量f，所述列向量f满足：
    Figure PCTCN2018120708-appb-100044
    其中，S为L×L的扰码矩阵，所述扰码矩阵为对角矩阵，且所述扰码矩阵中第l行的对角元素为所述L个码片中第l个码片对应的扰码，l为不大于L的正整数，g为对扩频后的至少一路所述待发送信号进行叠加后得到的信号在所述单位时间内所包括的L个码片所组成的L×1的列向量，w为N路所述加扰信号所包括的组数，每组加扰信号组所包括的至少一路所述加扰信号对应的扩频码的扩频因子相等，各组加扰信号组对应的扩频码的扩频因子的不相等，W i为第i组加扰信号组对应的扩频码组成的L×(k i×N i)的扩频矩阵，i为不大于w的正整数，且W i满足：
    Figure PCTCN2018120708-appb-100045
    表示直积，
    Figure PCTCN2018120708-appb-100046
    为k i阶单位矩阵，W' i为l i×N i的矩阵，l i为所述第i组加扰信号组中每一路所述加扰信号所对应的扩频码的扩频因子，k i为所述第i组加扰信号组中每一路所述加扰信号在所述单位时间内所传输的符号的个数，矩阵W' i中的第y列元素为所述第i组加扰信号组所包括的N i路所述加扰信号中，第y路所述加扰信号对应的扩频码组成的列向量，y为不大于N i的正整数，x i为第i组加扰信号组包括的N i路所述加扰信号所组成的(k i×N i)×1的列向量，所述(k i×N i)×1的列向量包括k i个按列排列的子向量，每个子向量包括的N i个元素分别指示N i路所述加扰信号中的一个符号，W'为w组加扰信号组对应的共w个扩频矩阵按行排列所组成的
    Figure PCTCN2018120708-appb-100047
    的组合扩频矩阵，x'为w组加扰信号组按列排列所组成的
    Figure PCTCN2018120708-appb-100048
    的加扰信号矩阵；
    所述第二确定子模块，用于：
    根据所述目标频段，确定对角元素为0或1的L×L的对角矩阵中，取值为1的对角元素所在行；
    去除所述对角矩阵中，取值为0的对角元素所在行，生成J×L的频段提取矩阵Λ，J为不大于L的正整数；
    根据所述信号模型，确定所述发射信号在所述目标频段内的功率模型P，所述功率模型P满足：
    P＝||ΛF 1f|| 2＝||ΛF 1SW′x′+ΛF 1Sg|| 2，其中，F 1为L×L的频域转换矩阵，||·||表示向量的欧式范数；
    所述第三确定子模块，用于：
    根据所述功率模型P，确定N路所述加扰信号组成的加扰信号矩阵x'，所述加扰信号矩阵x'满足：
    Figure PCTCN2018120708-appb-100049
    其中，P'为所述第一功率阈值。
  20. 根据权利要求18所述的装置，其特征在于，所述处理包括叠加、加扰、采用发射成型形滤波器滤波以及根据过采样因子R进行过采样，R为正整数；所述发射信号在所述单位时间内包括L×R个码片，所述l满足：
    Figure PCTCN2018120708-appb-100050
    T 0为所述单位时间，T c为所述第一制式的通信系统的码片周期，INT()表示对括号内的数值取整，所述获取子模块，用于：
    根据所述处理包括的操作类型，以及所述发射信号在所述单位时间内包括的码片个数L×R，确定所述信号模型为(L×R)×1的列向量f'，所述列向量f'满足：
    Figure PCTCN2018120708-appb-100051
    其中，S为L×L的扰码矩阵，所述扰码矩阵为对角矩阵，且所述扰码矩阵中第i行的对角元素为所述L个码片中第i个码片对应的扰码，g为对扩频后的至少一路所述待发送信号进行叠加后得到的信号在所述单位时间内所包括的L个码片所组成的L×1的列向量，w为N路所述加扰信号所包括的组数，每组加扰信号组所包括的至少一路所述加扰信号对应的扩频码的扩频因子相等，各组加扰信号组对应的扩频码的扩频因子的不相等，W i为第i组加扰信号组对应的扩频码组成的L×(k i×N i)的扩频矩阵，i为不大于w的正整数，且W i满足：
    Figure PCTCN2018120708-appb-100052
    Figure PCTCN2018120708-appb-100053
    表示直积，
    Figure PCTCN2018120708-appb-100054
    为k i阶单位矩阵，W' i为l i×N i的矩阵，l i为所述第i组加扰信号组中每一路所述加扰信号所对应的扩频码的扩频因子，k i为所述第i组加扰信号组中每一路所述加扰信号在所述单位时间内所传输的符号的个数，矩阵W' i中的第y列元素为所述第i组加扰信号组所包括的N i路所述加扰信号中，第y路所述加扰信号对应的扩频码组成的列向量，y为不大于N i的正整数，x i为第i组加扰信号组包括的N i路所述加扰信号所组成的(k i×N i)×1的列向量，所述(k i×N i)×1的列向量包括k i个按列排列的子向量，每个子向量包括的N i个元素分别指示N i路所述加扰信号中的一个符号，W'为w组加扰信号组对应的共w个扩频矩阵按行排列所组成的
    Figure PCTCN2018120708-appb-100055
    的组合扩频矩阵，x'为w组加扰信号组按列排列所组成的
    Figure PCTCN2018120708-appb-100056
    的加扰信号矩阵；H为(L×R)×L的滤波矩阵，所述滤波矩阵H中的第m行第n列的元素H mn满足：
    Figure PCTCN2018120708-appb-100057
    其中，RC 0(t)为所述发射成型滤波器的单位冲激响应函数，m为不大于(L×R)的正整数，n为不大于L的正整数。
    所述第二确定子模块，用于：
    根据所述目标频段，确定对角元素为0或1的(L×R)×(L×R)的对角矩阵中，取值为1的对角元素所在行；
    去除所述(L×R)×(L×R)的对角矩阵中，取值为0的对角元素所在行，生成J'×(L×R)的频段提取矩阵Λ 1，J'为不大于(L×R)的正整数；
    根据所述信号模型，确定所述发射信号在所述目标频段内的功率模型P，所述功率模型P满足：
    P＝||Λ 1F 2f'|| 2＝||Λ 1F 2HSW'x'+Λ 1F 2HSg|| 2，其中，F 2为(L×R)×(L×R)的频域转换矩阵，||·||表示向量的欧式范数；
    所述第三确定子模块，用于：
    根据所述功率模型P，确定N路所述加扰信号组成的加扰信号矩阵x'，所述加扰信号矩阵x'满足：
    Figure PCTCN2018120708-appb-100058
    其中，P'为所述第一功率阈值。
  21. 根据权利要求20所述的装置，其特征在于，所述装置还包括：
    第一检测模块，用于检测所述第一制式的通信系统中基带信号的第一采样频率是否小于所述第二制式的通信系统中基带信号的第二采样频率；
    第二确定模块，用于当所述第一采样频率小于所述第二采样频率时，确定所述过采样因子R为大于或等于2的整数；
    第三确定模块，用于当所述第一采样频率不小于所述第二采样频率时，确定所述过采样因子R为1。
  22. 根据权利要求19至21任一所述的装置，其特征在于，所述第二确定子模块确定对角元素为0或1的对角矩阵中，取值为1的对角元素所在行，包括：
    确定所述第一制式的通信系统所占用的第一频段的中心频率f0；
    判断所述目标频段的下限频率f1、所述目标频段的上限频率f2和所述第一频段的中心频率f0三者的大小；
    当所述中心频率f0满足：f1＜f0≤f2时，确定取值为1的对角元素所在行包括第1行至第
    Figure PCTCN2018120708-appb-100059
    行，以及第
    Figure PCTCN2018120708-appb-100060
    行至第L'行，其中fs为所述第一制式的通信系统的采样频率，其中，L'为所述对角矩阵所包括的总行数；
    当所述中心频率f0满足：f0＞f2时，确定取值为1的对角元素所在行包括第
    Figure PCTCN2018120708-appb-100061
    Figure PCTCN2018120708-appb-100062
    行至第
    Figure PCTCN2018120708-appb-100063
    行；
    当所述中心频率f0满足：f0≤f1时，确定取值为1的对角元素所在行包括第
    Figure PCTCN2018120708-appb-100064
    Figure PCTCN2018120708-appb-100065
    行至第
    Figure PCTCN2018120708-appb-100066
    行。
  23. 根据权利要求22所述的装置，其特征在于，所述第二确定子模块，还用于：
    当所述中心频率f0满足：f1＜f0≤f2时，确定取值为1的对角元素所在行还包括：第
    Figure PCTCN2018120708-appb-100067
    行至第
    Figure PCTCN2018120708-appb-100068
    行，和/或，第
    Figure PCTCN2018120708-appb-100069
    Figure PCTCN2018120708-appb-100070
    行至第
    Figure PCTCN2018120708-appb-100071
    行；
    当所述中心频率f0满足：f0＞f2时，确定取值为1的对角元素所在行还包括：第
    Figure PCTCN2018120708-appb-100072
    Figure PCTCN2018120708-appb-100073
    行至第
    Figure PCTCN2018120708-appb-100074
    行，和/或，第
    Figure PCTCN2018120708-appb-100075
    行至第
    Figure PCTCN2018120708-appb-100076
    行；
    当所述中心频率f0满足：f0≤f1时，确定取值为1的对角元素所在行还包括第
    Figure PCTCN2018120708-appb-100077
    Figure PCTCN2018120708-appb-100078
    行至第
    Figure PCTCN2018120708-appb-100079
    行，和/或，第
    Figure PCTCN2018120708-appb-100080
    行至第
    Figure PCTCN2018120708-appb-100081
    Figure PCTCN2018120708-appb-100082
    行；
    其中，Δ1、Δ2、Δ3、Δ4、Δ5和Δ6均为正整数。
  24. 根据权利要求22所述的装置，其特征在于，所述第二确定子模块，还用于：
    检测所述目标频段是否为连续频段；
    第二确定子模块判断所述目标频段的下限频率f1、所述目标频段的上限频率f2和所述第一频段的中心频率f0三者的大小，包括：
    当所述目标频段为连续频段时，判断所述目标频段的下限频率f1、所述目标频段的上限频率f2和所述第一频段的中心频率f0三者的大小；
    当所述目标频段不为连续频段时，所述第二确定子模块，还用于：
    分别确定所述目标频段中每个子频段对应的取值为1的对角元素所在行；将所述目标频段中各个子频段对应的取值为1的对角元素所在行的合集，确定为所述对角元素为0或1的对角矩阵中，取值为1的对角元素所在行。
  25. 根据权利要求16至21任一所述的装置，其特征在于，所述第一制式的通信系统的基站还用于发送所述第二制式的通信系统的信号，所述装置还包括：
    第四确定模块，用于确定所述第一制式的通信系统所占用的第一频段，以及所述第二制式的通信系统所占用的第二频段；
    所述第一发送模块，还用于若所述第二频段位于所述第一频段内，在发送所述第二制式的通信系统的信号时，采用所述第一制式的通信系统的发射成型滤波器对所述第二制式的通信系统的信号进行处理后发送。
  26. 根据权利要求16至21任一所述的装置，其特征在于，所述第一制式的通信系统与所述第二制式的通信系统共享的频段为预设频段，所述装置还包括：
    第二获取模块，用于获取所述第二制式的通信系统的调度信息，所述调度信息包括所述第二制式的通信系统的调度频段；
    第五确定模块，用于将所述调度频段和所述预设频段之间的重叠频段确定为所述目标频段。
  27. 根据权利要求16至21任一所述的装置，其特征在于，所述第一发送模块，用于：
    采用窄带宽滤波器对所述发射信号进行滤波后发送，所述窄带宽滤波器包括带通滤波器、带阻滤波器、高通滤波器和低通滤波器中的任一种；
    所述第一制式的通信系统与所述第二制式的通信系统共享的频段为预设频段，所述装置还包括：
    第二获取模块，用于获取所述第二制式的通信系统的调度信息，所述调度信息包括所述第二制式的通信系统的调度频段；
    第六确定模块，用于将所述调度频段中与所述窄带宽滤波器的通带重叠的部分确定为所述目标频段。
  28. 根据权利要求19至21任一所述的装置，其特征在于，所述获取子模块，还用于：
    获取所述第二制式的通信系统中每个符号的起始传输时刻；
    检测所述第二制式的通信系统中第一符号的起始传输时刻，与扩频后的每一路信号在所述第一符号的持续时间内传输的首个码片序列的起始传输时刻的第一时间差，其中码片序列是对一个符号进行扩频后得到的多个码片所组成的序列；
    在所述第一符号的起始传输时刻与第一路信号中首个码片序列的起始传输时刻的第一时间差不等于0时，计算在所述第一时间差内所传输的所述首个码片序列的码片个数n 0；
    根据所述码片个数n 0，确定所述第一路信号所属的信号组中，每一路信号在所述持续时间内采用的扩频码；
    其中，所述第一路信号所属的信号组中，任一路信号在所述持续时间内传输的首个码片序列指示的符号所采用的扩频码包括：所述任一路信号对应的扩频码中第n 0+1至第l'个元素，所述任一路信号在所述持续时间内传输的最后一个码片序列指示的符号所采用的扩频码包括：所述任一路信号对应的扩频码中第1至第(L'+n 0)％l'个元素，l'为所述第一路信号对应的扩频码的扩频因子，L'为所述发射信号在所述单位时间内包括的码片个数，％表示取余数。
  29. 根据权利要求28所述的装置，其特征在于，所述获取子模块根据所述码片个数n 0，确定所述第一路信号所属的信号组中，每一路信号在所述持续时间内采用的扩频码，包括：
    根据所述发射信号在所述单位时间内包括的码片个数L'，以及所述码片个数n 0，确定对角元素为0或1的(k' i×l')×(k' i×l')的对角矩阵中，取值为1的对角元素所在行包括第(n 0+1)行至第(n 0+L')行，k' i为所述第一路信号在所述第一符号的持续时间内所传输的符号的个数，l'为所述第一路信号对应的扩频码的扩频因子；
    去除所述(k' i×l')×(k' i×l')的对角矩阵中，取值为0的对角元素所在行，生成L'×(k' i×l')的码片提取矩阵K；
    确定所述第一路信号所属的信号组对应的扩频码组成的扩频矩阵W' i满足：
    Figure PCTCN2018120708-appb-100083
    Figure PCTCN2018120708-appb-100084
    其中，
    Figure PCTCN2018120708-appb-100085
    为k' i阶单位矩阵，V' i为l'×N' i的矩阵，且矩阵V' i中第y'列元素为所述第一路信号所属的信号组包括的N' i路信号中，第y'路信号对应的扩频码组成的列向量，y'为不大于N' i的正整数。
  30. 根据权利要求16至21任一所述的装置，其特征在于，所述装置还包括：
    第二发送模块，用于当检测到所述第一制式的通信系统中空闲扩频码的数量小于预设个数阈值，或者所述待发送信号的功率大于第二功率阈值时，向所述第二制式的通信系统的基站发送指示信息；
    所述指示信息用于指示所述第二制式的通信系统的基站在共享的预设频段内的允许调度频段，或者，所述指示信息用于指示所述第二制式的通信系统的基站在预设时间段内停止发送信号。
  31. 一种计算机可读存储介质，其特征在于，所述计算机可读存储介质中存储有指令，当所述计算机可读存储介质在计算机上运行时，使得计算机执行权利要求1至15任一所述的信号处理方法。
  32. 一种芯片，其特征在于，所述芯片包括可编程逻辑电路和/或程序指令，当所述芯片运行时用于实现如权利要求1至15任一所述的信号处理方法。
  33. 一种信号处理系统，其特征在于，所述系统包括：基站和至少一个终端设备；
    所述基站包括如权利要求16至30任一所述的信号处理装置。
PCT/CN2018/120708 2017-12-20 2018-12-12 信号处理方法、装置及系统 WO2019120126A1 (zh)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
CN201711387988.1A CN109951852B (zh) 2017-12-20 2017-12-20 信号处理方法、装置及系统
CN201711387988.1 2017-12-20

Publications (1)

Publication Number Publication Date
WO2019120126A1 true WO2019120126A1 (zh) 2019-06-27

Family

ID=66993041

Family Applications (1)

Application Number Title Priority Date Filing Date
PCT/CN2018/120708 WO2019120126A1 (zh) 2017-12-20 2018-12-12 信号处理方法、装置及系统

Country Status (2)

Country Link
CN (1) CN109951852B (zh)
WO (1) WO2019120126A1 (zh)

Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20230006705A1 (en) * 2019-12-13 2023-01-05 Huizhou Tcl Mobile Communication Co., Ltd. Method and device for downlink signal transmission in dual-connection architecture, and terminal

Families Citing this family (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN113542164B (zh) * 2021-07-13 2023-03-31 电子科技大学 一种盲信号检测中的通信参数估计方法及系统
CN114499554B (zh) * 2021-12-31 2024-06-11 华为技术有限公司 一种发送数据的方法、射频装置和控制装置
WO2024036949A1 (zh) * 2022-08-19 2024-02-22 华为技术有限公司 信号处理方法及装置

Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN1773895A (zh) * 2004-11-12 2006-05-17 株式会社Ntt都科摩 基站和扰码设定方法
EP2141935A1 (en) * 2007-03-30 2010-01-06 NTT DoCoMo, Inc. Mobile communication system, base station device, and user device and method
CN102833760A (zh) * 2011-06-15 2012-12-19 电信科学技术研究院 异系统间频谱共享情况下的干扰抑制方法和设备
WO2016101882A1 (zh) * 2014-12-26 2016-06-30 上海无线通信研究中心 一种网络间干扰协调方法

Family Cites Families (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
GB2447439B (en) * 2007-02-02 2012-01-25 Ubiquisys Ltd Access point power control
CN105453657B (zh) * 2014-06-16 2019-07-09 华为技术有限公司 一种接入点、站点、接入控制器及噪声发射方法
US10153970B2 (en) * 2014-11-26 2018-12-11 Qualcomm Incorporated Partial channel reservation on a shared communication medium
US20160234757A1 (en) * 2015-02-11 2016-08-11 Qualcomm Incorporated Discovering long term evolution (lte) advanced in unlicensed spectrum base stations

Patent Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN1773895A (zh) * 2004-11-12 2006-05-17 株式会社Ntt都科摩 基站和扰码设定方法
EP2141935A1 (en) * 2007-03-30 2010-01-06 NTT DoCoMo, Inc. Mobile communication system, base station device, and user device and method
CN102833760A (zh) * 2011-06-15 2012-12-19 电信科学技术研究院 异系统间频谱共享情况下的干扰抑制方法和设备
WO2016101882A1 (zh) * 2014-12-26 2016-06-30 上海无线通信研究中心 一种网络间干扰协调方法

Cited By (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20230006705A1 (en) * 2019-12-13 2023-01-05 Huizhou Tcl Mobile Communication Co., Ltd. Method and device for downlink signal transmission in dual-connection architecture, and terminal
US12028100B2 (en) * 2019-12-13 2024-07-02 Huizhou Tcl Mobile Communication Co., Ltd. Method and device for downlink signal transmission in dual-connection architecture, and terminal

Also Published As

Publication number Publication date
CN109951852B (zh) 2021-08-13
CN109951852A (zh) 2019-06-28

Similar Documents

Publication Publication Date Title
WO2019120126A1 (zh) 信号处理方法、装置及系统
US20220060303A1 (en) Nb lte prach design
AU2021215138B2 (en) Method for configuring transmission direction of time-frequency resource, and apparatus
CN105814829B (zh) 无线通信系统中的参考信号生成方法、设备和计算机可读介质
WO2016029364A1 (zh) 一种无线通信方法、设备及系统
CN109041199A (zh) 一种同步信号的传输方法和装置
CN107836129A (zh) 一种数据传输的方法、无线网络设备和通信系统
JP6740415B2 (ja) ライセンス不要アクセスについてのプリアンブルについての装置、システム、及び方法
WO2017052823A1 (en) Methods of performing communications, mobile terminal devices, and baseband modems
CN108811165A (zh) 资源配置的方法及装置
KR20150065807A (ko) 무선 시스템의 수신기 및 송신기를 위한 장치들, 방법들, 및 컴퓨터 프로그램들
US10014994B2 (en) Wireless devices, computer-readable media, and methods for high-efficiency local-area network (HEW) distributed sub-carrier allocation
US20230088011A1 (en) Resource configuration method and apparatus, terminal device and network device
US20220369386A1 (en) Wireless communication method, terminal device, and network device
CN116783974A (zh) 信道接入方法及设备
JP7358380B2 (ja) 送信装置、受信装置、送信方法及び受信方法
WO2023197154A1 (zh) 无线通信的方法、终端设备和网络设备
CN117461277A (zh) 无线通信的方法、终端设备和网络设备
CN117998591A (zh) 通信方法、装置、设备、存储介质及程序产品
CN118120306A (zh) 侧行通信方法和设备

Legal Events

Date Code Title Description
121 Ep: the epo has been informed by wipo that ep was designated in this application

Ref document number: 18892701

Country of ref document: EP

Kind code of ref document: A1

NENP Non-entry into the national phase

Ref country code: DE

122 Ep: pct application non-entry in european phase

Ref document number: 18892701

Country of ref document: EP

Kind code of ref document: A1