WO2019057771A1 - Convertisseur ca/cc comprenant des modules de phase formant convertisseurs élévateurs-abaisseurs - Google Patents

Convertisseur ca/cc comprenant des modules de phase formant convertisseurs élévateurs-abaisseurs Download PDF

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Publication number
WO2019057771A1
WO2019057771A1 PCT/EP2018/075349 EP2018075349W WO2019057771A1 WO 2019057771 A1 WO2019057771 A1 WO 2019057771A1 EP 2018075349 W EP2018075349 W EP 2018075349W WO 2019057771 A1 WO2019057771 A1 WO 2019057771A1
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Prior art keywords
converter
phase
output
voltage
load
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PCT/EP2018/075349
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German (de)
English (en)
Inventor
Michael Georg LEIBL
Lukas Franz Josef SCHRITTWIESER
Johann Walter Kolar
Dominik Bortis
Michail Marios ANTIVACHIS
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ETH Zürich
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Publication of WO2019057771A1 publication Critical patent/WO2019057771A1/fr

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H02M7/539—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters with automatic control of output wave form or frequency
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/66—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output with possibility of reversal
    • H02M7/68—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output with possibility of reversal by static converters
    • H02M7/72—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output with possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/79—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output with possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/797—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output with possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H02M3/1582—Buck-boost converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0043—Converters switched with a phase shift, i.e. interleaved
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/12—Arrangements for reducing harmonics from ac input or output
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/14—Arrangements for reducing ripples from dc input or output
    • H02M1/15—Arrangements for reducing ripples from dc input or output using active elements
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H02M3/1584—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load with a plurality of power processing stages connected in parallel
    • H02M3/1586—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load with a plurality of power processing stages connected in parallel switched with a phase shift, i.e. interleaved
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H02M7/539—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters with automatic control of output wave form or frequency
    • H02M7/5395—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters with automatic control of output wave form or frequency by pulse-width modulation

Definitions

  • AC system DC / AC conversion
  • UPS uninterruptible power supplies
  • the input DC voltage level in this case has due to the typically highly dependent on the state of charge terminal voltage electrochemical storage or
  • Fuel cells drive technology or UPS
  • solar cells photovoltaic
  • Input side DC / DC step-up converter a voltage intermediate circuit and an output side three-phase DC / AC converter (inverter) is executed (see Fig.l).
  • the inverter which in the end acts as a step-down converter in the case of power flow from the DC side to the three-phase AC side, can advantageously be designed for operation with a constant intermediate circuit voltage and thus with minimum construction output.
  • the DC link voltage level higher than the DC input voltage it is possible to generate a relatively high output voltage, which can be maintained independently of the battery state of charge, or can operate at the point of maximum power delivery regardless of the irradiation intensity and temperature for photovoltaic systems.
  • the high DC link voltage offers the advantage of mastering a wide speed range of a powered AC machine.
  • the intermediate circuit voltage becomes a three-phase
  • Pulse width modulated voltage system generates and in the realization of a
  • Variable speed drive in the simplest case, placed directly on the motor terminals.
  • stator current typically has a high switching-frequency ripple, which can lead to high rotor losses and thus due to the air gap limited cooling to a significant thermal load of the rotor. Furthermore, caused by the switching frequency common mode component of the machine terminal voltages bearing currents, which can lead to a destruction of the raceways of the bearing, to call disadvantageous.
  • the mentioned disadvantages can be achieved by a three-phase LC output filter of the inverter, which switching frequency harmonics of the pulse width modulated
  • this LC output filter must always be arranged, since the connected AC consumers i.A. must be supplied with a, deviating only slightly from a purely sinusoidal voltage.
  • the LC output filter is the first stage of an EMC filter intended to suppress the propagation of switching-frequency electromagnetic disturbances (currents) into the three-phase network.
  • the DC / DC step-up converter then works as a DC / DC step-down converter as a result of the reversed energy direction from the intermediate circuit voltage (it is antiparallel to the step-up converter diode for this purpose)
  • the three-phase AC / DC converter acts as an active rectifier in this case and ensures a sinusoidal profile of the currents absorbed by the grid and a constant value of the DC link voltage.
  • the literature has therefore proposed single-stage DC / AC converters which are formed from three identical bidirectional DC / DC phase converters having a common negative voltage rail and starting from the same DC Supply voltage three sinusoidally varying, phase-shifted offset, ie always opposite the negative voltage rail positively remaining voltages
  • Phase converter output voltages by shifting a symmetrical phase in-line load voltage system (which ultimately between the assigned
  • Phase terminal and the free neutral point of the three-phase load to be supplied formed by a positive offset in the amount of the amplitude of the Phasensinuslastschreiben.
  • Control method for which a phase converter output remains clamped in each case for one third of the output voltage period on the negative voltage rail, wherein in each case the phase with the most negative instantaneous value of the associated
  • Phasensinuslastschreib clamped and only the other two Cuk DC / DC phase converter clocks and generate output voltages such that compared to the clamped phase output sections of the respective outer conductor voltages are generated.
  • a reduction of the switching losses of the system is possible, further occurs at the output of a phase converter at most the value of the amplitude of the fundamental to be formed Bisaussenleiterschreib and not twice the value of the amplitude of the phase sink voltage.
  • the Bisaussenleiterdition shows a smooth course due to the arranged at the output of the Cuk DC / DC phase converter smoothing capacitors.
  • the object of the invention is therefore to provide a converter for the transmission of electrical energy between a DC and an AC system, which remedies at least one of the abovementioned disadvantages and has at least one of the following properties: and output voltage range, and produces continuous (filtered) output phase AC voltages, that it has a minimum number of inductive elements, that of lower
  • Power semiconductors are low, that he has a multi-loop control of the phase converter has, so that a high dynamics of the control of the phase converter output voltages is given.
  • the converter for transferring electrical energy between a DC system and an AC system has a positive DC input voltage rail on the DC side and a negative DC input voltage rail and at least two output phase terminals on the AC side.
  • there is a phase converter for each of the output phase terminals which is connected on a first side to the positive DC input voltage rail and the negative DC input voltage rail and on a second side to this output phase terminal and is designed as a step-up buck converter.
  • the converter has a control, which is designed, in the operation of the converter, each of the
  • Phase converter in response to a ratio of a DC input voltage to instantaneous values to be generated at the output phase terminals
  • Output phase voltages temporarily operated either as a pure buck converter or as a pure boost converter.
  • phase converters are not embodied as DC / DC Cuk converters but as multi-loop regulated step-down DC / DC converters, the specification of the setpoint values of the phase converter output voltages being such that, on the one hand, a minimum
  • control is adapted, in the operation of the converter in each of the phase converter, a timing of switches of the phase converter temporarily to a .
  • the regulation is designed to make the clocking of all phase converters in operation of the converter such that the same clock frequency is present for all phase converters and synchronization of the clocking of the converters minimizes a differential voltage component contained in the output phase voltages.
  • control is designed to perform the clocking of all phase converters during operation of the converter such that the same clock frequency is present for all phase converters and synchronization of the clocking of the converters minimizes a common-mode voltage component contained in the output phase voltages.
  • control is configured to offset the formation of output phase voltage setpoints during operation of the converter
  • Reference voltage rail may remain clamped
  • Phase converters is defined by the setpoint values of load external conductor voltages formed relative to the clamped output phase connection and formed by subtracting in each case two load phase voltage nominal values in this time segment, so that overall there is a sinusoidal profile of all the load external conductor voltages.
  • the phase converters are each formed as a cascaded buck-boost converter.
  • the phase converters are each realized by a circuit in which a bridge branch between the positive DC input voltage rail and a associated output phase terminal is arranged, a phase converter inductance between a center of the bridge branch and the negative DC input voltage rail is connected, an output capacitance between the
  • Output phase terminal and a common reference voltage rail is connected, which is connected to the DC input voltage rail.
  • an output diode is connected between the output phase terminal and the reference voltage rail, respectively, which has a positive output phase voltage at the output phase terminal relative to the output phase terminal
  • a switch can also be connected in parallel, or the output diode can be replaced by a switch with antiparallel output diode.
  • the phase with the lowest voltage can each be clamped over one third of the period (no switching losses for this phase) and thus the converter efficiency can be increased.
  • control is designed to select a constant offset of the output phase voltages so large during operation of the converter at relatively small amplitudes of the output phase voltages, that on the one hand, caused by generated load phase voltages fluctuation of the output phase voltages to lie symmetrically about a level of the DC input voltage
  • a double maximum amplitude of load phase voltages is not exceeded, this being achieved by lowering the offset at high amplitudes of the load phase voltages.
  • Fig. 1 Bidirectional three-phase buck-boost converter DC / AC converter system according to the prior art with input side DC / DC boost converter, DC link capacitor, output side voltage intermediate three-phase inverter and downstream LC output filter for generating a smoothed three-phase AC output voltage.
  • Fig. 2 Converter system with each arrangement of a DC / DC Wegsetzsteilers per output phase, each phase converter has an input side and a
  • Fig. 3 Time course of the supply of a three-phase machine to be generated
  • FIG. 5 shows the time curve of the setpoint values uout * of the phase converter output voltages uout (the individual voltages uan, ubn, ucn are designated uout in summary for the converter circuits according to FIG. 2, which have a lower amplitude UMpk of the setpoint values than the DC input voltage Uin the load phase voltages uM * can be used to achieve a minimization of the switching-frequency fluctuation of the current in the phase converter inductance (see Fig. 5.1) .
  • Figure 5.2 shows the time characteristic associated with the converter circuit according to Fig. 4, which is an alternative to Fig. 5.1 can also be used for the converter circuit according to Fig.2.
  • 2uMpk, max denotes the maximum value of the phase converter output voltages uout occurring at maximum load phase voltage amplitude; the associated time sequences of uout are shown in dotted lines.
  • Fig. 6 Device for controlling the output voltages of the phase converter to set a predetermined curve uM * the load phase voltages uM, as required for UPS systems or in the supply of variable speed three-phase machines.
  • the regulation has the same structure for each phase and is shown for the sake of clarity only for one phase.
  • Fig. 7 Apparatus for controlling the DC output voltage formed in the interaction of all the phase converter when using the converter system as
  • Three-phase pulse rectifier circuit wherein by a subordinate control a sinusoidal course of the network phase currents, each in phase with the associated
  • FIG. 9 shows an alternative embodiment of a part of the control circuit according to FIG. 6 to FIG. 8.
  • Each system phase converter (see FIG. 2) has an input-side bridge branch 3a, 3b, 3c located between the positive DC input voltage rail 1 and the negative DC input voltage rail 2, which is connected in series with an upper, typically collector or drain side, with the positive DC input voltage rail connected and a lower, typically emitter or source side connected to the negative DC input voltage rail switch, generally one
  • the bridge branch output 4a, 4b, 4c forms of which branches off a phase converter inductance La, LD, LC, which is connected with its second end to the input 5a, 5b, 5c of another output-side bridge branch 6a, 6b, 6c, wherein the source terminal of the lower switch or transistor of this bridge branch with a reference voltage rail n and the drain terminal of the upper transistor of this bridge branch is connected to the associated output phase terminal a, b, c, wherein to ensure a smooth course of the
  • Reference voltage rail is a smoothing capacitance Ca, Cb, Cc.
  • Phase converter common reference voltage rail n is finally connected to the negative rail 2 of the DC input voltage, whereby each phase converter advantageously has the structure of a buck-boost DC / DC converter and the entire three-phase DC / AC converter system only three inductors La, Lb, Lc.
  • a three-phase load is connected with its phase terminals to the output phase terminals a, b, c of the three phase converter and has a free neutral point, so that only the chained phase converter output voltages (load transient voltages), defined as the difference of two phase converter output voltages or a load phase terminal against a Laststernyak measured load phase voltage determines the formation of the load phase currents.
  • load transient voltages load transient voltages
  • phase converter output voltages are generated in such a way that the nominal values of the load phase voltages u_an, u_bn, u_cn, which typically have an output frequency sinusoidal and form a symmetrical three-phase system, are shifted to positive values (see FIG Phase output voltage a unipolar curve, ie only positive values or minimally shows the value zero. As mentioned above, this offset does not become effective in the load output voltages, and thus does not affect the current generation of the load.
  • another offset of three times the output frequency and an amplitude and phase may be added to this constant offset so as to ensure the unipolarity of the output phase voltages with a minimum value of the constant offset, whereby the voltage loading of the transistors of the output side bridge branches 6a, 6b, 6c the phase converter can be minimized at a defined load phase voltage amplitude to be generated (see FIG. 3.2).
  • the timing of the input and output side bridge branches 6a, 6b, 6c of the phase converter it should be noted that in regions in which a phase converter output voltage lying above the DC input voltage has to be generated, the upper switch or power transistor of the input side bridge branch 3a, 3b, 3c a phase converter can remain switched through, and only the output-side bridge branch 6a, 6b, 6c is clocked. The voltage ratio of the converter then corresponds to power flow from the DC input voltage to
  • Boost converter transistor and the antiparallel diode of the upper power transistor acts as a boost converter freewheeling diode, wherein in embodiments always the upper power transistor is also turned on, i. the power transistors of the output side bridge branch 6a, 6b, 6c are operated in push-pull. Since all power transistors antiparallel diodes are arranged, then a power flow of the
  • Phase converter output voltage into the DC input voltage wherein the function of the phase converter in this case, the one between
  • Phase converter output voltage and DC input voltage lying buck converter corresponds.
  • Phase converter output voltage must be generated remains in embodiments of the upper power transistor of the output side bridge branch 6a, 6b, 6c of the
  • Bridge branch 3a, 3b, 3c limited.
  • the voltage ratio of the converter then corresponds to power flow from the DC input voltage to
  • Phase converter inductance as Tiefsetzstellerindukt technically the upper power transistor of the input side bridge branch 3a, 3b, 3c as a buck converter transistor and anti-parallel to the lower power transistor diode acts as a buck converter freewheeling diode, in embodiments always switched through the lower power transistor, ie the power transistors of the input-side bridge branch 3a, 3b, 3c be operated in push-pull. Since antiparallel diodes are arranged for all power transistors, can then also be a power flow from the phase converter output voltage to the DC input voltage, wherein the function of the phase converter in this case corresponds to a lying between phase converter output voltage and DC input voltage boost converter.
  • Phase converter output voltages contained push-pull voltage component which leads to switching-frequency currents and thus possibly to high-frequency losses in the connected three-phase load is minimized, i. Switching frequency changes of the
  • Phase converter output voltages are mainly formed as common mode components, which cause a similar voltage shift relative to the reference voltage rail for all phase outputs.
  • Common mode shifts are sensitive, on the other hand, a synchronization of working again with the same clock frequency phase converter can be made such that the switching frequency common mode voltages are minimized, in which case, however, a higher differential mode component of the phase converter output voltages is to be accepted.
  • Output phase terminal may remain clamped to the reference voltage rail, which for the above-described phase converter topology (see Figure 2) by simply
  • Phase converter is then directly by the opposite of the clamped phase to be generated and by subtracting two load phase voltage setpoints to forming sections of the setpoints of the load Aussenleiterhoven defined so that a total of a sinusoidal waveform of all three load outer conductor voltages is reached again. Since the clamping is passed cyclically between the phases, each phase remains clamped for a third of the load phase voltage period when generating a sinusoidal balanced load phase voltage system and thus without switching losses, thus increasing the efficiency of energy transfer is achieved.
  • the input and / or output side bridge branch may advantageously be in multi-level structure, e.g. be performed as Flying Capacitor Multilevelbridge branch, which for setting the voltage ratio between DC input voltage and phase converter output voltage, a higher number of
  • the phase converters may be implemented by a plurality of parallel out-of-phase clocked systems, whereby the current fed into the output capacitance and from the DC input voltage relative to a single system advantageously has a higher effective frequency and a smaller variation.
  • FIG. 4 A converter system in embodiments with phase converters of relatively low complexity is shown in FIG. 4, where in each phase only one bridge branch is arranged between the positive terminal of the DC input voltage and the associated output or load phase terminal for realizing the bi-directional DC / DC step-down converter is and the associated phase converter inductance is connected from the center of the bridge branch to the reference voltage rail.
  • Output phase voltages must be taken into account (ie, the voltage is counted from the reference voltage rail against the phase terminals).
  • further diodes can be placed against the reference voltage rail starting from the output terminals of the phase converters. According to a clamp circuit is then in the presence of an active three-phase load or when connecting a three-phase network instead of a three-phase load, a polarity reversal of
  • a switch can also be connected in parallel in each case, or the output diode can be replaced by a switch with antiparallel output diode.
  • phase converters with an input and output side bridge branch see FIG. 2
  • the free-wheeling diodes of the output-side bridge branch act as clamping diodes during run-up and therefore no further explicit diodes are to be provided.
  • the constant offset can now be selected to be so large for the circuit according to FIG. 2 at low rotational speeds or relatively small amplitudes of the phase converter output voltages that, on the one hand, the fluctuation of the phase converter output voltages caused by the load phase voltages to be generated is symmetrical about the level of the DC input voltage on the other hand, the maximum speed associated twice maximum amplitude of the load phase voltage is not exceeded, this by lowering the offset correspondingly at high Amplitudes of the load phase voltages is achieved. As shown in FIG.
  • the setpoint values of the phase converter output voltages then typically have minimum values significantly greater than zero, and the currents in the phase converter inductors exhibit a relatively small ripple, since then the input and output side bridge branches operate alternately with duty ratios close to one (ie each upper
  • Bridge branches is thus an improvement in the efficiency of energy transfer achievable.
  • the phase converter output phase voltages are always as low as possible, in contrast to Fig. 5.1.
  • the constant offset regardless of the amplitude of the load phase voltage or machine speed to keep as small as possible, so only to choose so large that zero occurs as a minimum voltage value (see Fig.5.2). This is because then the upper power transistors of the input side bridge branches of the phase converters have low duty cycles, again resulting in a small variation in the currents in the phase converter inductors.
  • FIG. 2 A cascaded control of the three-phase converter system according to FIG. 2 is shown in FIG.
  • the control circuit is similar for each phase and shown in the interest of clarity only for one phase. Tensions are, as registered against the
  • the nominal value of a phase converter output voltage uout * is obtained by adding the typically sinusoidal setpoint value uM * of the associated
  • Load phase voltage uM of a fed three-phase load (eg an electric machine M) and the same for all phases setpoint uoff * offset uoff formed, which is typically generated by adding a constant over the output period proportion uoffDC * and a three times the output frequency fluctuating portion uoffAC *.
  • the time course of uoff * is selected such that uout * is limited to the lowest possible values for a given load-phase voltage system uM * to be generated , r
  • phase converter output voltage reference value uout * is compared with the measured actual value of the phase converter output voltage, and the deviation Deltout is fed to a phase converter output voltage controller Ruout, at the output of which is required to correct deltaoutput
  • Output capacitor current setpoint iCout * is formed, which by pre-control of the measured associated load phase current iLoad the output current i of the output side bridge branch BB of the phase converter determined by dividing by the duty cycle dB of the upper transistor T3 of this bridge branch in a target value iL * of the current iL in the Phase converter inductance L can be converted.
  • iL * By comparing iL * with the measured actual value iL, the control deviation deltaiL of the current is then formed in L and a
  • Phase inductance current regulator RiL supplied, which forms at its output the required to correct the deviation DeltaiL setpoint uL * the voltage to be applied to L.
  • the setpoint uA * is the one on the input side End A of L to be placed or to be generated at the output A of the input-side bridge branch BA voltage uA to be generated by adding uL * and uout.
  • the duty cycle dA i. the relative duty cycle of the upper transistor Tl of BA is then simply obtained in the sense of a step-down function of BB by dividing uA * and the actual value of the DC input voltage Vin.
  • uA * must be limited upwards by Uin and downwards by the value zero.
  • the relative duty cycle of the bridge branch BB can be easily generated by subtracting from uA * the measured DC input voltage Uin.
  • the way Difference obtained delta uA * is limited downwards by the value zero and upwards by uout, which corresponds to the physically adjustable limits of uA. If a positive value DeltauA * now occurs, this ultimately means that BB above L for correct
  • control circuit according to FIG. 6 also controls the operation for voltages Uin ⁇ uout, since the activation of the bridge branches BA and BB is indeed derived directly from the desired value uL * and the actual values uout and Uin.
  • control circuit is therefore independent of the respective ratio of Uin and uout * and also for both
  • Power flow directions i. for supplying a motor M Uin or feedback of braking energy of the motor M can be used in Uin.
  • the drive signals of the push-pull bridge arms BA and BB are obtained from dA and dB by corresponding pulse width modulation.
  • the converter circuit can be used on the one hand to supply an electric machine M, but on the other hand also as a three-phase rectifier system with advantageously sinusoidal mains currents iN and a regulated to a constant value DC output voltage Uout.
  • the difference between the DC output voltage setpoint Uout * and the measured value uout is formed and the control deviation Deltauout is fed to an output voltage regulator Ruout which is common to all phase converters and which at its output is used for a corresponding charge change of Cout
  • Phase voltage uinY to which a setpoint value of an offset that is the same for all phases, uoff, is added by the setpoint value uin * to the reference voltage rail n to receive related phase converter input voltage uin.
  • the offset setpoint value uoff * is typically generated by adding a constant component uoffDC * over the network period and a component uoffAC * fluctuating with three times the network frequency, and is designed so that uin * is limited to the lowest possible values uN for a given network phase voltage system the reverse voltage stress and the switching losses of the input side bridge branches of the phase converter can be minimized.
  • phase converter input voltage reference uin * is then used with the
  • Control deviation delta is fed to a phase converter input voltage controller Ruin, at the output of which is required for the correction of delta time
  • Input capacitor current setpoint iCin * is formed, which is subtracted from the setpoint value iN * of the associated line phase current to obtain the setpoint value iin * of the input current iin of the input-side bridge branch BA of the phase converter.
  • the setpoint value iL * of the current iL in the phase converter inductance L can then be obtained.
  • the comparison (subtraction) of iL * with the associated measured value iL leads to the deviation DeltaiL of the current in L which is supplied to a Phaseninduktriossstromregler RiL, at its output the setpoint uL * to correct the
  • Control deviation DeltaiL forms over L to be applied voltage uL.
  • the remaining control circuit between iL * and the relative on durations dA and dB of the bridge branches BA and BB is the same as for the circuit of Figure 6, which is why a description can be omitted here.
  • the control circuit according to Figure 6 and Figure 7 is based on a buck converter operation of the input side bridge branch BA and a through state of the transistor T3 of the output side bridge branch BB as regular operation, but also the case of a lying above the input voltage output of a phase converter, ie the boost converter operation is mastered.
  • the boost converter operation of the converter ie, a steady state of Tl and clocking of the bridge branch BB can be considered as a regular operation, which results in the alternative embodiment shown in FIG. 8 of a part of the control circuits of Figure 6 and Figure 7.
  • the remaining parts of the control circuits remain unchanged. The following description is therefore limited to the part of the already described devices to be replaced.
  • the setpoint value uL * is inverted and then physically from the output side to
  • Input voltage uin the phase converter added to determine the voltage setpoint uB * to be set at input B of BB. After limiting to uout up and zero down - it is only possible to set dB between zero and one - so the duty cycle, i. obtained the duty cycle of the upper transistor T3 of BB.
  • the control circuit also controls the operation for voltages uin> uout, since the activation of the bridge branches BB and BA yes directly from the setpoint uL * (and the actual values uin and uout) is derived.
  • the control circuit is therefore independent of the respective ratio of uin and uout and also for both power flow directions, i. for feeding a motor M from uin, or for realization of a photovoltaic inverter for feeding photovoltaic generated power (uin then represents the voltage of the
  • Solar panels dar or for the recovery of braking energy of a three-phase motor M in the DC input voltage uin, or for the operation of the device as an active three-phase rectifier system (generating a DC output voltage uout) can be used.
  • the setpoint value uL * is subtracted from the input voltage uin and limited up to uout and down to zero.

Landscapes

  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)
  • Inverter Devices (AREA)

Abstract

L'invention concerne un convertisseur servant à transférer une énergie électrique entre un système à tension continue (CC) et un système à tension alternative. Le convertisseur comporte côté tension continue un rail de tension d'entrée CC positif (1) et un rail de tension d'entrée CC négatif (2) et, côté tension alternative, au moins deux raccords de phase de sortie (a, b, c). Un convertisseur de phases (10a, 10b, 10c) est présent pour chacun des raccordements de phase de sortie (a, b, c) et est raccordé sur un premier côté au rail de tension d'entrée CC positif (1) et au rail de tension d'entrée CC négatif (2) et, sur un deuxième côté, audit raccordement de phase de sortie (a ; b ; c) et est réalisé sous la forme d'un convertisseur élévateur-abaisseur. Le convertisseur comporte un système de régulation qui est réalisé pour faire fonctionner, lors du fonctionnement du convertisseur, chacun des convertisseurs de phases (10a, 10b, 10c) en fonction d'un rapport entre la tension d'entrée CC et les valeurs instantanées de tensions de phase de sortie à générer sur les raccordements de phase de sortie (a, b, c), par intermittence soit sous la forme d'un simple convertisseur abaisseur soit sous la forme d'un simple convertisseur élévateur.
PCT/EP2018/075349 2017-09-20 2018-09-19 Convertisseur ca/cc comprenant des modules de phase formant convertisseurs élévateurs-abaisseurs WO2019057771A1 (fr)

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CH01159/17 2017-09-20
CH01159/17A CH714180B1 (de) 2017-09-20 2017-09-20 Konverter zur Übertragung von elektrischer Energie zwischen einem DC und einem AC-System.

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CN111711227A (zh) * 2020-07-22 2020-09-25 阳光电源股份有限公司 光伏发电系统及其启动控制方法
WO2022038288A1 (fr) * 2020-08-21 2022-02-24 Prodrive Technologies B.V. Convertisseur ca/cc électrique reconfigurable modulaire

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JP2011188638A (ja) * 2010-03-09 2011-09-22 Denso Corp 電力変換回路の制御装置
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DE102014219909A1 (de) * 2014-10-01 2016-04-07 Robert Bosch Gmbh Ladeschaltung für einen elektrischen Energiespeicher, elektrisches Antriebssystem und Verfahren zum Betreiben einer Ladeschaltung
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US20050218876A1 (en) * 2004-03-31 2005-10-06 Denso Corporation Reversible buck-boost chopper circuit, and inverter circuit with the same
US20090200970A1 (en) * 2008-02-12 2009-08-13 Denso Corporation Chopper control system for rotary machines
US20090237052A1 (en) * 2008-03-21 2009-09-24 Denso Corporation Control apparatus for controlling power conversion apparatus
JP2011188638A (ja) * 2010-03-09 2011-09-22 Denso Corp 電力変換回路の制御装置
DE102014211853A1 (de) * 2014-06-20 2015-12-24 Robert Bosch Gmbh Spannungskonverter und Verfahren zum Konvertieren einer elektrischen Spannung
DE102014219909A1 (de) * 2014-10-01 2016-04-07 Robert Bosch Gmbh Ladeschaltung für einen elektrischen Energiespeicher, elektrisches Antriebssystem und Verfahren zum Betreiben einer Ladeschaltung
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* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN111711227A (zh) * 2020-07-22 2020-09-25 阳光电源股份有限公司 光伏发电系统及其启动控制方法
WO2022038288A1 (fr) * 2020-08-21 2022-02-24 Prodrive Technologies B.V. Convertisseur ca/cc électrique reconfigurable modulaire

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CH714180A2 (de) 2019-03-29

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