WO2018234026A1 - Ensemble circuit convertisseur monoétagé comportant un régulateur linéaire - Google Patents

Ensemble circuit convertisseur monoétagé comportant un régulateur linéaire Download PDF

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Publication number
WO2018234026A1
WO2018234026A1 PCT/EP2018/064707 EP2018064707W WO2018234026A1 WO 2018234026 A1 WO2018234026 A1 WO 2018234026A1 EP 2018064707 W EP2018064707 W EP 2018064707W WO 2018234026 A1 WO2018234026 A1 WO 2018234026A1
Authority
WO
WIPO (PCT)
Prior art keywords
voltage
circuit arrangement
converter circuit
converter
linear regulator
Prior art date
Application number
PCT/EP2018/064707
Other languages
German (de)
English (en)
Inventor
John SCHÖNBERGER
Original Assignee
Tridonic Gmbh & Co Kg
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Tridonic Gmbh & Co Kg filed Critical Tridonic Gmbh & Co Kg
Publication of WO2018234026A1 publication Critical patent/WO2018234026A1/fr

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Classifications

    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
    • H05B45/30—Driver circuits
    • H05B45/37—Converter circuits
    • H05B45/3725—Switched mode power supply [SMPS]
    • H05B45/38—Switched mode power supply [SMPS] using boost topology
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
    • H05B45/30—Driver circuits
    • H05B45/395—Linear regulators
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
    • H05B45/30—Driver circuits
    • H05B45/355—Power factor correction [PFC]; Reactive power compensation
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
    • H05B45/30—Driver circuits
    • H05B45/37—Converter circuits
    • H05B45/3725—Switched mode power supply [SMPS]
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B20/00—Energy efficient lighting technologies, e.g. halogen lamps or gas discharge lamps
    • Y02B20/30—Semiconductor lamps, e.g. solid state lamps [SSL] light emitting diodes [LED] or organic LED [OLED]

Definitions

  • the invention relates to a single-stage converter circuit arrangement with a linearly arranged to the output linear regulator. More particularly, the invention relates to single stage converter circuitry for operating LEDs as a load having improved efficiency of the series-connected linear regulator, an LED lamp, and a method of operating LEDs as a load.
  • Single-stage converter circuits for the operation of light sources such as light emitting diodes (LEDs) as a load are known.
  • LEDs light emitting diodes
  • a rectified mains AC voltage UAC is supplied.
  • the single-stage converter circuit for example an up-converter, feeds a storage capacitor. The voltage drop across the storage capacitor provides an output voltage ULED at a load output of the converter circuit for driving a load current ILED.
  • an additional ripple voltage occurs at the load output of the converter circuit, which is synchronous with the rectified mains input voltage.
  • additional circuitry measures can be taken.
  • a linear regulator in series at the output of the converter circuit is suitable for suppressing an undesired ripple voltage, it also means an additional power loss of the thus modified converter circuit due to the voltage UREG dropping across the linear regulator.
  • the published patent application DE 100 40 154 A1 proposes to supply to a comparison circuit the output voltage dropping across the light emitting diodes and an output voltage to a voltage source.
  • a controlled by the comparison circuit control circuit leads the output voltage of the voltage source up to a small difference to the voltage dropping across the LEDs voltage and thus improves the Efficiency of generating a current for the LEDs.
  • the proposed measure according to DE 100 40 154 AI does not directly detect the voltage drop at the linear regulator, but only a voltage difference between the output voltage of the DC voltage source and the output voltage ULED for the LED.
  • a converter circuit arrangement has a switch and a linear regulator.
  • the linear regulator is arranged in series with a load output of the converter circuitry.
  • the converter circuitry further includes a regulator circuit that drives the switch based on a difference between an instantaneous voltage drop across the linear regulator and a voltage drop setpoint.
  • the procedure according to the invention relates directly (directly) determined voltage drop across the linear regulator to ground potential for a control of the control of the switch zoom.
  • a particularly preferred converter circuit arrangement is characterized in that the converter circuit arrangement has a detection circuit which is set up to detect zero crossings of an input-side mains voltage of the converter circuit arrangement.
  • a control circuit of the converter circuitry is configured to change a setpoint value for an output side load voltage of the converter circuitry based on the detected zero crossings.
  • An advantageous converter circuit arrangement comprises a sample-and-hold element.
  • the sample and hold circuit is configured to detect a value of the voltage drop across the linear regulator.
  • a timing circuit of the converter circuitry is configured to drive the sample-and-hold circuit based on the detected zero-crossings.
  • the control of the sample-and-hold element by means of the time circuit further improves the control loop, since thus always starting from a minimum value of the mains voltage, a sample of the voltage U RE G is taken via the linear regulator, which represents the minimum value of the voltage drop UREG_min via the linear regulator.
  • the difference to the current value of the mains voltage or of the ripple voltage is not constantly readjusted, but in comparison with the prior art, the difference between a minimum of the ripple voltage and the output voltage voltage is constantly controlled. The speed behavior of the control loop is thus also improved.
  • sample-and-hold element and / or the timing circuit and / or the control circuit are embodied integrated in a microcontroller circuit.
  • the said circuits and their functions can thus be realized in a technically simple manner by means of an integrated circuit, in particular a microcontroller, especially since a microcontroller is already provided for control purposes in many applications of the invention.
  • An embodiment of the converter circuit arrangement comprises as a converter circuit arrangement a single-stage converter, in particular a single-stage converter for operating an LED module with at least one LED.
  • the invention is to be used advantageously in particular for single-stage converter circuits with their topology-related ripple voltage component on the converter output voltage UOUT or a ridge current component of the load current ILED, in order accordingly achieve qualitatively improved outputs UOUT and ILED.
  • the flickering of LEDs operated by single-stage converter circuits can thus be effectively reduced or suppressed.
  • One embodiment of the converter circuitry includes a boost converter, buck converters, buck boost converters, flyback converters, or other switching topology.
  • the invention relates to an LED lamp, comprising a converter circuit arrangement and an LED module with at least one light-emitting diode.
  • the invention also relates to a method of operating an LED module having at least one light emitting diode, wherein a linear regulator is fed by a load output of a converter circuit, and the converter circuitry comprises a switch, the switch based on a difference from an immediately detected voltage drop across the linear regulator and a setpoint for the voltage drop is controlled.
  • FIG. 1 shows an overview of an application of a single-stage converter arrangement for the operation of light sources starting from an AC line voltage
  • Fig. 2 is a representation of the voltages U LED at the output of
  • Fig. 3 shows a circuit arrangement according to an embodiment of the invention for a
  • FIG. 1 gives an overview of an application of a single-stage converter circuit 1 for the operation of lamps starting from a mains AC voltage UAC.
  • the single-stage converter circuit 1 receives at its input a rectified mains voltage UDC.
  • the rectified AC line voltage UDC can be generated in a simple case by means of a rectifier circuit 2, for example, a bridge rectifier, from a mains AC voltage UAC.
  • an AC voltage source 3 provides the input side AC line voltage UAC.
  • a load-side output of the converter circuit 1 provides an output voltage UOUT which provides an output current ⁇ for operating an LED module 4 with one or more LEDs, wherein the output current ⁇ corresponds to a load current ILED in the LED module 4.
  • the LED converter 1 performs, inter alia, a power factor correction (English Power Factor Correction - short: PFC).
  • a power factor correction English Power Factor Correction - short: PFC
  • PFC Power Factor Correction
  • On the output side of the converter circuit 1 is a storage capacitor Cl, which is not shown in this schematic representation.
  • a power is provided by means of the pulsating output current ⁇ .
  • This fluctuating output current ⁇ is also responsible for a ripple voltage on the output voltage and a Rippeistromanteil on the load current ILED.
  • a Rippelastromanteil having, so fluctuating current ILED for feeding an LED module 4 leads to a correspondingly fluctuating light output of the LED module 4.
  • the fluctuating light output can by a viewer as disturbing flickering of the light of the LED module 4, in the case shown a flicker frequency of 100 Hz are perceived.
  • the LED module 4 may contain a plurality of LEDs in series and / or in parallel beyond the representation of FIG.
  • circuit arrangement shown in Fig. 1 is merely a simple example in which additional and usual and required functions and elements such as line filters, inductors, x and Y capacitors, special rectifier training as bridge rectifier, full bridge, half-bridge or individual diodes, smoothing a resulting DC voltage by means of smoothing capacitor, switching a DC voltage ("chopping"), transforming a resulting AC voltage by means of a transformer, rectifying an AC voltage and screening a DC voltage merely indicated or omitted for improved illustration.
  • additional and usual and required functions and elements such as line filters, inductors, x and Y capacitors, special rectifier training as bridge rectifier, full bridge, half-bridge or individual diodes, smoothing a resulting DC voltage by means of smoothing capacitor, switching a DC voltage (“chopping"), transforming a resulting AC voltage by means of a transformer, rectifying an AC voltage and screening a DC voltage merely indicated or omitted for improved illustration.
  • the load current ILED shown in Fig. 1 with a Rippeistromanteil can be improved by means of different circuit engineering measures.
  • an increased or additional capacity of the storage capacitor Cl at the output of the converter circuit 1 would be useful for reducing the ripple component.
  • This measure is associated with correspondingly increased space requirements for the circuit and additional and / or higher costs.
  • Fig. 1 Shown in Fig. 1 is an additional linear regulator 5 in series with the LED module 4 at the output of the converter circuit 1.
  • This solution for reducing the Rippelanteils compared to the solution by means of capacitor has a reduced space requirement, but the power loss of the entire converter circuit arrangement is thereby increased , The resulting in the linear regulator 5 power loss is
  • FIG. 2 A low power loss via the linear regulator 5 is in particular due to a voltage drop UREGO via the linear regulator 5, which corresponds to a minimum regulator voltage UREG_min and is dependent on a ripple voltage component of the output voltage UOUT (t) of the single-stage LED converter (converter circuit) 1.
  • the voltage UouT avg denotes an average value of the ripple voltage component of the time-dependent output voltage UOUT (t).
  • the single-stage converter circuit 1 of the converter circuit arrangement receives at its input a rectified mains AC voltage UDC.
  • the rectified AC line voltage U D C is generated by means of a rectifier circuit 2, here a rectifier as a full bridge, from a mains AC voltage UAC.
  • the AC line voltage UAC is provided in the case shown by a feeding mains power supply by an AC voltage source 3.
  • a load-side output of the converter circuit 1 provides an output voltage UOU T which drives an output current ⁇ for operating an LED module 4 with one or more LEDs, the output current ⁇ corresponding to a load current ILED for the LED module 4.
  • the single-stage converter circuit 1 has a switch Tl, which is clocked at high frequency. Due to the high-frequency timing of the switch Tl, the inductance LI is repeated up and demagnetized. During the blocking phase (switch-off time) of the switch Tl, the inductance LI outputs its magnetizing energy and drives a current through the diode D5 into the capacitance Cl at the output of the converter circuit (LED converter) 1 and provides an output current ⁇ for operating an LED module 4 ready.
  • the converter circuit 1 is formed as a boost converter (boost converter).
  • a detection circuit 6 for detecting the zero crossings of the AC line voltage UAC is arranged at the input of the rectifier 2.
  • the zero-crossing signal ZCD shown in FIG. 4B is provided, which for a short predetermined period of time, for each zero crossing of the mains alternating voltage UAC Voltage level corresponding to logic "0", while the zero-cross signal ZCD otherwise has a voltage level corresponding to logic "1".
  • the zero-crossing signal ZCD is supplied to a sample-and-hold circuit 9 comprising a sampling circuit 8 and a timing circuit 10.
  • Timing circuit 10 is shown as a "one shot timer.”
  • the programmable interval timer corresponds to a counter that generates an output when it reaches a preset count
  • Programmable interval timers are typically programmed by specifying a specific interval that determines how long the programmable interval timer will count until it generates an output signal, in the case shown the timing circuit 10 is used to generate, starting from the zero-crossing signal ZCD, a drive signal for the sample-and-hold circuit 9 delayed by a predetermined time interval Signal determines the time at which the sample-and-hold element 9 detects the regulator voltage UREG and how long it takes until a subsequent subsequent sampling the sampled value of the regulator voltage U RE G as a sampled minimum regulator voltage UREG_min at the output of the sampling circuit 8, in particular its sampling Holding member 9, providing.
  • the sampled minimum regulator voltage UREG_min is then supplied from the sampling circuit 9 to a control circuit 11.
  • a control circuit 11 with the comparator COMP, the loop filter Fil, and the following further comparators COMP2, COMP3, a reference voltage U ou t _ re f for the output voltage UOUT is then generated.
  • the reference voltage U ou t _ re f is compared by means of a comparator COMP3 with a measured via a voltage divider from the resistors R4, R5 voltage U ou t meas and the difference to control via a voltage regulator 7 for controlling the switch Tl, in the case shown Semiconductor switch in the form of a transistor, used.
  • the sampled minimum regulator voltage UREG min is regulated to zero.
  • the loop filter Fil can have a proportional and / or integral filter characteristic.
  • both the output voltage U ou t (t) are regulated and the regulator voltage Ureg min (t) controlled.
  • the use of the temporal mains voltage profile UAc (t) for precise detection of the minimum voltage of the regulator voltage U reg min (t) allows optimized control of the regulator voltage U reg (t) to reduce the power consumption of the linear regulator 5 with unchanged advantageous suppression of Rippelan fixing on the Output voltage UOUT and the load current ILED.
  • the detection circuit 6 thus detects zero crossings of the mains voltage UAc (t), uses the detected zero crossings of the mains voltage UAc (t) for clocking a sampling circuit 8 and subsequent subcircuits which provide a setpoint for the output voltage UOUT of the converter circuit arrangement 1 in synchronism with a mains voltage UAc (t). suitably changed (modulated).
  • the regulator voltage UREGO) wrr d falling across the linear regulator 5 is detected and converted into a corresponding control variable with a setpoint value for the controller voltage UREG ⁇ a l s , which is as low as possible, via a control algorithm.
  • FIG. 3 is the timing, in particular the time-varying timing ("fluctuating" timing) of the switch Tl of the single-stage converter circuit 1.
  • the embodiment of the invention shown in Fig. 3 is inexpensive by means of conventional integrated circuits, for example a microcontroller This can be realized in particular by the elements of programmable interval timers 10, sample and hold element 9, the comparator realized in the detection circuit 6 by means of the operational amplifier OP1, the voltage regulator 7 and the controller minimum voltage control circuit UREG min with the comparators COMP1, COMP2 , COMP3 and the filter Fil.
  • 4A, 4B, 4C, 4D show voltage waveforms and signals of the circuit arrangement according to the embodiment of the invention of FIG. 3 with a common time base t.
  • FIG. 4A shows a time course of the AC line voltage UACO.
  • FIG. 4B shows a detection signal ZCD at the output of the detection circuit 6 with the same time base.
  • the detection signal ZCD (short for Zero Crossing Detection) is logic "high” corresponding to the logic value of 1 and changes for a short time to a logic level “low” corresponding to the logic value 0 when the mains AC voltage UAC has a zero crossing ,
  • a drive signal "SAMPLE ADC” is shown with the same time base as is given by an output of the programmable interval timer 10 to a control input of the sample and hold element 9.
  • the drive signal is logic "high” corresponding to the logical value 1 and changes to a logic level for the time for a predetermined duration, "Low” corresponding to the logical value 0 when the AC line voltage UAC has a zero crossing.
  • the predetermined duration is preset by a counter interval of the programmable interval timer 10.
  • the thus controlled sample and hold element 9 stores the value of the voltage UREG present at the time of a rising clock signal of the drive signal "SAMPLE ADC" via the linear regulator 5 and outputs the stored value to an output of the sample and hold element 9
  • the relationship between the time course of the voltage UREGO) 12 via the linear regulator 5 and the output voltage UREG_min (t) 13 of the sample and hold element 9 is shown in Fig. 4D
  • the sampling time of the sample and hold element 9 is a suitably chosen one Time interval is delayed, so that the sampling takes place for a local minimum value of the regulator voltage UREG () 12.
  • the sampled value of the output voltage UREG_min (t) 13 is then held until a resampling.
  • the minimum regulator voltage UREG_min determination illustrated in FIG. 4 is only one of several possible implementations of the invention.
  • the invention also relates to an LED luminaire having a converter circuit arrangement according to the invention and an LED module 4 having at least one light-emitting diode LED.
  • the invention also relates to a method for operating an LED module 4 with at least one light emitting diode LED, wherein a linear regulator 5 by a load output of a Converter circuit arrangement is fed, and the converter circuit arrangement comprises a switch Tl, wherein the switch Tl is driven on the basis of a difference of an immediately detected voltage drop across the linear regulator 5 and a target value for the voltage drop.
  • the zero crossings of an input side mains voltage of the converter circuit arrangement can be detected, and a setpoint value for an output side load voltage of the converter circuit arrangement can be changed on the basis of the detected zero crossings.
  • a sample-and-hold element 9 is driven and a value of the voltage drop across the linear regulator 5 is detected by a sample-and-hold element 9.

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  • Dc-Dc Converters (AREA)

Abstract

L'invention concerne un ensemble circuit convertisseur comprenant un commutateur (T1) et un régulateur linéaire (5) monté en série avec une sortie de charge de l'ensemble circuit convertisseur, le circuit régulateur (7, 11) commandant le commutateur (T1) en fonction d'une différence entre une chute de tension directement détectée au niveau du régulateur linéaire (5) et une valeur théorique pour cette chute de tension.
PCT/EP2018/064707 2017-06-22 2018-06-05 Ensemble circuit convertisseur monoétagé comportant un régulateur linéaire WO2018234026A1 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
DE202017103713.4 2017-06-22
DE202017103713.4U DE202017103713U1 (de) 2017-06-22 2017-06-22 Einstufige Konverterschaltungsanordnung mit Linearregler

Publications (1)

Publication Number Publication Date
WO2018234026A1 true WO2018234026A1 (fr) 2018-12-27

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Application Number Title Priority Date Filing Date
PCT/EP2018/064707 WO2018234026A1 (fr) 2017-06-22 2018-06-05 Ensemble circuit convertisseur monoétagé comportant un régulateur linéaire

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Country Link
AT (1) AT17755U1 (fr)
DE (1) DE202017103713U1 (fr)
WO (1) WO2018234026A1 (fr)

Families Citing this family (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE102019131795A1 (de) * 2019-11-25 2021-05-27 Rk Rose + Krieger Gmbh Verbindungs- Und Positioniersysteme Schaltnetzteil und Regelverfahren für ein Schaltnetzteil

Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE10040154A1 (de) 2000-08-17 2002-03-07 Westiform Holding Ag Niederwan Leuchtreklame
US9018851B1 (en) * 2010-08-24 2015-04-28 Cirrus Logic, Inc Boost and linear LED control
WO2015143321A1 (fr) * 2014-03-21 2015-09-24 Cooledge Lighting Inc. Systèmes et procédés de commande de dispositif d'éclairage

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Publication number Priority date Publication date Assignee Title
JP2001215913A (ja) * 2000-02-04 2001-08-10 Toko Inc 点灯回路
WO2011092606A1 (fr) * 2010-02-01 2011-08-04 Koninklijke Philips Electronics N.V. Appareil permettant un démarrage en douceur d'une unité d'éclairage à semi-conducteurs
SE534808C2 (sv) * 2010-02-19 2011-12-27 Nordic Light Ab Förfarande för kontroll och styrning av utströmmen ur ett elektroniskt drivsystem som innehåller ett switchat kraftaggregat av flyback-typ jämte ett elektroniskt drivsystem enligt förfarandet.
DE102014205469A1 (de) * 2014-03-24 2015-09-24 Osram Gmbh Schaltungsanordnung und Verfahren zum Betreiben von Halbleiterlichtquellen
DE102015203950A1 (de) * 2015-03-05 2016-09-08 Tridonic Gmbh & Co Kg Betriebsgerät mit Erkennung des Wegfalls der Versorgungsspannung

Patent Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE10040154A1 (de) 2000-08-17 2002-03-07 Westiform Holding Ag Niederwan Leuchtreklame
US9018851B1 (en) * 2010-08-24 2015-04-28 Cirrus Logic, Inc Boost and linear LED control
WO2015143321A1 (fr) * 2014-03-21 2015-09-24 Cooledge Lighting Inc. Systèmes et procédés de commande de dispositif d'éclairage

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DE202017103713U1 (de) 2018-09-25
AT17755U1 (de) 2023-01-15

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