WO2018076690A1 - 用于优化无线电力传输的自适应功率放大器 - Google Patents

用于优化无线电力传输的自适应功率放大器 Download PDF

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Publication number
WO2018076690A1
WO2018076690A1 PCT/CN2017/086526 CN2017086526W WO2018076690A1 WO 2018076690 A1 WO2018076690 A1 WO 2018076690A1 CN 2017086526 W CN2017086526 W CN 2017086526W WO 2018076690 A1 WO2018076690 A1 WO 2018076690A1
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Prior art keywords
power supply
switching
mode
adaptive power
switching device
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PCT/CN2017/086526
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English (en)
French (fr)
Inventor
潘思铭
贺大玮
李暾
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深圳市易冲无线科技有限公司
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Publication of WO2018076690A1 publication Critical patent/WO2018076690A1/zh

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J50/00—Circuit arrangements or systems for wireless supply or distribution of electric power
    • H02J50/10—Circuit arrangements or systems for wireless supply or distribution of electric power using inductive coupling
    • H02J50/12—Circuit arrangements or systems for wireless supply or distribution of electric power using inductive coupling of the resonant type
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J50/00—Circuit arrangements or systems for wireless supply or distribution of electric power
    • H02J50/80—Circuit arrangements or systems for wireless supply or distribution of electric power involving the exchange of data, concerning supply or distribution of electric power, between transmitting devices and receiving devices
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J2207/00—Indexing scheme relating to details of circuit arrangements for charging or depolarising batteries or for supplying loads from batteries
    • H02J2207/20—Charging or discharging characterised by the power electronics converter
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J7/00—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J7/00—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries
    • H02J7/00032—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries characterised by data exchange
    • H02J7/00034—Charger exchanging data with an electronic device, i.e. telephone, whose internal battery is under charge
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0048—Circuits or arrangements for reducing losses
    • H02M1/0054—Transistor switching losses
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0048—Circuits or arrangements for reducing losses
    • H02M1/0054—Transistor switching losses
    • H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B40/00—Technologies aiming at improving the efficiency of home appliances, e.g. induction cooking or efficient technologies for refrigerators, freezers or dish washers
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Definitions

  • This application relates to a switching power supply. More specifically, the present application relates to a switching power supply and amplifier structure for optimizing a wireless charge transfer (WPT) system.
  • WPT wireless charge transfer
  • Wireless power transfer or wireless energy transfer is the transfer of electrical energy from a power source to a receiving device without the use of solid wires or conductors.
  • this term refers to a number of different power transfer techniques that utilize electromagnetic fields that change over time.
  • the transmitting device is connected to a power source, such as a main power line, and transmits energy to one or more receiving devices by an electromagnetic field passing through the intermediate space where the energy is converted back to electrical energy and utilized.
  • Wireless power transmission technology can be divided into two categories, no radiation and radiation.
  • electrical energy can be transmitted over short distances, such as by magnetic field utilizing inductive coupling between wire coils or by electric field utilizing capacitive coupling between electrodes.
  • Such applications include, but are not limited to, mobile phones, tablets, laptops, electric toothbrush chargers, radio frequency identification tags, smart cards and chargers for implantable medical devices like artificial cardiac pacemakers, and similar cars, trains or The electric vehicle of the bus is powered or charged.
  • radiation and far-field technologies sometimes referred to as "power clusters," electrical energy can be transmitted through a beam of electromagnetic radiation, such as a microwave or laser beam. These techniques can transfer energy over longer distances but are usually for the receiver.
  • A4WP Wireless Power Consortium
  • PTU single power transmitter unit
  • PRU power receiver units
  • the interface standard supports power transmission up to 50 watts and distances up to 5 cm.
  • the power transmission frequency can be 6.78 MHz, and up to eight devices can be powered by a single PTU depending on the geometry and power level of the transmitter and receiver.
  • Bluetooth smart links can be provided in the A4WP system to control power levels, validate payloads, and protect incompatible devices.
  • a Qi system can include a base station that is connected to a power source and provides inductive power, with a device that uses an inductive power supply.
  • the base station can include a power transmitter having a transmit coil that produces an oscillating magnetic field; the device can include a power receiver that houses the receive coil.
  • the magnetic field from the transmitter can induce an alternating current in the receiving coil according to Faraday's law of electromagnetic induction.
  • Further standardized WPT technology includes the "wireless charger” adopted by the Power Materials Consortium (PMA), which is based on inductively coupled power transmission, where the transmitter can change the current in the main induction coil to generate intersections from the charging point. Change the magnetic field.
  • PMA Power Materials Consortium
  • a receiver in a consumer device can have its own induction coil to draw power from the magnetic field and convert it back to current to charge the device battery.
  • Another part of the technique is to use system control communication via data on the coil (DoC), where the receiver can send feedback to the transmitter by changing the load seen by the transmitter coil.
  • DoC data on the coil
  • the protocol is based on the frequency of the signal transmission, allowing the transmitter to respond quickly.
  • WPT systems For power, WPT systems often rely on switching power supplies, using technologies such as Class D or Class E amplifiers.
  • technologies such as Class D or Class E amplifiers.
  • the traditional configuration of these amplifiers often leads to inefficiencies.
  • the amplifier When used in a single-ended switch configuration, the amplifier typically has a lower voltage gain and, as a result, Low output power.
  • the amplifier When used in a differential mode switch configuration, the amplifier has higher voltage gain and output power, but suffers from larger switching and drive losses, which in turn reduces efficiency. Therefore, techniques are needed to provide optimization in increased output power or higher efficiency depending on system requirements for different operating conditions.
  • an adaptive power supply that provides a radio transmission (WPT) from a WPT transmitter to a receiver, including: an input receiving power, and a switching device coupled to the input, wherein A first portion of the switching device is coupled to the first portion of the transmitter, and a second portion of the switching device is coupled to the second portion of the transmitter, wherein the switching device is configured to control the first and second portions of the switching device to
  • WPT radio transmission
  • the adaptive power supply is selectively operated between the single-ended switching mode and the differential switching mode.
  • the adaptive power amplifier includes a non-resonant inductor and a blocking capacitor.
  • the adaptive power supply includes a controller for determining whether the adaptive power supply provides a desired amount of power, wherein the controller can be configured to selectively use the single-ended switch if the desired amount of power is provided The adaptive power supply is operated in mode.
  • the controller may be configured to operate the adaptive power source selectively using the differential switching mode if the amount of power desired is not provided.
  • a method for providing wireless power transfer (WPT) from a WPT transmitter to a receiver including receiving power at an input for an adaptive power source; and controlling the switching device to be a WPT transmitter
  • the adaptive power supply is selectively operated between the single-ended mode and the differential mode, wherein the switching device includes a first switching portion that couples the first portion of the WPT transmitter and a second switching portion that couples the second portion of the WPT transmitter.
  • FIG. 1 shows a WPT system including a charger and a device configured to receive wireless power transfer, in an illustrative embodiment
  • FIG. 1A shows an equivalent circuit of the WPT circuit portion of the system of FIG. 1 in an illustrative embodiment
  • ZVS zero voltage switching
  • FIG. 3 shows a ZVS voltage mode class D amplifier for a transmit coil of a WPT system of a differential mode amplifier configured to provide wireless power to a receive coil;
  • FIG. 4 shows a ZVS voltage mode class D amplifier of a transmit coil of a WPT system for an adaptive switching power amplifier configured to provide wireless power to a receive coil, in an illustrative embodiment
  • Figure 5 shows a simulated waveform diagram showing single-ended mode and differential mode transitions, with the switch mode logic of the Figure 4 amplifier under the illustrative embodiment for switch Q1 open and switch Q4 closed;
  • Figure 6 shows a simulated waveform diagram showing single-ended mode and differential mode transitions, with the switching mode logic of the Figure 4 amplifier under the illustrative embodiment for switch Q1 closed and switch Q4 open;
  • Figure 7 shows a simulated waveform diagram showing a differential mode to single-ended mode transition, with the switch mode logic of the amplifier of Figure 4 under the illustrative embodiment for switch Q1 open and switch Q4 closed;
  • Figure 8 shows a simulated waveform showing the transition from differential mode to single-ended mode, along with Switch Q1 closes the switch mode logic of the amplifier of Figure 4 under the illustrative embodiment that is open to switch Q4.
  • first, second, third, etc. may be used herein to describe various elements, components, regions, layers and/or parts, these elements, components, regions, layers and/or parts are not subject to these terms. limit. These terms are only used to distinguish one element, component, region, layer Terms such as “first,” “second,” and other numerical terms when used herein do not denote a sequence or order unless the context clearly dictates. Thus, a first element, component, region, layer or portion may be referred to as a second element, component, region, layer or portion, without departing from the teachings of the exemplary embodiments.
  • a WPT system 100 comprising a charger 102 and a device 120 including an electrical energy storage device such as a battery 126.
  • device 120 can be an electronic device such as a smart phone, tablet, notebook, medical device, power tool, and the like.
  • device 120 can be a car, bus, train, or the like.
  • device 120 can be any device that can be configured to receive WPT signals to and/or recharge electrical energy storage devices (e.g., 126).
  • charger 102 may include a power inverter/controller 106 (hereinafter simply referred to as a "controller”) that receives electrical energy from a power source 108.
  • the power source 108 can be a power source or any other suitable energy.
  • Controller 106 may include, but is not limited to, a power inverter circuit, an amplifier circuit, an oscillator circuit, a filter circuit, an impedance matching circuit, a power control circuit, a processor circuit, a controller, and for generating and controlling a slave transmission Analogs of the transmission power of the machine 104 to the receiver 122, which may be constructed as coils, plates, magnetic armatures, and the like.
  • transmitter 104 and receiver 122 may include a single coil configured to provide magnetic resonance and/or magnetic inductive charging.
  • transmit coil 104 and receiver 122 may include multiple coils that may be configured in an overlapping and/or non-overlapping arrangement to provide magnetic resonance or magnetic inductive charging.
  • transmitter 104 and receiver 122 may include electrodes, such as plates, that are electrically inductively transmitting and coupling power.
  • transmitter 104 and receiver 122 may use a magnetically coupled coupling of a synchronously rotating rotating armature to transmit and couple power, the magnetic fields generated by the magnets on the armature being coupled together.
  • controller 106 may include communication circuitry to allow controller 106 to communicate with device 120 by wire or wirelessly (eg, WiFi, Bluetooth, infrared, etc.).
  • the communication circuitry of controller 106 may include a wireless antenna 110 for communicating data with wireless antenna 128 of device 120.
  • the communication data may include device specific information and power feedback data from device 120, where the power feedback data may include data related to power transfer efficiency, link efficiency, quality factors, and the like.
  • the power feedback data may alternatively be provided by directly using an RF power transmission link of the transmitter 104 and receiver 122 pairs suitable for packet-based communication sub-carrier communication bands.
  • device 120 may include power monitoring and charging circuitry 124 that may be coupled to processor 130 and electrical energy storage 126, which may operate as a load in some illustrative embodiments.
  • the power monitoring and charging circuit 124 can include, but is not limited to, an RF circuit, a rectifier circuit, an impedance matching circuit that can be configured to form an impedance matching network with the controller 106, a filtering circuit, a communication circuit that communicates via the wireless antenna 128, and
  • the electrical energy storage 126 provides charging of electrical energy Electrical circuit.
  • Power monitoring and charging circuitry 124 may also be coupled to processor 130, which may be configured to store and perform characteristics for measuring and/or calculating received electrical energy (eg, power transfer efficiency, link efficiency, quality factor)
  • the algorithm is, and is provided as feedback by wireless antenna 128 or other suitable means.
  • device 120 may be placed in a location adjacent to charger 102 to receive a WPT signal in receiver 122, which is processed/converted in power monitoring and charging circuit 124 and provided to electrical energy storage 126 For subsequent use.
  • electrical energy storage 126 can be coupled to other electronic devices within device 120 to provide operational power.
  • the transmitter 104 and receiver 122 may be physically aligned along the x, y and/or z axes to ensure that excessive signal loss due to misalignment in any of the axes is not introduced, On the contrary, it may have a significant impact on power signal transmission and efficiency.
  • the transmitter 102 may include an amplitude V P having a frequency ⁇ and the power source voltage for R P corresponds resistance.
  • the voltage source can be coupled to a transmitter resonator circuit that can include a capacitor C T , an inductor L T , and a resistor R T .
  • the energy can oscillate at a resonant frequency between the inductor L T (representing the energy stored in the magnetic field) and the capacitor C T (representing the energy stored in the electric field) and can be dissipated in the resistor R T .
  • the transmitter resonator circuit 102 may be coupled to a receiver inductor L R 120 through mutual inductance (M), which circuitry may be used, and C R R R L in the same manner to provide a resonant power to the load R.
  • M mutual inductance
  • resonators eg, 104, 122
  • the resonant frequency and quality factor of the transmitter and receiver (T, R) resonators can be expressed as
  • the transmitter (eg, 104) and receiver (eg, 122) coils may be represented by inductors L T and L R , respectively, which may be coupled by mutual inductance M, wherein Where k is the coupling coefficient or energy coupling ratio.
  • Each coil may have a series capacitor (C T , C R ) to form a resonator.
  • the resistors R T and R R can be considered to be parasitic resistances including all ohmic, non-conductive and radiative losses of the individual coils and resonant capacitors.
  • the load which may be an energy store 126, is represented by R L in this example.
  • the electrical energy transmitted to the load (eg, R L ) can be determined by dividing the maximum electrical energy available from the transmitter when both the transmitter and the receiver resonate at frequency ⁇ , or
  • Impedance matching eg, using an impedance transformation network
  • initial efficiency eg,
  • Efficiency can also be based on the rate of energy loss in the receiver ( ⁇ R ), and/or can be based on the magnetic coupling coefficient (k) between the resonators and the resonator quality of the transmitter and receiver (Q T , Q R ) The factors are as follows:
  • the efficiency of the WPT can be easily determined.
  • the WPT system can be configured to transmit power through a magnetic field resonant coupling between a transmitter (TX) and a receiver (RX) coil. Power can also be transmitted by magnetic field inductive coupling between the TX and RX coils.
  • a power amplifier should be provided on the input side to generate AC input energy to be delivered to the output side.
  • a non-limiting example includes a zero voltage switching amplifier.
  • AC alternating current
  • the zero crossing is the instantaneous point where there is no voltage.
  • a sine wave or other simple waveform it usually appears twice in each cycle. If the electrical power is to be switched, if the circuit switching occurs at the instant when there is no current (ie zero crossing), no electrical interference is generated.
  • a switching amplifier such as a pulse width modulation (PWM) amplifier
  • PWM pulse width modulation
  • an amplifier switch eg, a metal oxide semiconductor field effect transistor (MOSFETS)
  • MOSFETS metal oxide semiconductor field effect transistor
  • the amplifier input signal can be used to modulate the PWM carrier signal that can be used to drive the output device.
  • the low pass filter can be used to remove high frequency PWM carrier frequencies in some illustrative embodiments. Examples of switching amplifiers include, but are not limited to, Class D and Class E amplifiers.
  • VM Class D amplifier 200 a single-ended ZVS voltage mode (VM) Class D amplifier 200 is illustrated.
  • input power source 201 is provided to power transmitter coil 207, where switches 202 and 203 can be configured as complementary switches that alternately turn “on” and “off” on each positive and negative period from power source 201.
  • a non-resonant LC loop (204, 205) may be provided to effect zero switch node voltage conversion of switches 202 and 203.
  • the power transmitted from coil 207 can be received at receive coil 208 and capacitor 209 prior to being stored (e.g., 126) or transmitting DC power to the circuit prior to rectification in 210.
  • amplifier 200 provides lower voltage stress on power switches (202, 203) compared to Class E, and/or current mode Class D amplifiers.
  • the configuration of amplifier 200 can also provide a wider load condition for zero voltage switching (compared to conventional VM Class D amplifiers) and an easier radiated EMI filter design (compared to Class E amplifiers).
  • such amplifiers have the disadvantage of low voltage gain (e.g., 1/2 Vin), where it is converted to low output power for a given input voltage and load impedance.
  • this limitation may be mitigated by potentially doubling the output power capacity with a Class D amplifier of differential mode (DM) zero voltage switching VM compared to single-ended mode.
  • DM differential mode
  • Figure 3 a differential mode amplifier for providing wireless power to a receiver coil is shown where input power supply 301 is provided to transmitter coil 309, where capacitor 302 can be configured with differential switches 303-304 and 305-306 are connected in parallel, with the source terminal of switch 303 and the drain terminal of switch 304 coupled together as shown and output to the positive terminal of inductor 307. The source terminal of switch 305 and the drain terminal of switch 306 are coupled together as shown and output to the negative terminal of inductor 307.
  • the inductor ripple current through inductor 307 can then be provided to achieve zero switching node voltage switching (via switches 303-304 and 305-306).
  • the power transmitted from coil 309 can be received at receive coil 310 and capacitor 311 prior to storage (e.g., 126) or transmission of DC power to the circuit prior to rectification at 312.
  • DM zero-voltage switching amplifiers As briefly mentioned above, one of the disadvantages of DM zero-voltage switching amplifiers is that increased switching can result in Single-ended mode reduces efficiency compared to twice the switching and drive losses. Moreover, during certain operations, the switching inductor 307 may be saturated by the DC bias voltage if the duty cycle is not exactly 50%, which may be caused by clock signal tolerance or asymmetric time delay. This situation may even cause further switching losses, and potentially lead to zero voltage switching failures. Therefore, those skilled in the art often face the dilemma of selecting a high efficiency amplifier that may produce sub-optimal, lower power (as shown in FIG. 2), or a high power amplifier amplifier (shown in FIG. 3) that selects suboptimal efficiency.
  • FIG. 4 an adaptive zero voltage switching class D amplifier, under an exemplary embodiment, is shown.
  • the differential mode switch is provided coupled to input voltage 401 across capacitor 402 by switches 403-404 and 405-406 as shown.
  • the source terminal of switch 403 and the drain terminal of switch 404 are coupled together as shown and output to one terminal of inductor 407.
  • the source terminal of switch 405 and the drain terminal of switch 406 are coupled together as shown and output to one terminal of capacitor 408.
  • the location of 407 and 408 can be exchanged without losing the versatility of this approach.
  • blocking capacitor 408 is added in series with the switching inductor to block the DC bias saturation inductor 407, which in turn makes the zero voltage switching more reliable and, at the same time, improves the efficiency of amplifier 400.
  • the use of blocking capacitor 408 enables the amplifier to change modes and operate adaptively in single-ended mode or differential mode with simple adaptive control logic. For a given load impedance, the input voltage V IN of the power amplifier can be adjusted to deliver the desired output power.
  • the amplifier 400 may be placed in an initial single-ended operation mode by the power switch Q 2 configured as a continuous off state and the power switch Q 3 is configured to continuously conducting state, Q 1 and Q 4 leaving the switching operation.
  • Single-ended mode operation can also be implemented by configuring Q 2 and Q 3 to switch, while Q 1 is configured to be continuously turned off and Q 4 is configured to be continuously turned on.
  • the desired output power can be transmitted by adjusting V IN using the allowed input voltage range. The desired output power can then be maintained with optimized efficiency of the single-ended mode of operation with minimized switching losses and drive losses. However, if the desired output power cannot be transmitted even at the maximum input voltage, this would indicate that the output power capability in single-ended mode is not large enough to handle such load impedance. In this case, circuit 400 can be switched to differential mode operation to optimize output power capability.
  • mode logic 501 is shown for from low (single-ended mode) 506 to high (differential mode) 508, where mode change 507 is shown with a dashed line extending through the analog waveform.
  • Switch Q 1, Q 4 and Q 3, Q waveforms incoming analog gate 2 are each shown as 502-503 and 504-505.
  • switches 502 and 503 can be configured to complementarily switch there where switch 504 is high and switch 505 is low.
  • switch 504 can be configured to be in a continuous on state and switch 505 can be configured as a continuous off state.
  • mode change 507 is implemented by setting mode logic 501 to operate in a high 508 differential mode. Once mode change 507 occurs, switch 504 can follow the falling edge (509) of switch 502 from the “always on” state to the switched state, switch 505 can follow the rising edge (510) of the gate drive signal of switch 503 from “always off” The “on” state changes to the switching state as shown.
  • the mode change transition can be completed in less than one switching cycle, and there is no switch breakdown problem (eg, a current surge that is simultaneously turned on by both switches) since it has been responsible for dead time, For example, between Q 1 and Q 4 .
  • mode logic 601 transitioning from low (single-ended mode) 606 to high (differential mode) 608 is shown where mode change 607 is shown with a dashed line extending through the analog waveform.
  • Each incoming analog gate waveform of switches Q 1 , Q 4 and Q 3 , Q 2 is shown as 602-603 and 604-605, respectively.
  • switches 602 and 603 can be configured to complementarily switch when switch 604 is high and switch 605 is low.
  • switch 604 can be configured to be in a continuous conduction state and switch 605 can be configured as a continuous off state.
  • mode change 607 is implemented by setting mode logic 601 to operate in a high 608 differential mode. As shown, once mode change 607 occurs, switch 604 can follow the falling edge (609) of switch 602 from the "always on” state to the switch state, switch 605 can follow the rising edge of the gate drive signal of switch 603 (610). ) Change from the "always off” state to the on state. In the example of FIG. 6, it can be seen that when switch 602 is on and switch 603 is off (compared to FIG. 5, where mode change 507 occurs when switch 502 is off and switch 503 is on) mode change 607 occur. Those skilled in the art will appreciate that the mode change transition can be completed in less than one switching cycle, regardless of the state of the switch during the mode change operation.
  • the mode of operation can be switched from a single-ended mode of operation to a differential mode of operation, particularly if the desired output power for a given load impedance for a single-ended mode of operation cannot be satisfied.
  • the load impedance may change due to a change in the relative position between the TX and RX coils, or as the output current changes.
  • the operating mode can be switched back to single-ended mode to optimize efficiency.
  • mode logic 701 transitioning from high (differential mode) 706 to low (single-ended mode) 708 is shown where mode change 707 is shown with a dashed line extending through the analog waveform.
  • Each incoming analog gate waveform of switches Q 1 , Q 4 and Q 3 , Q 2 is shown as 702-703 and 704-705, respectively.
  • switches 702-703 and 704-705 can be configured to switch complementarily.
  • the configuration of the circuit causes mode logic 701 Initially operating in high differential mode 706, and switches 702-703 and 704-705 are all complementarily switched.
  • mode change 707 occurs, switch 704 can follow the rising edge (709) of switch 702 from the switch state to the "always on” state, and switch 705 can follow the falling edge (710) of switch 703 gate drive signal to become "always Shutdown status.
  • the mode change transition e.g., 707 can be completed in less than one switching cycle, regardless of the state of the switch during the mode change operation.
  • mode logic 801 transitioning from high (differential mode) 806 to low (single-ended mode) 808 is shown where analog changes 807 are shown to extend through the dashed lines of the analog waveform.
  • Each incoming analog gate waveform of switches Q 1 , Q 4 and Q 3 , Q 2 is shown as 802-803 and 804-805, respectively.
  • switches 802-803 and 804-805 can be configured to complementarily switch.
  • mode logic 801 of FIG. 8 initially operates in high differential mode 806, and switches 802-803 and 804-805 are both complementary switches, where switch 804 The switch 805 is also high when low, and vice versa.
  • switch 804 can follow the rising edge (809) of switch 802 from the differential switch state to the "always on” state, and switch 805 can follow the falling edge (810) of the gate drive signal of switch 803. "Always off” state.
  • mode change 807 occurs when switch 802 is turned “on” and switch 803 is “off” (as compared to FIG. 7, where mode change 707 when switch 702 is turned off and switch 703 is turned “on”). occur).
  • the mode change transition e.g., 807) can be completed in less than one switching cycle.
  • the present disclosure provides an innovative adaptive zero voltage switching amplifier for maintaining efficiency and output power optimization in wireless power transfer.
  • amplifiers eg, Class D, Class E
  • the present application can reduce the required maximum input voltage by half, thereby reducing the rated voltage of the power device, and also reducing switching and drive losses, improving overall system efficiency.
  • WPT applications the present application allows the amplifier to operate in single-ended mode to efficiently transmit output power when the TX and RX coils are properly coupled.
  • the present application allows the amplifier to switch to differential mode operation to maintain output power.

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Abstract

用于从WPT发射机向接收机提供无线电力传输的系统装置和方法。开关装置被配置为具有耦合到WPT发射机（104）第一部分的开关装置的第一部分，以及耦合到WPT发射机（104）的第二部分的第二部分。控制器（106）可以确定自适应电源是否提供期望的功率量，其中开关装置被配置为控制开关装置的第一和第二部分以选择性地在单端模式和差分模式之间操作自适应电源以提供期望的功率量优化的效率。

Description

用于优化无线电力传输的自适应功率放大器
相关申请
本申请要求美国临时专利，申请号62/248,646的优先权，申请于2015年10月30日，名称为“用于优化无线电力传输的自适应功率放大器”，其内容在此被全部引用。
技术领域
本申请涉及开关电源。更明确地，本申请涉及用于优化无线充电传输(WPT)系统的开关电源和放大器结构。
背景技术
无线电力传输(WPT)或者无线能源传输是不使用固体电线或者导体将电能从电源传输给接收设备。一般来说，这个术语是指许多利用随时间变化的电磁场的不同电能传输技术。在无线电传输中，传送装置被连接到电源，例如主电源线路，并且通过穿过中间空间的电磁场将能量传输给一个或多个接收装置，在接收装置中能量被转化回电能并被利用。无线电力传输技术可以分为两类，无辐射和辐射。
在近场或非辐射技术中，电能可以越过短距离被传输例如通过磁场利用电线线圈之间的电感耦合或者通过电场利用电极之间的电容耦合。利用这些技术，可以在100kHz频率70％频率下在两米距离内无线传输电能。这类应用包括，但不限于，手机、平板电脑、笔记本电脑、电动牙刷充电器、射频识别标签、智能卡和类似人工心脏起搏器的植入式医疗器械的充电器，以及类似汽车、火车或者公共汽车的电动交通工具的感应供电或者充电。在辐射和远场技术中，有时被称为“电力集束”,电能可以通过电磁辐射束传输，如微波或激光束。 这些技术可以将能量传输更长的距离但通常是针对接收器。
多年来许多标准化技术已经被开发，包括，但不限于，无线电力联盟(A4WP)，其基于磁共振原理的用于无线电力传输的接口标准(“Rezence”)，在那里单个电力发射机单元(PTU)能够向一个或多个电力接收机单元充电(PRUs)。接口标准支持功率传输高达50瓦，距离高达5厘米。电力传输频率可以是6.78MHz，而且根据发射机和接收机的几何形状和功率水平高达8个设备能够由单个PTU供电。在A4WP系统中蓝牙智能链接可以被提供以控制功率等级，确认有效载荷，以及保护不兼容设备。
另一种标准化的WPT技术包括依赖平面线圈间电磁感应的“Qi”。一个Qi系统可以包括一个基站，该基站被连接到电源并提供电感电源，与一个使用电感电源的设备。该基站可以包括一个具有产生振荡磁场的发射线圈的功率发射机；这个设备可以包括容纳接收线圈的功率接收机。来自发射机的磁场可以根据法拉第电磁感应定律在接收线圈中感应交流电。进一步标准化的WPT技术包括被电力物质联盟(PMA)采纳的“无线充电器”，该技术基于感应耦合的电力传输，在那里发射机可以在主感应线圈中改变电流以从在充电点中产生交变磁场。在消耗设备中的接收机可以有其自己的感应线圈从磁场中获取电力，并将它转换回电流为设备电池充电。该技术的另外一部分是通过线圈上的数据(DoC)使用系统控制通信，在那里接收机可以通过改变发射机线圈所看到的负载向发射机发送反馈。该协议是基于信号传输的频率，从而使发射机快速响应。
对于电力来说，WPT系统经常依赖开关电源，利用诸如D类或E类放大器之类的技术。然而，这些放大器的传统配置常常导致效率低下。当被用在单端的开关配置里时，放大器通常具有较低的电压增益，以及，作为结果，较 低的输出功率。当被用在差分模式的开关配置时，放大器具有较高的电压增益和输出功率，但遭受较大的切换和驱动损耗，相反降低了效率。因此，需要技术以根据不同的操作条件的系统要求提供在增加的输出功率或者较高的效率上的优化。
概要
因此，在一些说明性实施例下，自适应电源供应被公开已提供从WPT发射机到接收机的无线电传输(WPT)，包括：接收电力的输入端，以及耦合到输入端的开关装置，其中所述开关装置的第一部分耦合到发射机的第一部分，并且所述开关装置的第二部分耦合到发射机的第二部分，其中开关装置被构造为控制开关装置的第一和第二部分以在单端开关模式和差分开关模式之间选择性地操作自适应电源。
在一些说明性实施例中，自适应功率放大器包括非谐振电感和阻塞电容器。其他说明性实施例中，自适应电源包括用于确定自适应电源是否提供被期望的功率量的控制器，其中控制器可以被构造为如果被期望的功率量被提供选择性地使用单端开关模式地操作自适应电源。在进一步的示例性实施例中，控制器可以被构造为如果被期望的功率量没有被提供选择性地使用差分开关模式操作自适应电源。
在一些示例性实施例中，公开了一种用于从WPT发射机到接收机提供无线功率传输(WPT)的方法，包括在输入端为自适应电源接收电力；以及控制开关装置为WPT发射机选择性地在单端模式和差分模式之间操作自适应电源，其中开关装置包括耦合WPT发射机的第一部分的第一开关部分与耦合WPT发射机的第二部分的第二开关部分。
附图简介
从以下所给的详细描述与附图中本申请将更加充分地被理解，附图仅以示例的方式被给出，因此不限制本申请，在这里：
图1显示的是在一个说明性实施例下包括充电器与被构造为接收无线功率传输的设备的WPT系统；
图1A显示的是一个说明性实施例下图1系统的WPT电路部分的等效电路；
图2显示的是用于被构造为向接收线圈提供无线功率的单端模式放大器的WPT系统的发射线圈的零电压开关(ZVS)电压模式D类放大器；
图3显示的是用于被构造为向接收线圈提供无线功率的差分模式放大器的WPT系统的发射线圈的ZVS电压模式D类放大器；
图4显示的是在一个说明性实施例下用于被构造为向接收线圈提供无线功率的自适应开关功率放大器的WPT系统的发射线圈的ZVS电压模式D类放大器；
图5显示的是展示单端模式和差分模式过渡的仿真波形图，随着用于开关Q1断开与开关Q4闭合的说明性实施例下的图4放大器的开关模式逻辑；
图6显示的是展示单端模式和差分模式过渡的仿真波形图，随着用于开关Q1闭合与开关Q4断开的说明性实施例下的图4放大器的开关模式逻辑；
图7显示的是展示差分模式到单端模式过渡的仿真波形图，随着用于开关Q1断开与开关Q4闭合的说明性实施例下的图4放大器的开关模式逻辑；以及
图8显示的是展示差分模式到单端模式过渡的仿真波形图，随着用于在 开关Q1闭合与开关Q4断开的说明性实施例下的图4放大器的开关模式逻辑。
详细说明
此处提供的图形和描述已经被简化以说明相关方面以便清楚理解此处被描述的装置、系统和方法为了清楚起见，同时排除可能在典型的类似设备、系统和方法中找到的其它方面。那些普通技术人员因此可以认识到其它元件和/或操作可以是可取的和/或必需的以实现此处被描述的设备、系统和方法。但是因为这样的元件和操作在本领域是已知的，并且因为它们不助于更好的理解本申请，所以这里可以不提供这些元件和操作的详述。然而，本申请被认为本质上包括所有这些本领域普通技术人员应当已知的所描述的方面的元件，变化和修改。
示例性实施例被全面提供使得本申请充分彻底地将所公开的实施例的范围全部传达给本领域技术人员。许多具体细节被详细阐述以提供本申请实施例的充分理解，例如特定部件、装置和方法的示例。然而，对于本领域技术人员显而易见的是，具体公开的细节不需要被使用，以及示例性实施例可以以不同的形式实施。因此，示例性实施例不应被解释为限制本申请的范围。在一些示例性实施例中，公知的过程，公知的设备结构和公知的技术可以不被详细描述。
此处使用的术语是为了仅描述特殊示例性实施例的目的而不欲意是限制的。如此处所用，单数形式“一”，“一”和“这”也可以欲意包括复数形式，除非上下文另有明确指示。术语“包括”，“包括”，“包含”和“具有”是包容性的，因此指定所述特征，整体，步骤，操作，元件和/或组件的存在，但不排除存在或添加一个或多个其他特征，整数，步骤，操作，元件，组件和/或其组合。此处描述的步骤，过程和操作不被解释为必须要求它们以详述或说明的特定顺序执行，除非被特别确定为优选的执行顺序。还应当理解，可以采用额外的或 替代的步骤。
当一个元件或层被称为“上”，“衔接”，“连接到”或“耦合到”另一个元件或层时，它可以是直接在另一个元件或层上，衔接，连接或耦合到另一元件或层，或者可以存在介于中间的元件或层。相反，当元件被称为“直接上”，“直接衔接到”，“直接连接到”或“直接耦合到”另一个元件或层时，可以没有介于中间的元件或层。用于描述元件之间的关系的其它单词应当以类似的方式来解释(例如，“之间”对“直接之间”，“相邻”对“直接相邻”等)。如此处所用，术语“和/或”包括一个或多个相关列出的项目的任何和所有结合。
尽管术语第一，第二，第三等可以在此被用来描述不同的元件，组件，区域，层和/或部分，这些元件，组件，区域，层和/或部分不应受这些术语的限制。这些术语仅用于区分一个元件，组件，区域，层或部分与另一个元件，组件，区域，层或部分。术语诸如“第一”，“第二”和其它数字的术语当在此被使用时不意味着序列或顺序，除非上下文清楚地表示。因此，在不脱离示例性实施例的教导下，以下讨论的第一元件，组件，区域，层或部分可以被称为第二元件，组件，区域，层或部分。
现在参考如图1，在一个说明性实施例下的WPT系统100被展示，包括充电器102和包括诸如电池126的电能储存装置的设备120。在一个非限制实施例中，设备120可以是电子设备，例如智能手机，平板电脑，笔记本电脑，医疗设备，电力工具等。在另一个非限制示例中，设备120可以是汽车，公共汽车，火车等。本领域技术人员应当理解，设备120可以是能够被构造成接收WPT信号到电力设备120和/或对电能储存设备(如126)再充电的任何设备。
在图1的例子中，充电器102可以包括从电源108接收电能的电力逆变器/控制器106(以下简称“控制器”)。电源108可以是电源或任何其它合适的 能源。控制器106可以包括，但不限制于，电力逆变器电路，放大器电路，振荡器电路，滤波器电路，阻抗匹配电路，功率控制电路，处理器电路，控制器以及用于产生和控制从发射机104到接收机122的传输电力的类似物，其可以被构造为线圈，板，磁性衔铁，及类似物。
在一些说明性实施例中，发射机104和接收机122可以包括被构造成提供磁共振和/或磁感应充电的单个线圈。在一些示例性实施例中，传输线圈104和接收机122可以包括可以以重叠和/或非重叠布置构造以提供磁共振或磁感应充电的多个线圈。在一些说明性实施例中，发射机104和接收机122可以包括经电感应传输和耦合功率的电极，例如板。在一些说明性实施例中，发射机104和接收机122可以使用由同步旋转的旋转电枢的磁动力耦合来发射和耦合功率，由电枢上的磁铁产生的磁场耦合在一起。
在一些说明性实施例中，控制器106可以包括通信电路以允许控制器106通过有线或无线方式(例如，WiFi，蓝牙，红外线等)与设备120进行通信。控制器106的通信电路可以包括用于与设备120的无线天线128通信数据的无线天线110。通信数据可以包括来自设备120的设备特定信息和功率反馈数据，在那里功率反馈数据可以包括与功率传输效率，链路效率，质量因素等有关的数据。功率反馈数据可以通过直接使用发射机104和接收机122对的适用于基于分组的通信的子载波通信频带的RF功率传输链路来备选地提供。
在一些说明性实施例中，设备120可以包括功率监测和充电电路124，其可以耦合到处理器130和电能存储器126，其在一些说明性实施例中可以作为负载工作。功率监测和充电电路124可以包括，但不限于，RF电路，整流器电路，阻抗匹配电路，其可被构造为与控制器106形成阻抗匹配网络，滤波电路，经由无线天线128通信的通信电路以及向电能存储器126提供电能的充 电电路。功率监测和充电电路124还可以耦合到处理器130，处理器130可被构造为存储和执行用于测量和/或计算所接收的电能的特性(例如，电能传输效率，链路效率，品质因数等)的算法，并且通过无线天线128或其他合适的方式将其提供为反馈。
在说明性实施例中，设备120可以放置在充电器102邻近的位置中以便在接收机122中接收WPT信号，WPT信号在功率监测和充电电路124中处理/转换，并提供给电能存储器126用于后续使用。尽管在图1中未明确示出，在一个实施例中电能存储器126可以被耦接到设备120内的其它电子设备以提供操作电源。在WPT传送期间，可能有利的是发射机104和接收机122沿x，y和/或z轴物理对准，以确保由于任何轴中未对准而导致过大的信号损失不被引入，其相反可能会对电力信号传输和效率产生重大影响。
转向附图1A，等效电路使用图1的WPT系统100的部分被显示出来，在那里，在该非限制示例中，发射机104和接收机122被配置为谐振WPT电路。发射机102可以包括振幅VP频率ω并具有电源电阻RP的电压源。电压源可以被耦接到可以包括电容器CT，电感器LT和电阻器RT的发射机谐振器电路。能量可以在电感器LT(表示存储在磁场中的能量)和电容器CT(表示存储在电场中的能量)之间的谐振频率处振荡并且可以在电阻器RT中消散。发射机102的谐振器电路可以通过互感(M)耦合到接收机120的电感器LR，其可以使用电路CR和RR同样地谐振以提供负载RL的电能。
一般来说，谐振器(例如，104,122)可以通过多个参数被描述，包括，但不限于，其谐振频率ω及其固有损耗率Γ。这些参数的比率可用于确定谐振器的质量因子或Q，在那里Q＝ω/2Γ来测量谐振器存储能量多好。发射机和接收机(T，R)谐振器的谐振频率和质量因子可以表示为
Figure PCTCN2017086526-appb-000001
与
Figure PCTCN2017086526-appb-000002
从图1A，发射机(例如104)和接收机(例如122)线圈可以分别由电感器LT和LR表示，它们可以通过互感M耦合，其中
Figure PCTCN2017086526-appb-000003
其中k是耦合系数或能量耦合率。每个线圈可以具有串联电容器(CT，CR)以形成谐振器。电阻RT和RR可以被认为是包括各个线圈和谐振电容器的所有欧姆的，非传导性的和辐射的损耗的寄生电阻。负载，可以是能量储存器126，在本示例中由RL表示。
传输到负载(例如RL)的电能可以通过划分当发射机和接收机都在频率ω共振时从发射机可获得的最大电能确定，或者
Figure PCTCN2017086526-appb-000004
其中U可以被认为是系统的性能度量(“品质因数”)，并且可以表示为
Figure PCTCN2017086526-appb-000005
阻抗匹配(例如，使用阻抗变换网络)可以被用于尽可能接近地匹配电阻以提高初始效率(例如，
Figure PCTCN2017086526-appb-000006
)，其中功率传输的效率可以最大化，根据
Figure PCTCN2017086526-appb-000007
其中更高效率的能量传输可以在更高的U值下实现。
效率也可以基于在接收机(ΓR)内的能量损失率，和/或可以基于谐振器之间的 磁耦合系数(k)和发射机和接收机(QT，QR)的谐振器质量因子如下：
Figure PCTCN2017086526-appb-000008
通过使用谐振器质量因子和特定应用的发射机和接收机之间的度量耦合范围，WPT的效率能够容易地被确定。
如本领域技术人员能够认识到的，WPT系统可以被构造为功率通过发射机(TX)和接收机(RX)线圈之间的磁场谐振耦合传输。功率也可以通过TX和RX线圈之间的磁场感应耦合传输。对于两种无线功率传输技术，功率放大器应在输入端侧被提供以产生要传递到输出端侧的交流输入能量。
虽然在本申请中许多电源和放大器配置被考虑，但当应用到WPT系统时，某些放大器配置提供有利的特征。一个非限制示例包括零电压开关放大器。在交流(AC)系统中，过零点是没有电压的瞬时点。在正弦波或其他简单波形中，通常每个周期内出现两次。如果电功率将被切换，若电路转换在没有电流(即过零点)的瞬间发生，则没有电气干扰产生。
在这种应用中，开关放大器，诸如脉冲宽度调制(PWM)放大器，可以被有利地使用。在这个说明性的放大器类型中，放大器开关(例如，金属氧化物半导体场效应晶体管(MOSFETS))可以被配置为要么完全导通或完全断开，这显著降低在输出端的功率损失，允许效率高达90-95％。放大器输入信号可用于调制可以被用于驱动输出装置的PWM载波信号。在一些说明性实施例中低通滤波器可以被用来去除高频率的PWM载波频率。开关放大器的示例包括，但不限于，D类和E类放大器。
转到图2，单端ZVS电压模式(VM)D类放大器200被说明。在该示 例中，输入电源201被提供到功率发射机线圈207，在那里开关202和203可以被配置为在来自电源201的每个正和负周期上交替导通和关断的互补开关。非谐振LC回路(204,205)可以被提供以实现开关202和203的零开关节点电压转换。从线圈207传输的功率可以在210中进行整流以前在存储(例如126)或传输直流电源到电路以前在接收线圈208和电容器209被接收。
放大器200的一个优点在于该配置在功率开关(202,203)上提供较低的电压应力，与E类，和/或电流模式D类放大器相比。此外，放大器200的配置还可以给零电压开关提供更宽的负载条件(与传统的VM D类放大器相比)，与更容易的辐射EMI滤波器设计(与E类放大器相比)。然而，这种放大器具有低电压增益(例如，1/2Vin)的缺点，在那里，对于给定的输入电压和负载阻抗，它转换为低输出功率。
在一些说明性实施例中，与单端模式相比，这个限制可以通过利用差分模式(DM)零电压开关VM的D类放大器潜在地加倍输出功率容量来缓解。转到图3，用于向接收机线圈提供无线电力的差分模式放大器被示出，在那里输入电源301被提供到发射机线圈309，在那里电容器302可以被配置为与差分开关303-304和305-306并联，其中开关303的源极端子和开关304的漏极端子如图所示耦合在一起并输出到电感器307的正极端子。开关305的源极端子和开关306的漏极端子如图所示耦合在一起并输出到电感器307的负极端子。然后通过电感器307的电感纹波电流可以被提供以实现零开关节点电压转换(经由开关303-304和305-306)。从线圈309传输的功率可以在312进行整流以前在存储(例如126)或传输直流电源到电路以前在接收线圈310和电容器311被接收。
如上简述，DM零电压开关放大器的缺点之一是增加的开关可能导致与 单端模式相比两倍开关和驱动损耗，降低效率。此外，在某些操作期间，开关电感器307可能被直流偏置电压饱和如果占空比不是精确的50％，这可能是由时钟信号容限或不对称的时间延迟引起的。这种情况甚至可能引起进一步的开关损耗，与潜在地导致零电压开关故障。因此，本领域技术人员经常面临选择可能产生次优，较低功率的高效率放大器(如图2所示)，或选择次优效率的高功率放大器放大器(如图3所示)的困境。
转到图4，在一个示例性实施例下的自适应零电压开关D类放大器被示出。在该示例中，差分模式开关通过如图所示开关403-404和405-406跨过电容器402被耦接到输入电压401被提供。开关403的源极端子和开关404的漏极端子如图所示耦合在一起并输出到电感器407的一个端子。开关405的源极端子和开关406的漏极端子如图所示耦合在一起并输出到电容器408的一个端子。407和408的位置能够被交换不会失去这种方法的通用性。
在这个例子中，阻塞电容器408被添加与开关电感器串联以阻止直流偏置饱和电感器407，这反过来使得零电压开关更可靠并且，与此同时，改善放大器400的效率。此外，利用阻塞电容器408使得放大器能够改变模式并在简单的自适应控制逻辑下自适应地工作在单端模式或差分模式。对于给定的负载阻抗，功率放大器的输入电压VIN可以被调整以传输期望的的输出功率。
因此，放大器400可以被置于初始的单端操作模式通过将电源开关Q2配置为连续断开状态并将电源开关Q3配置为连续导通状态，留下Q1和Q4进行切换操作。单端模式操作也可以被实现通过配置Q2和Q3进行切换来，同时，Q1被配置为连续关断与Q4被配置为连续导通。在一个示例中，在单端模式操作期间，期望的输出功率可以被传输通过使用允许的输入电压范围调整VIN。然后可以利用最小化的开关损耗和驱动损耗的单端操作模式的优化效率来维 持期望的输出功率。然而，如果即使在最大输入电压下期望的输出功率也不能被传输，则这将表明在单端模式下的输出功率能力不足够大以处理这种负载阻抗。在这种情况下，电路400可以被切换到差分模式操作以优化输出功率能力。
在一个实施例下用于从单端模式到差分模式的转换控制逻辑在图5中示出。在该示例中，模式逻辑501被示出用于从低(单端模式)506到高(差分模式)508，在那里模式改变507以延伸穿过模拟波形的虚线被示出。开关Q1，Q4和Q3，Q2的进来的模拟门波形中的每一个分别被示出为502-503和504-505。如图中能够被看见的，开关502和503可以被配置为互补地开关在那里在开关504为高且开关505为低。在单端模式操作506期间，开关504可以被配置为连续的接通状态且开关505可以被配置为连续关断状态。一旦模式转换被需要，模式改变507被实现通过设置模式逻辑501为高508差分模式操作。一旦模式改变507发生，开关504可以跟随开关502的下降沿(509)从“始终导通”状态变到切换状态，开关505可以跟随开关503的门驱动信号的上升沿(510)从“始终断开”状态变为如图所示的切换状态。在说明性实施例中，模式变化转换可以在少于一个开关周期内完成，且没有开关击穿问题(例如，由两个开关同时导通的电流冲击)既然它已经通过死区时间来负责，例如，在Q1和Q4之间。
在一份说明性实施例下的从另一个从单端模式到差分模式的转换控制逻辑在图6中被示出。在该示例中，从低(单端模式)606到高(差分模式)608转换的模式逻辑601被示出，在那里模式改变607以延伸穿过模拟波形的虚线被示出。开关Q1，Q4和Q3，Q2的每个进来的模拟门波形分别显示为602-603和604-605。如图中能被看到的，开关602和603可以被配置为在开关604为高且开关605为低处互补地开关。
在单端模式操作606期间，开关604可以被配置为连续的导通状态与开关605可以被配置为连续关断状态。一旦模式转换被需要，模式改变607被实现通过设置模式逻辑601为高608差分模式操作。如图所示，模式改变607一旦发生，开关604可以跟随开关602的下降沿(609)从“始终导通”状态变到开关状态，开关605可以跟随开关603的门驱动信号的上升沿(610)从“始终关断”状态变到开关状态。在图6的示例中，可以看出当开关602导通且开关603关断时(与图5相比，在那里当开关502为关断且开关503导通时模式改变507发生)模式改变607发生。本领域技术人员能够理解，不管在模式改变操作期间开关状态如何，模式改变转换可以在少于一个开关周期内完成。
通过执行模式改变(507,607)，操作模式可以从单端操作模式转换到差分操作模式，特别是在对于单端操作模式下给定的负载阻抗期望的输出功率不能被满足的情况下。然而，一旦放大器处于差分模式，负载阻抗可能由于TX和RX线圈之间的相对位置的变化，或者随输出电流的变化而改变。对于更新的负载阻抗，如果可以传输被期望输出功率的调整后的VIN小于最大输入电压的一半，这表明可以在单端模式相同的输出功率能够被传输。因此，操作模式可以被转回到单端模式以优化效率。
在一个说明性实施例下的从差分模式转换到单端模式的模式逻辑图在图7中被示出。在该示例中，从高(差分模式)706转换到低(单端模式)708的模式逻辑701被示出，在那里模式改变707以延伸穿过模拟波形的虚线被示出。开关Q1，Q4和Q3，Q2的每个进来的模拟门波形分别显示为702-703和704-705。从图中能被看见的，开关702-703和704-705可以被配置为互补地切换。
与图5-6的实施例相反，电路的配置(例如，图4)使得模式逻辑701 最初在高差分模式706工作，并且开关702-703和704-705都是互补地切换。一旦发生模式改变707，开关704可以跟随开关702的上升沿(709)从开关状态变为“始终导通”状态，并且开关705可以跟随开关703门驱动信号的下降沿(710)变为“始终关断”状态。如前所述，不管在模式改变操作期间的开关状态如何，模式改变转变(例如707)可以在少于一个开关周期内完成。
在一个说明性实施例下，从差分模式转换到单端模式的另一种模式逻辑图在图8中示出。在该示例中，从高(差分模式)806转换到低(单端模式)808的模式逻辑801被示出，在那里模拟改变807以延伸穿过模拟波形的虚线被示出。开关Q1，Q4和Q3，Q2的每个进来的模拟门波形分别显示为802-803和804-805。从图中能被看见，开关802-803和804-805可以被配置为互补地开关。
与图7类似，电路的配置(例如，图4)是图8的模式逻辑801最初在高差分模式806下工作，并且开关802-803和804-805都是互补地开关，在那里当开关804为低时开关805也为高，反之亦然。一旦模式改变807发生，开关804可以跟随开关802的上升沿(809)从差分开关状态变为“始终导通”状态，并且开关805可以跟随开关803的门驱动信号的下降沿(810)变为“总是关断”状态。在图8的示例中，可以看出，当开关802导通与开关803为关断时模式改变807发生(与图7相比，在那里当开关702关断且开关703接通时模式改变707发生)。再一次，不管在模式改变操作期间的开关状态如何，模式改变转变(例如，807)可以在少于一个开关周期内完成。
本领域技术人员应当理解本公开里提供了一种创新的自适应零电压开关放大器，用于在无线功率传输中保持效率和输出功率优化。通过在单端模式操作和差分模式操作之间自适应转换，放大器(例如D类，E类)能根据不同的 负载阻抗优化效率和输出功率能力。与常规放大器相比，本申请可以将所需的最大输入电压减小一半，从而降低功率设备的额定电压，并且还可以减少开关和驱动损耗，改善整体系统效率。在WPT应用中，本申请允许放大器在单端模式中操作以当TX和RX线圈被正确耦合时有效地传输输出功率。然而，当TX和RX线圈不是最佳耦合时，本申请允许放大器切换到差分模式操作以维持输出功率。
在前面的详细描述中，可以看出，出于简化本申请目的在各个实施例中不同特征被组合在一起。公开的方法不应被认为反应以下意图，即随后要保护的实施例比在每条权利要求中明确叙述的需要更多的特征。
此外，本申请的描述被提供以使本领域的任何技术人员能够制造或者使用公开的实施例。对本申请的各种修改对于本领域技术人员将是显而易见的，并且在不脱离本申请精神或范围下，此处被定义的一般原理可以应用于其它变形。因此，本申请不在于被限于此处所描述的示例和设计，而在于被赋予与此处被公开的原理和新颖特征一致的最大范围。

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  1. 一种用于从WPT发射机向接收机提供无线电力传输(WPT)的自适应电源，包括：
    用于接收电力的输入端，以及
    开关装置，耦接到输入端，其中所述开关装置的第一部分耦合到发射机的第一部分，并且所述开关装置的第二部分耦合到发射机的第二部分，
    其中开关装置被配置为控制开关装置的第一和第二部分以选择性地在单端开关模式和差分开关模式之间操作自适应电源。
  2. 根据权利要求1所述的自适应电源，其中开关装置的第一部分包括多个串联耦合的开关并联耦合到所述输入端。
  3. 根据权利要求2所述的自适应电源，其中开关装置的第二部分包括多个串联耦合的开关并联耦合到开关装置的第一部分。
  4. 根据权利要求3所述的自适应电源，其中第一和第二开关部分的串联耦合开关包括至少包括MOSFET器件，GaN器件和/或SiC器件中的一个的开关。
  5. 根据权利要求1所述的自适应电源，其中所述自适应电源包括非谐振电感器和阻塞电容器。
  6. 根据权利要求5所述的自适应电源，还包括用于确定期望功率量是否被自适应电源提供的控制器。
  7. 根据权利要求6所述的自适应电源，其中控制器被配置为如果期望功率量被提供，则使用单端模式选择性地操作自适应电源。
  8. 根据权利要求6所述的自适应电源，其中控制器被配置为如果在单端模式下期望的功率量未被提供，则使用差分模式选择性地操作自适应电源。
  9. 一种从WPT发射机向接收机提供无线电力传输(WPT)的方法，包括：
    在自适应电源的输入端接收电力；以及
    控制开关装置选择性地在单端模式和差分模式之间操作用于WPT发射器的自适应电源，其中开关装置包括耦合到WPT发射机第一部分的第一开关部分以及耦合到WPT发射机的第二部分的第二开关部分。
  10. 根据权利要求9所述的方法，其中控制开关装置包括通过并联耦合到输入端的多个串联耦合开关控制第一开关部分。
  11. 根据权利要求10所述的方法，其中控制开关装置包括通过并联耦合到开关装置的第一开关部分的多个串联耦合开关控制第二开关部分。
  12. 根据权利要求11所述的方法，其中第一和第二开关部分的串联耦合开关包括MOSFET器件，GaN器件或SiC器件中的至少一个。
  13. 根据权利要求9所述的方法，其中自适应电源包括非谐振电感器和阻塞电容器。
  14. 根据权利要求13所述的方法，还包括通过控制器确定期望的功率量是否被自适应电源提供。
  15. 根据权利要求14所述的方法，还包括如果期望的功率量被提供，则使用单端模式选择性地操作自适应电源。
  16. 根据权利要求14所述的方法，还包括如果期望的功率量未被提供，则使用差分模式选择性地操作自适应电源。
  17. 一种用于从WPT发射机向接收机提供无线电力传输(WPT)的自适应电源，包括：
    用于接收电力的输入端，以及
    开关装置，被耦合到输入端，其中开关装置的第一部分耦合到所述WPT 发射机的第一部分，以及开关装置的第二部分耦合到所述WPT发射机的第二部分；以及
    控制器，用于确定期望的功率量是否被自适应电源提供，
    其中开关装置被配置为控制开关装置的第一和第二部分选择性地在单端模式和差分模式之间操作自适应电源以提供期望的功率量。
  18. 根据权利要求17所述的自适应电源，其中开关装置的第一部分包括并联耦合到输入端的多个串联耦合开关。
  19. 根据权利要求18所述的自适应电源，其中开关装置的第二部分包括并联耦合到开关装置第一部分的多个串联耦合开关。
  20. 根据权利要求6所述的自适应电源，其中控制器被配置为如果期望的功率量被提供则使用单端模式选择性地操作自适应电源(i)，以及(ii)如果在单端模式下期望的功率量未被提供则使用差分模式。
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