WO2018000803A1 - 一种具有耦合抑制窄带的缝隙天线 - Google Patents

一种具有耦合抑制窄带的缝隙天线 Download PDF

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Publication number
WO2018000803A1
WO2018000803A1 PCT/CN2017/000405 CN2017000405W WO2018000803A1 WO 2018000803 A1 WO2018000803 A1 WO 2018000803A1 CN 2017000405 W CN2017000405 W CN 2017000405W WO 2018000803 A1 WO2018000803 A1 WO 2018000803A1
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Prior art keywords
capacitor
antenna
slot
slot antenna
slit
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PCT/CN2017/000405
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English (en)
French (fr)
Inventor
吴琦
苏东林
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北京航空航天大学
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Priority to US16/076,305 priority Critical patent/US10734730B2/en
Publication of WO2018000803A1 publication Critical patent/WO2018000803A1/zh

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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q13/00—Waveguide horns or mouths; Slot antennas; Leaky-waveguide antennas; Equivalent structures causing radiation along the transmission path of a guided wave
    • H01Q13/10—Resonant slot antennas
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q13/00—Waveguide horns or mouths; Slot antennas; Leaky-waveguide antennas; Equivalent structures causing radiation along the transmission path of a guided wave
    • H01Q13/10—Resonant slot antennas
    • H01Q13/103—Resonant slot antennas with variable reactance for tuning the antenna
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/36—Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith
    • H01Q1/38—Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith formed by a conductive layer on an insulating support
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/52—Means for reducing coupling between antennas; Means for reducing coupling between an antenna and another structure
    • H01Q1/521—Means for reducing coupling between antennas; Means for reducing coupling between an antenna and another structure reducing the coupling between adjacent antennas
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/28—Combinations of substantially independent non-interacting antenna units or systems

Definitions

  • the present invention relates to a slot antenna, and more particularly to a slot antenna having a coupling suppression narrow band.
  • the present invention contemplates a slot antenna having a coupling suppression narrow band.
  • the present invention performs capacitive loading on a specific location of a copper clad layer on a finite dielectric plate to increase isolation between the antennas.
  • the invention designs a slot antenna with coupling suppression for loading capacitors, and solves the technical problem of how to suppress the out-of-band coupling between the narrow-band antennas on the finite medium plate, and adopts a copper-clad process on the dielectric plate.
  • a slit antenna having a coupling suppression narrow band designed by the present invention is composed of a dielectric plate (1), a copper clad layer (2), an A capacitor (3), and a B capacitor (4).
  • the copper layer (2) An A slit (21) and a B slit (22) are provided, and an A capacitor (3) and a B capacitor (4) are mounted at both ends of the B slot (22).
  • the copper-clad layer (2) has a copper-clad thickness of 0.018 to 0.035 mm.
  • the structural dimensions of the slot antenna of the present invention are constrained by a wavelength of 50 mm to 5000 mm.
  • the invention utilizes a dielectric plate to simulate a limited ground plane.
  • the load capacitance can be utilized to further improve the isolation between the antennas.
  • the slot antenna of the invention is simple to manufacture, and the operating frequency of the antenna can be changed by adjusting the size of the antenna, and the application is wider.
  • the slot antenna of the invention has many features such as low profile, light weight, simple processing, easy conformity with objects, mass production, diversified electrical properties, wideband and integrated components with active devices and circuits, and is suitable for mass production. It can simplify the production and debugging of the whole machine, thus greatly reducing the cost.
  • the gap is set on the conventional antenna, and the capacitor is loaded in the slot, which can easily realize the rectification of the conventional antenna and improve the isolation between the antennas.
  • Figure 1 is a structural view of a slot antenna of the present invention.
  • FIG. 2 is a structural diagram of a slot antenna with no capacitance applied.
  • Fig. 3A is a S11 parameter diagram of the slot antenna of the first embodiment.
  • Fig. 3B is a S12 parameter diagram of the slot antenna of the first embodiment.
  • Fig. 3C is a S22 parameter diagram of the slot antenna of the first embodiment.
  • 4A is a view showing an E-plane of the slot antenna of the first embodiment.
  • 4B is a view showing a H-plane direction of the slot antenna of the first embodiment.
  • FIG. 5 is a S12 parameter diagram of loading a different capacitance value of the slot antenna of Embodiment 1.
  • FIG. 5 is a S12 parameter diagram of loading a different capacitance value of the slot antenna of Embodiment 1.
  • the present invention contemplates a slot antenna having a coupling suppression narrow band, which is composed of a dielectric plate 1, a copper clad layer 2, and an A capacitor 3 and a B capacitor 4.
  • the copper clad layer 2 is provided with an A slit 21 and a B slit 22, and both ends of the B slit 22 are provided with an A capacitor 3 and a B capacitor 4.
  • the copper-clad layer 2 has a copper-clad thickness of 0.018 to 0.035 mm.
  • the length of the dielectric plate 1 is a 1
  • the width of the dielectric plate 1 is b 1
  • the thickness of the dielectric plate 1 is generally 0.5 to 1.5 mm.
  • the length of the A slit 21 is a 21
  • the width of the A slit 21 is b 21 .
  • the length of the B slit 22 is a 22
  • the width of the B slit 22 is b 22 .
  • the interval between the A slit 21 and the B slit 22 is denoted by D.
  • the mounting interval between the A capacitor 3 and the B capacitor 4 is denoted by d.
  • the feed mode of the slot antenna designed by the present invention is the center feed, that is, at the midpoint of the slot.
  • the A capacitor 3 and the B capacitor 4 are selected from the high frequency type high Q type GJM series capacitors produced by Murata Corporation of Japan, and the capacitance values are 0.2 pF to 20 pF.
  • the wavelength ⁇ is 50 mm to 5000 mm as the slot antenna constrained size design:
  • a 1 (0.8 ⁇ 1.5) ⁇
  • b 1 (0.6 ⁇ 1.0) ⁇
  • a 22 (0.005 - 0.01) ⁇
  • b 22 (0.4 - 0.6) ⁇ .
  • the thickness of the copper clad layer 2 is 0.035 mm.
  • the capacitance value of the A capacitor 3 is 4.6 pF, and the capacitance value of the B capacitor 4 is 4.6 pF.
  • the performance evaluation of the S parameter was carried out for the embodiment 1.
  • the dotted line in the figure indicates a conventional antenna (i.e., unloaded capacitor), and the solid line indicates the antenna of the embodiment 1 of the present invention.
  • the S11 parameter indicates the performance of the B-slot, and its performance at the operating frequency of 140 MHz is substantially unchanged before and after the capacitor is loaded.
  • the present invention uses S12 to evaluate the isolation between the A-slot and the B-slot before and after capacitive loading.
  • the conventional antenna at a working frequency of 140 MHz is -22 dB.
  • the antenna of Embodiment 1 was reduced to -34 dB, which was reduced by 12 dB.
  • the S22 parameter indicates the performance of the B-slot, and its performance at the operating frequency of 280 MHz is substantially unchanged before and after the capacitor is loaded.
  • the performance evaluation before and after the capacitive loading was performed using the pattern: the broken line in the figure indicates a conventional antenna, and the solid line indicates the antenna of the embodiment 1 designed. It can be seen from the E-plane pattern of FIG. 4A and the H-plane pattern of FIG. 4B that the antenna radiation performance is not affected when the operating frequency is 140 MHz.
  • the S12 value of the antenna of the embodiment 1 of the present invention at the operating frequency of 140 MHz is the same as the capacitance
  • the variation of the load value is shown in Figure 5. It is significantly suppressed at a capacitance value of 4.6 pF, and S12 is optimal.
  • the thickness of the copper clad layer 2 is 0.035 mm.
  • the capacitance value of the A capacitor 3 is 3.2 pF, and the capacitance value of the B capacitor 4 is 3.2 pF.
  • the broken line in the figure indicates a conventional antenna
  • the solid line indicates the antenna of the embodiment 2 designed.
  • the present invention uses the S11 parameter to indicate the performance of the A-slot, and its performance at the operating frequency of 140 MHz is substantially unchanged before and after the capacitive loading.
  • the invention uses S12 to evaluate the isolation between the A-slot and the B-slot before and after the capacitive loading, and the coupling degree at the working frequency of 400 MHz is -18 dB.
  • the antenna of Embodiment 2 is reduced to -30 dB, which is reduced by 12 dB.
  • the present invention uses the S22 parameter to indicate the performance of the B-slot, and its performance at the operating frequency of 400 MHz is substantially unchanged before and after the capacitive loading.
  • the performance evaluation of the capacitor before and after the load is applied. It can be seen from the E-plane pattern that when the operating frequency is 140 MHz, the directionality is better after the capacitor is loaded, which is closer to the dipole antenna. It can be seen from the H-plane pattern that the radiation performance of the H-plane antenna is not affected when the operating frequency is 140 MHz.
  • the mutual coupling value of the antenna of the embodiment 2 of the present invention at the operating frequency of 400 MHz is the same as the capacitance
  • the variation of the load value shows that the capacitance value is significantly suppressed at 3.2 pF, and S12 is optimal.

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  • Details Of Aerials (AREA)

Abstract

本发明公开了一种具有耦合抑制窄带的缝隙天线，该缝隙天线由介质板（1）、覆铜层（2）、A电容（3）和B电容（4）构成。所述覆铜层（2）上开有A缝隙（21）和B缝隙（22），所述B缝隙（22）内的两端安装有A电容（3）和B电容（4）。本发明是在有限底板上的特定位置进行电容加载，以此增加天线之间的隔离度，有利于实现对缝隙天线的整改。

Description

一种具有耦合抑制窄带的缝隙天线 技术领域
本发明涉及一种缝隙天线，更特别地说，是指一种具有耦合抑制窄带的缝隙天线。
背景技术
随着雷达系统及无线通信设备的不断进步与发展，缝隙技术在其天线的设计中有着越来越广泛的应用。加工在波导壁上的波导缝隙阵列天线，由于其具有口径效率高、损耗小、功率容量大、结构紧凑、加工与安装便捷等显著优点，成为当前雷达天线的优选形式。另一方面，具有多频带、双极化特性的平面印刷缝隙天线，以其小型化、低成本的优势，在移动终端设备及无线通信基站中得到广泛应用。另外，在各行各业的天线设计中可以发现，当天线的工作频率并不重叠时，天线间很强的带外耦合是不能忽略的。
发明内容
为了抑制有限介质板上的窄带天线间的带外耦合，本发明设计了一种具有耦合抑制窄带的缝隙天线。本发明是在有限介质板上的覆铜层的特定位置进行电容的加载，以此增加天线之间的隔离度。
本发明设计了一种加载电容的具有耦合抑制的缝隙天线，所要解决的是如何抑制有限介质板上的窄带天线间的带外耦合的技术问题，采用的是在介质板上采用覆铜工艺加工有存在间隙的覆铜层，存在间隙的覆铜层之间焊接有两个电容；馈电点为两个缝隙的中点处。
本发明设计的一种具有耦合抑制窄带的缝隙天线，其由介质板(1)、覆铜层(2)、A电容(3)和B电容(4)构成。所述覆铜层(2) 上设有A缝隙(21)和B缝隙(22)，所述B缝隙(22)内的两端安装有A电容(3)和B电容(4)。所述覆铜层(2)的覆铜厚度为0.018～0.035mm。对于本发明的缝隙天线的结构尺寸是以波长为50mm～5000mm作为约束的。
本发明缝隙天线的优点在于：
①本发明利用介质板模拟有限地平面，在介质板尺寸固定情况下，可以利用加载电容进一步提升天线之间的隔离度。
②本发明缝隙天线制作简单，可通过调整天线尺寸来改变天线的工作频率，应用更广泛。
③本发明缝隙天线具有轮廓低、重量轻、加工简单、易于与物体共形、批量生产、电性能多样化、宽带和与有源器件和电路集成为统一的组件等诸多特点，适合大规模生产，能简化整机的制作与调试，从而大大降低成本。
④采用在传统天线上设置缝隙，且在缝隙中加载电容，能够方便实现对传统天线的整改，提升天线之间的隔离度。
附图说明
图1是本发明缝隙天线的结构图。
图2是未加载电容的缝隙天线的结构图。
图3A是实施例1缝隙天线的S11参数图。
图3B是实施例1缝隙天线的S12参数图。
图3C是实施例1缝隙天线的S22参数图。
图4A是实施例1缝隙天线的E面方向图。
图4B是实施例1缝隙天线的H面方向图。
图5是实施例1缝隙天线的加载不同电容值的S12参数图。
1.介质板 2.覆铜层 21.A缝隙
22.B缝隙 3.A电容 4.B电容
具体实施方式
下面将结合附图和实施例对本发明做进一步的详细说明。
参见图1所示，本发明设计了一种具有耦合抑制窄带的缝隙天线，该缝隙天线由介质板1、覆铜层2和A电容3和B电容4构成。所述覆铜层2上开有A缝隙21和B缝隙22，所述B缝隙22内的两端安装有A电容3和B电容4。
在本发明中，覆铜层2的覆铜厚度为0.018～0.035mm。
介质板1的长记为a1、介质板1的宽记为b1、介质板1的厚度一般为0.5～1.5mm。
A缝隙21的长记为a21、A缝隙21的宽记为b21。
B缝隙22的长记为a22、B缝隙22的宽记为b22。
A缝隙21与B缝隙22的间隔记为D。
A电容3与B电容4的安装间隔记为d。
本发明设计的缝隙天线的馈电方式为中心馈电，即在缝隙的中点。
在本发明中，A电容3和B电容4选用日本村田公司生产的高频型高Q型GJM系列型号电容，电容值为0.2pF～20pF。
在本发明中，考虑到天线实际应用场景，以波长λ为50mm～5000mm作为缝隙天线约束尺寸设计：
a1＝(0.8～1.5)λ、b1＝(0.6～1.0)λ；
d＝0.76b22；
D＝(0.3～0.5)λ；
a21＝(0.005～0.01)λ、b21＝(0.2～0.3)λ；
a22＝(0.005～0.01)λ、b22＝(0.4～0.6)λ。
实施例1
介质板1的长a1＝175cm、介质板1的宽b1＝110cm、介质板1的厚度一般为0.8mm。覆铜层2的厚度为0.035mm。
A缝隙21的长a21＝1cm，A缝隙21的宽b21＝43.9cm。
B缝隙22的长a22＝1cm，B缝隙22的宽b22＝89cm。
A缝隙21与B缝隙22的D＝75cm。
A电容3和B电容4与的间距d＝68cm。A电容3的电容值为4.6pF，B电容4的电容值为4.6pF。
对实施例1采用S参数进行性能评价：图中虚线表示传统天线(即未加载电容)，实线表示本发明设计的实施例1天线。
参见图3A所示，S11参数表示B缝隙的工作性能，在电容加载前后其在工作频率140MHz处的性能基本不变。
参见图3B所示，本发明使用S12评价电容加载前后A缝隙与B缝隙之间的隔离度，如图3B所示，在工作频率140MHz处的耦合度传统天线为-22dB。而实施例1天线降低到-34dB，下降了12dB。参见图3C所示，S22参数表示B缝隙的工作性能，在电容加载前后其在工作频率280MHz处的性能基本不变。
对实施例1采用方向图进行电容加载前后性能评价：图中虚线表示传统天线，实线表示设计的实施例1天线。从图4A的E面方向图和图4B的H面方向图中可以看出，工作频率为140MHz时，天线辐射性能不受影响。
本发明实施例1天线在工作频率为140MHz时的S12值随电容 加载值的变化曲线如图5所示，在电容值为4.6pF处明显地被抑制了，且S12为最优。
实施例2
介质板1的长a1＝175cm、介质板1的宽b1＝110cm、介质板1的厚度一般为0.8mm。覆铜层2的厚度为0.035mm。
A缝隙21的长a21＝1cm，A缝隙21的宽b21＝30.7cm。
B缝隙22的长a22＝0.5cm，B缝隙22的宽b22＝89cm。
A缝隙21与B缝隙22的D＝76cm。
A电容3和B电容4与的间距d＝68cm。A电容3的电容值为3.2pF，B电容4的电容值为3.2pF。
对实施例2采用S参数进行性能评价：图中虚线表示传统天线，实线表示设计的实施例2天线。
本发明使用S11参数表示A缝隙的工作性能，在电容加载前后其在工作频率140MHz处的性能基本不变。
本发明使用S12评价电容加载前后A缝隙与B缝隙之间的隔离度，在工作频率400MHz处的耦合度传统天线为-18dB。而实施例2天线降低到-30dB，下降了12dB。
本发明使用S22参数表示B缝隙的工作性能，在电容加载前后其在工作频率400MHz处的性能基本不变。
对实施例2采用方向图进行电容加载前后性能评价：从E面方向图中可以看出，工作频率为140MHz时，电容加载后方向性更好，更加接近偶极子天线。从H面方向图中可以看出，工作频率为140MHz时，H面天线辐射性能不受影响。
本发明实施例2天线在工作频率为400MHz时的互耦值随电容 加载值的变化曲线可知，在电容值为3.2pF处明显地被抑制了，且S12为最优。

Claims (6)

  1. 一种具有耦合抑制窄带的缝隙天线，其特征在于：该缝隙天线由介质板(1)、覆铜层(2)、A电容(3)和B电容(4)构成。所述覆铜层(2)上开有A缝隙(21)和B缝隙(22)，所述B缝隙(22)内的两端安装有A电容(3)和B电容(4)。
  2. 根据权利要求1所述的一种具有耦合抑制窄带的缝隙天线，其特征在于：覆铜层(2)的覆铜厚度为0.018～0.035mm。
  3. 根据权利要求1所述的一种具有耦合抑制窄带的缝隙天线，其特征在于：缝隙天线的结构尺寸以波长为50mm～5000mm作为约束的。
  4. 根据权利要求3所述的一种具有耦合抑制窄带的缝隙天线，其特征在于缝隙天线结构为：
    a1＝(0.8～1.5)λ、b1＝(0.6～1.0)λ；
    d＝0.76b22；
    D＝(0.3～0.5)λ；
    a21＝(0.005～0.01)λ、b21＝(0.2～0.3)λ；
    a22＝(0.005～0.01)λ、b22＝(0.4～0.6)λ。
  5. 根据权利要求1所述的一种具有耦合抑制窄带的缝隙天线，其特征在于：缝隙天线中加载的电容值为0.2pF～20pF。
  6. 根据权利要求1所述的一种具有耦合抑制窄带的缝隙天线，其特征在于：在缝隙中加载电容适合对传统天线进行整改。
PCT/CN2017/000405 2016-06-27 2017-06-26 一种具有耦合抑制窄带的缝隙天线 WO2018000803A1 (zh)

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US16/076,305 US10734730B2 (en) 2016-06-27 2017-06-26 Narrow band slot antenna with coupling suppression

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CN106025562B (zh) * 2016-06-27 2018-06-05 北京航空航天大学 一种具有耦合抑制窄带的缝隙天线
CN113555692B (zh) * 2020-04-23 2023-02-03 华为技术有限公司 一种电子设备
TWI819549B (zh) * 2021-07-20 2023-10-21 宏達國際電子股份有限公司 偵測裝置和偵測方法

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