WO2015196629A1 - Procédé et dispositif pour estimer un décalage de fréquence de porteuses - Google Patents

Procédé et dispositif pour estimer un décalage de fréquence de porteuses Download PDF

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Publication number
WO2015196629A1
WO2015196629A1 PCT/CN2014/088426 CN2014088426W WO2015196629A1 WO 2015196629 A1 WO2015196629 A1 WO 2015196629A1 CN 2014088426 W CN2014088426 W CN 2014088426W WO 2015196629 A1 WO2015196629 A1 WO 2015196629A1
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domain channel
channel response
time domain
ofdm symbol
zero
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PCT/CN2014/088426
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English (en)
Chinese (zh)
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文武
许秋平
王凯
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中兴通讯股份有限公司
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Publication of WO2015196629A1 publication Critical patent/WO2015196629A1/fr

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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes

Definitions

  • the present invention relates to the field of communications technologies, and in particular, to a method and apparatus for carrier frequency offset estimation in an Orthogonal Frequency Division Multiplexing (OFDM) system.
  • OFDM Orthogonal Frequency Division Multiplexing
  • the CP correlation method and the conventional RS method are included.
  • the cyclic prefix (CP: Cyclic Prefix) correlation method uses the cyclic prefix CP of the OFDM symbol to perform frequency offset estimation. Since the CP and the OFDM symbol tail end transmit data are the same, the transmission data of the OFDM symbol tail end is multiplied by the corresponding CP segment. The conjugate of the data can obtain the phase difference caused by the carrier frequency offset, and then estimate the frequency offset. However, there will be problems with poor estimation accuracy.
  • the conventional reference signal (RS: Reference Signal) method performs frequency offset estimation by using the frequency domain channel response on the same pilot subcarrier of two OFDM symbols before and after, directly multiplies two frequency domain channel responses by conjugate, and then according to the conjugate The phase of the multiplied result determines the frequency offset.
  • this method limits the pilots of two OFDM symbols to be at the same subcarrier position, otherwise the frequency offset estimation result will be seriously affected by multipath or time offset.
  • one subframe of a regular cyclic prefix (Normal CP) frame structure includes 14 OFDM symbols, symbols 0, and pilots of symbol 7, symbol 4, and symbol 11
  • the subcarriers have the same position, and the frequency offset can be estimated based on the conventional RS method, but the estimation range is small, only -/+1KHz; if the frequency offset estimation can be based on the symbol 4 and the symbol 7, the estimation range can reach -/+2.3KHz.
  • their pilot subcarrier positions are staggered from each other, and the conventional RS method is not available in this case.
  • a method for carrier frequency offset estimation including:
  • a carrier frequency offset is determined based on the obtained peak phase relationship in the first time domain channel response and the second time domain channel response.
  • the user terminal or the neighboring base station performs zero-interpolation on the frequency domain channel responses of all pilot subcarriers of the first OFDM symbol and all pilot subcarriers of the second OFDM symbol in the received downlink baseband received signal respectively.
  • a carrier frequency offset is determined based on the obtained peak phase relationship in the first time domain channel response and the second time domain channel response.
  • the step of performing zero-interpolation processing on the frequency domain channel responses of all pilot subcarriers of the first OFDM symbol and all pilot subcarriers of the second OFDM symbol in the received downlink baseband received signal respectively includes: :
  • All frequency domain pilot channel responses of the first OFDM symbol are respectively placed on pilot subcarrier positions preset by the first OFDM symbol, and all non-pilot subcarriers are set to zero;
  • the step of determining a carrier frequency offset according to the peak phase relationship in the obtained first time domain channel response and the second time domain channel response comprises:
  • a carrier frequency offset corresponding to the peak phase difference is determined according to a time interval preset by the first OFDM symbol and the second OFDM symbol.
  • the step of determining a peak phase difference between the first time domain channel response and the second time domain channel response according to the first time domain channel response and the second time domain channel response comprises:
  • selecting the peak position in the following manner comprises:
  • the step of determining a carrier frequency offset according to the peak phase relationship in the obtained first time domain channel response and the second time domain channel response further includes:
  • first OFDM symbol and the second OFDM symbol have an extra phase difference, determining the additional phase difference according to the pilot position offset and the time domain channel delay preset by the first OFDM symbol and the second OFDM symbol;
  • a carrier frequency offset is determined based on the additional phase difference and a peak phase relationship in the first time domain channel response and the second time domain channel response.
  • an apparatus for estimating a carrier frequency offset includes:
  • a zero insertion module configured to perform a zero-interpolation process on a frequency domain channel response of all pilot subcarriers of the first OFDM symbol and all pilot subcarriers of the second OFDM symbol in the received downlink baseband received signal, to obtain a first a zero-frequency domain channel response and a second zero-frequency frequency domain channel response;
  • the transforming module is configured to perform inverse Fourier transform on the first zero-frequency frequency domain channel response and the second zero-cut frequency domain channel response, respectively, to obtain a first time domain channel response and a second time domain channel response;
  • a determining module configured to determine a carrier frequency offset according to the obtained peak phase relationship in the first time domain channel response and the second time domain channel response.
  • the zero insertion module further comprises:
  • a first submodule configured to place all frequency domain pilot channel responses of the first OFDM symbol on pilot subcarrier positions preset by the first OFDM symbol, and to zero all non-pilot subcarriers;
  • the second submodule is configured to place all frequency domain pilot channel responses of the second OFDM symbol on pilot subcarrier positions preset by the second OFDM symbol, and to zero all non-pilot subcarriers.
  • the determining module further comprises:
  • a difference submodule configured to determine a peak phase difference between the first time domain channel response and the second time domain channel response according to the first time domain channel response and the second time domain channel response;
  • a frequency offset submodule configured to determine a carrier frequency offset corresponding to the peak phase difference according to a time interval preset by the first OFDM symbol and the second OFDM symbol.
  • the present invention has the beneficial effects that the frequency domain channel estimation of the pilot subcarrier can be transformed into the time domain, and the peak of the time domain channel response is used to converge the signal energy, thereby effectively suppressing noise and increasing the frequency. Partial estimation performance, frequency offset estimation is more accurate. At the same time, the problem that the frequency offset estimation is limited to the same subcarrier position is avoided.
  • FIG. 1 is a schematic diagram of a method for estimating carrier frequency offset according to an embodiment of the present invention
  • FIG. 2 is a structural diagram of a device for estimating a carrier frequency offset according to an embodiment of the present invention
  • 3 is a LTE downlink reference signal RS mapping diagram of carrier frequency offset estimation according to an embodiment of the present invention
  • FIG. 4 is an additional phase difference diagram of an LTE 4, 7 symbol time domain channel response of a carrier frequency offset estimation according to an embodiment of the present invention
  • FIG. 5 is an overall flowchart of carrier frequency offset estimation according to an embodiment of the present invention.
  • FIG. 1 is a schematic diagram of a method for estimating a carrier frequency offset according to an embodiment of the present invention. As shown in FIG. 1 , the specific steps are as follows:
  • Step S1 performing zero-interpolation processing on the frequency domain channel responses of all pilot subcarriers of the first OFDM symbol and all pilot subcarriers of the second OFDM symbol in the received downlink baseband received signal, to obtain a first zero insertion Frequency domain channel response and second zero-frequency frequency domain channel response.
  • step S1 the user terminal or the neighboring base station separately inserts frequency domain channel responses of all pilot subcarriers of the first OFDM symbol and all pilot subcarriers of the second OFDM symbol in the received downlink baseband received signal.
  • Zero processing obtaining a first zero-interpolation frequency domain channel response and a second zero-interpolation frequency domain channel response;
  • a carrier frequency offset is determined based on the obtained peak phase relationship in the first time domain channel response and the second time domain channel response.
  • all frequency domain pilot channel responses of the first OFDM symbol are respectively placed on pilot subcarrier positions preset by the first OFDM symbol, and all non-pilot subcarriers are set to zero;
  • Step S2 performing inverse Fourier transform on the first zero-interpolation frequency domain channel response and the second zero-interpolation frequency domain channel response, respectively, to obtain a first time domain channel response and a second time domain channel response.
  • Step S3 Determine a carrier frequency offset according to the obtained peak phase relationship in the first time domain channel response and the second time domain channel response.
  • step S3 determining a peak phase difference between the first time domain channel response and the second time domain channel response according to the first time domain channel response and the second time domain channel response;
  • a carrier frequency offset corresponding to the peak phase difference is determined according to a time interval preset by the first OFDM symbol and the second OFDM symbol.
  • the step of determining a peak phase difference between the first time domain channel response and the second time domain channel response according to the first time domain channel response and the second time domain channel response comprises:
  • step of selecting the peak position includes:
  • the step of determining a carrier frequency offset according to the peak phase relationship in the obtained first time domain channel response and the second time domain channel response further includes:
  • first OFDM symbol and the second OFDM symbol have an extra phase difference, determining the additional phase difference according to the pilot position offset and the time domain channel delay preset by the first OFDM symbol and the second OFDM symbol;
  • a carrier frequency offset is determined based on the additional phase difference and a peak phase relationship in the first time domain channel response and the second time domain channel response.
  • the method includes: a zero insertion module, a transformation module, and a determination module.
  • the zero insertion module is configured to perform a zero insertion process on a frequency domain channel response of all pilot subcarriers of the first OFDM symbol and all pilot subcarriers of the second OFDM symbol in the received downlink baseband received signal, respectively The first zero-interpolation frequency domain channel response and the second zero-crossing frequency domain channel response.
  • the first submodule of the zero insertion module is configured to place all frequency domain pilot channel responses of the first OFDM symbol on the pilot subcarrier positions preset by the first OFDM symbol, and all non-pilots The subcarrier is set to zero.
  • the second submodule of the zero insertion module is configured to place all frequency domain pilot channel responses of the second OFDM symbol on pilot subcarrier positions preset by the first OFDM symbol, and to all non-pilot subcarriers Zero.
  • the transform module is configured to perform inverse Fourier transform on the first zero-frequency frequency domain channel response and the second zero-cut frequency domain channel response, respectively, to obtain a first time domain channel response and a second time domain channel response.
  • the determining module is configured to determine a carrier frequency offset according to the obtained peak phase relationship in the first time domain channel response and the second time domain channel response.
  • the difference submodule of the determining module is configured to determine the first time domain channel response and the second time domain channel response according to the first time domain channel response and the second time domain channel response. Peak phase difference between.
  • the frequency offset submodule of the determining module is configured to determine a carrier frequency offset corresponding to the peak phase difference according to a time interval preset by the first OFDM symbol and the second OFDM symbol.
  • FIG. 3 is a schematic diagram of an LTE downlink reference signal RS mapping of a carrier frequency offset estimation according to an embodiment of the present invention.
  • a user terminal or a neighboring base station receives a downlink baseband received signal.
  • the frequency domain pilot channel response is placed in the original subcarrier position according to a preset resource mapping manner (ie, the mapping manner of the LTE downlink reference signal RS), and the non-pilot subcarrier is set to zero, thereby constructing a zero-frequency frequency domain channel. response.
  • a preset resource mapping manner ie, the mapping manner of the LTE downlink reference signal RS
  • Pilot1(k) and Pilot2(k) are defined as the transmitted pilot symbols of Sym1 and Sym2, respectively.
  • k belongs to the pilot subcarrier position, they are each taken The corresponding frequency domain pilot channel response value.
  • the time domain channel response is obtained by performing an Inverse Discrete Fourier Transform (IDFT) on H1(k) and H2(k):
  • IDFT Inverse Discrete Fourier Transform
  • n has a value range of [0, N-1].
  • the peak position is obtained from the time domain channel responses h1(n), h2(n). Since the subcarrier spacing is ⁇ K, there will be a peak of ⁇ K repetition in the time domain channel response h1(n), h2(n).
  • FIG. 4 is an additional phase difference diagram of the LTE 4 and 7 symbol time domain channel response according to the carrier frequency offset estimation provided by the embodiment of the present invention, as shown in FIG. 4, according to the time domain channel response h1(n), h2(n) Phase difference between peaks Frequency offset
  • the basic equation is as follows:
  • FIG. 5 is an overall flowchart of a carrier frequency offset estimation according to an embodiment of the present invention. As shown in FIG. 5, this embodiment is only a preferred embodiment of the present invention, and is not intended to limit the present invention. It will be apparent to those skilled in the art that various modifications and changes can be made in the present invention. Any modifications, equivalent substitutions, improvements, etc. made within the spirit and scope of the present invention are intended to be included within the scope of the present invention.
  • the LTE bandwidth is 10M
  • the conventional CP is taken as an example
  • the symbols 4 and 7 correspond to Sym1 and Sym2 (15.36MHz sampling rate).
  • the specific implementation method is as follows:
  • N 1024
  • the frequency domain pilot channel estimates H1(k) and H2(k) of symbols 4, 7 are determined. It is assumed that the time intervals of the two baseband OFDM symbols 4, 7 are ⁇ t, each symbol has N subcarrier positions, the pilot position set of symbol 4 is P1, and the pilot position of symbol 7 is offset from the pilot position of symbol 4. Move v (take a negative value if offset in a small direction), and set the subcarrier spacing between pilots to ⁇ K.
  • the symbols 4 and 7 are DFT-transformed, and the fast Fourier transform (FFT) can also be used. Among them, FFT and DFT have the same effect, but have higher efficiency.
  • FFT fast Fourier transform
  • Pilot1(k) and Pilot2(k) are defined as the transmitted pilot symbols of symbols 4 and 7, respectively, and when k belongs to the pilot subcarrier position, they are each Take the corresponding frequency domain pilot channel response value.
  • the time domain channel response is obtained by IDFT transform for the frequency domain channel responses of symbols 4 and 7, and can also be used as an inverse fast Fourier transform (IFFT).
  • IFFT inverse fast Fourier transform
  • IFFT and IDFT have the same effect, but only have higher efficiency.
  • the IDFT transform is performed on H1(k) and H2(k) to obtain the time domain channel response:
  • n has a value range of [0, N-1].
  • the search for the peak position can be determined only based on the time domain channel response h1(n) or h2(n), or both can be searched and then the preferred peak position can be taken.
  • the specific method is as follows:
  • Cplength represents the CP length of the current symbol. If six peaks are found in each of the symbols 4 and 7, the magnitude of the maximum peak is compared, and the time domain channel response of the six peak positions of the symbol having the smallest maximum peak is acquired in accordance with the six peak positions of the symbol having the largest peak value.
  • the time domain channel response of symbols 4, 7 is determined as follows:
  • the extra phase difference at the peak is That is, the extra phase difference at the 1st, 3rd, and 5th peaks is 0, and the extra phase difference at the 2nd, 4th, and 6th peaks is ⁇ . Therefore, the actually obtained phase difference caused by the frequency offset needs to eliminate the extra phase difference in the peak phase difference between the time domain channel responses to obtain the phase difference finally used for the frequency offset determination.
  • the time between the points 4 and 7 obtained by dividing the number of points by the sampling rate is determined by determining the frequency offset as follows:
  • the present invention has the following technical effects: by transforming the frequency domain channel estimation of the pilot subcarrier into the time domain, the peak of the time domain channel response is concentrated to the signal energy, thereby effectively suppressing noise and improving the frequency offset estimation. performance.
  • the frequency domain channel response is placed at the atomic carrier position before the IFFT transform, the frequency offset estimation is more accurate, so that the problem that the pilot is not affected by the time shift is not present at the same carrier position.
  • the frequency domain channel estimation of the pilot subcarrier by transforming the frequency domain channel estimation of the pilot subcarrier into the time domain, the peak of the time domain channel response is used to converge the signal energy, thereby effectively suppressing noise and improving frequency offset estimation performance.
  • the frequency offset estimation is more accurate.
  • the problem that the frequency offset estimation is limited to the same subcarrier position is avoided.

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Abstract

La présente invention se rapporte au domaine technique des communications. La présente invention concerne un procédé et un dispositif pour estimer un décalage de fréquence de porteuses. Le procédé consiste : à réaliser respectivement un traitement d'insertion de zéro sur des réponses de canal de domaine fréquentiel de toutes les sous-porteuses pilotes d'un premier symbole de multiplexage par répartition orthogonale de la fréquence (OFDM) et de toutes les sous-porteuses pilotes d'un second symbole OFDM dans des signaux reçus de bande de base de liaison descendante reçue, pour obtenir une première réponse de canal de domaine fréquentiel d'insertion de zéro et une seconde réponse de canal de domaine fréquentiel d'insertion de zéro ; à réaliser respectivement une transformation de Fourier inverse sur la première réponse de canal de domaine fréquentiel d'insertion de zéro et la seconde réponse de canal de domaine fréquentiel d'insertion de zéro pour obtenir une première réponse de canal de domaine temporel et une seconde réponse de canal de domaine temporel ; et à déterminer un décalage de fréquence des porteuses selon la relation de phase de pic dans la première réponse de canal de domaine temporel obtenue et la seconde réponse de canal de domaine temporel obtenue. Au moyen de la présente invention, l'estimation de canal de domaine fréquentiel des sous-porteuses pilotes est transformée dans le domaine temporel, ainsi, l'énergie de signal est rassemblée au niveau des pics des réponses de canal de domaine temporel, et les performances d'estimation de décalage de fréquence sont améliorées. Pendant ce temps, le problème selon lequel l'estimation de décalage de fréquence est limitée aux mêmes emplacements de sous-porteuse est évité.
PCT/CN2014/088426 2014-06-27 2014-10-11 Procédé et dispositif pour estimer un décalage de fréquence de porteuses WO2015196629A1 (fr)

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Cited By (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN111464471A (zh) * 2020-04-02 2020-07-28 宁波艾欧迪互联科技有限公司 一种nr pusch的频偏计算方法
WO2020178459A1 (fr) * 2019-03-07 2020-09-10 Technische Universiteit Delft Détermination de distance fondée sur la phase destinée à des réseaux sans fil
US11108596B2 (en) 2016-10-27 2021-08-31 Fraunhofer-Gesellschaft Zur Foerderung Der Angewandten Forschung E.V. Channel estimation of frequency sub bands
CN114421999A (zh) * 2021-12-31 2022-04-29 北京四季豆信息技术有限公司 基于hplc双模无线系统的信道估计方法、装置和电子设备
CN114666190A (zh) * 2022-03-21 2022-06-24 东南大学 一种基于改进时域插值的信道估计方法

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Publication number Priority date Publication date Assignee Title
CN110881012B (zh) * 2019-11-18 2022-05-31 展讯通信（上海）有限公司 一种ofdm调制信号的时间估计方法及装置
CN110855595B (zh) * 2019-11-29 2022-04-01 紫光展讯通信(惠州)有限公司 时偏估计方法、装置、接收机及存储介质

Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN1984107A (zh) * 2005-12-12 2007-06-20 中国科学院上海微系统与信息技术研究所 多载波系统的前导序列及其应用方法
CN101035103A (zh) * 2006-03-09 2007-09-12 华为技术有限公司 一种正交频分复用接入系统的前导码生成方法及装置
CN101420404A (zh) * 2007-10-26 2009-04-29 华为技术有限公司 峰值对消方法、峰值对消装置与基准消峰信号生成装置

Family Cites Families (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN102790737B (zh) * 2011-05-17 2017-11-28 中兴通讯股份有限公司 一种系统的同步方法及装置

Patent Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN1984107A (zh) * 2005-12-12 2007-06-20 中国科学院上海微系统与信息技术研究所 多载波系统的前导序列及其应用方法
CN101035103A (zh) * 2006-03-09 2007-09-12 华为技术有限公司 一种正交频分复用接入系统的前导码生成方法及装置
CN101420404A (zh) * 2007-10-26 2009-04-29 华为技术有限公司 峰值对消方法、峰值对消装置与基准消峰信号生成装置

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* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US11108596B2 (en) 2016-10-27 2021-08-31 Fraunhofer-Gesellschaft Zur Foerderung Der Angewandten Forschung E.V. Channel estimation of frequency sub bands
WO2020178459A1 (fr) * 2019-03-07 2020-09-10 Technische Universiteit Delft Détermination de distance fondée sur la phase destinée à des réseaux sans fil
US11889459B2 (en) 2019-03-07 2024-01-30 Koninklijke Kpn N.V. Phase-based distance determination for wireless networks
CN111464471A (zh) * 2020-04-02 2020-07-28 宁波艾欧迪互联科技有限公司 一种nr pusch的频偏计算方法
CN111464471B (zh) * 2020-04-02 2023-04-11 宁波大学 一种nr pusch的频偏计算方法
CN114421999A (zh) * 2021-12-31 2022-04-29 北京四季豆信息技术有限公司 基于hplc双模无线系统的信道估计方法、装置和电子设备
CN114666190A (zh) * 2022-03-21 2022-06-24 东南大学 一种基于改进时域插值的信道估计方法
CN114666190B (zh) * 2022-03-21 2024-01-26 东南大学 一种基于改进时域插值的信道估计方法

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