WO2015184949A1 - 在干扰条件下的lte上行系统的信号检测方法和装置 - Google Patents

在干扰条件下的lte上行系统的信号检测方法和装置 Download PDF

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WO2015184949A1
WO2015184949A1 PCT/CN2015/079103 CN2015079103W WO2015184949A1 WO 2015184949 A1 WO2015184949 A1 WO 2015184949A1 CN 2015079103 W CN2015079103 W CN 2015079103W WO 2015184949 A1 WO2015184949 A1 WO 2015184949A1
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matrix
interference
signal
subcarrier
module
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PCT/CN2015/079103
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French (fr)
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秦洪峰
熊高才
林灯生
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中兴通讯股份有限公司
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Priority to US15/519,311 priority patent/US10129063B2/en
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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2647—Arrangements specific to the receiver only
    • H04L27/2649—Demodulators
    • H04L27/26524—Fast Fourier transform [FFT] or discrete Fourier transform [DFT] demodulators in combination with other circuits for demodulation
    • H04L27/26526—Fast Fourier transform [FFT] or discrete Fourier transform [DFT] demodulators in combination with other circuits for demodulation with inverse FFT [IFFT] or inverse DFT [IDFT] demodulators, e.g. standard single-carrier frequency-division multiple access [SC-FDMA] receiver or DFT spread orthogonal frequency division multiplexing [DFT-SOFDM]
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/0413—MIMO systems
    • H04B7/0456—Selection of precoding matrices or codebooks, e.g. using matrices antenna weighting
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/0202—Channel estimation
    • H04L25/022—Channel estimation of frequency response
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/0202—Channel estimation
    • H04L25/0224—Channel estimation using sounding signals
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/0202—Channel estimation
    • H04L25/024—Channel estimation channel estimation algorithms
    • H04L25/0242—Channel estimation channel estimation algorithms using matrix methods
    • H04L25/0248—Eigen-space methods
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/03—Shaping networks in transmitter or receiver, e.g. adaptive shaping networks
    • H04L25/03993—Noise whitening
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2602—Signal structure
    • H04L27/2605—Symbol extensions, e.g. Zero Tail, Unique Word [UW]
    • H04L27/2607—Cyclic extensions
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04W—WIRELESS COMMUNICATION NETWORKS
    • H04W72/00—Local resource management
    • H04W72/20—Control channels or signalling for resource management
    • H04W72/21—Control channels or signalling for resource management in the uplink direction of a wireless link, i.e. towards the network
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04W—WIRELESS COMMUNICATION NETWORKS
    • H04W84/00—Network topologies
    • H04W84/02—Hierarchically pre-organised networks, e.g. paging networks, cellular networks, WLAN [Wireless Local Area Network] or WLL [Wireless Local Loop]
    • H04W84/04—Large scale networks; Deep hierarchical networks
    • H04W84/042—Public Land Mobile systems, e.g. cellular systems

Definitions

  • This paper relates to the field of communications, and in particular to a signal detection method and apparatus for an LTE uplink system under interference conditions.
  • the LTE (Long Term Evolution) system has adopted SC-FDMA (Single-Carrier Frequency-Division Multiple Access) technology as an uplink multiple access technology. Since the LTE system adopts global frequency reuse, the neighboring cell interference phenomenon is more serious; in addition, in some frequency bands, the LTE uplink may suffer from interference caused by multiple different systems, such as:
  • Microwave oven (50% of the busyness in the 2.4 GHz band will generate pulse interference).
  • the presence of interference will seriously affect system performance and reduce cell throughput.
  • the traditional MMSE (Minimum Mean Square Error) equalization detection algorithm can only suppress inter-symbol interference caused by frequency selective fading of the channel. In the case of different system interference, the MMSE equalization detection algorithm is completely Invalid. Therefore, it is highly desirable to propose a detection algorithm with anti-differential system interference.
  • the embodiments of the present invention provide a signal detection method and apparatus for an LTE uplink system under interference conditions, to solve how to avoid the traditional LTE uplink based on Minimum Mean Square Error (MMSE) equalization in the frequency domain. Detection method lost under different system interference conditions The problem of effectiveness.
  • MMSE Minimum Mean Square Error
  • the embodiment of the present invention provides a signal detection method for an LTE uplink system under interference conditions, which is applicable to an antenna configuration of one transmit antenna and one M receive antenna, and the method includes:
  • Frequency domain equalization is performed on the received signal after interference preprocessing.
  • the step of extracting the LTE uplink reference demodulation signal DMRS inserted in each antenna receiving signal, and then calculating the channel gain h l,k of each receiving antenna includes:
  • F N is an N ⁇ N discrete Fourier transform DFT matrix, where N is the number of subcarriers, g is a time domain rectangular window, Q is a window length, and Q is less than a cyclic prefix length;
  • Q 1 is the length of the rectangular window, and the value of Q 1 is the number of non-zero elements of the diagonal matrix ⁇ .
  • the combined signal matrix Y k and the gain matrix H k are respectively:
  • Y k [y 1,k ,...,y M,k ] T
  • H k [h 1,k ,...,h M,k ] T .
  • the step of calculating the interference noise covariance matrix R k on each subcarrier includes:
  • K represents the number of accumulated subcarriers. Indicates rounding down.
  • the step of performing interference preprocessing on the received signals on each of the combined subcarriers includes:
  • D is calculated as follows:
  • ⁇ is a diagonal matrix
  • U is a unitary matrix
  • 1/2 1/2 indicates that the diagonal elements are squared
  • s k represents the transmitted signal of the kth subcarrier
  • u k represents the interference noise vector of the kth subcarrier
  • the basis The steps of performing frequency domain equalization on the received signal after interference preprocessing include:
  • the embodiment of the present invention further provides a signal detecting apparatus for an LTE uplink system under interference conditions, which is applicable to an antenna configuration of one transmitting antenna and M receiving antennas, where the apparatus includes:
  • the transform module is configured to receive the baseband signal of the M receiving antennas, and after fast Fourier transform, demap the frequency domain baseband signals y l, k , 1 ⁇ l ⁇ M, 1 ⁇ k ⁇ N s , wherein l represents l The root receiving antenna, where k is the subcarrier number, and N s is the number of subcarriers actually occupied by the user equipment.
  • a channel gain calculation module configured to extract an LTE uplink reference demodulation signal DMRS inserted in each antenna received signal, and then calculate a channel gain h l,k of each of the receiving antennas;
  • a combination module configured to combine a baseband signal of the M receiving antennas and a channel gain to obtain a signal matrix Yk , and a gain matrix Hk ;
  • Interference noise covariance matrix calculating module configured for interfering noise covariance matrix R k is calculated on each subcarrier
  • the interference pre-processing module is configured to perform interference pre-processing on the received signal on each of the combined sub-carriers to obtain a received signal after interference pre-processing And channel gain
  • D R k -1/2;
  • Frequency domain equalization module set to Frequency domain equalization is performed on the received signal after interference preprocessing.
  • the channel gain calculation module includes:
  • a pilot vector extraction submodule configured to extract an uplink reference demodulation signal inserted in each antenna received signal Where l represents the lth receive antenna;
  • Least squares estimation submodule set to pair Do the least squares estimation LS to get the LS estimated output vector X is an uplink reference demodulation signal
  • the eigenvalue weighting sub-module is set to calculate the frequency domain correlation matrix of the time domain rectangular window, and obtains:
  • F N is an N ⁇ N discrete Fourier transform DFT matrix, where N is the number of subcarriers, g is a time domain rectangular window, Q is a window length, and Q is less than a cyclic prefix length;
  • Q 1 is the length of the rectangular window, and the value of Q 1 is the number of non-zero elements of the diagonal matrix ⁇ .
  • the signal matrix Y k obtained by combining the combination modules and the gain matrix H k are respectively:
  • Y k [y 1,k ,...,y M,k ] T
  • H k [h 1,k ,...,h M,k ] T .
  • the interference noise covariance matrix calculation module includes:
  • An uplink reference demodulation signal extraction submodule configured to extract an uplink reference demodulation signal of each subcarrier in the combined signal
  • the interference noise covariance matrix calculation submodule is set to calculate the interference noise covariance matrix R k of each subcarrier:
  • K represents the number of accumulated subcarriers. Indicates rounding down.
  • the interference preprocessing module includes:
  • the pre-processing matrix calculation sub-module is set to perform eigenvalue decomposition on the interference noise covariance matrix of each subcarrier:
  • ⁇ is a diagonal matrix
  • U is a unitary matrix
  • 1/2 1/2 means that the diagonal elements are squared;
  • the whitening processing sub-module is set to multiply the received signal of each subcarrier by the D to obtain:
  • s k represents the transmitted signal of the kth subcarrier
  • u k represents the interference noise vector of the kth subcarrier
  • the frequency domain equalization module is configured according to Frequency domain equalization of the received signal after interference preprocessing means:
  • the frequency domain equalization module calculates the weight vector w of the frequency domain equalization, and combines the received signals after interference preprocessing among them,
  • the embodiment of the invention further provides a computer storage medium, wherein the computer storage medium stores computer executable instructions, and the computer executable instructions are used to execute the above method.
  • the beneficial effects of the embodiment of the present invention are: performing interference pre-processing such as whitening of the received user signal including interference, obeying the white noise distribution after the whitening interference signal, and using the relevant LTE uplink receiving signal after the interference pre-processing signal Machine processing eliminates the effects of interference from different systems.
  • FIG. 1 is a flowchart of a signal detection method of an LTE uplink system under interference conditions in an embodiment of the present invention
  • FIG. 2 is a structural diagram of a typical LTE uplink system transmitter in an embodiment of the present invention.
  • FIG. 3 is a structural diagram of a baseband receiver of a typical LTE uplink system in an embodiment of the present invention
  • FIG. 4 is a schematic structural diagram of a signal detecting apparatus of an LTE uplink system under interference conditions according to an embodiment of the present invention
  • FIG. 5 is a schematic structural diagram of a channel gain calculation module of the foregoing apparatus according to an embodiment of the present invention.
  • FIG. 6 is a schematic structural diagram of an interference noise covariance matrix calculation module of the foregoing apparatus according to an embodiment of the present invention.
  • FIG. 7 is a schematic structural diagram of an interference preprocessing module of the foregoing apparatus according to an embodiment of the present invention.
  • FIG. 8 is a performance comparison diagram of an embodiment of the present invention and a conventional detection method in a case where the dry signal ratio is fixed and the signal to noise ratio is changed.
  • Embodiment 1 A signal detection method for an LTE uplink system under interference conditions is applicable to an antenna configuration of one transmit antenna and M receive antennas, where the method includes:
  • This embodiment proposes a new signal detection technique in an LTE uplink system under interference conditions, and the non-white interference is equivalent to white noise by some transformation, that is, the so-called whitening, which simplifies the analysis process and Make the effects of interference more intuitive. Therefore, it is necessary to pre-process the interference in combination with the receiver of the related art.
  • Solved the traditional LTE uplink based on frequency domain MMSE equalization The problem of detection methods failing under interference conditions. The influence of noise and interference is fully eliminated during the detection process, and the accuracy of detection is improved.
  • the step S2 includes:
  • F N is an N ⁇ N DFT (Discrete Fourier Transform) matrix
  • N is the number of subcarriers
  • g is a time domain rectangular window
  • Q is a window length.
  • the value of Q is smaller than the cyclic prefix length.
  • N s is the number of subcarriers actually occupied by the user equipment
  • the least squares estimation value is The feature field is windowed to obtain:
  • Q 1 is the length of the rectangular window, and the value of Q 1 is the number of non-zero elements of the diagonal matrix ⁇ .
  • the step S4 includes:
  • K represents the number of accumulated subcarriers. Indicates rounding down.
  • the step S5 includes:
  • ⁇ is a diagonal matrix
  • U is a unitary matrix
  • 1/2 1/2 indicates the square of its diagonal elements.
  • s k represents the transmitted signal of the kth subcarrier
  • u k represents the interference noise vector of the kth subcarrier
  • the noise obeys the white noise distribution, and the power of the noise
  • step S6 includes:
  • Embodiment 2 A signal detecting apparatus for an LTE uplink system under interference conditions, which is applicable to an antenna configuration of one transmitting antenna and M receiving antennas, where the apparatus includes:
  • the transform module is configured to receive the baseband signal of the M receiving antennas, and after fast Fourier transform, demap the frequency domain baseband signals y l, k , 1 ⁇ l ⁇ M, 1 ⁇ k ⁇ N s , wherein l represents l The root receiving antenna, where k is the subcarrier number, and N s is the number of subcarriers actually occupied by the user equipment.
  • a channel gain calculation module configured to extract an LTE uplink reference demodulation signal DMRS inserted in each antenna received signal, and then calculate a channel gain h l,k of each of the receiving antennas;
  • a combination module configured to combine a baseband signal of the M receiving antennas and a channel gain to obtain a signal matrix Yk , and a gain matrix Hk ;
  • Interference noise covariance matrix calculating module configured for interfering noise covariance matrix R k is calculated on each subcarrier
  • Frequency domain equalization module set to Frequency domain equalization is performed on the received signal after interference preprocessing.
  • the channel gain calculation module includes:
  • a pilot vector extraction submodule configured to extract an uplink reference demodulation signal inserted in each antenna received signal Where l represents the lth receive antenna;
  • Least squares estimation submodule set to pair Do the least squares estimation LS to get the LS estimated output vector X is an uplink reference demodulation signal
  • the eigenvalue weighting sub-module is set to calculate the frequency domain correlation matrix of the time domain rectangular window, and obtains:
  • F N is a N ⁇ N DFT matrix
  • N is a number of subcarriers
  • g is a time domain rectangular window
  • Q is a window length
  • Q is less than a cyclic prefix length
  • Q 1 is the length of the rectangular window, and the value of Q 1 is the number of non-zero elements of the diagonal matrix ⁇ .
  • the signal matrix Y k and the gain matrix H k obtained by combining the combination modules are respectively:
  • Y k [y 1,k ,...,y M,k ] T
  • H k [h 1,k ,...,h M,k ] T .
  • the interference noise covariance matrix calculation module includes:
  • An uplink reference demodulation signal extraction submodule configured to extract an uplink reference demodulation signal of each subcarrier in the combined signal
  • the interference noise covariance matrix calculation submodule is set to calculate the interference noise covariance matrix R k of each subcarrier:
  • K represents the number of accumulated subcarriers. Indicates rounding down.
  • the interference preprocessing module includes:
  • the pre-processing matrix calculation sub-module is set to perform eigenvalue decomposition on the interference noise covariance matrix of each subcarrier:
  • ⁇ is a diagonal matrix
  • U is a unitary matrix
  • 1/2 1/2 means that the diagonal elements are squared;
  • the whitening processing sub-module is set to multiply the received signal of each subcarrier by the D to obtain:
  • u k represents the interference noise vector of the kth subcarrier
  • the frequency domain equalization module is configured according to Frequency domain equalization of the received signals after interference preprocessing includes:
  • the frequency domain equalization module calculates the weight vector w of the frequency domain equalization, and combines the received signals after interference preprocessing among them,
  • a typical LTE uplink system transmitter includes: code block segmentation and CRC (loop) Redundancy check code) check module, channel coding module, interleaving and rate matching module, QAM (Quadrature Amplitude Modulation) modulation module, DFT module, subcarrier mapping module, plus cyclic prefix module.
  • code block segmentation and CRC loop
  • CRC loop
  • QAM Quadrature Amplitude Modulation
  • a typical LTE uplink system baseband receiver includes: an FFT module, a channel gain calculation module, an interference noise covariance matrix calculation module, a frequency domain equalization module, an IFFT (Inverse Fast Fourier Transform) module, and a time domain.
  • Equalization module and sink module wherein:
  • the FFT module is configured to perform FFT transformation on a baseband received signal vector
  • the IFFT module is configured to transform the frequency domain equalized data into a time domain
  • the time domain equalization module is configured to perform time domain equalization on the time domain signal.
  • an interference pre-processing sub-module is added in front of the frequency domain equalization module.
  • a signal detecting apparatus in an LTE uplink system under interference conditions of the present embodiment includes a transform module (including an FFT, a demapping submodule), a channel gain calculation module, a combination module, and an interference noise association.
  • a transform module including an FFT, a demapping submodule
  • a channel gain calculation module including an FFT, a demapping submodule
  • a combination module including an interference noise association.
  • Variance matrix calculation module, interference preprocessing module and frequency domain equalization module including an FFT, a demapping submodule
  • the channel gain calculation module includes a pilot vector extraction submodule, a least squares estimation submodule, and a feature value weighting submodule; wherein:
  • a pilot vector extraction sub-module configured to extract an uplink reference demodulation signal for each of the receiving antennas
  • a least squares estimation sub-module configured to perform least square channel estimation based on the extracted uplink reference demodulation signal to obtain a least square channel estimation value
  • the eigenvalue weighting sub-module is configured to perform windowing processing on the least square channel estimation value to obtain a channel estimation value for filtering out interference.
  • the interference noise covariance matrix calculation module includes an uplink reference demodulation signal extraction submodule and an interference noise covariance matrix calculation submodule:
  • An uplink reference demodulation signal extraction submodule configured to extract an uplink reference demodulation signal of each subcarrier in the combined signal
  • Interference noise covariance matrix calculation sub-module set to calculate the interference noise covariance matrix for each subcarrier.
  • the interference pre-processing module includes a pre-processing matrix calculation sub-module and a whitening processing sub-module:
  • Whitening processing sub-module set to calculate the signal of each subcarrier after interference preprocessing And channel gain
  • FIG. 8 is a comparison diagram of performance comparison between an embodiment of the present invention and a traditional detection method based on MMSE equalization in an idle ratio (ISR), a signal-to-noise ratio (SNR), and an extended pedestrian channel (EPA) model.
  • the conventional detection method fails, and the algorithm of the embodiment of the present invention can work normally.
  • BER is the bit error rate.
  • all or part of the steps of the above embodiments may also be implemented by using an integrated circuit. These steps may be separately fabricated into individual integrated circuit modules, or multiple modules or steps may be fabricated into a single integrated circuit module. achieve.
  • the devices/function modules/functional units in the above embodiments may be implemented by a general-purpose computing device, which may be centralized on a single computing device or distributed over a network of multiple computing devices.
  • each device/function module/functional unit in the above embodiment When each device/function module/functional unit in the above embodiment is implemented in the form of a software function module and sold or used as a stand-alone product, it can be stored in a computer readable storage medium.
  • the above mentioned computer readable storage medium may be a read only memory, a magnetic disk or an optical disk or the like.
  • the foregoing technical solution solves the problem that the traditional LTE uplink based frequency domain MMSE equalization detection method fails under the condition of different system interference, and fully eliminates the influence of noise and interference in the detection process, and improves the detection precision.

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Abstract

一种在干扰条件下的LTE上行系统的信号检测方法及装置；所述方法包括：接收M根接收天线的基带信号，经过快速傅里叶变换，解映射得到频域基带信号；提取每根天线接收信号中插入的DMRS，然后计算每个接收天线的信道增益hl,k；组合M根接收天线的基带信号和信道增益得到信号矩阵Yk，及增益矩阵Hk；计算每个子载波上的干扰噪声协方差矩阵Rk；对组合后的每一子载波上的接收信号进行干扰预处理，得到干扰预处理后的接收信号（式）1和信道增益（式）2；其中D=Rk -1/2；根据（式）3 对干扰预处理后的接收信号做频域均衡。上述技术方案可防止传统的检测方法在干扰条件下失效。

Description

在干扰条件下的LTE上行系统的信号检测方法和装置 技术领域
本文涉及通信领域，特别涉及一种在干扰条件下的LTE上行系统的信号检测方法和装置。
背景技术
LTE(长期演进)系统已经将SC-FDMA(Single-carrier Frequency-Division Multiple Access，单载波频分多址)技术作为上行链路的多址技术。由于LTE系统采用全局频率复用，邻小区干扰现象较为严重；此外，在某些频段下，LTE上行可能会遭受多种异系统带来的干扰，如：
(1)无绳电话(2.4或5.xGHz)；
(2)蓝牙个人区域联网设备(2.4GHz)；
(3)蓝牙无线耳机；
(4)微波炉(在2.4GHz频带中50％的忙闲度将产生脉冲干扰)。
干扰的存在将严重影响系统性能，降低小区吞吐量。传统的基于MMSE(Minimum Mean Square Error，最小均方误差)均衡的检测算法只能抑制由于信道的频率选择性衰落引起的符号间干扰，在有异系统干扰存在的情况下，MMSE均衡检测算法完全失效。因此，迫切希望能够提出一种具有抗异系统干扰的检测算法。
但是，因为这些异系统的干扰不具有平坦的功率谱特性，且不同的干扰对LTE接收机的性能影响差别很大，故分析过程比较复杂。当多种干扰和噪声同时存在时，难以评估非白干扰对系统性能的影响。
发明内容
本发明实施例提供了一种在干扰条件下的LTE上行系统的信号检测方法和装置，以解决如何避免传统的LTE上行链路基于频域最小均方误差(Minimum Mean Square Error，MMSE)均衡的检测方法在异系统干扰条件下失 效的问题。
为了解决上述问题，本发明实施例提供了一种在干扰条件下的LTE上行系统的信号检测方法，适用于1根发射天线和M根接收天线的天线配置，所述方法包括：
接收M根接收天线的基带信号，经过快速傅里叶变换，解映射得到频域基带信号yl,k,1≤l≤M,1≤k≤Ns，其中l表示第l根接收天线，k表示子载波序号，Ns表示用户设备实际占用子载波数目；
提取每根天线接收信号中插入的LTE上行参考解调信号DMRS，然后计算每根接收天线的信道增益hl,k；
组合M根接收天线的基带信号和信道增益得到信号矩阵Yk，及增益矩阵Hk；
计算每个子载波上的干扰噪声协方差矩阵Rk；
对组合后的每一子载波上的接收信号进行干扰预处理，得到干扰预处理后的接收信号
Figure PCTCN2015079103-appb-000001
和信道增益
Figure PCTCN2015079103-appb-000002
其中D＝Rk -1/2；
根据
Figure PCTCN2015079103-appb-000003
对干扰预处理后的接收信号做频域均衡。
可选地，所述提取每根天线接收信号中插入的LTE上行参考解调信号DMRS，然后计算每根接收天线的信道增益hl,k的步骤包括：
提取每根天线接收信号中插入的上行参考解调信号
Figure PCTCN2015079103-appb-000004
其中l表示第l根接收天线；
对
Figure PCTCN2015079103-appb-000005
做最小二乘估计LS，得到LS估计输出向量
Figure PCTCN2015079103-appb-000006
X为上行参考解调信号；
计算时域矩形窗的频域相关矩阵，得：
Figure PCTCN2015079103-appb-000007
其中，FN为N×N的离散傅里叶变换DFT矩阵，N为子载波数目，g为时域矩形窗，Q为窗长，Q的取值小于循环前缀长度；
计算用户设备实际占用子载波的频域相关矩阵，得：
Figure PCTCN2015079103-appb-000008
对
Figure PCTCN2015079103-appb-000009
做特征值分解，得：
Figure PCTCN2015079103-appb-000010
将最小二乘估计值在
Figure PCTCN2015079103-appb-000011
的特征域进行加窗处理，得：
Figure PCTCN2015079103-appb-000012
其中Q1为矩形窗窗长，Q1的取值为对角矩阵Λ非零元素的个数。
可选地，组合所得到的信号矩阵Yk，和增益矩阵Hk分别为：
Yk＝[y1,k,…,yM,k]T，Hk＝[h1,k,…,hM,k]T。
可选地，所述计算每个子载波上的干扰噪声协方差矩阵Rk的步骤包括：
提取组合信号中每个子载波的上行参考解调信号
Figure PCTCN2015079103-appb-000013
计算每个子载波的干扰噪声协方差矩阵Rk，Rk的计算方法如下：
Figure PCTCN2015079103-appb-000014
其中，K表示累计的子载波数目，
Figure PCTCN2015079103-appb-000015
表示向下取整。
可选地，所述对组合后的每一子载波上的接收信号进行干扰预处理的步骤包括：
计算预处理矩阵D，D计算方法如下：
对每个子载波的干扰噪声协方差矩阵做特征值分解：
Rk＝UVUH＝(UV1/2UH)·(UV1/2UH)H
其中，Λ为对角矩阵，U为酉矩阵，Λ1/2表示对其对角元素开方；
令D＝Rk -1/2＝UΛ-1/2UH；
白化处理：
用所述D乘上每个子载波的接收信号得到：
Figure PCTCN2015079103-appb-000016
其中，sk表示第k个子载波的发送信号，uk表示第k个子载波的干扰噪 声向量，则经过干扰预处理后的信道矩阵
Figure PCTCN2015079103-appb-000017
可选地，所述根据
Figure PCTCN2015079103-appb-000018
对干扰预处理后的接收信号做频域均衡的步骤包括：
计算频域均衡的权值向量w，并合并干扰预处理后的接收信号
Figure PCTCN2015079103-appb-000019
w的计算方法如下：
Figure PCTCN2015079103-appb-000020
本发明实施例还提供了一种在干扰条件下的LTE上行系统的信号检测装置，适用于1根发射天线和M根接收天线的天线配置，所述装置包括：
变换模块，设置为接收M根接收天线的基带信号，经过快速傅里叶变换，解映射得到频域基带信号yl,k,1≤l≤M,1≤k≤Ns，其中l表示第l根接收天线，k表示子载波序号，Ns表示用户设备实际占用子载波数目；
信道增益计算模块，设置为提取每根天线接收信号中插入的LTE上行参考解调信号DMRS，然后计算每根接收天线的信道增益hl,k；
组合模块，设置为组合M根接收天线的基带信号和信道增益得到信号矩阵Yk，及增益矩阵Hk；
干扰噪声协方差矩阵计算模块，设置为计算每个子载波上的干扰噪声协方差矩阵Rk；
干扰预处理模块，设置为对组合后的每一子载波上的接收信号进行干扰预处理，得到干扰预处理后的接收信号
Figure PCTCN2015079103-appb-000021
和信道增益
Figure PCTCN2015079103-appb-000022
其中，D＝Rk -1/2；
频域均衡模块，设置为根据
Figure PCTCN2015079103-appb-000023
对干扰预处理后的接收信号做频域均衡。
可选地，所述信道增益计算模块包括：
导引向量提取子模块，设置为提取每根天线接收信号中插入的上行参考解调信号
Figure PCTCN2015079103-appb-000024
其中l表示第l根接收天线；
最小二乘估计子模块，设置为对
Figure PCTCN2015079103-appb-000025
做最小二乘估计LS，得到LS估计输出向量
Figure PCTCN2015079103-appb-000026
X为上行参考解调信号；
特征值加权子模块，设置为计算时域矩形窗的频域相关矩阵，得：
Figure PCTCN2015079103-appb-000027
其中，FN为N×N的离散傅里叶变换DFT矩阵，N为子载波数目，g为时域矩形窗，Q为窗长，Q的取值小于循环前缀长度；
并计算用户设备实际占用子载波的频域相关矩阵，得：
Figure PCTCN2015079103-appb-000028
对得到
Figure PCTCN2015079103-appb-000029
做特征值分解，得：
Figure PCTCN2015079103-appb-000030
以及将最小二乘估计值在
Figure PCTCN2015079103-appb-000031
的特征域进行加窗处理，得：
Figure PCTCN2015079103-appb-000032
其中Q1为矩形窗窗长，Q1的取值为对角矩阵Λ非零元素的个数。
可选地，所述组合模块组合所得到的信号矩阵Yk，和增益矩阵Hk分别为：
Yk＝[y1,k,…,yM,k]T，Hk＝[h1,k,…,hM,k]T。
可选地，所述干扰噪声协方差矩阵计算模块包括：
上行参考解调信号提取子模块，设置为提取组合信号中每个子载波的上行参考解调信号
Figure PCTCN2015079103-appb-000033
干扰噪声协方差矩阵计算子模块，设置为计算每个子载波的干扰噪声协方差矩阵Rk：
Figure PCTCN2015079103-appb-000034
其中，K表示累计的子载波数目，
Figure PCTCN2015079103-appb-000035
表示向下取整。
可选地，所述干扰预处理模块包括：
预处理矩阵计算子模块，设置为对每个子载波的干扰噪声协方差矩阵做特征值分解：Rk＝UΛUH＝(UΛ1/2UH)·(UΛ1/2UH)H，令D＝Rk -1/2＝UΛ-1/2UH；其中， Λ为对角矩阵，U为酉矩阵，Λ1/2表示对其对角元素开方；
白化处理子模块，设置为用所述D乘上每个子载波的接收信号得到：
Figure PCTCN2015079103-appb-000036
其中，sk表示第k个子载波的发送信号，uk表示第k个子载波的干扰噪声向量，则经过干扰预处理后的信道矩阵
Figure PCTCN2015079103-appb-000037
可选地，所述频域均衡模块根据
Figure PCTCN2015079103-appb-000038
对干扰预处理后的接收信号做频域均衡是指：
所述频域均衡模块计算频域均衡的权值向量w，并合并干扰预处理后的接收信号
Figure PCTCN2015079103-appb-000039
其中，
Figure PCTCN2015079103-appb-000040
本发明实施例还提供了一种计算机存储介质，所述计算机存储介质中存储有计算机可执行指令，所述计算机可执行指令用于执行上述的方法。
本发明实施例的有益效果是：将接收到的包括干扰的用户信号进行白化等干扰预处理，使白化后的干扰信号服从白噪声分布，对经过干扰预处理后的信号用相关的LTE上行接收机处理，消除了异系统的干扰影响。
附图概述
图1本发明实施例中在干扰条件下的LTE上行系统的信号检测方法流程图；
图2本发明实施例中的典型LTE上行系统发射机结构图；
图3本发明实施例中的典型LTE上行系统基带接收机结构图；
图4为本发明实施例中干扰条件下LTE上行系统的信号检测装置的结构示意图；
图5为本发明实施例中上述装置的信道增益计算模块的结构示意图；
图6为本发明实施例中上述装置的干扰噪声协方差矩阵计算模块结构示意图；
图7为本发明实施例中上述装置的干扰预处理模块结构示意图；
图8为本发明实施例与传统检测方法在干信比固定，信噪比变化情况下的性能对比图。
本发明的较佳实施方式
下面将结合附图及实施例对本发明的技术方案进行更详细的说明。
需要说明的是，如果不冲突，本发明实施例以及实施例中的各个特征可以相互结合，均在本发明的保护范围之内。另外，虽然在流程图中示出了逻辑顺序，但是在某些情况下，可以以不同于此处的顺序执行所示出或描述的步骤。
实施例一、一种在干扰条件下的LTE上行系统的信号检测方法，适用于1根发射天线和M根接收天线的天线配置，所述方法包括：
S1、接收M根接收天线的基带信号，然后经过快速傅里叶变换(Fast Fourier Transform，FFT)，解映射得到频域基带信号yl,k,1≤l≤M,1≤k≤Ns，其中l表示第l根接收天线，k表示子载波序号，Ns表示用户设备实际占用子载波数目；
S2、提取每根天线接收信号中插入的LTE上行参考解调信号DMRS，计算每根接收天线的信道增益hl,k；
S3、组合M根接收天线的基带信号和信道增益得到信号矩阵Yk，及增益矩阵Hk；
S4、计算每个子载波上的干扰噪声协方差矩阵Rk；
S5、令D＝Rk -1/2，对步骤S3中组合后的每一子载波上的接收信号进行干扰预处理，得到干扰预处理后的接收信号
Figure PCTCN2015079103-appb-000041
和信道增益
Figure PCTCN2015079103-appb-000042
S6、根据
Figure PCTCN2015079103-appb-000043
对干扰预处理后的接收信号做频域均衡。
本实施例提出了一种在干扰条件下的LTE上行系统中的新的信号检测技术，将非白干扰通过某种变换等效为白噪声，即通常所说的白化，将简化其分析过程并使干扰影响效果更加直观。所以需要对干扰进行预处理来和相关技术的接收机相结合。解决了传统的LTE上行链路基于频域MMSE均衡的 检测方法在干扰条件下失效的问题。在检测过程中充分消除噪声和干扰的影响，提高了检测的精度。
本实施例的一种实施方式中，所述步骤S2包括：
S201、提取每根天线接收信号中插入的上行参考解调信号
Figure PCTCN2015079103-appb-000044
其中l表示第l根接收天线；
S202、对
Figure PCTCN2015079103-appb-000045
做最小二乘估计(Least Squares，LS)，得到LS估计输出向量
Figure PCTCN2015079103-appb-000046
X为上行参考解调信号；
S203、计算时域矩形窗的频域相关矩阵，得：
Figure PCTCN2015079103-appb-000047
其中，FN为N×N的DFT(离散傅里叶变换)矩阵，N为子载波数目，g为时域矩形窗，Q为窗长，一般Q的取值小于循环前缀长度。
S204、计算用户设备实际占用子载波的频域相关矩阵，得：
Figure PCTCN2015079103-appb-000048
其中，Ns为用户设备实际占用的子载波数目；
S205、对
Figure PCTCN2015079103-appb-000049
做特征值分解，得：
Figure PCTCN2015079103-appb-000050
S206、将最小二乘估计值在
Figure PCTCN2015079103-appb-000051
的特征域进行加窗处理，得：
Figure PCTCN2015079103-appb-000052
其中Q1为矩形窗窗长，Q1的取值为对角矩阵Λ非零元素的个数。
本实施例的一种实施方式中，所述步骤S3中得到的信号矩阵Yk，和增益矩阵Hk分别为：Yk＝[y1,k,…,yM,k]T，Hk＝[h1,k,…,hM,k]T。
本实施例的一种实施方式中，所述步骤S4包括：
S401、提取组合信号中每个子载波的上行参考解调信号
Figure PCTCN2015079103-appb-000053
S402、计算每个子载波的干扰噪声协方差矩阵Rk，Rk的计算方法如下：
Figure PCTCN2015079103-appb-000054
其中，K表示累计的子载波数目，
Figure PCTCN2015079103-appb-000055
表示向下取整。
本实施例的一种实施方式中，所述步骤S5包括：
S501、计算预处理矩阵D，D计算方法如下：
对每个子载波的干扰噪声协方差矩阵做特征值分解：
Rk＝UΛUH＝(UΛ1/2UH)·(UΛ1/2UH)H
其中，Λ为对角矩阵，U为酉矩阵，Λ1/2表示对其对角元素开方。所以，
Figure PCTCN2015079103-appb-000056
令D＝Rk -1/2＝UΛ-1/2UH。
S502、白化处理：
用D乘上每个子载波的接收信号得到：
Figure PCTCN2015079103-appb-000057
其中，sk表示第k个子载波的发送信号，uk表示第k个子载波的干扰噪声向量，则经过干扰预处理后的信道矩阵
Figure PCTCN2015079103-appb-000058
噪声的协方差矩阵
Figure PCTCN2015079103-appb-000059
为：
Figure PCTCN2015079103-appb-000060
因此，白化后噪声服从白噪声分布，且噪声的功率
Figure PCTCN2015079103-appb-000061
本实施方式中，所述步骤S6包括：
计算频域均衡的权值向量w，并合并干扰预处理后的接收信号
Figure PCTCN2015079103-appb-000062
w的计算方法如下：
Figure PCTCN2015079103-appb-000063
实施例二、一种在干扰条件下的LTE上行系统的信号检测装置，适用于1根发射天线和M根接收天线的天线配置，所述装置包括：
变换模块，设置为接收M根接收天线的基带信号，经过快速傅里叶变换， 解映射得到频域基带信号yl,k,1≤l≤M,1≤k≤Ns，其中l表示第l根接收天线，k表示子载波序号，Ns表示用户设备实际占用子载波数目；
信道增益计算模块，设置为提取每根天线接收信号中插入的LTE上行参考解调信号DMRS，然后计算每根接收天线的信道增益hl,k；
组合模块，设置为组合M根接收天线的基带信号和信道增益得到信号矩阵Yk，及增益矩阵Hk；
干扰噪声协方差矩阵计算模块，设置为计算每个子载波上的干扰噪声协方差矩阵Rk；
干扰预处理模块，设置为对组合后的每一子载波上的接收信号进行干扰预处理，得到干扰预处理后的接收信号
Figure PCTCN2015079103-appb-000064
和信道增益
Figure PCTCN2015079103-appb-000065
其中，D＝Rk -1/2；
频域均衡模块，设置为根据
Figure PCTCN2015079103-appb-000066
对干扰预处理后的接收信号做频域均衡。
本实施例的一种实施方式中，所述信道增益计算模块包括：
导引向量提取子模块，设置为提取每根天线接收信号中插入的上行参考解调信号
Figure PCTCN2015079103-appb-000067
其中l表示第l根接收天线；
最小二乘估计子模块，设置为对
Figure PCTCN2015079103-appb-000068
做最小二乘估计LS，得到LS估计输出向量
Figure PCTCN2015079103-appb-000069
X为上行参考解调信号；
特征值加权子模块，设置为计算时域矩形窗的频域相关矩阵，得：
Figure PCTCN2015079103-appb-000070
其中，FN为N×N的DFT矩阵，N为子载波数目，g为时域矩形窗，Q为窗长，Q的取值小于循环前缀长度；
并计算用户设备实际占用子载波的频域相关矩阵，得：
Figure PCTCN2015079103-appb-000071
对得到的
Figure PCTCN2015079103-appb-000072
做特征值分解，得：
Figure PCTCN2015079103-appb-000073
以及将最小二乘估计值在
Figure PCTCN2015079103-appb-000074
的特征域进行加窗处理，得：
Figure PCTCN2015079103-appb-000075
其中Q1为矩形窗窗长，Q1的取值为对角矩阵Λ非零元素的个数。
本实施例的一种实施方式中，所述组合模块组合所得到的信号矩阵Yk，和增益矩阵Hk分别为：
Yk＝[y1,k,…,yM,k]T，Hk＝[h1,k,…,hM,k]T。
本实施例的一种实施方式中，所述干扰噪声协方差矩阵计算模块包括：
上行参考解调信号提取子模块，设置为提取组合信号中每个子载波的上行参考解调信号
Figure PCTCN2015079103-appb-000076
干扰噪声协方差矩阵计算子模块，设置为计算每个子载波的干扰噪声协方差矩阵Rk：
Figure PCTCN2015079103-appb-000077
其中，K表示累计的子载波数目，
Figure PCTCN2015079103-appb-000078
表示向下取整。
本实施例的一种实施方式中，所述干扰预处理模块包括：
预处理矩阵计算子模块，设置为对每个子载波的干扰噪声协方差矩阵做特征值分解：Rk＝UΛUH＝(UΛ1/2UH)·(UΛ1/2UH)H，令D＝Rk -1/2＝UΛ-1/2UH；其中，Λ为对角矩阵，U为酉矩阵，Λ1/2表示对其对角元素开方；
白化处理子模块，设置为用所述D乘上每个子载波的接收信号得到：
Figure PCTCN2015079103-appb-000079
其中，uk表示第k个子载波的干扰噪声向量，则经过干扰预处理后的信道矩阵
Figure PCTCN2015079103-appb-000080
可选的，本实施方式中，所述频域均衡模块根据
Figure PCTCN2015079103-appb-000081
对干扰预处理后的接收信号做频域均衡包括：
所述频域均衡模块计算频域均衡的权值向量w，并合并干扰预处理后的接收信号
Figure PCTCN2015079103-appb-000082
其中，
Figure PCTCN2015079103-appb-000083
如图2所示，典型的LTE上行系统发射机包括：码块分段和CRC(循环 冗余校验码)校验模块，信道编码模块，交织和速率匹配模块，QAM(正交振幅调制)调制模块，DFT模块，子载波映射模块，加循环前缀模块。
如图3所示，典型的LTE上行系统基带接收机包括：FFT模块、信道增益计算模块、干扰噪声协方差矩阵计算模块、频域均衡模块、IFFT(快速傅里叶逆变换)模块、时域均衡模块和信宿模块，其中：
所述的FFT模块，设置为将基带接收信号向量进行FFT变换；
所述的IFFT模块，设置为将频域均衡后的数据变换到时域；
所述的时域均衡模块，设置为对时域信号进行时域均衡。
本实施例在频域均衡模块前增加干扰预处理子模块。
如图4所示，本实施例的一种在干扰条件下的LTE上行系统中的信号检测装置，包括变换模块(包括FFT，解映射子模块)、信道增益计算模块、组合模块、干扰噪声协方差矩阵计算模块、干扰预处理模块和频域均衡模块。
如图5所示，所述的信道增益计算模块包括导引向量提取子模块、最小二乘估计子模块、特征值加权子模块；其中：
导引向量提取子模块：设置为提取每根接收天线的上行参考解调信号；
最小二乘估计子模块：设置为根据提取的上行参考解调信号进行最小二乘信道估计得到最小二乘信道估计值；
特征值加权子模块：设置为对最小二乘信道估计值进行加窗处理，得到滤出干扰的信道估计值。
如图6所示，所述的干扰噪声协方差矩阵计算模块包括上行参考解调信号提取子模块、干扰噪声协方差矩阵计算子模块：
上行参考解调信号提取子模块：设置为提取合并信号中每个子载波的上行参考解调信号；
干扰噪声协方差矩阵计算子模块：设置为计算每个子载波的干扰噪声协方差矩阵。
如图7所示，所述的干扰预处理模块包括预处理矩阵计算子模块、白化处理子模块：
预处理矩阵计算子模块：设置为根据计算出的每个子载波的干扰噪声协方差矩阵计算预处理矩阵D，D＝Rk -1/2；
白化处理子模块：设置为计算干扰预处理后每个子载波的信号
Figure PCTCN2015079103-appb-000084
和信道增益
Figure PCTCN2015079103-appb-000085
图8为本发明实施例与基于MMSE均衡的传统检测方法在干信比(ISR)固定，信噪比(SNR)变化，扩展步行信道(EPA)模型下的性能对比图，仿真假设有1根发射天线，接收端有2根接收天线，即M＝2，计算干扰噪声协方差矩阵时取K为24，其中SNR＝4:2:16dB，ISR＝0dB，从图中可以看出，在强干扰情况下，传统检测方法失效,而本发明实施例的算法能够正常工作。BER为误码率。
上述说明示出并描述了本发明的一个优选实施例，但如前所述，应当理解本发明并非局限于本文所披露的形式，不应看作是对其他实施例的排除，而可用于各种其他组合、修改和环境，并能够在本文所述发明构想范围内，通过上述教导或相关领域的技术或知识进行改动。而本领域人员所进行的改动和变化不脱离本发明的精神和范围，则都应在本发明所附权利要求的保护范围内。
当然，本发明还可有其他多种实施例，在不背离本发明精神及其实质的情况下，熟悉本领域的技术人员当可根据本发明作出各种相应的改变和变形，但这些相应的改变和变形都应属于本发明的权利要求的保护范围。
本领域普通技术人员可以理解上述实施例的全部或部分步骤可以使用计算机程序流程来实现，所述计算机程序可以存储于一计算机可读存储介质中，所述计算机程序在相应的硬件平台上(如系统、设备、装置、器件等)执行，在执行时，包括方法实施例的步骤之一或其组合。
可选地，上述实施例的全部或部分步骤也可以使用集成电路来实现，这些步骤可以被分别制作成一个个集成电路模块，或者将它们中的多个模块或步骤制作成单个集成电路模块来实现。
上述实施例中的各装置/功能模块/功能单元可以采用通用的计算装置来实现，它们可以集中在单个的计算装置上，也可以分布在多个计算装置所组成的网络上。
上述实施例中的各装置/功能模块/功能单元以软件功能模块的形式实现并作为独立的产品销售或使用时，可以存储在一个计算机可读取存储介质中。上述提到的计算机可读取存储介质可以是只读存储器，磁盘或光盘等。
工业实用性
上述技术方案解决了传统的LTE上行链路基于频域MMSE均衡的检测方法在异系统干扰条件下失效的问题，并且在检测过程中充分消除噪声和干扰的影响，提高了检测的精度。

Claims (13)

  1. 一种适用于1根发射天线和M根接收天线的天线配置的在干扰条件下的LTE上行系统的信号检测方法，所述方法包括：
    接收M根接收天线的基带信号，经过快速傅里叶变换，解映射得到频域基带信号yl,k,1≤l≤M,1≤k≤Ns，其中l表示第l根接收天线，k表示子载波序号，Ns表示用户设备实际占用子载波数目；
    提取每根天线接收信号中插入的LTE上行参考解调信号DMRS，然后计算每根接收天线的信道增益hl,k；
    组合M根接收天线的基带信号和信道增益得到信号矩阵Yk，及增益矩阵Hk；
    计算每个子载波上的干扰噪声协方差矩阵Rk；
    对组合后的每一子载波上的接收信号进行干扰预处理，得到干扰预处理后的接收信号
    Figure PCTCN2015079103-appb-100001
    和信道增益
    Figure PCTCN2015079103-appb-100002
    其中D＝Rk -1/2；
    根据
    Figure PCTCN2015079103-appb-100003
    对干扰预处理后的接收信号做频域均衡。
  2. 如权利要求1所述的方法，其中，所述提取每根天线接收信号中插入的LTE上行参考解调信号DMRS，然后计算每根接收天线的信道增益hl,k的步骤包括：
    提取每根天线接收信号中插入的上行参考解调信号
    Figure PCTCN2015079103-appb-100004
    其中l表示第l根接收天线；
    对
    Figure PCTCN2015079103-appb-100005
    做最小二乘估计LS，得到LS估计输出向量
    Figure PCTCN2015079103-appb-100006
    X为上行参考解调信号；
    计算时域矩形窗的频域相关矩阵，得：
    Figure PCTCN2015079103-appb-100007
    其中，FN为N×N的离散傅里叶变换DFT矩阵，N为子载波数目，g为时域矩形窗，Q为窗长，Q的取值小于循环前缀长度；
    计算用户设备实际占用子载波的频域相关矩阵，得：
    Figure PCTCN2015079103-appb-100008
    对
    Figure PCTCN2015079103-appb-100009
    做特征值分解，得：
    Figure PCTCN2015079103-appb-100010
    将最小二乘估计值在
    Figure PCTCN2015079103-appb-100011
    的特征域进行加窗处理，得：
    Figure PCTCN2015079103-appb-100012
    其中Q1为矩形窗窗长，Q1的取值为对角矩阵Λ非零元素的个数。
  3. 如权利要求1所述的方法，其中，组合所得到的信号矩阵Yk，和增益矩阵Hk分别为：
    Yk＝[y1,k,…,yM,k]T，Hk＝[h1,k,…,hM,k]T。
  4. 如权利要求1所述的方法，其中，所述计算每个子载波上的干扰噪声协方差矩阵Rk的步骤包括：
    提取组合信号中每个子载波的上行参考解调信号
    Figure PCTCN2015079103-appb-100013
    计算每个子载波的干扰噪声协方差矩阵Rk，Rk的计算方法如下：
    Figure PCTCN2015079103-appb-100014
    其中，K表示累计的子载波数目，
    Figure PCTCN2015079103-appb-100015
    表示向下取整。
  5. 如权利要求1所述的方法，其中，所述对组合后的每一子载波上的接收信号进行干扰预处理的步骤包括：
    计算预处理矩阵D，D计算方法如下：
    对每个子载波的干扰噪声协方差矩阵做特征值分解：
    Rk＝UΛUH＝(UΛ1/2UH)·(UΛ1/2UH)H
    其中，Λ为对角矩阵，U为酉矩阵，Λ1/2表示对其对角元素开方；
    令D＝Rk -1/2＝UΛ-1/2UH；
    白化处理：
    用所述D乘上每个子载波的接收信号得到：
    Figure PCTCN2015079103-appb-100016
    其中，sk表示第k个子载波的发送信号，uk表示第k个子载波的干扰噪声向量，则经过干扰预处理后的信道矩阵
    Figure PCTCN2015079103-appb-100017
  6. 如权利要求5所述的方法，其中，所述根据
    Figure PCTCN2015079103-appb-100018
    对干扰预处理后的接收信号做频域均衡的步骤包括：
    计算频域均衡的权值向量w，并合并干扰预处理后的接收信号
    Figure PCTCN2015079103-appb-100019
    w的计算方法如下：
    Figure PCTCN2015079103-appb-100020
  7. 一种适用于1根发射天线和M根接收天线的天线配置的在干扰条件下的LTE上行系统的信号检测装置，所述装置包括：
    变换模块，设置为接收M根接收天线的基带信号，经过快速傅里叶变换，解映射得到频域基带信号yl,k,1≤l≤M,1≤k≤Ns，其中l表示第l根接收天线，k表示子载波序号，Ns表示用户设备实际占用子载波数目；
    信道增益计算模块，设置为提取每根天线接收信号中插入的LTE上行参考解调信号DMRS，然后计算每根接收天线的信道增益hl,k；
    组合模块，设置为组合M根接收天线的基带信号和信道增益得到信号矩阵Yk，及增益矩阵Hk；
    干扰噪声协方差矩阵计算模块，设置为计算每个子载波上的干扰噪声协方差矩阵Rk；
    干扰预处理模块，设置为对组合后的每一子载波上的接收信号进行干扰预处理，得到干扰预处理后的接收信号
    Figure PCTCN2015079103-appb-100021
    和信道增益
    Figure PCTCN2015079103-appb-100022
    其中，D＝Rk -1/2；
    频域均衡模块，设置为根据
    Figure PCTCN2015079103-appb-100023
    对干扰预处理后的接收信号做频域均衡。
  8. 如权利要求7所述的装置，其中，所述信道增益计算模块包括：
    导引向量提取子模块，设置为提取每根天线接收信号中插入的上行参考解调信号
    Figure PCTCN2015079103-appb-100024
    其中l表示第l根接收天线；
    最小二乘估计子模块，设置为对
    Figure PCTCN2015079103-appb-100025
    做最小二乘估计LS，得到LS估计输出向量
    Figure PCTCN2015079103-appb-100026
    X为上行参考解调信号；
    特征值加权子模块，设置为计算时域矩形窗的频域相关矩阵，得：
    Figure PCTCN2015079103-appb-100027
    其中，FN为N×N的离散傅里叶变换DFT矩阵，N为子载波数目，g为时域矩形窗，Q为窗长，Q的取值小于循环前缀长度；
    并计算用户设备实际占用子载波的频域相关矩阵，得：
    Figure PCTCN2015079103-appb-100028
    对得到
    Figure PCTCN2015079103-appb-100029
    做特征值分解，得：
    Figure PCTCN2015079103-appb-100030
    以及将最小二乘估计值在
    Figure PCTCN2015079103-appb-100031
    的特征域进行加窗处理，得：
    Figure PCTCN2015079103-appb-100032
    其中Q1为矩形窗窗长，Q1的取值为对角矩阵Λ非零元素的个数。
  9. 如权利要求7所述的装置，其中，所述组合模块组合所得到的信号矩阵Yk，和增益矩阵Hk分别为：
    Yk＝[y1,k,…,yM,k]T，Hk＝[h1,k,…,hM,k]T。
  10. 如权利要求7所述的装置，其中，所述干扰噪声协方差矩阵计算模块包括：
    上行参考解调信号提取子模块，设置为提取组合信号中每个子载波的上行参考解调信号
    Figure PCTCN2015079103-appb-100033
    干扰噪声协方差矩阵计算子模块，设置为计算每个子载波的干扰噪声协方差矩阵Rk：
    Figure PCTCN2015079103-appb-100034
    其中，K表示累计的子载波数目，
    Figure PCTCN2015079103-appb-100035
    表示向下取整。
  11. 如权利要求7所述的装置，其中，所述干扰预处理模块包括：
    预处理矩阵计算子模块，设置为对每个子载波的干扰噪声协方差矩阵做特征值分解：Rk＝UΛUH＝(UΛ1/2UH)·(UΛ1/2UH)H，令D＝Rk -1/2＝UΛ-1/2UH；其中，Λ为对角矩阵，U为酉矩阵，Λ1/2表示对其对角元素开方；
    白化处理子模块，设置为用所述D乘上每个子载波的接收信号得到：
    Figure PCTCN2015079103-appb-100036
    其中，sk表示第k个子载波的发送信号，uk表示第k个子载波的干扰噪声向量，则经过干扰预处理后的信道矩阵
    Figure PCTCN2015079103-appb-100037
  12. 如权利要求11所述的装置，其中，
    所述频域均衡模块，是设置为计算频域均衡的权值向量w，并合并干扰预处理后的接收信号
    Figure PCTCN2015079103-appb-100038
    其中，
    Figure PCTCN2015079103-appb-100039
  13. 一种计算机存储介质，所述计算机存储介质中存储有计算机可执行指令，所述计算机可执行指令用于执行权利要求1～6中任一项所述的方法。
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