WO2015062950A1 - Prédiction du passage par zéro pour un courant de charge d'un convertisseur résonant - Google Patents

Prédiction du passage par zéro pour un courant de charge d'un convertisseur résonant Download PDF

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Publication number
WO2015062950A1
WO2015062950A1 PCT/EP2014/072706 EP2014072706W WO2015062950A1 WO 2015062950 A1 WO2015062950 A1 WO 2015062950A1 EP 2014072706 W EP2014072706 W EP 2014072706W WO 2015062950 A1 WO2015062950 A1 WO 2015062950A1
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WO
WIPO (PCT)
Prior art keywords
load current
zero
crossing
phase shifter
switching
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Application number
PCT/EP2014/072706
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English (en)
Inventor
Peter Lürkens
Original Assignee
Koninklijke Philips N.V.
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Publication date
Application filed by Koninklijke Philips N.V. filed Critical Koninklijke Philips N.V.
Publication of WO2015062950A1 publication Critical patent/WO2015062950A1/fr

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Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
    • H02M1/083—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the ignition at the zero crossing of the voltage or the current
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/4815—Resonant converters
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Definitions

  • the invention relates to a method and a system for prediction of zero-crossing for a load current of a resonant converter a predefined time before the actual zero crossing occurs.
  • the invention relates further to a high voltage generator and an X-ray tube.
  • phase- shift-means For the control of the switching frequency of a resonant converter, a phase- shift-means is used, which detects the moment of the zero crossing of the load current a short time in advance. By this it is achieved, that the switching of the inverter output voltage happens at moment short, in terms of the switching period, before the actual zero crossing and hard switching is avoided.
  • signal propagation delays and reaction time of components of the resonant converter can be accounted for.
  • WO 2006/114719 Al describes a resonant DC/DC converter for supplying an output power comprises a switching device for supplying a switched voltage to a resonant circuit having a transformer.
  • the switched voltage of the described converter is derived from an intermediate circuit voltage having substantially a fixed pulse width and frequency so that the zero crossings of the resonant current generated in the resonant current are defined.
  • the switching configuration of a described inverter circuit is selected by a control device to either increase, decrease or maintain at a substantially constant level the resonant current according to the polarity of the switched voltage, so as to control the output power as required.
  • improved switching could reduce the energy consumption and losses in the switching means of the converter.
  • HO-SUNG KIM ET AL "Protection circuit to prevent a transition from ZVS mode to ZCS mode under variable frequency operation", INTELEC 2009, IEEE, PISCATAWAY, NJ, USA, 18 October 2009, pages 1-4, XP031579393 describes a protection circuit for resonant power converters using soft switching topologies.
  • An aspect of the invention relates to a system for prediction of zero-crossing for a load current of a resonant converter, the system comprising:
  • a processing unit configured to receive a direction and a step height of a switching event
  • a differentiator unit configured to determine a polarity of a gradient of the load current
  • phase shifter unit configured to provide a zero-crossing prediction for a sinusoidal current waveform
  • a comparator unit configured to evaluate an expected change of a slope of the load current at the moment of the switching event by superimposing a signal with a phase shifter output of the resonant converter based on the received direction and the step height and based on an effective inductance of the resonant converter; the signal
  • phase shifter output depending on the polarity of the gradient of the load current and further depending on a difference-integral between a first tangent of the load current before a switching event and a second tangent of the load current after the switching event.
  • a further aspect of the invention relates to a high voltage generator comprising the system for prediction of zero-crossing for a load current, an electrical resonant circuit, excitable by a converter on a low voltage side of the high voltage generator, and a
  • transformer generating a high ac- voltage for feeding a high voltage rectifier.
  • a further aspect of the invention relates to an X-ray tube comprising an anode, a cathode, and a high voltage generator, wherein the high voltage generator is connected to either the anode or the cathode of the X-ray tube, or different output levels of the generator to each electrode.
  • the expected change of the slope by switching of the inverter in advance is considered. This is achieved by combining or superimposing a signal with the phase shifter output which equals the integral of the difference of the slopes before and after the switching event over the period from the switching moment until the actual zero crossing of the current:
  • a switching event is defined as a switching of the driver circuit characterized by the step height, time and further characteristics. Resonant techniques are used to allow the switching devices to turn-on and turn-off at zero current or zero voltage, hence the switching loss becomes low.
  • a further advantage of the invention may be seen that by evaluation of the sign of the current slope instable conditions may not occur, during which the zero-crossing detector would generate persistently inverter switching signals with the maximum possible frequency. Therefore, it is proposed to derive the sign of the correction from the current gradient. This changes in the middle of a switching cycle, so that the corrected phase shift signal becomes insensitive to the switching actions of the inverter itself.
  • a differentiator unit is further provided with the system, wherein the differentiator unit is designed to determine a polarity of a gradient of the load current. This allows significant operational benefits in terms of more precise prediction of the zero current.
  • an effective inductance of the resonant converter is considered and used to evaluate the expected change of the slope of the load current. This advantageously provides that the phase shifter produces a waveform which is subject to the upcoming switching of the inverter output.
  • the method further comprises the step of determining a polarity of a gradient of the load current. This allows adjusting the prediction of the zero-crossing of the load current to the present polarity of the gradient of the load current.
  • the signal superimposed with the phase shifter output depends on the polarity of the gradient of the load current. This allows an improved prediction of the zero-crossing.
  • the signal superimposed with the phase shifter output further depends on a difference-integral between a first tangent of the load current before a switching event and a second tangent of the load current after the switching event. Thereby the quality of the zero-crossing predictor is increased.
  • a time window is considered, during which further switching events are suppressed for a predetermined time period. This minimizes the influence of unwanted switching events with an excessive frequency.
  • an amplitude of an output voltage of the resonant converter corresponds to a bus voltage.
  • a further aspect of the invention relates to a system comprising a processing unit as a digital circuit and a differentiator unit and a comparator unit as analog circuits, both circuits building up the hybrid system.
  • Fig. 1 shows a circuit diagram of a resonant LCC converter for explaining the invention
  • Fig. 2 shows a circuit diagram of a resonant LLC converter for explaining the invention
  • Fig. 3 shows a flow diagram of a method for prediction of zero-crossing for a load current of a resonant converter according to an exemplary embodiment of the invention
  • Fig. 4 shows a multiple y-axes diagram comprising a current-time diagram of the load current and a voltage-time diagram of the inverter voltage for explaining the invention
  • Fig. 5 shows a multiple y-axes diagram comprising a current-time diagram of the load current and a voltage-time diagram of the inverter voltage for explaining the invention
  • Fig. 6 shows a multiple y-axes diagram comprising a current-time diagram of the load current and a voltage-time diagram of the inverter voltage for explaining the invention
  • Fig. 7 shows a multiple y-axes diagram comprising a current-time diagram of the load current and a voltage-time diagram of the inverter voltage for explaining the invention
  • Fig. 8 shows a circuit diagram of a system for prediction of zero-crossing for a load current of a resonant converter according to an exemplary embodiment of the invention
  • Fig. 9 shows a circuit diagram of a system for prediction of zero-crossing for a load current of a resonant converter according to an exemplary embodiment of the invention
  • Fig. 10 shows a circuit diagram of a system for prediction of zero-crossing for a load current of a resonant converter according to an exemplary embodiment of the invention
  • Fig. 11 shows a three dimensional parameter map for explaining the invention.
  • Fig. 12 shows a circuit diagram of a system for prediction of zero-crossing for a load current of a resonant converter according to an exemplary embodiment of the invention
  • Fig. 13 shows a schematic diagram of a high voltage generator according to an exemplary embodiment of the invention.
  • Fig. 14 shows a schematic diagram of an X-ray tube according to an exemplary embodiment of the invention.
  • Figure 1 shows a circuit diagram of a resonant LCC circuit 10 for explaining the invention.
  • Figure 1 shows a resonant LCC circuit 10, e.g. used in a resonant LCC converter, comprising a first inductor LI and a first capacitor CI and a second capacitor C2. The load is connected in parallel to the second capacitor C2.
  • Load current is understood so far as the inverter output current.
  • the load of the converter is not depicted in detail. It can be a simple resistor, a gas discharge lamp, but also a rectifier with an output smoothing capacitor, or a more complex load circuit, e.g. a high voltage multiplier.
  • This configuration represents the resonant circuit in an LCC resonant converter commonly used in electronic lamp ballast for gas-discharge lamps.
  • Resonant converters can achieve very low switching loss thus enable resonant topologies to operate at high switching frequency.
  • the actual switching of the resonant converter may happen at a moment, when the load current is still high enough to allow for a complete commutation of the output voltage of the resonant converter by recharging of capacitors before the load current reverses and soft-switching becomes impossible.
  • These capacitors are usually in parallel to the inverter switches or formed by their parasitic drain-source capacitance.
  • the phase-shifter means can be realized with an amplifier and a differentiator component, in which the output signal ps, depending on t and ⁇ is formed according the following rule:
  • this phase shift signal produces a new sinusoidal signal which zero crossings are by a time ⁇ in advance of the zero-crossings of the original current waveform.
  • FIG. 2 shows a circuit diagram of a resonant circuit in an LLC converter for explaining the invention.
  • a resonant circuit of an LLC converter is depicted in Figure 2, using two inductors and one capacitor, a resonant circuit for an LLC converter 11 , comprising a first inductor LI, a second inductor L2 and a first capacitor CI, with the load connected in parallel to the second inductor L2.
  • This configuration represents resonant circuit in an LLC inverter.
  • the load is considered to be constituted from the items given in the description of Figure 1.
  • Figure 3 shows a flow diagram of a method for prediction of zero-crossing for a load current of a resonant converter according to an exemplary embodiment of the invention. The method comprises the following steps:
  • evaluating S3 an expected change of a slope of the load current I-inv at the moment of the switching event by superimposing a signal with a phase shifter output of the resonant circuit 10, 11 based on the considered direction and the considered step height is performed, whereby the zero-crossing of the load current I-inv is predicted S4.
  • the method may further comprise the step of determining a polarity of a gradient of the load current, wherein evaluating the expected change is further based on the determined polarity of the gradient of the load current.
  • Figure 4 shows a multiple y-axes diagram comprising a current-time diagram of the load current and a voltage-time diagram of the inverter voltage for explaining the invention.
  • a time period of approximately 1.7 x 10 "5 seconds is depicted.
  • the first y-axis on the left shows the inverter voltage
  • the second y-axis on the right depicts the load current.
  • the inverter voltage V-inv follows a step function comprising three steps, i.e. three switching events occur during the depicted time period.
  • Figure 4 shows the prediction for a real circuit, in which current waveforms are not sinusoidal, but deviate the more, the lower the effective quality factor of the resonant system is. It is actually advantageous, to operate at a low quality factor, because it reduces the reactive power in the reactive components of the resonant converter circuit, which otherwise would lead to increased losses.
  • FIG 4 a representative situation is depicted.
  • the inverter switching should occur 0.47 in advance of the zero crossing of the load current.
  • the first signal curve 23 of the phase-shifter which is designed with the same ⁇ -property, does not exhibit a zero crossing yet at this moment.
  • the ⁇ -property of the phase shifter may be increased to 1.3 ⁇ , i.e. 2.8-fold.
  • the amplitude of higher- frequency signal component in the waveform is increased by the same factor and such the sensitivity to higher frequency components in the current waveform, as depicted by a second signal curve 24.
  • Figure 5 shows a multiple y-axes diagram comprising a current-time diagram of the load current and a voltage-time diagram of the inverter voltage V-inv for explaining the invention. The same physical quantities are plotted on the two y-axes and the x-axis as in Figure 4.
  • Figure 5 shows the aspects of the prediction in detail.
  • the phase shifter produces a waveform which is subject to the switching of the resonant converter output voltage.
  • the diagram of Figure 5 shows also the tangents both immediately before, e.g. first tangent 33 and second tangent 34, and after, e.g.
  • the change of the slopes of the current waveforms is defined by the change of the voltage and the effective circuit (resonant) inductance.
  • Figure 6 shows a multiple y-axes diagram comprising a current-time diagram of the load current and a voltage-time diagram of the inverter voltage for explaining the invention. The same physical quantities are plotted on the two y-axes and the x-axis as in Figure 4.
  • the effective inductance includes also the leakage of the transformer, if present.
  • the change of the voltage is practically solely determined by the change of the inverter output voltage. Therefore, a relevant back-electromagnetic force curve EMF of the system is determined by the voltage of the resonant series and parallel capacitors. However, these cannot change in the switching instance by principle.
  • a fifth tangent 44 and sixth tangent 45 are set to the load current curve.
  • a differential integral curve 46 denotes the value of the difference-integral between the fifth tangent 44 and the sixth tangent 45 before and after the switching event.
  • Figure 7 shows a multiple y-axes diagram comprising a current-time diagram of the load current and a voltage-time diagram of the inverter voltage for explaining the invention. The same physical quantities are plotted on the two y-axes and the x-axis as in Figure 4.
  • phase shifter output signal 52 advantageously predicts the zero-crossing of the load current. It is proposed to derive the sign of the correction from the current gradient. This changes in the middle of a switching cycle, so that the corrected phase shift signal becomes insensitive to the switching actions of the inverter itself.
  • Other lock mechanisms can also be considered, e. g. a time window, in which further switching actions are suppressed for a certain time after a switching action.
  • the amplitude of the inverter output voltage usually resembles the DC bus voltage. If this is sufficiently constant, a precise measurement may not be necessary and the correction may be applied using constant quantities, which are only depending on the switching states, as depicted in the formula stated above.
  • Figure 8 shows a circuit diagram of a system for prediction of zero-crossing for a load current of a resonant converter according to an exemplary embodiment of the invention.
  • the system 100 comprises a differentiator unit 140, a processing unit 1 10 and a comparator unit 120.
  • the differentiator unit 140 consisting of a differentiation 143 and a polarity detector 142, may be designed to determine the sign of the slope of the inverter current.
  • the processing unit 1 10 might be designed to consider a direction and a step height of the switching event.
  • the comparator unit 120 may be designed to evaluate the integral over the advance time of an expected change of a slope of the load current at the moment of the switching event by superimposing a signal with a phase shifter output of the resonant converter based on the sign of the slope of the inverter current, the considered direction, or the considered step height, or the effective inductance of the circuit, whereby the zero-crossing of the load current is predicted.
  • the system 100 further comprises a phase shifter 130.
  • the differentiator unit 140 may comprise a differentiator circuit 142 and a polarity detector unit 143.
  • a potential analogue electronics implementation of the system 100 comprises a zero-biased comparator 122 and four additional comparators 125 to which the original phase shifter signal are supplied. For the four additional comparators 125 zero is not used as the threshold level, but instead the DC bus voltage, multiplied with a factor (-2, - 1 , 1 , 2)XTXV DC /L I , representing the influence of the switching state (-2, - 1 , 1 , 2), the DC voltage V DC , and the effective inductance L r .
  • the parameter ⁇ indicates the desired time shift.
  • the system 100 may further comprise a frequency generator circuit 160.
  • the differentiator unit 140 produces the sign of the current gradient i'.
  • the selection of the appropriate comparator is realized in a digital way by means of the sign of the current gradient and the combination of the initial and subsequent switching state (s, s+1).
  • FIG 8 an exemplary structure of the system 100 is depicted.
  • the inverter current signal is differentiated and supplied to a polarity detector unit 143 of the differentiator unit 140. Additionally, the inverter current signal is supplied to the phase shifter 130.
  • the output signal of the phase shifter 130 is connected to the inputs of a number of the comparators 125 of the comparator unit 120.
  • One comparator i.e. the zero-biased
  • comparator 122 compares the signal with a zero threshold.
  • a signal is generated by a signal generator circuit 121 by scaling the DC bus voltage with the factor: T p /(L r +L s i g ).
  • L r +L s i g represents the effective inductance of the resonant circuit 10, 11, and Tp the desired advancement of the zero-crossing detection.
  • This signal is supplied to a number of amplifiers 124 of the comparator unit 120 or gains, which have gain factors of (-2, -1, 1, 2).
  • the outputs of the amplifiers 124 serve as threshold levels for the additional
  • comparators 125 The number of additional amplifiers 124 and comparators 122, 125 and the required gain factors result from the number and the amplitude of the different possible voltage transitions at the output terminal of the inverter.
  • a neutral point clamped, NPC, -inverter with three voltage levels at each branch would require eight additional comparators 125 in the comparator unit 120 and amplifiers with the gain factors of -2, -1.5, -1, -0.5, 0.5, 1.0, 1.5, 2.0.
  • the polarity signal is submitted to a selection block circuit 113 together with the current switching state and the upcoming switching state.
  • the switching states are received from a system control unit under consideration of various system states and reference quantities.
  • the system control unit is not subject to this invention.
  • the selection block circuit 1 13 of the processing unit may receive input value concerning the current voltage amplitude 111 and the subsequent voltage amplitude 112, e. g. after the next switching event.
  • the selection block circuit 113 for example controls a selector switch 114 of the processing unit 110.
  • the selector switch 114 selects one of the comparator outputs to synchronize the frequency generator 160 which produces the reference for the inverter switching signals. Each time, when the frequency generator produces a pulse, the new switching state becomes active in the inverter, and supersedes the current switching state.
  • Figure 9 shows a circuit diagram of a system for prediction of zero-crossing for a load current of a resonant converter according to an exemplary embodiment of the invention.
  • Figure 9 shows a simplified solution of the system, e. g. with a superposition of a fixed correction quantity, which only depends on the DC bus voltage, however neglecting correct considerations of transitions starting with a voltage o zero. If only considering the extreme transitions of +1-2 the switching would happen somewhat too early in unfavorable cases, but never critically too late.
  • Figure 10 shows a circuit diagram of a system for prediction of zero-crossing for a load current of a resonant converter according to an exemplary embodiment of the invention.
  • Figure 10 shows an even further simplified implementation achieving the compensation by direct superposition of the comparator with a fixed correction quantity which is derived from the actual current direction assuming a constant DC bus voltage.
  • a polarity detector determines the current direction and produces a polarity signal which is amplified with the factor and which serves as a threshold for the comparator.
  • Figure 1 1 shows a three dimensional parameter map for explaining the invention.
  • the three axes are defined by the DC bus voltage (z-axis), the transition (x-axis), and the phase advance (y-axis).
  • VDC 1 , VDC2, and VDC3 the measured phase shifts are plotted as dots the curve is calculated by the measured phase shifts and represents a fitted line.
  • Figure 12 shows a circuit diagram of a system for prediction of zero-crossing for a load current of a resonant converter according to an exemplary embodiment of the invention.
  • Figure 12 shows an analog implementation option of the preceding circuit with consideration of the actual DC bus voltage. Derivation of the compensation signal from the actual output voltage is usually not recommended, because there will be no correction for output voltage levels of zero leading to a too late detection of the zero crossing of the current.
  • the further reference signs as depicted in Figure 12 were already described in Figure 8 and are, therefore, not explained in detail.
  • Figure 13 shows a schematic diagram of a high voltage generator according to an exemplary embodiment of the invention.
  • the high voltage generator 200 may comprise a system 100, an electrical inverter 210 on a low voltage side 220 with a resonant circuit 10,11, wherein the system 100 is used for the prediction of zero-crossing for the load current of a resonant circuit 10,11 implemented in the low voltage side 220.
  • the high voltage generator 200 may further comprise a transformer 230 in a high voltage unit 240. Depending on the purpose, the high voltage unit may have a rectifier 250.
  • the high voltage generator 200 may be constructed for an X-ray tube or for lighting applications or for further purpose.
  • Figure 14 shows a schematic diagram of an X-ray tube according to an exemplary embodiment of the invention.
  • the X-ray tube 300 may comprise an anode 310, a cathode 320, and a high voltage generator 200, wherein the high voltage generator 200 is connected to the anode 310 and the cathode 320 of the X-ray tube in order to generate a direct voltage on the X-ray tube 300.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Inverter Devices (AREA)

Abstract

L'invention porte sur un système et un procédé pour la prédiction du passage par zéro pour un courant de charge d'un convertisseur résonant. Pour réaliser une prédiction en temps réel du passage par zéro sans accroissement de la propriété du déphaseur, le changement attendu de la pente en commutant l'onduleur est pris en compte à l'avance. Cela est réalisé en combinant ou superposant un signal avec la sortie du déphaseur ou en réglant l'entrée de référence d'un comparateur par un signal qui est égal à l'intégrale de la différence des pentes avant et après l'événement de commutation sur la période entre le moment de la commutation et le passage par zéro effectif du courant.
PCT/EP2014/072706 2013-10-30 2014-10-23 Prédiction du passage par zéro pour un courant de charge d'un convertisseur résonant WO2015062950A1 (fr)

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EP13190778 2013-10-30
EP13190778.4 2013-10-30

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Cited By (7)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN110361596A (zh) * 2019-06-18 2019-10-22 上海宝准电源科技有限公司 一种基于过零点检测的谐振检测策略
CN110618308A (zh) * 2019-10-18 2019-12-27 Tcl空调器(中山)有限公司 一种单相变交流电压零点检测方法及装置
US20200128638A1 (en) * 2018-10-19 2020-04-23 Control4 Corporation Predictive lighting control using load current slew rate for power switching
CN112448586A (zh) * 2019-09-05 2021-03-05 半导体组件工业公司 Llc谐振电源转换器以及用于控制其的方法和控制器
CN112816768A (zh) * 2021-03-09 2021-05-18 青岛海信日立空调系统有限公司 交流电压信号过零检测装置
CN114755487A (zh) * 2022-06-15 2022-07-15 深圳市航智精密电子有限公司 一种磁通门电流传感器及电流测量方法
CN116760846A (zh) * 2023-08-21 2023-09-15 国网山东省电力公司日照供电公司 基于首个过零点识别的双端故障录波数据同步方法及系统

Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2006114719A1 (fr) 2005-04-26 2006-11-02 Koninklijke Philips Electronics N.V. Convertisseur continu-continu resonant a commutation a zero de courant
US20100149843A1 (en) * 2008-05-02 2010-06-17 Hendrik Walde Preemptive protection for a power convertor
CN202351312U (zh) * 2011-08-30 2012-07-25 刘闯 高频谐振电流的过零点检测电路
US20120200273A1 (en) 2011-02-07 2012-08-09 Eom Hyun-Chul Switch controller and converter including the same

Patent Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2006114719A1 (fr) 2005-04-26 2006-11-02 Koninklijke Philips Electronics N.V. Convertisseur continu-continu resonant a commutation a zero de courant
US20100149843A1 (en) * 2008-05-02 2010-06-17 Hendrik Walde Preemptive protection for a power convertor
US20120200273A1 (en) 2011-02-07 2012-08-09 Eom Hyun-Chul Switch controller and converter including the same
CN202351312U (zh) * 2011-08-30 2012-07-25 刘闯 高频谐振电流的过零点检测电路

Non-Patent Citations (2)

* Cited by examiner, † Cited by third party
Title
HO-SUNG KIM ET AL.: "Protection circuit to prevent a transition from ZVS mode to ZCS mode under variable frequency operation", INTELEC 2009, 18 October 2009 (2009-10-18), pages 1 - 4, XP031579393
HO-SUNG KIM ET AL: "Protection circuit to prevent a transition from ZVS mode to ZCS mode under variable frequency operation", TELECOMMUNICATIONS ENERGY CONFERENCE, 2009. INTELEC 2009. 31ST INTERNATIONAL, IEEE, PISCATAWAY, NJ, USA, 18 October 2009 (2009-10-18), pages 1 - 4, XP031579393, ISBN: 978-1-4244-2490-0 *

Cited By (12)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20200128638A1 (en) * 2018-10-19 2020-04-23 Control4 Corporation Predictive lighting control using load current slew rate for power switching
US10925131B2 (en) * 2018-10-19 2021-02-16 Wirepath Home Systems, Llc Predictive lighting control using load current slew rate for power switching
CN110361596A (zh) * 2019-06-18 2019-10-22 上海宝准电源科技有限公司 一种基于过零点检测的谐振检测策略
CN112448586A (zh) * 2019-09-05 2021-03-05 半导体组件工业公司 Llc谐振电源转换器以及用于控制其的方法和控制器
CN110618308A (zh) * 2019-10-18 2019-12-27 Tcl空调器(中山)有限公司 一种单相变交流电压零点检测方法及装置
CN110618308B (zh) * 2019-10-18 2021-11-09 Tcl空调器(中山)有限公司 一种单相变交流电压零点检测方法及装置
CN112816768A (zh) * 2021-03-09 2021-05-18 青岛海信日立空调系统有限公司 交流电压信号过零检测装置
CN112816768B (zh) * 2021-03-09 2022-08-02 青岛海信日立空调系统有限公司 交流电压信号过零检测装置
CN114755487A (zh) * 2022-06-15 2022-07-15 深圳市航智精密电子有限公司 一种磁通门电流传感器及电流测量方法
CN114755487B (zh) * 2022-06-15 2022-09-20 深圳市航智精密电子有限公司 一种磁通门电流传感器及电流测量方法
CN116760846A (zh) * 2023-08-21 2023-09-15 国网山东省电力公司日照供电公司 基于首个过零点识别的双端故障录波数据同步方法及系统
CN116760846B (zh) * 2023-08-21 2023-11-14 国网山东省电力公司日照供电公司 基于首个过零点识别的双端故障录波数据同步方法及系统

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