WO2015062081A1 - 一种Linc功放合路电路 - Google Patents

一种Linc功放合路电路 Download PDF

Info

Publication number
WO2015062081A1
WO2015062081A1 PCT/CN2013/086437 CN2013086437W WO2015062081A1 WO 2015062081 A1 WO2015062081 A1 WO 2015062081A1 CN 2013086437 W CN2013086437 W CN 2013086437W WO 2015062081 A1 WO2015062081 A1 WO 2015062081A1
Authority
WO
WIPO (PCT)
Prior art keywords
circuit
power amplifier
combining
phase
line
Prior art date
Application number
PCT/CN2013/086437
Other languages
English (en)
French (fr)
Inventor
王尧强
武胜波
张希坤
Original Assignee
华为技术有限公司
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by 华为技术有限公司 filed Critical 华为技术有限公司
Priority to PCT/CN2013/086437 priority Critical patent/WO2015062081A1/zh
Priority to CN201380004307.2A priority patent/CN104272584B/zh
Publication of WO2015062081A1 publication Critical patent/WO2015062081A1/zh

Links

Classifications

    • HELECTRICITY
    • H03ELECTRONIC CIRCUITRY
    • H03FAMPLIFIERS
    • H03F1/00Details of amplifiers with only discharge tubes, only semiconductor devices or only unspecified devices as amplifying elements
    • H03F1/02Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation
    • H03F1/0205Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation in transistor amplifiers
    • H03F1/0294Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation in transistor amplifiers using vector summing of two or more constant amplitude phase-modulated signals
    • HELECTRICITY
    • H03ELECTRONIC CIRCUITRY
    • H03FAMPLIFIERS
    • H03F3/00Amplifiers with only discharge tubes or only semiconductor devices as amplifying elements
    • H03F3/189High-frequency amplifiers, e.g. radio frequency amplifiers
    • HELECTRICITY
    • H03ELECTRONIC CIRCUITRY
    • H03FAMPLIFIERS
    • H03F3/00Amplifiers with only discharge tubes or only semiconductor devices as amplifying elements
    • H03F3/20Power amplifiers, e.g. Class B amplifiers, Class C amplifiers
    • H03F3/24Power amplifiers, e.g. Class B amplifiers, Class C amplifiers of transmitter output stages
    • H03F3/245Power amplifiers, e.g. Class B amplifiers, Class C amplifiers of transmitter output stages with semiconductor devices only
    • HELECTRICITY
    • H03ELECTRONIC CIRCUITRY
    • H03FAMPLIFIERS
    • H03F2200/00Indexing scheme relating to amplifiers
    • H03F2200/204A hybrid coupler being used at the output of an amplifier circuit

Definitions

  • the present invention relates to the field of wireless communications, and in particular, to a line power amplifier combining circuit. Background technique
  • a line power amplifier is a kind of power amplifier that combines a signal whose amplitude and phase change with time into two equal-phase out-of-phase signals and combines them through a power amplifier.
  • the Line power amplifier fully utilizes the characteristics of the amplifier to efficiently amplify the constant envelope signal, and uses an efficient combining method to achieve high efficiency of the overall power amplifier.
  • Line amplifiers include Line amplifier technology with Chireix combiner (heterophase combiner) and Line amplifier technology with matched hybird bridge (hybrid bridge).
  • Chireix combiner the Line power amplifier technology using Chireix combiner will be described in more detail in FIG. 1, which decomposes the envelope modulation bandpass s in two different phase constant envelopes in the out-of-phase modulator.
  • Signals 8 and s 2 are applied to the power amplifier, and the outputs of the power amplifiers are combined in a hybrid device to recover the envelope modulation waveform.
  • the output amplitude of ut is the phase shift result between signals ⁇ 1 and s 2.
  • the amplitude maximum is obtained, and when inverted, the amplitude minimum is obtained.
  • This hybrid construction expands the high efficiency region to include lower output power levels by replacing the impedance load with a compensating reactance network, thereby maintaining higher efficiency.
  • the design of the output combined network is limited, the electrical length of the microstrip line is limited to a certain value, which affects the flexibility of the design; and because there is no separate bridge isolation end, the signal cannot be made.
  • the mismatched portion is coupled to use digital enhancement techniques.
  • FIG. 2 the circuit block diagram of the line power amplifier technology using the matched hybird bridge (hybrid bridge) is shown in FIG. 2, and the difference between the technology and the line power amplifier technology of the Chireix combiner shown in FIG.
  • the point is that the two out-of-phase constant envelope signals ⁇ 1 and s 2 in Figure 2 are applied to the power amplifiers A and B, respectively, modulated by circuit A and circuit B, and then output through the hybrid bridge combiner.
  • the signals of the A and B in phase are output through the circuit C, and the signals of the A and B non-in-phase are consumed by the isolation terminal 4 on the load.
  • this method has a separate bridge isolation end, since it is only a simple combination, it is impossible to increase the efficiency of the two-way power amplifier by using load traction, and more power is wasted on the isolated end load.
  • the embodiment of the invention provides a L i ne power amplifier combining circuit, which can improve the efficiency of the power amplifier by using load traction, and has flexible design. There is a separate bridge isolation end, so that the mismatched part of the signal can be coupled. Use digital enhancement technology.
  • a L i ne power combine circuit in a first aspect, includes an out-of-phase modulator, a first power amplifier, a second power amplifier, a first adjustment circuit, a second adjustment circuit, and a hybrid Bridge combiner, output circuit, passive microwave circuit;
  • the first power amplifier and the second power amplifier are respectively connected between two output ends of the different phase modulator and the first adjustment circuit and the second adjustment circuit, the first The adjustment circuit and the second adjustment circuit are also respectively connected to two input ends of the hybrid bridge combiner, and the output circuit and the passive microwave circuit are respectively connected to the non-inverting output end of the hybrid bridge combiner , the out-of-phase output is connected;
  • the first adjustment circuit, the second adjustment circuit, and the output circuit cooperate with the passive microwave circuit such that an amplitude of an output signal of the first power amplifier and the second power amplifier is smaller than a first At a threshold, there is a new efficiency extreme point.
  • the passive microwave circuit specifically includes:
  • microstrip line wherein an electrical length of the microstrip line is determined by the location of the new efficiency extreme point, and the first adjustment circuit and the second adjustment circuit;
  • the passive microwave circuit is coupled to the out-of-phase output of the hybrid bridge circuit and includes:
  • the microstrip line is coupled to an out-of-phase output of the hybrid bridge circuit.
  • the microstrip line is also grounded.
  • the L i ne power amplifier combining circuit further includes a first resistor
  • the microstrip line is further connected to the first resistor, and the first resistor is further grounded, wherein a resistance of the first resistor is greater than a second threshold, so that the microstrip line is approximately open.
  • the L i ne power combining circuit further includes a coupling sampling circuit and a digital domain circuit; wherein the digital domain circuit Including the out-of-phase modulator, the coupled sampling circuit is connected between the out-of-phase output end of the hybrid bridge combiner and the digital domain circuit, and the output ends of the digital domain circuit are respectively Connecting a first power amplifier and the second power amplifier;
  • the coupled sampling circuit is configured to detect a heterogeneous combination signal in the L i ne power combining circuit
  • the digital domain circuit is configured to perform digital preprocessing on signals input to the first power amplifier and the second power amplifier according to the out-of-phase combining signals collected by the coupled sampling circuit, so that Achieve digital enhancements.
  • the coupled sampling circuit includes a second resistor
  • the second resistor is used to adjust the ratio of voltage and electricity entering the coupled sampling circuit.
  • the digital domain circuit is configured to perform the heterogeneous combination according to the coupled sampling circuit according to the fourth possible implementation manner or the fifth possible implementation manner.
  • the road signal is digitally preprocessed to the signals input to the first power amplifier and the second power amplifier, so that the digital enhancement effect is specifically included:
  • the digital domain circuit is configured to perform the heterogeneous combination according to the coupled sampling circuit according to the fourth possible implementation manner or the fifth possible implementation manner
  • the road signal is digitally preprocessed to the signals input to the first power amplifier and the second power amplifier, so that the digital enhancement effect is specifically included:
  • the input signal of the line power amplifier combining circuit causes the input signals of the first power amplifier and the second power amplifier to be changed to achieve a digital enhancement effect.
  • An embodiment of the present invention provides a line power amplifier combining circuit, where the line power amplifier combining circuit includes an out-of-phase modulator, a first power amplifier, a second power amplifier, a first adjusting circuit, a second adjusting circuit, and a hybrid bridge. a circuit, an output circuit, and a passive microwave circuit; wherein the first power amplifier and the second power amplifier are respectively connected to two output ends of the different phase modulator and the first adjustment circuit, Between the second adjustment circuits, the first adjustment circuit and the second adjustment circuit are also respectively connected to two input ends of the hybrid bridge combiner, and the output circuit and the passive microwave circuit are respectively The non-inverting output terminal and the out-of-phase output terminal of the hybrid bridge combiner are connected.
  • the present invention firstly uses a hybrid bridge combiner for a non-isolated combination of a Class-type power amplifier, through the first adjustment circuit, the second adjustment circuit, the output circuit, and the The cooperation of the source microwave circuit makes it possible to increase the efficiency of the two-way power amplifier by using load traction, so that the first power amplifier and the second power amplifier can operate in a high efficiency state, and the line power amplifier combined circuit
  • the first adjustment circuit, the second adjustment circuit, the output circuit, and the passive microwave circuit are designed to be flexible, and a separate bridge isolation end exists in the line power amplifier combination circuit, so that the signal can be in the signal
  • the mismatched portion is coupled to use digital enhancement techniques.
  • FIG. 1 is a circuit block diagram of a typical prior art line power amplifier technology for a heterogeneous combiner
  • Figure 2 is a typical prior art line amplifier for matching hybird bridges. Circuit block diagram of the technology
  • FIG. 3 is a circuit diagram of a line power amplifier combined circuit according to an embodiment of the present invention.
  • FIG. 4 is a specific design diagram of a line power amplifier combining circuit according to an embodiment of the present invention.
  • FIG. 5 is a specific design diagram of another line power amplifier combining circuit according to an embodiment of the present invention.
  • FIG. 6 is a specific design diagram of another line power amplifier combining circuit according to an embodiment of the present invention.
  • FIG. 7 is a schematic diagram of a simulation result according to an embodiment of the present invention.
  • FIG. 8 is a schematic diagram of another simulation result according to an embodiment of the present invention.
  • FIG. 9 is a schematic diagram of still another simulation result according to an embodiment of the present invention.
  • FIG. 10 is still another line power amplifier combining circuit according to an embodiment of the present invention.
  • FIG. 1 is a block diagram of a typical prior art line power amplifier technology for a heterogeneous combiner (i.e., Chireix combiner).
  • the signal s in is connected via input 105 to an out-of-phase modulator 110, which includes two outputs 115 and 116.
  • s in signal intensity is represented as the phase difference are respectively located between 81 and 32 two output signals on the outputs 115 and 116.
  • the outputs are connected to power amplifiers 120 and 130, respectively.
  • Power amplifiers 120 and 130 represent any type of Class B unbalanced amplifier. Therefore, in the out-of-phase modulator 110, two out-of-phase constant envelope signals S i and s 2 are decomposed from the envelope modulation bandpass waveform s in .
  • the outputs of the power amplifiers are combined in a Chireix-type output combining network 150 to form an amplified linear signal.
  • the phase differences of these constant amplitude out-of-phase signals are determined by the out-of-phase modulator 110 such that the result from their vector sum produces an output signal s.
  • the expected range of ut The expected range of ut .
  • power amplifiers 120, 130 are coupled to an output combining network 150, which includes two transmission lines 140, 145 having an electrical length ⁇ /4 and an impedance R, where ⁇ represents the operation of the power amplifier.
  • the wavelength of the center frequency of the band, R is the selected output impedance of the power amplifier that provides maximum power efficiency.
  • the network includes two compensating reactances. That is, capacitor C125 and inductor L135, they are used to The efficient area is expanded to include lower output levels.
  • the transmission line is connected in a connection point 160, and the output 165 outputs the output signal s . 160 ut conducting from the connection point to the load RL170.
  • the output combined network in Figure 1 not only re-inserts the amplitude modulation into the signal, but it also provides dynamic adjustment of the impedance presented to each power amplifier (out-of-phase). This out-of-phase adjustment of the impedance causes the DC power consumption through each active device to decrease as the combined output amplitude decreases, thereby providing a power amplifier when the amplitude of the output signal is near a certain smaller value. It also maintains high efficiency.
  • the embodiment of the present invention provides a line power amplifier combining circuit 300.
  • the line power amplifier combining circuit 300 includes an out-of-phase modulator 301, a first power amplifier 302, a second power amplifier 303, and a first The adjustment circuit 304, the second adjustment circuit 305, the hybrid bridge combiner 306, the output circuit 307, and the passive start wave circuit 308.
  • the first power amplifier 302 and the second power amplifier 303 are respectively connected between the two output ends of the different phase modulator 301 and the first adjustment circuit 304 and the second adjustment circuit 305.
  • the first adjusting circuit 304 and the second adjusting circuit 305 are also respectively connected to two input ends of the hybrid bridge combiner 306, and the output circuit 307 and the passive start wave circuit 308 are respectively It is connected to the non-inverting output end and the out-of-phase output end of the hybrid bridge combiner 306.
  • the first adjustment circuit 304, the second adjustment circuit 305, and the output circuit 307 cooperate with the passive microwave circuit 308 to make the first power amplifier 302 and the second power amplifier 303 When the amplitude of the output signal is less than the first threshold, there is a new efficiency extreme point.
  • s in signal intensity is represented as 3 which are located between the two output signals of the output terminal 301 of phase modulator 8 and s 2 The phase difference.
  • the signals ⁇ 1 and s 2 are respectively amplified by the first power amplifier 302 and the second power amplifier 303, respectively, the phase adjustment and impedance of the first adjustment circuit 304 and the second adjustment circuit 305 are respectively passed.
  • the hybrid bridge combiner 306 enters through the 1st end and the 1st end respectively, and after the combined circuit of the hybrid bridge combiner 306, the in-phase signal in the Line power combiner circuit passes.
  • the output circuit 307 outputs, and due to the presence of the passive microwave circuit 308, the non-in-phase signal is partially or completely reflected back at the non-isolated terminal 3, such that the passive microwave circuit 308 and the first adjustment
  • the passive microwave circuit 308 and the first adjustment When the amplitudes of the output signals of the first power amplifier 302 and the second power amplifier 303 are less than the first threshold, there is a new one under the cooperation of the circuit 304, the second adjustment circuit 305, and the output circuit 307.
  • the efficiency extreme point that is, the first power amplifier and the second power amplifier can maintain a higher efficiency when the amplitude of the output signal is near a certain smaller value.
  • the efficiency of the power amplifier corresponding to the smaller output amplitude is generally lower.
  • the first power amplifier 302 and the first power amplifier 302 can be caused by the cooperation of the passive microwave circuit 308, the output circuit 307, the first adjustment circuit 304, and the second adjustment circuit 305.
  • the amplitude of the output signal of the second power amplifier 303 is less than the first threshold, there is a new efficiency extreme point.
  • the amplifier 302 and the second power amplifier 303 also maintain a higher efficiency when the amplitude of the output signal is near a certain smaller value.
  • the “less than the first threshold” is used to ensure that there is a new efficiency extreme point when the amplitude of the output signal is small.
  • the first threshold is not specifically limited in the embodiment of the present invention.
  • the "new efficiency extreme point” is only a theoretical reference.
  • the actual circuit may not have the extreme point due to the quality factor, etc., but only the efficiency extreme point near the maximum amplitude. .
  • the range is higher than the average design without “new efficiency extreme points”.
  • a Line power combiner circuit 300 for the first time, a Hybrid combiner is used for a non-isolated combination of a Class-type power amplifier, through the first adjustment circuit, the first The adjusting circuit, the cooperation with the passive microwave circuit and the output circuit, so that the efficiency of the two-way power amplifier can be improved by using load traction, so that the first power amplifier and the second power amplifier can be outputted When the amplitude of the signal is near a certain small value, the amplifier can maintain high efficiency.
  • the first adjustment circuit, the second adjustment circuit, the output circuit and the passive microwave circuit are designed flexibly, and there is a separate power in the line power amplifier combination circuit.
  • the bridge isolated end allows coupling of mismatched portions of the signal to use digital enhancement techniques.
  • the passive microwave circuit 308 may specifically include: a microstrip line, wherein an electrical length of the microstrip line is determined by the new efficiency extreme point, and the first adjustment circuit and the second adjustment The circuit is determined.
  • connection of the passive microwave circuit to the out-of-phase output of the hybrid bridge combiner may specifically include:
  • the microstrip line is coupled to a different phase output of the hybrid bridge combiner.
  • the microstrip line may be an open circuit or a grounding.
  • the embodiment of the present invention does not specifically limit this.
  • the design of the first adjustment circuit, the second adjustment circuit, and the output circuit is also particularly important.
  • the design method of these circuits may refer to the circuit A in the prior art as shown in FIG. 2 .
  • the design method of the circuit B and the circuit C is not described in detail in the embodiment of the present invention.
  • FIG. 4 a specific design diagram of a line power amplifier combining circuit is exemplarily shown, wherein the first adjusting circuit 304 is composed of a microstrip line A and a capacitor C, and the second The adjustment circuit 305 is composed of a starter line B and an inductor L.
  • the passive microwave circuit 308 is composed of a microstrip line D, wherein the microstrip line D is open, the microstrip line A, the microstrip line B
  • the first adjusting circuit 304, the second adjusting circuit 305, the output circuit 307 cooperate with the passive start wave circuit 308, so that the When the amplitude of the output signals of the first power amplifier 302 and the second power amplifier 303 is less than the first threshold, there is a new efficiency extreme point, that is, the first power amplifier 302 and the second power amplifier can be made When the amplitude of the output signal of 303 is near a certain small value, the amplifier can maintain high efficiency.
  • the embodiment of the present invention further provides a specific design of a line power amplifier combining circuit, wherein the first adjusting circuit 304 is composed of a microstrip line A and a capacitor C, The second adjustment circuit 305 is composed of a start-up line B and an inductor L.
  • the passive start-up circuit 308 is composed of a start-up line D + a first resistor R1, wherein one end of the first resistor R1 and the microstrip line D Connected, the other end is grounded, and the first resistance is greater than a second threshold such that the microstrip line is approximately open.
  • the second threshold is to ensure that the microstrip line is approximately open after being grounded through the first resistor, and the size of the second threshold is not specifically limited.
  • the line power amplifier combining circuit shown in FIG. 4 and the line power amplifier combining circuit shown in FIG. 5 are different only in the implementation manner of the microstrip line open circuit, and the line power amplifier shown in FIG. 5 is used in the embodiment of the present invention.
  • the combination circuit will not be described again. For details, refer to the description of the line power amplifier combination circuit shown in FIG.
  • the embodiment of the present invention further provides a specific design scheme of the line power amplifier combining circuit, wherein the Line power amplifier combining circuit shown in FIG. 6 and the Line power amplifier shown in FIG.
  • the difference in the combining circuit is only that in the L inc power combining circuit shown in FIG. 6, the passive microwave circuit 308 is specifically grounded by the microstrip line, which is equivalent to the short circuit of the microstrip line.
  • the passive microwave circuit 308 is specifically a microstrip line open circuit.
  • the line amplifier circuit shown in FIG. 6 has a microstrip line.
  • the first adjustment circuit 304, the second adjustment circuit 305, and the output circuit 307 cooperate with the passive microwave circuit 308 to make the first power amplifier 302 and the second power amplifier 303
  • the amplitude of the output signal is less than the first threshold, there is a new efficiency extreme point, that is, the amplitude of the output signals at the first power amplifier 302 and the second power amplifier 303 may be at a certain smaller value.
  • the amplifier can also maintain high efficiency when nearby.
  • the electrical length of the microstrip line involved in FIG. 4, FIG. 5, and FIG. 6 may be the position according to the new efficiency extreme point, and the microstrip in the first adjustment circuit and the second adjustment circuit.
  • the electrical length of the line is determined by the circuit simulation and the actual simulation. The embodiment of the present invention does not specifically limit this, and only two specific design schemes of the line power amplifier combining circuit are given.
  • FIG. 4, FIG. 5, and FIG. 6 has other equivalents, for example, the capacitor C is replaced by a micro-strip line of a certain electrical length, and the like, which is not specifically limited in this embodiment of the present invention.
  • the key is that the equivalent electrical length is the same.
  • the embodiments of the present invention exemplarily give three simulation results, as shown in FIG. 7, FIG. 8, and FIG. 9, respectively. among them,
  • the simulation shown in FIG. 7 is a phase-efficiency diagram obtained by using the circuit block diagram of the line power amplifier technology of the matched hybird bridge in the prior art shown in FIG. 2; the simulation 2 shown in FIG.
  • the simulation shown in Figure 9 is the phase-efficiency map finally simulated by the design of the inappropriate passive microwave circuit based on the simulation 2.
  • Simulation 1 In combination with the circuit block diagram shown in FIG. 2, the first power amplifier and the second power amplifier use an ideal class B power amplifier model; the phase angle of the two out-of-phase signals is relative to the phase angle of the composite signal The angle of complement is the ta, where the ta is scanned from 0 to 90 degrees, as shown in Figure 7, when the out-of-phase output of the hybrid bridge combiner When good isolation matching is achieved, the output impedance of the two power amplifiers does not change with the change of theta, indicating that the load of the two power amplifiers is stable and does not change with the change of the signal. When theta is smaller, it is wasted to the isolated end. The greater the power on the load.
  • the simulation is only a special case under ideal conditions.
  • the reflection coefficient curve and the efficiency curve may not be identical, but the isolation matching principle and effect are not affected.
  • Simulation 2 In combination with the circuit block diagram shown in FIG. 3, the first power amplifier and the second power amplifier use an ideal class B power amplifier model; the phase angle of the two out-of-phase signals is relative to the phase angle of the composite signal.
  • the angle of complement is theta, where theta is scanned from 0 to 90 degrees.
  • the simulation is only a special case under ideal conditions.
  • the reflection coefficient curves may not be exactly the same, but it does not affect Hybird's non-isolated matching and leads to active load traction.
  • Simulation 3 Based on the above simulation 2, the design of the passive microwave circuit is changed. From the simulation results in Figure 9, it can be seen that the design of the inappropriate passive microwave circuit makes non-isolated matching The active load pull has no significant effect on the isolation match of the simulation one.
  • the simulation result of simulation 2 shown in FIG. 8 and the simulation of simulation 3 shown in FIG. The comparison of the results also intuitively reflects that the design of the passive microwave circuit does not necessarily lead to a high efficiency load pulling effect, and the position of the high efficiency region of the specific power amplifier is required, and then the first adjustment circuit 304 is designed.
  • the line power amplifier combining circuit further includes a coupling sampling circuit and a digital domain circuit.
  • the digital domain circuit includes the out-of-phase modulator, the coupled sampling circuit is connected between the out-of-phase output end of the hybrid bridge combiner and the digital domain circuit, and the digital domain circuit The output ends are respectively connected to the first power amplifier and the second power amplifier.
  • the coupled sampling circuit is configured to detect a heterogeneous combination signal in the line power amplifier combining circuit.
  • the digital domain circuit is configured to perform digital preprocessing on signals input to the first power amplifier and the second power amplifier according to the out-of-phase combining signals collected by the coupled sampling circuit, so that Achieve digital enhancements.
  • an embodiment of the present invention further provides a line power amplifier combining circuit 300.
  • the Line power combining circuit 300 includes an out-of-phase modulator 301, a first power amplifier 302, and a second power amplifier 303.
  • the first power amplifier 302 and the second power amplifier 303 are respectively connected between the two output ends of the different phase modulator 301 and the first adjustment circuit 304 and the second adjustment circuit 305.
  • the first adjusting circuit 304 and the second adjusting circuit 305 are also respectively connected to two input ends of the hybrid bridge combiner 306, and the output circuit 307 and the passive start wave circuit 308 are respectively Connected to the non-inverting output end of the hybrid bridge combiner 306 and the out-of-phase output end, the coupled sampling circuit 309 is connected to the different phase of the digital domain circuit 310 and the hybrid bridge combiner 306 Between the outputs, the output of the digital domain circuit 310 is connected to the first power amplifier 302 and the second power amplifier 303, respectively.
  • the signal s in is input through the input of the out-of-phase modulator 301, and the signal strength of s in is represented as two output signals ⁇ 1 and respectively located at the output of the out-of-phase modulator 301.
  • the phase difference between s 2 When the signals ⁇ 1 and s 2 are respectively amplified by the first power amplifier 302 and the second power amplifier 303, respectively, the phase adjustment and impedance of the first adjustment circuit 304 and the second adjustment circuit 305 are respectively passed.
  • the hybrid bridge combiner 306 is entered through the 1st end and the 2nd end respectively, and after the combination of the hybrid bridge combiner 306, the in-phase signal in the Line power combiner circuit passes.
  • the output circuit 307 outputs, and due to the presence of the passive microwave circuit 308, the non-in-phase signal is partially or completely reflected back at the non-isolated end 3, such that the passive microwave circuit 308 and the When the amplitudes of the output signals of the first power amplifier 302 and the second power amplifier 303 are less than the first threshold, the adjustment circuit 304, the second adjustment circuit 305, and the output circuit 307 cooperate
  • the new efficiency extreme point allows the first power amplifier and the second power amplifier to maintain a higher efficiency when the amplitude of the output signal is near a certain smaller value.
  • the coupled sampling circuit 309 collects the out-of-phase combining signals of the two power amplifiers in the line power amplifier combining circuit at the non-isolated terminal 3, and the digital domain circuit 310 is collected according to the coupled sampling circuit 309.
  • the out-of-phase combining signal performs digital pre-processing on signals input to the first power amplifier 302 and the second power amplifier 303 to achieve a digital enhancement effect.
  • the signals input to the first power amplifier 302 and the second power amplifier 303 are digitally preprocessed.
  • the out-of-phase modulator 301 performs signal decomposition.
  • the embodiment of the present invention does not specifically limit the range of the decomposition or the angle of the decomposition.
  • the digital preprocessing of the signals input to the first power amplifier 302 and the second power amplifier 303 according to the out-of-phase combining signals collected by the coupled sampling circuit 309 may further include:
  • the input of the line power amplifier combining circuit can be reduced.
  • the phase angle of the signal If the angle of the input signal decomposition of the line power amplifier combining circuit is larger according to the out-of-phase combining signal collected by the coupling sampling circuit 309, the input of the line power amplifier combining circuit can be reduced. The phase angle of the signal.
  • the signal of 303 is used for digital preprocessing.
  • the two methods correspond to the specific design of different digital domain circuits 310.
  • the method for digitally pre-processing the signals input to the first power amplifier 302 and the second power amplifier 303 corresponds to the specific design of the corresponding digital domain circuit 310, which will not be described in detail in the embodiments of the present invention.
  • the digital domain circuit 310 is configured to digitally preprocess the signals input to the first power amplifier and the second power amplifier according to the out-of-phase combining signals collected by the coupled sampling circuit, so as to achieve Digital enhancement effect.
  • the coupled sampling circuit includes a second resistor, wherein the second resistor is used to adjust a ratio of a voltage and a current entering the coupled sampling circuit.
  • the second resistor is used to adjust a ratio of a voltage and a current entering the coupled sampling circuit.
  • An embodiment of the present invention provides a L i ne power amplifier combining circuit, where the L i ne power amplifier combining circuit includes an out-of-phase modulator, a first power amplifier, a second power amplifier, a first adjusting circuit, a second adjusting circuit, a hybrid bridge combiner, an output circuit, and a passive microwave circuit; wherein the first power amplifier and the second power amplifier are respectively connected to two output ends of the out-of-phase modulator and the first adjustment Between the circuit and the second adjustment circuit, the first adjustment circuit and the second adjustment circuit are also respectively connected to two input ends of the hybrid bridge combiner, the output circuit and the passive microwave The circuit is respectively connected to the non-inverting output end and the out-of-phase output end of the hybrid bridge combiner.
  • the present invention firstly uses a hybrid bridge combiner for a non-isolated combination of a Line-type power amplifier, through the first adjustment circuit, the second adjustment circuit, the output circuit, and the
  • the cooperation of the passive microwave circuit makes it possible to increase the efficiency of the two-way power amplifier by using load traction, that is, when the amplitude of the output signal is near a certain small value, the first power amplifier and the second power amplifier are The power amplifier can also maintain high efficiency.
  • the first adjustment circuit, the second adjustment circuit, the output circuit, and the passive microwave circuit are flexible in design, and There is a separate bridge isolated end in the L i ne amplifier combining circuit, so that the mismatched portion of the signal can be coupled to use digital enhancement techniques.

Landscapes

  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Amplifiers (AREA)
  • Microwave Amplifiers (AREA)

Abstract

本发明实施例提供一种Linc功放合路电路,能够利用负载牵引提高功放的效率,并且设计灵活,存在单独的电桥隔离端。所述Linc功放合路电路包括异相调制器、第一功率放大器、第二功率放大器、第一调整电路、第二调整电路、混合电桥合路器、输出电路、无源微波电路;其中,所述第一功率放大器和所述第二功率放大器分别连接于所述异相调制器的两个输出端与所述第一调整电路、所述第二调整电路之间,所述第一调整电路和所述第二调整电路还分别与混合电桥合路器的两个输入端相连,所述输出电路和所述无源微波电路分别与所述混合电桥合路器的同相输出端、异相输出端相连。本发明适用于无线通信领域。

Description

一种 Line功放合路电路 技术领域
本发明涉及无线通信领域, 尤其涉及一种 Line功放合路电路。 背景技术
Line功放是把一路幅度与相位随时间变化的信号, 分解为两路 等幅异相的信号, 分别经过功率放大器进行合路的一种功放。 所述 Line功放充分利用放大器能够高效率地放大恒包络信号的特点, 釆 用高效的合路方法, 来达到整体功放的高效率。
Line 功放包括釆用 Chireix合路器 (异相合路器) 的 Line 功 放技术和釆用匹配的 hybird 电桥 (混合电桥) 的 Line 功放技术。 现有技术中, 釆用 Chireix合路器的 Line功放技术将在图 1 中更加 详细的描述, 它在异相调制器中将包络调制带通 sin分解为两个异相 的恒定包络信号 8 和 s2, 它们被施加到功率放大器, 功率放大器的 输出在混合型装置中进行组合, 从而恢复包络调制波形。 放大后的 输出信号 s。ut的输出幅度是信号 §1和 s2之间的相移结果, 当信号同 相时, 得到幅度最大值, 而在反相时, 得到幅度最小值。 该混合体 构造通过用补偿电抗网络代替阻抗负载, 得以将高效率的区域扩展 为包括较低输出功率级, 由此保持较高的效率。 但是该合路方法中, 输出组合网络的设计受到较多的限制, 微带线的电气长度限制在一 定数值, 影响了设计的灵活性; 并且因为没有单独的电桥隔离端, 使得无法对信号中失配的部分进行耦合釆样以使用数字增强技术。
现有技术中, 釆用匹配的 hybird 电桥 (混合电桥) 的 Line功 放技术的电路框图如图 2 所示, 该技术与图 1 所示的釆用 Chireix 合路器的 Line功放技术的区别点在于, 图 2 中两个异相的恒定包络 信号 §1和 s2分别被施加到功率放大器 A、 B后, 分别经过电路 A和 电路 B的调制, 然后经过混合电桥合路器输出, A、 B同相的信号经 过电路 C输出, A、 B非同相的信号则经过隔离端 4 消耗在负载上。 该方法虽然有单独的电桥隔离端, 但由于仅仅是单純的合路, 无法 利用负载牵引提高两路功放的效率, 有较多功率浪费在隔离端负载 上。
发明内容
本发明实施例提供一种 L i ne功放合路电路,能够利用负载牵引 提高功放的效率, 并且设计灵活, 存在单独的电桥隔离端, 使得可 以对信号中失配的部分进行耦合釆样以使用数字增强技术。
为达到上述目 的, 本发明实施例釆用如下技术方案:
第一方面, 提供一种 L i ne功放合路电路, 所述 L i n e功放合路 电路包括异相调制器、 第一功率放大器、 第二功率放大器、 第一调 整电路、 第二调整电路、 混合电桥合路器、 输出电路、 无源微波电 路;
其中, 所述第一功率放大器和所述第二功率放大器分别连接于 所述异相调制器的两个输出端与所述第一调整电路、 所述第二调整 电路之间, 所述第一调整电路和所述第二调整电路还分别与混合电 桥合路器的两个输入端相连, 所述输出电路和所述无源微波电路分 别与所述混合电桥合路器的同相输出端、 异相输出端相连;
所述第一调整电路、 所述第二调整电路、 所述输出电路与所述 无源微波电路配合作用, 以使得所述第一功率放大器和所述第二功 率放大器的输出信号的幅度小于第一阈值时, 存在新的效率极值点。
在第一种可能的实现方式中, 结合第一方面, 所述无源微波电 路具体包括:
微带线,其中,所述微带线的电长度由所述新的效率极值点的位 置, 以及所述第一调整电路与所述第二调整电路确定;
所述无源微波电路与所述混合电桥电路器的异相输出端相连具 体包括:
所述微带线与所述混合电桥电路的异相输出端相连。
在第二种可能的实现方式中, 结合第一种可能的实现方式, 所 述微带线还接地。 在第三种可能的实现方式中, 结合第一种可能的实现方式, 所 述 L i ne功放合路电路还包括第一电阻;
所述微带线还与所述第一电阻相连, 所述第一电阻还接地, 其 中, 所述第一电阻的阻值大于第二阈值, 以使得所述微带线近似开 路。
在第四种可能的实现方式中, 结合第一方面或第一种可能的实 现方式,所述 L i ne功放合路电路还包括耦合釆样电路、数字域电路; 其中, 所述数字域电路包含所述异相调制器, 所述耦合釆样电 路连接于所述混合电桥合路器的异相输出端与所述数字域电路之 间, 所述数字域电路的输出端分别与所述第一功率放大器、 所述第 二功率放大器相连;
所述耦合釆样电路,用于检测所述 L i ne功放合路电路中的异相 合路信号;
所述数字域电路, 用于根据所述耦合釆样电路釆集到的所述异 相合路信号, 对输入所述第一功率放大器和所述第二功率放大器的 信号做数字预处理, 以使得达到数字增强效果。
在第五种可能的实现方式中, 结合第四种可能的实现方式, 所 述耦合釆样电路包括第二电阻;
其中, 所述第二电阻用于调节进入所述耦合釆样电路的电压、 电 的配比。
在第六种可能的实现方式中, 根据第四种可能的实现方式或第 五种可能的实现方式, 所述数字域电路, 用于根据所述耦合釆样电 路釆集到的所述异相合路信号, 对输入所述第一功率放大器和所述 第二功率放大器的信号做数字预处理, 以使得达到数字增强效果具 体包括:
根据所述耦合釆样电路釆集到的所述异相合路信号, 调整所述 L i n e功放合路电路的输入信号分解的幅度或夹角, 以使得所述第一 功率放大器和所述第二功率放大器的输入信号发生改变, 以达到数 字增强效果。 在第七种可能的实现方式中, 根据第四种可能的实现方式或第 五种可能的实现方式, 所述数字域电路, 用于根据所述耦合釆样电 路釆集到的所述异相合路信号, 对输入所述第一功率放大器和所述 第二功率放大器的信号做数字预处理, 以使得达到数字增强效果具 体包括:
根据所述耦合釆样电路釆集到的所述异相合路信号, 调整所述
Line功放合路电路的输入信号, 以使得所述第一功率放大器和所述 第二功率放大器的输入信号发生改变, 以达到数字增强效果。
本发明实施例提供一种 Line功放合路电路, 所述 Line功放合 路电路包括异相调制器、 第一功率放大器、 第二功率放大器、 第一 调整电路、 第二调整电路、 混合电桥合路器、 输出电路、 无源微波 电路; 其中, 所述第一功率放大器和所述第二功率放大器分别连接 于所述异相调制器的两个输出端与所述第一调整电路、 所述第二调 整电路之间, 所述第一调整电路和所述第二调整电路还分别与混合 电桥合路器的两个输入端相连, 所述输出电路和所述无源微波电路 分别与所述混合电桥合路器的同相输出端、 异相输出端相连。
基于上述实施例的描述, 本发明首次将混合电桥合路器用于 Line类功放的非隔离合路, 通过所述第一调整电路、 所述第二调整 电路、 所述输出电路与所述无源微波电路的配合作用, 使得可以利 用负载牵引提高两路功放的效率, 即可使所述第一功率放大器和所 述第二功率放大器工作在高效率状态, 同时所述 Line功放合路电路 中, 所述第一调整电路、 所述第二调整电路、 所述输出电路与所述 无源微波电路设计灵活, 并且该 Line功放合路电路中存在单独的电 桥隔离端, 使得可以对信号中失配的部分进行耦合釆样以使用数字 增强技术。
附图说明
图 1为典型的现有技术中釆用异相合路器的 Line功放技术的电 路框图;
图 2为典型的现有技术中釆用匹配的 hybird电桥的 Line功放 技术的电路框图;
图 3为本发明实施例提供的一种 Line功放合路电路;
图 4为本发明实施例提供的一种 Line功放合路电路的具体设计 图;
图 5为本发明实施例提供的另一种 Line功放合路电路的具体设 计图;
图 6为本发明实施例提供的另一种 Line功放合路电路的具体设 计图;
图 7为本发明实施例提供的一种仿真结果示意图;
图 8为本发明实施例提供的另一种仿真结果示意图;
图 9为本发明实施例提供的又一种仿真结果示意图;
图 10为本发明实施例提供的又一种 Line功放合路电路。
具体实施方式
图 1 是典型的现有技术中釆用异相合路器 (即, Chireix 合路 器) 的 Line 功放技术的电路框图。 信号 sin经由输入端 105 连接到 异相调制器 110, 所述异相调制器 110 包括两个输出端 115和 116。 sin的信号强度表示为分别位于输出端 115和 116上的两个输出信号 81和 32之间的相位差。 如图 1 所示, 各输出端分别连接到功率放大 器 120和 130。 功率放大器 120和 130代表任何类型的 B类不平衡 放大器。 因此, 在异相调制器 110 中, 从包络调制带通波形 sin分解 出两个异相的恒定包络信号 S i和 s2。在 Chireix型输出组合网络 150 中将功率放大器的输出进行组合以形成放大的线性信号。 这些恒定 幅度的异相信号的相位差由异相调制器 110 确定, 以使得来自它们 的向量总和的结果产生输出信号 s。ut的期望幅度。
如图 1所示, 功率放大器 120、 130连接到输出组合网络 150, 该网络 150 包括具有电气长度 λ/4 和阻抗 R 的两路传输线路 140、 145, 其中 λ表示功率放大器工作时所处的频带的中心频率的波长, R 是提供最大功率效率的功率放大器的选定输出阻抗。 此外, 该网 络包括两个补偿电抗。 即电容器 C125 和电感器 L135, 他们用于将 高效率的区域扩展为包括较低输出级。 所述传输线路在连接点 160 中进行连接, 输出端 165 将所述输出信号 sut的从连接点 160传导 到负载 RL170。 变换后的负载 RJ70等于所有功率放大器的最佳负载 并联, 即 RL=R/2。
图 1 中的输出组合网络不仅将幅度调制重新插入到信号中, 而 且它还提供对呈献给每个功率放大器 (异相) 的阻抗的动态调整。 阻抗的这种异相调整使得通过每个有源设备的直流功耗随着组合后 的输出幅度的减小而减小, 由此在输出信号的幅度在某个较小值的 附近时, 功放也能保持较高效率。
实施例一、
本发明实施例提供一种 Line功放合路电路 300, 具体如图 3所 示, 所述 Line功放合路电路 300 包括异相调制器 301、 第一功率放 大器 302、 第二功率放大器 303、 第一调整电路 304、 第二调整电路 305、 混合电桥合路器 306、 输出电路 307、 无源啟波电路 308。
其中, 所述第一功率放大器 302和所述第二功率放大器 303分 别连接于所述异相调制器 301 的两个输出端与所述第一调整电路 304、 所述第二调整电路 305之间, 所述第一调整电路 304和所述第 二调整电路 305还分别与所述混合电桥合路器 306 的两个输入端相 连, 所述输出电路 307 和所述无源 啟波电路 308 分别与所述混合电 桥合路器 306 的同相输出端、 异相输出端相连。
所述第一调整电路 304、 所述第二调整电路 305、 所述输出电路 307 与所述无源微波电路 308 配合作用, 以使得所述第一功率放大 器 302 和所述第二功率放大器 303 的输出信号的幅度小于第一阈值 时, 存在新的效率极值点。
具体的, 如图 3所示, 信号 Sin经由所述异相调制器 301 的输入 端输入, sin的信号强度表示为分别位于异相调制器 301 输出端的 两个输出信号 8 和 s2之间的相位差。当信号 §1和 s2分别经过所述第 一功率放大器 302、 所述第二功率放大器 303 的放大, 再分别经过 所述第一调整电路 304、 所述第二调整电路 305 的相位调整和阻抗 匹配后, 再分别经过 1 端和 1 端进入所述混合电桥合路器 306, 经 过所述混合电桥合路器 306 的合路后, 所述 Line功放合路电路中的 同相信号经过所述输出电路 307输出, 而由于无源微波电路 308 的 存在, 非同相的信号则在非隔离端 3 处部分或全部被反射回去, 使 得在所述无源微波电路 308 与所述第一调整电路 304、 所述第二调 整电路 305、 所述输出电路 307 的配合作用下, 所述第一功率放大 器 302 和所述第二功率放大器 303 的输出信号的幅度小于第一阈值 时, 存在新的效率极值点, 即可使所述第一功率放大器和所述第二 功率放大器在输出信号的幅度在某个较小值的附近时, 功放也能保 持较高效率。
需要说明的是,在现有的釆用匹配的混合电桥的 Line功放技术 中, 因为仅在功率放大器输出信号的幅度为最大幅度值附近的某个 值时存在一个效率极值点, 所以所述功率放大器除了在最大幅度点 附近的输出幅度点时对应的功放的效率较高之外, 输出幅度较小点 对应的功放的效率一般较低。 而本发明中, 通过所述无源微波电路 308、 所述输出电路 307与所述第一调整电路 304、 所述第二调整电 路 305 的配合作用下, 可以使得所述第一功率放大器 302 和所述第 二功率放大器 303 的输出信号的幅度小于第一阈值时, 存在新的效 率极值点。 进而, 因为存在新的效率极值点, 所以在所述新的效率 极值点与所述最大幅度点附近处的效率极值点之间存在一个较高效 率的区域,使得所述第一功率放大器 302和所述第二功率放大器 303 在输出信号的幅度在某个较小值的附近时, 功放也能保持较高效率。
其中, 所述 "小于第一阈值" 是为了保证在输出信号的幅度较 小时也能存在新的效率极值点, 本发明实施例对所述第一阈值不作 具体限定。
需要说明的是, 所述 "新的效率极值点" 仅是理论的提法, 实 际电路由于品质因数等原因, 可能不存在该极值点, 而只存在最大 幅度附近处的效率极值点。 但一般情况下会存在该 "新的效率极值 点" 所导致的效率曲线的一个 "上凸" 或 "拱起", 使得效率在较大 范围内高于普通的没有 "新的效率极值点" 的设计。
本发明实施例所述的一种 Line 功放合路电路 300, 首次将 Hybrid combiner (混合电桥合路器) 用于 Line 类功放的非隔离合 路, 通过所述第一调整电路、 所述第二调整电路、 与所述无源微波 电路、 所述输出电路的配合作用, 使得可以利用负载牵引提高两路 功放的效率, 即可使所述第一功率放大器和所述第二功率放大器在 输出信号的幅度在某个较小值的附近时, 功放也能保持较高效率。 同时所述 Line功放合路电路中, 所述第一调整电路、 所述第二调整 电路、 所述输出电路与所述无源微波电路设计灵活, 并且该 Line功 放合路电路中存在单独的电桥隔离端, 使得可以对信号中失配的部 分进行耦合釆样以使用数字增强技术。
特别的, 所述无源微波电路 308具体可以包括: 微带线, 其中 所述微带线的电长度由所述新的效率极值点, 以及所述第一调整电 路与所述第二调整电路确定。
所述无源微波电路与混合电桥合路器的异相输出端相连具体可 以包括:
所述微带线与混合电桥合路器的异相输出端相连。
其中, 所述微带线可以是开路, 也可以接地, 本发明实施例对 此不作具体限定。
需要说明的是, 所述第一调整电路、 所述第二调整电路、 所述 输出电路的设计也尤为重要, 但是这些电路的设计方法可参考如图 2所示的现有技术中电路 A、 电路 B、 电路 C的设计方法, 本发明实 施例对此不再赘述。
具体的, 如图 4所示, 这里示例性的给出一种 Line功放合路电 路的具体设计图, 其中, 所述第一调整电路 304 由微带线 A和电容 C构成, 所述第二调整电路 305 由 啟带线 B与电感 L构成, 所述无 源微波电路 308 由微带线 D构成, 其中, 所述微带线 D开路, 所述 微带线 A、 所述微带线 B、 所述微带线 D的电长度分别为 δ 、 λ /4 + δ 、 1ί* λ /2 + λ /4_ δ , 其中, 0 δ λ /4 , k = 0, 1, 2, 3, … 。 在如图 4所示的 Line功放合路电路中,所述第一调整电路 304、 所述第二调整电路 305、 所述输出电路 307与所述无源啟波电路 308 配合作用,使得所述第一功率放大器 302和所述第二功率放大器 303 的输出信号的幅度小于第一阈值时, 存在新的效率极值点, 即可以 使得在所述第一功率放大器 302 和所述第二功率放大器 303 的输出 信号的幅度在某个较小值的附近时, 功放也能保持较高效率。
可选的, 如图 5所示, 本发明实施例还给出一种 Line功放合路 电路的具体设计方案, 其中, 所述第一调整电路 304 由微带线 A和 电容 C构成, 所述第二调整电路 305 由 啟带线 B与电感 L构成, 所 述无源啟波电路 308 由 啟带线 D +第一电阻 R1 构成, 其中, 所述第 一电阻 R1 的一端与微带线 D相连, 另一端接地, 所述第一电阻大于 第二阈值, 以使得所述微带线近似开路。
其中, 所述微带线 A、 所述微带线 B、 所述微带线 D的电长度分 别为 δ 、 λ /4 + δ 、 k* λ /2 + λ /4- δ , 其中, 0 δ λ /4 , k = 0, 1, 2, 3, ...。
需要说明的是, 所述第二阈值是为了保证所述微带线通过所述 第一电阻接地后可以近似开路, 对所述第二阈值的大小不作具体限 定。
图 4所示的 Line功放合路电路和图 5所示的 Line功放合路电 路仅是在微带线开路的实现方式上有所不同, 本发明实施例对所述 图 5所示的 Line功放合路电路就不再赘述, 具体可参考图 4所示的 Line功放合路电路的描述。
可选的, 如图 6所示, 本发明实施例还给出一种 Line功放合路 电路的具体设计方案, 其中, 图 6所示的 Line功放合路电路中与图 4 所示的 Line 功放合路电路的区别仅在于, 在图 6 所示的 L inc 功 放合路电路中, 无源微波电路 308 具体为微带线接地, 相当于微带 线短路。 而图 4所示的 L i nc功放合路电路中, 无源微波电路 308具 体为微带线开路, 当然, 因为电路设计的改变, 图 6所示的 Line功 放合路电路中, 微带线 A、 微带线 B、 微带线 D的电长度也发生改变, 分别为 δ '、 λ /4 + δ '、 k* λ /2 + λ /4- δ ', 其中, 0 δ ' λ /4 , k = 0, 1, 2, 3, ...。
其中, 所述第一调整电路 304、 所述第二调整电路 305、 所述输 出电路 307 与所述无源微波电路 308 配合作用, 使得所述第一功率 放大器 302 和所述第二功率放大器 303 的输出信号的幅度小于第一 阈值时, 存在新的效率极值点, 即可以使得在所述第一功率放大器 302 和所述第二功率放大器 303 的输出信号的幅度在某个较小值的 附近时, 功放也能保持较高效率。
需要说明的是, 图 4、 图 5、 图 6 中所涉及的微带线的电长度可 以是根据所述新的效率极值点的位置, 以及第一调整电路与第二调 整电路中微带线的电长度, 经过电路仿真以及实际模拟后确定的, 本发明实施例对此不作具体限定, 仅给出 Line功放合路电路的两种 具体设计方案。
需要说明的是, 图 4、 图 5、 图 6给出的电路还有其它的等效形 式, 比如电容 C 用某一电长度的微带线替换等, 本发明实施例对此 不作具体限定, 关键在于等效的电长度一致即可。
针对上述实施例的描述, 本发明实施例示例性的给出三种仿真 结果, 分别如图 7、 图 8、 图 9所示。 其中,
图 7 所示的仿真一为利用图 2 所示的现有技术中釆用匹配的 hybird电桥的 Line功放技术的电路框图仿真得出的相位-效率图; 图 8所示的仿真二为利用图 3所示的本发明提供的 Line功放合 路电路仿真得出的相位 -效率图;
图 9 所示的仿真三为在仿真二的基础上, 不恰当的无源微波电 路的设计最终仿真出的相位 -效率图。
下面对这三种仿真分别进行说明:
仿真一: 结合图 2 所示的电路框图, 所述第一功率放大器和所 述第二功率放大器釆用理想的 B 类功率放大器模型; 两路异相信号 的相位角相对于合成信号相位角的夹角的补角为 the t a,其中, the t a 从 0度扫描到 90度, 如图 7所示, 当混合电桥合路器的异相输出端 实现了 良好的隔离匹配时, 两路功放的输出阻抗不随 theta 的变化 而变化, 说明两路功放的负载是稳定的, 不会随着信号的变化而变 化, 当 theta越小时, 浪费到隔离端负载上的功率越大。
需要说明的是, 该仿真仅是一个理想状态下的特例, 对于实际 功率放大器以及其它类型的功率放大器, 反射系数曲线和效率曲线 可能不完全相同, 但不影响隔离匹配原理和效果的普遍性。
仿真二: 结合图 3所示的电路框图, 所述第一功率放大器和所 述第二功率放大器釆用理想的 B 类功率放大器模型; 两路异相信号 的相位角相对于合成信号相位角的夹角的补角为 theta,其中, theta 从 0度扫描到 90度, 如图 8所示, 当混合电桥合路器的异相输出端 实现非隔离匹配时, 左侧的仿真结果显示, 两路功放的输出阻抗随 着 theta 的变化而变化, 一部分 theta 张角对应的阻抗曲线更加接 近理想功放的高效率区域( 实轴及其附近), 说明两路功放的负载是 不稳定的, 而右侧的仿真结果显示, 当 theta在 20度附近时, 出现 新的效率极值点, theta 为 20-90 度之间的值时, 功放的效率便一 直处于 70%左右, 说明相互之间的负载牵引作用使得功率放大器工 作在高效率状态。
同样, 需要说明的是该仿真仅是一个理想状态下的特例, 对于 实际的功率放大器以及其它类型的功率放大器, 反射系数曲线可能 不完全相同, 但不影响 Hybird非隔离匹配以及导致有源负载牵引的 原理和效果的普遍性。
通过图 7所示的仿真一的仿真结果和图 8所示的仿真二的仿真 结果的对比, 也直观的反映出本发明实施例中的 Line功放合路电路 可以利用负载牵引提高功放的效率。
仿真三: 在上述仿真二的基础上, 将所述无源微波电路的设计 进行了一定变化, 从图 9 的仿真结果可以看到, 不恰当的无源微波 电路的设计, 使得非隔离匹配产生的有源负载牵引相对于仿真一的 隔离匹配并没有明显的效果。
通过图 8所示的仿真二的仿真结果和图 9所示的仿真三的仿真 结果的对比, 也直观的反映出无源微波电路的设计不必然导致高效 率的负载牵引效果, 需要根据具体功率放大器的高效率区域的位置, 然后设计所述第一调整电路 304、 所述第二调整电路 305、 以及无源 微波电路 308 和输出电路 307 的对应设计, 使得无源微波电路 308 的非隔离匹配导致的有源负载牵引将所述第一功率放大器 302 和所 述第二功率放大器 303牵引到高效率的工作状态。
进一步的, 所述 Line功放合路电路还包括耦合釆样电路, 数字 域电路。
其中, 所述数字域电路包含所述异相调制器、 所述耦合釆样电 路连接于所述混合电桥合路器的异相输出端与所述数字域电路之 间, 所述数字域电路的输出端分别与所述第一功率放大器、 所述第 二功率放大器相连。
所述耦合釆样电路,用于检测所述 Line功放合路电路中的异相 合路信号。
所述数字域电路, 用于根据所述耦合釆样电路釆集到的所述异 相合路信号, 对输入所述第一功率放大器和所述第二功率放大器的 信号做数字预处理, 以使得达到数字增强效果。
具体的, 如图 10所示, 本发明实施例还提供一种 Line功放合 路电路 300, 所述 Line 功放合路电路 300 包括异相调制器 301、 第 一功率放大器 302、 第二功率放大器 303、 第一调整电路 304、 第二 调整电路 305、 混合电桥合路器 306、 输出电路 307、 无源 波电路 308、 耦合釆样电路 309、 数字域电路 310。
其中, 所述第一功率放大器 302和所述第二功率放大器 303分 别连接于所述异相调制器 301 的两个输出端与所述第一调整电路 304、 所述第二调整电路 305之间, 所述第一调整电路 304和所述第 二调整电路 305还分别与所述混合电桥合路器 306 的两个输入端相 连, 所述输出电路 307 和所述无源 啟波电路 308 分别与所述混合电 桥合路器 306 的同相输出端、 异相输出端相连, 所述耦合釆样电路 309 连接于所述数字域电路 310 与所述混合电桥合路器 306 的异相 输出端之间, 所述数字域电路 310 的输出端分别与所述第一功率放 大器 302、 所述第二功率放大器 303相连。
具体的, 如图 10所示, 信号 sin经由所述异相调制器 301 的输 入端输入, sin的信号强度表示为分别位于所述异相调制器 301 输 出端的两个输出信号 §1和 s2之间的相位差。当信号 §1和 s2分别经过 所述第一功率放大器 302、 所述第二功率放大器 303 的放大, 再分 别经过所述第一调整电路 304、 所述第二调整电路 305 的相位调整 和阻抗匹配后,再分别经过 1端和 2端进入所述混合电桥合路器 306, 经过所述混合电桥合路器 306 的合路后, 所述 Line功放合路电路中 的同相信号经过所述输出电路 307 输出, 而由于所述无源微波电路 308 的存在, 非同相的信号则在非隔离端 3 处部分或全部被反射回 去, 使得在所述无源微波电路 308 与所述第一调整电路 304、 所述 第二调整电路 305、 所述输出电路 307 的配合作用下, 所述第一功 率放大器 302 和所述第二功率放大器 303 的输出信号的幅度小于第 一阈值时, 存在新的效率极值点, 即可使所述第一功率放大器和所 述第二功率放大器在输出信号的幅度在某个较小值的附近时, 功放 也能保持较高效率。
同时,所述耦合釆样电路 309在非隔离端 3处釆集该 Line功放 合路电路中两路功放的异相合路信号, 所述数字域电路 310 根据所 述耦合釆样电路 309 釆集到的所述异相合路信号, 对输入所述第一 功率放大器 302 和所述第二功率放大器 303 的信号做数字预处理, 以使得达到数字增强效果。
需要说明的是, 所述根据所述耦合釆样电路 309釆集到的所述 异相合路信号, 对输入所述第一功率放大器 302 和所述第二功率放 大器 303的信号做数字预处理具体可以包括:
根据所述耦合釆样电路 309釆集到的所述异相合路信号, 调整 所述 Line功放合路电路的输入信号分解的幅度或夹角, 进而使得所 述第一功率放大器 302 和所述第二功率放大器 303 的输入信号发生 改变, 以达到数字增强效果, 进一步提高所述功放合路电路的效率。 例如:
若根据所述耦合釆样电路 309釆集到的所述异相合路信号分析 所述 Line功放合路电路的输入信号分解的夹角较大, 则所述异相调 制器 301 在进行信号分解时, 可以降低分解的幅度或减小分解的夹 角, 本发明实施例对此不作具体限定。
或者
所述根据所述耦合釆样电路 309釆集到的所述异相合路信号, 对输入所述第一功率放大器 302 和所述第二功率放大器 303 的信号 做数字预处理具体还可以包括:
根据所述耦合釆样电路 309釆集到的所述异相合路信号, 调整 所述 Line功放合路电路的输入信号, 进而使得所述第一功率放大器 302 和所述第二功率放大器 303 的输入信号发生改变, 以达到数字 增强效果, 进一步提高所述功放合路电路的效率。 例如:
若根据所述耦合釆样电路 309釆集到的所述异相合路信号分析 所述 Line功放合路电路的输入信号分解的夹角较大, 则可以减小所 述 Line功放合路电路的输入信号的相位角。
需要说明的是, 上述仅是示例性的给出两种根据所述耦合釆样 电路 309 釆集到的所述异相合路信号, 对输入所述第一功率放大器 302 和所述第二功率放大器 303 的信号做数字预处理的方法, 此两 种方法对应不同的数字域电路 310 的具体设计, 当然, 还可能存在 其它根据所述耦合釆样电路 309 釆集到的所述异相合路信号, 对输 入所述第一功率放大器 302 和所述第二功率放大器 303 的信号做数 字预处理的方法, 对应相应的数字域电路 310 的具体设计, 本发明 实施例对此不再赘述, 仅说明所述数字域电路 310 用于根据所述耦 合釆样电路釆集到的所述异相合路信号, 对输入所述第一功率放大 器和所述第二功率放大器的信号做数字预处理, 以使得达到数字增 强效果。
具体的, 所述耦合釆样电路包括第二电阻, 其中, 所述第二电 阻用于调节进入所述耦合釆样电路的电压、 电流的配比。 当然, 也可能通过其它的电路设计调节进入所述耦合釆样电路 的电压、 电流的配比, 本发明实施例对此不作具体限定。
需要说明的是, 上述基于理想 B类放大器的实施例的描述, 同 样适用于实际的 B类或非 B类放大器的设计。
本发明实施例提供一种 L i ne功放合路电路, 所述 L i ne功放合 路电路包括异相调制器、 第一功率放大器、 第二功率放大器、 第一 调整电路、 第二调整电路、 混合电桥合路器、 输出电路、 无源微波 电路; 其中, 所述第一功率放大器和所述第二功率放大器分别连接 于所述异相调制器的两个输出端与所述第一调整电路、 所述第二调 整电路之间, 所述第一调整电路和所述第二调整电路还分别与混合 电桥合路器的两个输入端相连, 所述输出电路和所述无源微波电路 分别与所述混合电桥合路器的同相输出端、 异相输出端相连。
基于上述实施例的描述, 本发明首次将混合电桥合路器用于 L i n e类功放的非隔离合路, 通过所述第一调整电路、 所述第二调整 电路、 所述输出电路与所述无源微波电路的配合作用, 使得可以利 用负载牵引提高两路功放的效率, 即可使所述第一功率放大器和所 述第二功率放大器在输出信号的幅度在某个较小值的附近时, 功放 也能保持较高效率, 同时所述 L i n e功放合路电路中, 所述第一调整 电路、 所述第二调整电路、 所述输出电路与所述无源微波电路设计 灵活, 并且该 L i ne功放合路电路中存在单独的电桥隔离端, 使得可 以对信号中失配的部分进行耦合釆样以使用数字增强技术。

Claims

权 利 要 求 书
1、 一种 L i ne功放合路电路, 其特征在于:
所述 L i ne功放合路电路包括异相调制器、 第一功率放大器、 第 二功率放大器、 第一调整电路、 第二调整电路、 混合电桥合路器、 输 出电路、 无源微波电路;
其中,所述第一功率放大器和所述第二功率放大器分别连接于所 述异相调制器的两个输出端与所述第一调整电路、 所述第二调整电路 之间, 所述第一调整电路和所述第二调整电路还分别与混合电桥合路 器的两个输入端相连, 所述输出电路和所述无源微波电路分别与所述 混合电桥合路器的同相输出端、 异相输出端相连;
所述第一调整电路、 所述第二调整电路、 所述输出电路与所述无 源微波电路配合作用, 以使得所述第一功率放大器和所述第二功率放 大器的输出信号的幅度小于第一阈值时, 存在新的效率极值点。
2、 根据权利要求 1所述的 L i ne功放合路电路, 其特征在于, 所 述无源微波电路具体包括:
微带线,其中, 所述微带线的电长度由所述新的效率极值点的位 置, 以及所述第一调整电路与所述第二调整电路确定;
所述无源微波电路与所述混合电桥电路器的异相输出端相连具 体包括:
所述微带线与所述混合电桥电路的异相输出端相连。
3、 根据权利要求 2所述的 L i ne功放合路电路, 其特征在于, 所 述微带线还接地。
4、 根据权利要求 2所述的 L i ne功放合路电路, 其特征在于, 所 述 L i ne功放合路电路还包括第一电阻;
所述微带线还与所述第一电阻相连,所述第一电阻还接地,其中, 所述第一电阻的阻值大于第二阈值, 以使得所述微带线近似开路。
5、根据权利要求 1或 2所述的 L i ne功放合路电路,其特征在于, 所述 L i ne功放合路电路还包括耦合釆样电路、 数字域电路;
其中, 所述数字域电路包含所述异相调制器, 所述耦合釆样电路 连接于所述混合电桥合路器的异相输出端与所述数字域电路之间, 所 述数字域电路的输出端分别与所述第一功率放大器、 所述第二功率放 大器相连;
所述耦合釆样电路, 用于检测所述 L i ne功放合路电路中的异相 合路信号;
所述数字域电路,用于根据所述耦合釆样电路釆集到的所述异相 合路信号, 对输入所述第一功率放大器和所述第二功率放大器的信号 做数字预处理, 以使得达到数字增强效果。
6、 根据权利要求 5所述的 L i ne功放合路电路, 其特征在于, 所 述耦合釆样电路包括第二电阻;
其中, 所述第二电阻用于调节进入所述耦合釆样电路的电压、 电 ¾ u的配比。
7、根据权利要求 5或 6所述的 L i ne功放合路电路,其特征在于, 所述数字域电路, 用于根据所述耦合釆样电路釆集到的所述异相合路 信号, 对输入所述第一功率放大器和所述第二功率放大器的信号做数 字预处理, 以使得达到数字增强效果具体包括:
根据所述耦合釆样电路釆集到的所述异相合路信号, 调整所述 L i ne 功放合路电路的输入信号分解的幅度或夹角, 以使得所述第一 功率放大器和所述第二功率放大器的输入信号发生改变, 以达到数字 增强效果。
8、根据权利要求 5或 6所述的 L i ne功放合路电路,其特征在于, 所述数字域电路, 用于根据所述耦合釆样电路釆集到的所述异相合路 信号, 对输入所述第一功率放大器和所述第二功率放大器的信号做数 字预处理, 以使得达到数字增强效果具体包括:
根据所述耦合釆样电路釆集到的所述异相合路信号, 调整所述 L i ne 功放合路电路的输入信号, 以使得所述第一功率放大器和所述 第二功率放大器的输入信号发生改变, 以达到数字增强效果。
PCT/CN2013/086437 2013-11-01 2013-11-01 一种Linc功放合路电路 WO2015062081A1 (zh)

Priority Applications (2)

Application Number Priority Date Filing Date Title
PCT/CN2013/086437 WO2015062081A1 (zh) 2013-11-01 2013-11-01 一种Linc功放合路电路
CN201380004307.2A CN104272584B (zh) 2013-11-01 2013-11-01 一种Linc功放合路电路

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
PCT/CN2013/086437 WO2015062081A1 (zh) 2013-11-01 2013-11-01 一种Linc功放合路电路

Publications (1)

Publication Number Publication Date
WO2015062081A1 true WO2015062081A1 (zh) 2015-05-07

Family

ID=52162408

Family Applications (1)

Application Number Title Priority Date Filing Date
PCT/CN2013/086437 WO2015062081A1 (zh) 2013-11-01 2013-11-01 一种Linc功放合路电路

Country Status (2)

Country Link
CN (1) CN104272584B (zh)
WO (1) WO2015062081A1 (zh)

Families Citing this family (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN109687828B (zh) * 2019-02-28 2023-12-19 清华大学 一种射频功率放大器及基站
CN110011623A (zh) * 2019-03-28 2019-07-12 杭州电子科技大学温州研究院有限公司 一种双频带射频异向功率放大器
CN113131963A (zh) * 2019-12-31 2021-07-16 深圳市大富科技股份有限公司 一种补偿电路以及一种通信电路

Citations (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US6930547B2 (en) * 2002-08-09 2005-08-16 Andrew Corporation Linearizing LINC amplifiers using pre-distortion
CN1833358A (zh) * 2003-03-28 2006-09-13 安德鲁公司 具有输出混合耦合器的Doherty放大器
US7313416B1 (en) * 2004-09-01 2007-12-25 Rockwell Collins, Inc. Scalable power amplifier
CN101427460A (zh) * 2006-04-21 2009-05-06 艾利森电话股份有限公司 与linc技术结合的输出网络
CN101651459A (zh) * 2009-09-15 2010-02-17 电子科技大学 高效率线性linc发射机
CN101729079A (zh) * 2008-10-13 2010-06-09 电子科技大学 一种linc发射机

Family Cites Families (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US6054896A (en) * 1998-12-17 2000-04-25 Datum Telegraphic Inc. Controller and associated methods for a linc linear power amplifier
US6710650B1 (en) * 2002-09-30 2004-03-23 Nortel Networks Limited Amplifier switching

Patent Citations (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US6930547B2 (en) * 2002-08-09 2005-08-16 Andrew Corporation Linearizing LINC amplifiers using pre-distortion
CN1833358A (zh) * 2003-03-28 2006-09-13 安德鲁公司 具有输出混合耦合器的Doherty放大器
US7313416B1 (en) * 2004-09-01 2007-12-25 Rockwell Collins, Inc. Scalable power amplifier
CN101427460A (zh) * 2006-04-21 2009-05-06 艾利森电话股份有限公司 与linc技术结合的输出网络
CN101729079A (zh) * 2008-10-13 2010-06-09 电子科技大学 一种linc发射机
CN101651459A (zh) * 2009-09-15 2010-02-17 电子科技大学 高效率线性linc发射机

Also Published As

Publication number Publication date
CN104272584B (zh) 2017-06-20
CN104272584A (zh) 2015-01-07

Similar Documents

Publication Publication Date Title
CN109327191B (zh) 四路多尔蒂放大器及移动通信基站
CN103490733B (zh) 一种频率比1.25至2.85的双频带Doherty功率放大器
US8289085B2 (en) Amplifier circuit
KR101731321B1 (ko) 도허티 증폭기에서 효율을 향상시키기 위한 장치 및 방법
US20150070094A1 (en) Doherty power amplifier with coupling mechanism independent of device ratios
WO2017179000A1 (en) Inverse class-f power amplifier
WO2015062081A1 (zh) 一种Linc功放合路电路
CN105556833B (zh) 具有附加的延迟元件的多赫蒂放大器
JP5829885B2 (ja) バラン
CN109302151B (zh) 补偿线的电长度确定方法及Doherty功率放大器
EP3396856A1 (en) Push-pull amplification systems and methods
CN105471398A (zh) 一种功率放大器电路及功率放大器
JP5921482B2 (ja) ドハティ型増幅器
Bogusz et al. A waveform-engineered outphasing RFPA using a broadband balun combiner
Andersson et al. A 0.85–2.7 GHz two-cell distributed GaN power amplifier designed for high efficiency at 1-dB compression
KR20110033383A (ko) 클래스 f 및 인버스 클래스 f 도허티 증폭기
JP5390495B2 (ja) 高周波増幅器
CN105474534B (zh) 一种基于异相相位调制功放的功率放大方法以及设备
WO2020107390A1 (zh) 功率放大器电路
CN102265506B (zh) 陶赫蒂Doherty电路、多路陶赫蒂Doherty电路和基站设备
Mahin et al. A 3.1 w high gain 51% fractional bandwidth GaN HEMT power amplifier design for far-field wireless power transfer (WPT) applications
JP7264327B2 (ja) インピーダンス整合回路及びインピーダンス整合方法
KR100516035B1 (ko) 임의의 전기적 길이를 갖는 도허티 증폭기의 전력결합구조를 위한 전력 결합 방법
CN112968672B (zh) 一种对称Doherty功放结构及射频收发机
Rawat et al. Load-pull assisted cad design of inverted Doherty Amplifier without quarter-wave transformer

Legal Events

Date Code Title Description
121 Ep: the epo has been informed by wipo that ep was designated in this application

Ref document number: 13896831

Country of ref document: EP

Kind code of ref document: A1

NENP Non-entry into the national phase

Ref country code: DE

122 Ep: pct application non-entry in european phase

Ref document number: 13896831

Country of ref document: EP

Kind code of ref document: A1