WO2015030524A1 - Procédé et dispositif permettant de détecter un signal de synchronisation montant à chaque étape dans un système d'accès sans fil prenant en charge une bande de hautes fréquences - Google Patents

Procédé et dispositif permettant de détecter un signal de synchronisation montant à chaque étape dans un système d'accès sans fil prenant en charge une bande de hautes fréquences Download PDF

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Publication number
WO2015030524A1
WO2015030524A1 PCT/KR2014/008071 KR2014008071W WO2015030524A1 WO 2015030524 A1 WO2015030524 A1 WO 2015030524A1 KR 2014008071 W KR2014008071 W KR 2014008071W WO 2015030524 A1 WO2015030524 A1 WO 2015030524A1
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Prior art keywords
detection filter
base station
rach
detection
signal
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PCT/KR2014/008071
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English (en)
Korean (ko)
Inventor
김기태
이길봄
정재훈
김진민
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엘지전자 주식회사
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Priority to JP2016538858A priority Critical patent/JP2016538791A/ja
Priority to US14/906,960 priority patent/US9680682B2/en
Priority to EP14839221.0A priority patent/EP3041300B1/fr
Priority to KR1020167000812A priority patent/KR20160048757A/ko
Priority to CN201480047432.6A priority patent/CN105493582A/zh
Publication of WO2015030524A1 publication Critical patent/WO2015030524A1/fr

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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2647—Arrangements specific to the receiver only
    • H04L27/2655—Synchronisation arrangements
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2647—Arrangements specific to the receiver only
    • H04L27/2655—Synchronisation arrangements
    • H04L27/2662—Symbol synchronisation
    • H04L27/2663—Coarse synchronisation, e.g. by correlation
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L5/00—Arrangements affording multiple use of the transmission path
    • H04L5/0001—Arrangements for dividing the transmission path
    • H04L5/0003—Two-dimensional division
    • H04L5/0005—Time-frequency
    • H04L5/0007—Time-frequency the frequencies being orthogonal, e.g. OFDM(A), DMT
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L7/00—Arrangements for synchronising receiver with transmitter
    • H04L7/04—Speed or phase control by synchronisation signals
    • H04L7/08—Speed or phase control by synchronisation signals the synchronisation signals recurring cyclically
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04W—WIRELESS COMMUNICATION NETWORKS
    • H04W88/00—Devices specially adapted for wireless communication networks, e.g. terminals, base stations or access point devices
    • H04W88/08—Access point devices
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2647—Arrangements specific to the receiver only
    • H04L27/2655—Synchronisation arrangements
    • H04L27/2668—Details of algorithms
    • H04L27/2669—Details of algorithms characterised by the domain of operation
    • H04L27/2671—Time domain
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2647—Arrangements specific to the receiver only
    • H04L27/2655—Synchronisation arrangements
    • H04L27/2668—Details of algorithms
    • H04L27/2673—Details of algorithms characterised by synchronisation parameters
    • H04L27/2675—Pilot or known symbols
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2647—Arrangements specific to the receiver only
    • H04L27/2655—Synchronisation arrangements
    • H04L27/2668—Details of algorithms
    • H04L27/2681—Details of algorithms characterised by constraints
    • H04L27/2684—Complexity
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2647—Arrangements specific to the receiver only
    • H04L27/2655—Synchronisation arrangements
    • H04L27/2668—Details of algorithms
    • H04L27/2681—Details of algorithms characterised by constraints
    • H04L27/2688—Resistance to perturbation, e.g. noise, interference or fading
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2647—Arrangements specific to the receiver only
    • H04L27/2655—Synchronisation arrangements
    • H04L27/2689—Link with other circuits, i.e. special connections between synchronisation arrangements and other circuits for achieving synchronisation
    • H04L27/2695—Link with other circuits, i.e. special connections between synchronisation arrangements and other circuits for achieving synchronisation with channel estimation, e.g. determination of delay spread, derivative or peak tracking

Definitions

  • the present invention relates to a method for detecting an uplink synchronization signal in a wireless access system supporting a high frequency band and a method for designing a detection filter therefor.
  • Wireless access systems are widely deployed to provide various kinds of communication services such as voice and data.
  • a wireless access system is a multiple access system capable of supporting communication with multiple users by sharing available system resources (bandwidth, transmission power, etc.).
  • multiple access systems include code division multiple access (CDMA) systems, frequency division multiple access (FDMA) systems, time division multiple access (TDMA) systems, orthogonal frequency division multiple access (OFDMA) systems, and single carrier frequency (SC-FDMA). division multiple access) system.
  • CDMA code division multiple access
  • FDMA frequency division multiple access
  • TDMA time division multiple access
  • OFDMA orthogonal frequency division multiple access
  • SC-FDMA single carrier frequency division multiple access
  • An object of the present invention is to provide methods for efficiently detecting an uplink synchronization signal in a communication environment using a high frequency band.
  • Another object of the present invention is to provide a two-stage sync signal detection method for detecting sync signals with low complexity.
  • Another object of the present invention is to provide a method of designing a detection filter for obtaining uplink synchronization in a high frequency band.
  • Another object of the present invention is to provide an apparatus supporting these methods.
  • the present invention provides a method of detecting an uplink synchronization signal in a wireless access system supporting a high frequency band, a method of designing a detection filter for the same, and apparatuses for supporting the same.
  • a method for detecting a random access channel (RACH) signal by a base station in a radio access system supporting a high frequency band includes assigning a cyclic shift value used in a base station and a random access channel. Constructing a receiving signal vector for the signals transmitted through the method; deriving a cyclic shift candidate greater than or equal to a reference value from the received signal vector using the first detection filter; and RACH from the cyclic shift candidate using the second detection filter. Detecting a signal, the first detection filter and the second detection filter may be set based on the cyclic shift value.
  • a base station for detecting a random access channel (RACH) signal in a radio access system supporting a high frequency band may include a transmitter, a receiver, and a processor configured to detect a RACH signal.
  • the processor allocates a cyclic shift value used in the base station, configures a received signal vector for signals transmitted through a random access channel, and uses the first detection filter to select a cyclic shift greater than or equal to a reference value from the received signal vector. And detect the RACH signal from the cyclic shift candidate using the second detection filter, wherein the first detection filter and the second detection filter may be set based on the cyclic shift value.
  • the first detection filter may be set assuming that the number of constituting the random access channel is one. In this case, ⁇ is the first detection filter.
  • ⁇ denotes the total length of the Zadoff-Churse sequence
  • ⁇ de denotes the modulo operation
  • the second detection filter may be set in consideration of the number of effective channels constituting the random access channel.
  • the second detection filter G m is (( m ) JJ ( m + 1 ) J C (( m + ,
  • m denotes a cyclic shift value
  • L denotes the number of effective channels
  • N denotes the total length of the Zadofchu sequence
  • ⁇ de denotes the modulo operation
  • the cyclic shift value may be set in consideration of the number of effective channels.
  • the cyclic shift candidate may mean a section in which a correlation of correlations derived from a Zero Correlation Zone (ZCZ) is greater than or equal to the reference value.
  • ZCZ Zero Correlation Zone
  • FIG. 1 is a diagram for explaining physical channels and a signal transmission method using the same.
  • FIG. 2 shows the structure of a radio frame.
  • FIG. 3 is a diagram illustrating a resource grid for a downlink slot.
  • 5 shows the structure of a downlink subframe.
  • FIG. 6 is a diagram illustrating conceptual features of a small cell.
  • FIG. 7 is a diagram illustrating an example of a RACH preamble structure.
  • Figure 9 shows the generation of an effective multipath when the RACH subcarrier spacing is large
  • FIG. 10 is a diagram illustrating one of ZCZ setting methods considering effective delay L of a channel.
  • FIG. 1 is a diagram illustrating one method of extracting a reception vector r according to a time delay in ZCZ.
  • FIG. 12 is a view showing a state in which a synchronization signal is correctly received using a second detection filter considering the effective channel L.
  • FIG. 13 is a diagram illustrating one method of detecting a RACH signal in stages
  • FIG. 14 is a diagram for describing a method for detecting multiple users according to an embodiment of the present invention.
  • FIG. 15 is a means by which the methods described in FIGS. 1 to 14 can be implemented.
  • Embodiments of the present invention described in detail below provide a method for transmitting and receiving data symbols using the correlation between antennas constituting a massive antenna, and apparatuses for supporting the same.
  • each component or feature may be considered optional unless otherwise stated.
  • Each component or feature may be embodied in a form that is not combined with other components or features.
  • some components and / or features may be combined to form an embodiment of the present invention.
  • the order of the operations described may vary. Some configurations or features of one embodiment may be included in another embodiment or may be substituted for components or features of another embodiment.
  • the base station is meant as a terminal node of a network that directly communicates with a mobile station. Certain operations described as being performed by the base station in this document may be performed by an upper node of the base station in some cases.
  • various operations performed for communication with a mobile station in a network composed of a plurality of network nodes including a base station may be performed by the base station or other network nodes other than the base station.
  • the 'base station' may be replaced by terms such as a fixed station, a Node B, an eNode B (eNB), an advanced base station (ABS), or an access point.
  • a terminal may be a user equipment (UE), a mobile station (MS), a subscriber station (SS), or a mobile subscriber station (MSS: Mobile). It may be replaced with terms such as Subscriber Station, Mobile Terminal, or Advanced Mobile Station (AMS).
  • UE user equipment
  • MS mobile station
  • SS subscriber station
  • MSS mobile subscriber station
  • AMS Advanced Mobile Station
  • the transmitting end refers to a fixed and / or mobile node that provides a data service or a voice service
  • the receiving end refers to a fixed and / or mobile node that receives a data service or a voice service. Therefore, in uplink, a mobile station can be a transmitting end and a base station can be a receiving end. Similarly, in downlink, a mobile station may be a receiving end and a base station may be a transmitting end.
  • Embodiments of the present invention may be supported by standard documents disclosed in at least one of IEEE 802.XX systems, 3rd Generation Partnership Project (3GPP) systems, 3GPP LTE systems, and 3GPP2 systems, which are wireless access systems.
  • 3GPP 3rd Generation Partnership Project
  • Embodiments of the present invention may be supported by 3GPP TS 36.21 1, 3GPP TS 36.212, 3GPP TS 36.213 and 3GPP TS 36.321 documents. That is, obvious steps or portions not described among the embodiments of the present invention may be described with reference to the above documents. In addition, all terms disclosed in this document may be described by the above standard document.
  • the uplink registered signal may be used as a synchronizing signal, a RACH preamble, or an RACH signal.
  • a subject performing communication with a terminal may be referred to as a user, and the terminal and the user may have the same meaning.
  • the reception filter for detecting the RACH signal in the high frequency band may be used in the same sense as the term detection filter.
  • CDMA code division multiple access
  • FDMA frequency division multiple access
  • TDMA time division multiple access
  • OFDMA orthogonal frequency division multiple access
  • SC-FDMA single carrier frequency division multiple access
  • CDMA may be implemented by a radio technology such as Universal Terrestrial Radio Access (UTRA) or CDMA2000.
  • TDMA supports Global System for Mobile communications (GSM) / General Packet Radio Service (GPRS) / Enhanced Data Rates for GSM Evolution).
  • GSM Global System for Mobile communications
  • GPRS General Packet Radio Service
  • OFDMA may be implemented with a radio technology such as IEEE 802.1 1 (Wi-Fi), IEEE 802.16 (WiMAX), IEEE 802-21, Evolved UTRA (E-UTRA), or the like.
  • UTRA is a part of Universal Mobile Telecommunications System (UMTS).
  • 3GPP Long Term Evolution (LTE) is part of an Evolved UMTS (E-UMTS) using E-UTRA, and employs OFDMA in downlink and SC-FDMA in uplink.
  • LTE-A (Advanced) system is an improved system of the 3GPP LTE system.
  • embodiments of the present invention will be described based on the 3GPP LTE / LTE-A system, but can also be applied to IEEE 802.16e / m system and the like.
  • a user equipment receives information from a base station through downlink (DL) and transmits information to the base station through uplink (UL).
  • the information transmitted and received by the base station and the terminal includes general data information and various control information, and various physical channels exist according to the type / use of the information they transmit and receive.
  • FIG. 1 is a diagram for explaining physical channels that can be used in embodiments of the present invention and a signal transmission method using the same.
  • the UE turns on again or enters a new cell, and performs an initial cell search operation such as synchronizing with the base station in step S1.
  • the UE receives a Primary Synchronization Channel (P-SCH) and a Secondary Synchronization Channel (S-SCH) from the base station, synchronizes with the base station, and obtains information such as a cell ID.
  • the terminal may receive a physical broadcast channel (PBCH) signal from the base station to obtain broadcast information in a cell.
  • PBCH physical broadcast channel
  • the UE may check the downlink channel state by receiving a downlink reference signal (DL RS) in an initial cell search step.
  • DL RS downlink reference signal
  • the UE After the initial cell discovery, the UE receives a physical downlink control channel (PDCCH) and a physical downlink control channel (PDSCH) according to physical downlink control channel information in step S12. By doing so, more specific system information can be obtained.
  • PDCCH physical downlink control channel
  • PDSCH physical downlink control channel
  • the terminal may perform a random access procedure such as steps S13 to S16 to complete the access to the base station.
  • the UE transmits a preamble through a physical random access channel (PRACH) (S 13), and a physical downlink control channel and a physical downlink shared channel to the preamble for the preamble.
  • PRACH physical random access channel
  • the answer message may be received (S14).
  • the UE performs contention resolution such as transmitting an additional physical random access channel signal (S15) and receiving a physical downlink control channel signal and a physical downlink shared channel signal (S16). Procedure).
  • the UE After performing the above-described procedure, the UE subsequently receives a physical downlink control channel signal and / or a physical downlink shared channel signal as a general uplink / downlink signal transmission procedure (S17) and a physical uplink shared channel ( A PUSCH (physical uplink shared channel) signal and / or a physical uplink control channel (PUCCH) signal may be transmitted (S18).
  • a physical downlink control channel signal and / or a physical downlink shared channel signal as a general uplink / downlink signal transmission procedure (S17) and a physical uplink shared channel (A PUSCH (physical uplink shared channel) signal and / or a physical uplink control channel (PUCCH) signal may be transmitted (S18).
  • S17 general uplink / downlink signal transmission procedure
  • a PUSCH (physical uplink shared channel) signal and / or a physical uplink control channel (PUCCH) signal may be transmitted (S18).
  • UCI uplink control information
  • HARQ-ACK / NACK Hybrid Automatic Repeat and reQuest Acknowledgement / Negative-ACK
  • SR Scheduling Request
  • CQI Channel Quality Indication
  • PMI Precoding Matrix Indication
  • RI Rank Indication
  • UCI is generally transmitted periodically through a PUCCH, but may be transmitted through a PUSCH when control information and traffic data should be transmitted at the same time.
  • the UCI may be aperiodically transmitted through the PUSCH by the network request / instruction.
  • FIG. 2 shows the structure of a radio frame used in embodiments of the present invention.
  • FIG. 2 (a) shows a frame structure type 1.
  • the type 1 frame structure can be applied to both full duplex Frequency Division Duplex (FDD) systems and half duplex FDD systems.
  • FDD Frequency Division Duplex
  • One subframe is defined as two consecutive slots, and the i-th subframe includes slots corresponding to 2i and 2i + l. That is, a radio frame consists of 10 subframes.
  • the time taken to transmit one subframe is called a transmission time interval ( ⁇ ).
  • a slot includes a plurality of OFDM symbols or SC-FDMA symbols in the time domain.
  • a plurality of resource blocks are included in the frequency domain.
  • One slot includes a plurality of orthogonal frequency division multiplexing (OFDM) symbols in the time domain. Since 3GPP LTE uses OFDMA in downlink, the OFDM symbol is for representing one symbol period. The OFDM symbol may be referred to as one SC-FDMA symbol or symbol period.
  • a resource block is a resource allocation unit and includes a plurality of consecutive subcarriers in one slot. In a full-duplex FDD system, 10 subframes may be used simultaneously for downlink transmission and uplink transmission during each 10 ms period. At this time, uplink and downlink transmission are separated in the frequency domain. On the other hand, in the case of a half-duplex FDD system, the terminal cannot transmit and receive at the same time.
  • the structure of the above-described radio frame is just one example, and the number of subframes included in the radio frame or the number of slots included in the subframe and the number of OFDM symbols included in the slot may vary. Can be.
  • Type 2 frame structure is applied to the TDD system.
  • a type 2 frame has a special field consisting of three fields: Downlink Pilot Time Slot (DwPTS), Guard Period (GP), and Uplink Pilot Time Slot (UpPTS).
  • DwPTS Downlink Pilot Time Slot
  • GP Guard Period
  • UpPTS Uplink Pilot Time Slot
  • DwPTS is used for initial cell search, synchronization, or channel estimation in the terminal.
  • UpPTS is channel estimation at base station and uplink transmission
  • the guard interval is the "period to eliminate the interference caused in the uplink and the uplink due to a multipath delay of a downlink signal link between the downlink.
  • Table 1 shows the structure of a special frame (length of DwPTS / GP / UpPTS).
  • FIG. 3 is a diagram illustrating a resource grid in a downlink slot that can be used in embodiments of the present invention.
  • one downlink slot includes a plurality of OFDM symbols in the time domain.
  • one downlink slot includes seven OFDM symbols, and one resource block includes an example of 12 subcarriers in a frequency domain, but is not limited thereto.
  • Each element on the resource grid is a resource element, and one resource block includes 12 ⁇ 7 resource elements.
  • the number NDL of resource blocks included in the downlink slot depends on the downlink transmission bandwidth.
  • the structure of the uplink slot may be the same as the structure of the downlink slot.
  • FIG. 4 shows a structure of an uplink subframe that can be used in embodiments of the present invention.
  • an uplink subframe may be divided into a control region and a data region in the frequency domain.
  • the control region is allocated a PUCCH carrying uplink control information.
  • the data area is allocated with a PUSCH carrying user data.
  • one UE does not simultaneously transmit a PUCCH and a PUSCH.
  • the PUCCH for one UE is allocated an RB pair in a subframe. RBs belonging to an RB pair have different portions in each of the two slots. Occupies a carrier. This RB pair allocated to the PUCCH is said to be frequency hopping at the slot boundary (slot boundary).
  • FIG. 5 shows a structure of a downlink subframe that can be used in embodiments of the present invention.
  • up to three OF 4 symbols from the OFDM symbol index 0 in the first slot in a subframe are control regions to which control channels are allocated, and the remaining OFDM symbols are data regions to which a PDSCH is allocated. (data region).
  • An example of a downlink control channel used in 3GPP LTE includes a Physical Control Format Indicator Channel (PCFICH), a PDCCH, and a Physical Hybrid-ARQ Indicator Channel (PHICH).
  • PCFICH Physical Control Format Indicator Channel
  • PDCCH Physical Hybrid-ARQ Indicator Channel
  • PHICH Physical Hybrid-ARQ Indicator Channel
  • the PCFICH is transmitted in the first OFDM symbol of a subframe and carries information about the number of OFDM symbols (ie, the size of a control region) used for transmission of control channels in the subframe.
  • PHICH is a male answer channel for the uplink and carries an acknowledgment (ACK) negative-acknowledgement (ACK) signal for a hybrid automatic repeat request (HARQ).
  • Control information transmitted through the PDCCH is called downlink control information (DCI).
  • the downlink control information includes uplink resource allocation information, downlink resource allocation information or an uplink transmission (Tx) power control command for a certain terminal group.
  • Embodiments of the present invention provide a transmission diversity securing method using correlation of antennas in a communication environment supporting a massive antenna.
  • Massive antennas are easy to implement in the high frequency band (a few GHz) where the distance between the antennas can be short. Due to the nature of the massive antenna in which a large number of antennas are arranged in a narrow area, it may be possible to implement all antennas in a form of independence having low correlation with each other.
  • the beamforming technique is applied to the massive antenna, since the performance is maximized when the correlation between antennas is high, the extreme characteristics of the correlation between antennas are all at once. Therefore, by using the correlation characteristics of the massive antenna it is possible to secure the service coverage of the base station, in particular, the effect can be maximized when transmitting the control channel.
  • the embodiments of the present invention can be applied under the same principle not only in the cell band of 3GHz or less, but also in a high frequency broadband communication situation of more than 3GHz, and can be applied to a small cell as well as a conventional macro cell.
  • a wireless access environment to which a massive antenna can be applied will be described.
  • the 3GPP LTE-A system is a wireless access system that operates based on the Rel-10 to Rel-11 standards.
  • the wireless access system to which embodiments of the present invention are applied may be a system defined in the standards of 3GPP LTE Rel-12 or below.
  • the Rel-12 system considers the introduction of local area cells (ie, small cells) and the local access (LAA) method to further support user-specific services.
  • FIG. 6 illustrates conceptual features of a small sal.
  • the left side shows a conventional celller band
  • the right side shows a high frequency band to which a small cell is applied. That is, the small sal may be operated by setting a wide system band in a band having a higher center frequency rather than a frequency band operated in an existing Celller system LTE system.
  • the existing cellular bands support basic sal coverage based on control signals such as system information (SI).
  • SI system information
  • LAA local access
  • the delay spread (Delay spread): can be reduced by the delay of • 10 signal according to the distance between the base station and the terminal shortened.
  • Subcarrier spacing When applying the same OFDM-based frame as the existing LTE system, since the frequency band allocated to each UE is large, the subcarrier spacing used in the small cell is the existing LTE system. It can be set to an extreme value greater than 15kHz.
  • the UE can transmit an uplink signal only when it is synchronized with the base station and can receive scheduling for data transmission. That is, the main role of the random access channel (RACH) is to enable wireless access through a transmission scheme such that signals transmitted by unsynchronized terminals do not orthogonal or overlap each other as much as possible.
  • RACH random access channel
  • the main role of the RACH is uplink initial access and short message transmission.
  • initial network connection and short connection through RACH was made.
  • the short message transmission through the RACH is not provided.
  • the RACH is configured separately from the existing uplink data transmission channel.
  • fRA 1.25kHz
  • f 15kHz
  • FIG. 7 is a diagram illustrating an example of a RACH preamble structure.
  • the UE transmits a RACH preamble (ie, a RACH signal) to the base station through the RACH to synchronize uplink.
  • the RACH preamble consists of a Cyclic Prefix (CP) and a RACH sequence, and when the RACH parameter is configured at the base station to generate the RACH preamble, the RACH is considered in consideration of the guard type according to the sal radius. Configure the parameters.
  • the CP is set in consideration of the maximum channel delay spread + round trip-time, and the GT absorbs the round trip time.
  • the CP is generated by inserting the second half of the OFDM symbol into the CP section of the preamble, thereby enabling periodic correlation of the RACH receiver.
  • timing advance 0ms
  • the LTE system uses 64 signatures to distinguish terminals, while the WCDMA system uses 16 signatures.
  • a Zadofchu (ZC) sequence such as Equation 1 may be used for the RACH preamble.
  • Equation 1 u denotes the root index of the ZC sequence, and N zc denotes the length of the ZC sequence.
  • Equation 2 a PN sequence shown in Equation 2 may be used.
  • x 2 (n + 3 ⁇ ) (x 2 (n + 3) + x 2 (n + l) + x 2 (n + l) + x 2 ( «)) mod 2
  • RACH Preamble Transmission Band Two main factors considered in setting the transmission band of the RACH preamble are diversity gain and transmission power limitation of the UE. That is, unlike the base station, the terminal is limited in the performance of a power amplifier. Therefore, when a wide frequency band is allocated for RACH preamble transmission, energy per resource unit / resource element may be lowered while frequency diversity may be maximized. On the contrary, when a narrow band is allocated for RACH preamble transmission, energy per resource unit / resource element is high, but frequency diversity is minimized.
  • the LTE system sets the subcarrier spacing Af ⁇ of the RACH to be smaller than about ⁇ / 12 times the basic subcarrier spacing ⁇ / for the existing data.
  • the base station may cause a decrease in detection performance for the RACH preamble.
  • the base station may cause a decrease in detection performance for the RACH preamble.
  • the base station may cause a decrease in detection performance for the RACH preamble.
  • an approach of lowering the size of ⁇ as in the existing LTE may cause significant performance degradation.
  • the base station may perform correlation on the RACH sequence transmitted by each terminal by using a small ⁇ to distinguish each terminal or to estimate a timing difference.
  • the Doppler effect must be taken into account in the high frequency channel, since the RACH subcarrier spacing must also be set to be the same as the basic subcarrier spacing, the number of effective channels cannot be assumed to be a single tap at this time.
  • FIG. 8 illustrates a concept of effective single path generation and base station sequence reception when RACH subcarrier spacing is small
  • FIG. 9 illustrates a concept of effective multipath generation and base station sequence reception when RACH subcarrier spacing is large.
  • FIG. 8 ZC sequence ⁇ , ⁇ ',... Through RACH with relatively small subcarrier spacing.
  • ⁇ / When ⁇ / is transmitted, the length of the RACH transmitted symbol is increased on the time axis, and the effective channel interval is assumed to be a single wrap. That is, FIG. 8 assumes a case of a RACH preamble used in a bandwidth supported by a general celller system (eg, LTE / LTE-A system).
  • a general celller system eg, LTE / LTE-A system
  • h 0 and h u h L-1 denote a channel through which a RACH preamble is transmitted, and ⁇ , ⁇ ,... , ⁇ Means zc sequence.
  • TA uplink timing advance
  • Embodiments of the present invention provide methods for detecting an uplink synchronization signal suitable for a communication environment using a high frequency band.
  • the present invention provides methods for designing a synchronization signal detection filter in consideration of a relationship between channel characteristics of a high frequency band and subcarrier spacing of a synchronization signal.
  • the high frequency band assumes wide broadband communication, the period of a single sample on the time axis may be extremely short.
  • the synchronization signal detection filter must be designed in consideration of this.
  • the base station provides a two-step synchronization signal detection process for detecting synchronization signals with low complexity.
  • ZCZ in addition to detecting the synchronization signal from each terminal, it is possible to estimate the exact symbol timing at which each terminal transmits the synchronization signal.
  • Equation 3 means a RACH signal received through a multipath delay channel at a base station.
  • each component may be defined as in Equations 4, 5, and 6 below.
  • n [" 0 « 2 ... n n _
  • Equation 4 refers to the .NxN zc sequence matrix S.
  • Equation 5 refers to the Nxl channel vector h
  • Equation 6 refers to the Nx AWGN (Additive White Gaussian Noise) vector n.
  • s (') means Nxl zc sequence vector cyclically shifted by /.
  • Equation 4 (>) means Modulo 'm' operation.
  • ho, h l5 h L-1 means a valid multiple delay channel, and the total channel length is L.
  • the portion (NL) of the ZC sequence length excluding the effective channel length L is filled with 0 sequence.
  • an N x size G matrix which is a detection filter capable of detecting terminals transmitting the RACH signal, may be defined as in Equation 7 below.
  • a cyclic shift value 'm' which is orthogonally-independently assigned to each UE is allocated in the unit shown in Equation 9 below.
  • N cs means a cyclic shift value used when generating the RACH preamble in the LTE / LTE-A system. Therefore, since the size of the sample in which the actual signal exists in ZCZ is 'L,' the detection filter G becomes the N matrix.
  • the base station finds a point at which the maximum value is derived by multiplying the Hermitian matrix of the detection filter G matrix, which is generated based on the cyclic shift value 'm, allocated to each terminal, for the reception vector r.
  • Equation 10 may be developed as in Equation 11 below.
  • the uplink synchronization signal received by the base station is represented as the sum of powers for the channels through which the uplink synchronization signal transmitted by the first terminal passes.
  • the detection result for the uplink synchronization signal transmitted by the second terminal may be developed as in Equation 12 below.
  • the base station may determine reception of the RACH signal. Therefore, the detection filter G "may be referred to as a filter representing a sequence detection interval of each terminal based on the cyclic shift value used for the transmission of the ZC sequence by each terminal.
  • m means a cyclic shift-based ZCZ value allocated to each UE.
  • the m value is determined in consideration of the total effective channel delay number L.
  • the base station allocates m values to the terminals, respectively, so that the base station can detect the terminal that has transmitted the uplink synchronization signal.
  • the assignment of the m value means that when the base station broadcasts information on the m value through a broadcast channel, each terminal may configure the RACH signal using the m value.
  • the maximum delay allowed for each UE is limited to N cs , and since a channel valid delay period L is introduced to prevent overlap between each ZCZ, a cyclic shift period of the entire ZC sequence Is set as shown in FIG.
  • the RACH sequence having different cyclic shift values transmitted by each terminal allows a reception delay of a maximum Ncs interval.
  • FIG. 10 is a diagram illustrating one of ZCZ setting methods considering a valid delay L of a channel.
  • FIG. 11 is a diagram illustrating one method of extracting a reception vector r according to a time delay in ZCZ.
  • the configuration of the reception vector r is expressed as in Equation 13 below. If the RACH signal transmitted by the terminal far away from the base station (eg, a terminal located at a cell boundary) is maximum
  • the reception vector r is expressed as in Equation 14 below.
  • the base station sequentially configures a reception signal vector r having a length N for a maximum N cs of the reception signal delay of the terminal, and confirms RACH detection through correlation with the G matrix, which is a detection filter. In this case, it could be confirmed that due to the multipath generated by the effective channel delay described above, the detection complexity is increased or decreased by X.
  • the present invention proposes a step-by-step RACH detection method for reducing the detection complexity as follows.
  • the base station In the first detection step (ie, the initial detection step), the base station assumes the multiple delay channel as an effective single channel and detects a section in which the sequence correlation derived from each ZCZ becomes equal to or greater than the reference value. Assume the value is set on the environment and / or system.
  • One ZCZ index 'n,' assigned to each UE is one of a cyclic shift value 'tn' determined as shown in Equation 9.
  • the reason for using the ZCZ value is that each terminal is received from the reception delay caused by the position of the plurality of terminals are different from each other This is to prevent the overlapping of the transmitted ZC sequences (ie, RACH signals) and to perform timing advance (TA).
  • the reason for setting the ZCZ as long as the effective channel length is to determine the correct reception position for the ZC sequence received through the multipath.
  • the complexity increases from x l to N x Z.
  • a signal detection operation since a signal detection operation must be performed for all ZC sequences in the multi-user based uplink control channel structure, the complexity of signal detection of a base station increases.
  • the detection filter G is designed by assuming that the effective channel section of the detection filter G matrix is partly or extremely one.
  • the G matrix which is a detection filter used in the first detection step
  • the first detection filter which is the G matrix used in the first detection step, be composed of a matrix or a ⁇ ⁇ /, (/ ' ⁇ / _) matrix.
  • the base station sets the first detection filter, which is the G matrix when the effective channel length L is assumed to be 1 in the first detection step, so that the base station transmits the uplink synchronization signal.
  • the initial detection step means finding the position with the largest channel gain of all effective channels.
  • the base station may determine that the RACH signal of any terminal among the RACH resources allocated so as not to overlap each other in the first detection step is currently being received.
  • the detection filter G matrix described in Equation 7 is changed and applied as in Equation 15 in the first detection step.
  • the base station may derive the cyclic shift value 'm' candidate used by the terminal that has transmitted the received RACH signal using the first detection filter derived from Equation 15. In this case, the base station may select one or more cyclic shift values that are greater than or equal to a reference value among the cyclic shift values correlated as candidates for the second detection step.
  • the base station may derive an accurate sequence correlation value and a delay value by applying all effective channel delays L.
  • the base station may perform a second detection step of detecting the RACH signal by setting a second detection filter for the effective channel L for the cyclic shift candidates detected through the first detection filter described in Section 3.2.1. .
  • the second detection step is for the base station to acquire the correct uplink time synchronization of the terminal in the ZCZ. Therefore, the second detection filter may be set to the G matrix described in Equation 7 for the effective channel delay L. That is, the second detection filter is composed of the N x matrix of Equation (7).
  • the base station configures a second detection filter as shown in Equation 7 for the entire effective channel L, and performs the second detection step only on the ZCZ candidates derived in the first detection step. This allows the base station to determine the correct time synchronization.
  • the powers of the effective channels are not necessarily arranged in order. Do not. That is, even if h 0 is a preferred channel, the reception channel with the highest power does not mean accurate time synchronization.
  • the base station since the ZC sequence correlation value is maximized only when the second detection filter is correctly aligned with respect to the entire effective channel, the base station performs accurate time synchronization at the point aligned with h 0 as shown in FIG. Can be detected.
  • FIG. 12 is a diagram illustrating a state in which a synchronization signal is correctly received using a second detection filter considering the effective channel L.
  • FIG. FIG. 12 (a) shows the detection of the RACH signal using the G matrix as the detection filter in the multiple delay channel
  • FIG. 12 (b) shows the detection of the correct synchronization signal through the detection process of the second step of the present invention. Indicates.
  • the base station can estimate the degree of delay of the time synchronization ho, through which the base station can find the correct symbol timing of each terminal in addition to the synchronization signal of each terminal.
  • FIG. 13 is a diagram illustrating one method of detecting a RACH signal in stages.
  • FIG. 13 is a view for explaining the method of detecting the two-stage RACH signal described in the above section 3.2 from the viewpoint of the base station and the terminal.
  • the base station allocates a cyclic shift value m necessary for the terminal to generate the RACH signal.
  • the base station may periodically broadcast the cyclic ' transition value—m through the system ' information (S1310).
  • One or more terminals configure the RACH signal using the cyclic shift value m, and transmit the RACH signal to the base station.
  • the base station may receive the RACH signal from one or more terminals through the RACH composed of multiple delay channels, and may configure the received signal vector r based on the RACH signal.
  • the received signal vector r may be represented by Equation 3 (1320).
  • the base station configures the first detection filter assuming the multiple delay channel as one effective channel. For a method of configuring the first detection filter, refer to Equation 15 described in Section 3.2.1 (S 1330).
  • the base station derives a cyclic shift (eg, ZCZ) candidate based on the first detection filter. That is, more than a reference value among the RACH signals detected through the first detection filter.
  • a cyclic shift eg, ZCZ
  • the base station configures a second detection filter to derive the correct sequence correlation value and / or the delay value of each RACH signals.
  • a method of configuring the second detection filter refer to the contents described in Section 3.2.2, but the second detection filter may be configured as shown in Equation (7). That is, the second detection filter is configured in consideration of the number L of effective channels (S1350).
  • the base station detects the RACH signal with respect to the cyclic shift value candidates derived in step S1340 using the second detection filter. That is, the base station may detect the RACH signal by estimating the exact symbol start point at which each RACH signal is transmitted using the second detection filter (S1360).
  • the first detection filter and the second detection filter may be configured in every frame or every subframe at the base station.
  • the first detection filter and the second detection filter may be fixedly used in a predetermined number, and may be configured to have a fixed value on the system.
  • the base station may perform two stages of RACH signal detection using the first detection filter and the second detection filter configured according to the cyclic shift value m.
  • FIG. 14 is a diagram for describing a method of detecting a multiple user according to an embodiment of the present invention.
  • the base station can confirm that a predetermined or more peak value (correlation) occurs in ZCZ # 0 and ZCZ # 2 through the above-described first step detection process. Therefore, the base station can identify the first terminal and the second through the RACH.
  • the UE may detect that the RACH signal has been transmitted (that is, the connection has been performed).
  • the base station may estimate the exact symbol start point at which the RACH signals of the first terminal and the second terminal are transmitted by performing a second step detection process on the detected ZCZ.
  • the detection method of the uplink synchronization signal suitable for a communication environment using a high frequency band has been described.
  • a detection filter design method is proposed in consideration of the channel characteristics of the high frequency band and the subcarrier spacing relationship of the synchronization signal, and a two-stage synchronization signal detection method with low complexity is proposed.
  • the present invention proposes a basic principle of the design of the multi-user synchronization signal detection filter considering the multi-path channel delay, and based on this, a step-by-step synchronization signal detection process is presented.
  • ZCZ in the synchronization signal detection filter proposed in the present invention, it is possible to estimate the exact symbol timing of each terminal in addition to the synchronization signal detection of each terminal.
  • the present invention relates to a specific method for the detection of an uplink synchronization signal suitable for a high frequency broadband communication environment, but its use is not limited to a small cell. It can also be applied to regular cells. That is, when the general cell lorler system is applied to the high frequency band, it may be applied to the general cell lorler system rather than the small cell. 4. Implementation device
  • the apparatus described with reference to FIG. 15 is a means by which the methods described with reference to FIGS. 1 to 14 may be implemented.
  • a UE may operate as a transmitting end in uplink and a receiving end in downlink.
  • an e-Node B eNB
  • eNB e-Node B
  • the terminal and the base station may include a transmitter (Tx module: 1540, 1550) and a receiver (Rx module: 1550, 1570), respectively, to control transmission and reception of information, data, and / or messages.
  • the antenna may be a massive antenna, and a mesh antenna is a term that collectively refers to an antenna group in which a plurality of antennas are arranged in a two-dimensional or three-dimensional form.
  • the terminal and the base station respectively, the processor (Processor 1520, 1530) for performing the above-described embodiments of the present invention and the memory (1580, 1590) that can temporarily or continuously-process the processing of the processor May each include
  • Embodiments of the present invention can be performed using the components and functions of the above-described terminal and base station apparatus.
  • the processor of the base station may design a detection filter or perform a two-stage RACH signal detection method by combining the methods described in Sections 1 to 3 described above.
  • the processor of the terminal may configure the RACH signal based on the received cyclic shift value, and transmits it to the base station to match uplink synchronization. For details, refer to the details described in Section 3.
  • the transmission and reception modules included in the terminal and the base station include a packet modulation and demodulation function, a high speed packet channel coding function, and an orthogonal frequency division multiple access (OFDMA) Orthogonal Frequency Division Multiple Access (or packet) scheduling, time division duplex (TDD) packet scheduling, and / or channel multiplexing may be performed.
  • OFDMA orthogonal frequency division multiple access
  • TDD time division duplex
  • the terminal and the base station of FIG. 15 may further include low power RF (Intermediate Frequency) models.
  • the transmission and reception may be viewed as a transmitter receiver, respectively, and may be referred to as a transceiver when used together.
  • the terminal is a personal digital assistant (PDA), a cellular phone, a personal communication service (PCS) phone, a GSM (Global System for Mobile) phone, a WCDMA (Wideband CDMA). ) Phones, mobile broadband system (MBS) phones, hand-held PCs, notebook PCs, smart phones, or multi-mode multi-band (MM-MB) terminals.
  • PDA personal digital assistant
  • PCS personal communication service
  • GSM Global System for Mobile
  • WCDMA Wideband CDMA
  • MBS mobile broadband system
  • hand-held PCs hand-held PCs
  • notebook PCs notebook PCs
  • smart phones or multi-mode multi-band (MM-MB) terminals.
  • MM-MB multi-mode multi-band
  • a smart phone is a terminal that combines the advantages of a mobile communication terminal and a personal portable terminal, and is a terminal incorporating data communication functions such as schedule management, fax transmission, and internet access, which are functions of a personal portable terminal. It may mean.
  • a multimode multiband terminal can be equipped with a multi-modem chip to operate in both portable Internet systems and other mobile communication systems (e.g., code division multiple access (CDMA) 2000 systems, wideband CDMA (WCDMA) systems, etc.) Speak the terminal.
  • CDMA code division multiple access
  • WCDMA wideband CDMA
  • the method according to the embodiments of the present invention may include one or more application specific integrated circuits (ASICs), digital signal processors (DSPs), digital signal processing devices (DSPDs), and programmable PLDs. logic devices), field programmable gate arrays (FPGAs), processors, controllers, microcontrollers, microprocessors, and the like.
  • ASICs application specific integrated circuits
  • DSPs digital signal processors
  • DSPDs digital signal processing devices
  • FPGAs field programmable gate arrays
  • processors controllers, microcontrollers, microprocessors, and the like.
  • firmware or software the method according to the embodiments of the present invention may be implemented in the form of modules, procedures, or functions that perform the functions or operations described above.
  • software code may be stored in the memory units 1580 and 1590 and driven by the processors 1520 and 1530.
  • the memory unit may be located inside or outside the processor, and may exchange data with the processor by various known means.
  • Embodiments of the present invention can be applied to various wireless access systems.
  • various radio access systems include 3rd Generation Partnership Project (3GPP), 3GPP2 and / or IEEE 802.XX (Institute of Electrical and Electronic Engineers 802) systems.
  • 3GPP 3rd Generation Partnership Project
  • 3GPP2 3rd Generation Partnership Project2
  • IEEE 802.XX Institute of Electrical and Electronic Engineers 802
  • Embodiments of the present invention can be applied not only to the various radio access systems, but also to all technical fields that use the various radio access systems.

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  • Computer Networks & Wireless Communication (AREA)
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Abstract

La présente invention porte sur un procédé qui sert à détecter un signal de synchronisation montant dans un système d'accès sans fil prenant en charge une bande de hautes fréquences, sur un procédé conçu pour concevoir un filtre de détection destiné à cette détection, et sur des dispositifs prévus pour prendre en charge lesdits procédés. Selon un mode de réalisation, un procédé qui permet à une station de base de détecter un signal de canal d'accès aléatoire (RACH) dans un système d'accès sans fil prenant en charge une bande de hautes fréquences comprend : l'affectation d'une valeur de décalage circulaire utilisée par la station de base ; la configuration d'un vecteur de signaux de réception pour des signaux émis par le biais du RACH ; la déduction, au moyen d'un premier filtre de détection, d'un candidat de décalage circulaire supérieur ou égal à une valeur de référence à partir du vecteur de signaux de réception ; et la détection, au moyen d'un second filtre de détection, du signal de RACH à partir du candidat de décalage circulaire, le premier et le second filtre de détection pouvant être réglés sur la base de la valeur de décalage circulaire.
PCT/KR2014/008071 2013-08-29 2014-08-29 Procédé et dispositif permettant de détecter un signal de synchronisation montant à chaque étape dans un système d'accès sans fil prenant en charge une bande de hautes fréquences WO2015030524A1 (fr)

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JP2016538858A JP2016538791A (ja) 2013-08-29 2014-08-29 高周波帯域を支援する無線接続システムにおいて段階別上りリンク同期信号検出方法及び装置
US14/906,960 US9680682B2 (en) 2013-08-29 2014-08-29 Method and device for detecting uplink synchronization signal in each step in wireless access system supporting high frequency band
EP14839221.0A EP3041300B1 (fr) 2013-08-29 2014-08-29 Procédé et dispositif permettant de détecter un signal de synchronisation montant à chaque étape dans un système d'accès sans fil prenant en charge une bande de hautes fréquences
KR1020167000812A KR20160048757A (ko) 2013-08-29 2014-08-29 고주파 대역을 지원하는 무선 접속 시스템에서 단계별 상향링크 동기 신호 검출 방법 및 장치
CN201480047432.6A CN105493582A (zh) 2013-08-29 2014-08-29 用于在支持高频带的无线接入系统中在每个步骤中检测上行链路同步信号的方法和设备

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EP3041300A1 (fr) 2016-07-06
EP3041300A4 (fr) 2017-04-26
US20160173315A1 (en) 2016-06-16
EP3041300B1 (fr) 2018-10-10
US9680682B2 (en) 2017-06-13
CN105493582A (zh) 2016-04-13

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