WO2014137817A1 - Excitation and use of guided surface wave modes on lossy media - Google Patents

Excitation and use of guided surface wave modes on lossy media Download PDF

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Publication number
WO2014137817A1
WO2014137817A1 PCT/US2014/019477 US2014019477W WO2014137817A1 WO 2014137817 A1 WO2014137817 A1 WO 2014137817A1 US 2014019477 W US2014019477 W US 2014019477W WO 2014137817 A1 WO2014137817 A1 WO 2014137817A1
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WIPO (PCT)
Prior art keywords
waveguide probe
polyphase waveguide
probe
lossy conducting
conducting medium
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PCT/US2014/019477
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English (en)
French (fr)
Inventor
James F. Corum
Kenneth L. CORUM
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Cpg Technologies, Llc.
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Publication date
Priority claimed from US13/789,538 external-priority patent/US9912031B2/en
Priority claimed from US13/789,525 external-priority patent/US9910144B2/en
Priority to CA2902460A priority Critical patent/CA2902460C/en
Priority to MX2015011406A priority patent/MX355731B/es
Priority to NZ712566A priority patent/NZ712566A/en
Priority to AU2014226221A priority patent/AU2014226221B2/en
Priority to JP2015561472A priority patent/JP6392790B2/ja
Priority to BR112015021835A priority patent/BR112015021835A2/pt
Priority to CN201480021978.4A priority patent/CN105164852B/zh
Priority to DK14713640.2T priority patent/DK2932558T3/da
Application filed by Cpg Technologies, Llc. filed Critical Cpg Technologies, Llc.
Priority to EP14713640.2A priority patent/EP2932558B1/en
Priority to AP2015008677A priority patent/AP2015008677A0/xx
Priority to SG11201507166YA priority patent/SG11201507166YA/en
Priority to EA201591655A priority patent/EA201591655A1/ru
Priority to KR1020157024283A priority patent/KR102137005B1/ko
Publication of WO2014137817A1 publication Critical patent/WO2014137817A1/en
Priority to IL240240A priority patent/IL240240B/en
Priority to PH12015501919A priority patent/PH12015501919A1/en
Priority to SA515361007A priority patent/SA515361007B1/ar
Priority to HK16105833.2A priority patent/HK1218024A1/zh

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Classifications

    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/04—Adaptation for subterranean or subaqueous use
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/36—Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith

Definitions

  • FIG. 1 is a chart that depicts a field strength as a function of distance for a guided electromagnetic field and a radiated electromagnetic field.
  • FIG. 2 is a drawing that illustrates a propagation interface with two regions employed for transmission of a guided surface wave according to various embodiments of the present disclosure.
  • FIG. 3 is a drawing that illustrates a polyphase waveguide probe disposed with respect to a propagation interface of FIG. 2 according to an embodiment of the present disclosure.
  • FIG. 4 is a drawing that provides one example illustration of a phase shift in a ground current that facilitates the launching of a guided surface-waveguide mode on a lossy conducting medium in the propagation interface of FIG. 3 according to an embodiment of the present disclosure.
  • FIG. 5 is a drawing that illustrates a complex angle of insertion of an electric field synthesized by the polyphase waveguide probes according to the various embodiments of the present disclosure.
  • FIG. 6 is a schematic of a polyphase waveguide probe according to an embodiment of the present disclosure.
  • FIGS. 7A-J are schematics of specific examples of the polyphase waveguide probe of FIG. 6 according to various embodiments of the present disclosure.
  • FIGS. 8A-C are graphs that illustrate field strengths of guided surface waves at select transmission frequencies generated by the various embodiments of polyphase waveguide probes according to the various embodiments of the present disclosure.
  • FIG. 9 shows one example of a graph of experimental measurements of field strength of a guided surface wave at 59 Megahertz as a function of distance generated by a polyphase waveguide probe according to an embodiment of the present disclosure.
  • FIG. 10 shows a graph of experimental measurements of the phase as a function of distance of the guided surface wave of FIG. 9 according to an embodiment of the present disclosure.
  • FIG. 11 shows another example of a graph of experimental measurements of field strength as a function of distance of a guided surface wave generated by a polyphase waveguide probe at 1.85 Megahertz according to an embodiment of the present disclosure.
  • FIGS. 12A-B depict examples of receivers that can be employed to receive energy transmitted in the form of a guided surface wave launched by a polyphase waveguide probe according to the various embodiments of the present disclosure.
  • FIG. 13 depicts an example of an additional receiver that can be employed to receive energy transmitted in the form of a guided surface wave launched by a polyphase waveguide probe according to the various embodiments of the present disclosure.
  • FIG. 14A depicts a schematic diagram representing the Thevenin-equivalent of the receivers depicted in FIGS. 12A-B according to an embodiment of the present disclosure.
  • FIG. 14B depicts a schematic diagram representing the Norton-equivalent of the receiver depicted in FIG. 13 according to an embodiment of the present disclosure.
  • a radiated electromagnetic field comprises
  • a radiated electromagnetic field is generally a field that leaves an electric structure such as an antenna and propagates through the atmosphere or other medium and is not bound to any waveguide structure.
  • electromagnetic waves leave an electric structure such as an antenna, they continue to propagate in the medium of propagation (such as air) independent of their source until they dissipate regardless of whether the source continues to operate. Once electromagnetic waves are radiated, they are not recoverable unless intercepted, and, if not intercepted, the energy inherent in radiated electromagnetic waves is lost forever. Electrical structures such as antennas are designed to radiate electromagnetic fields by maximizing the ratio of the radiation resistance to the structure loss resistance. Radiated energy spreads out in space and is lost regardless of whether a receiver is present. The energy density of radiated fields is a function of distance due to geometrical spreading. Accordingly, the term "radiate" in all its forms as used herein refers to this form of electromagnetic propagation.
  • a guided electromagnetic field is a propagating electromagnetic wave whose energy is concentrated within or near boundaries between media having different electromagnetic properties.
  • a guided electromagnetic field is one that is bound to a waveguide and can be characterized as being conveyed by the current flowing in the waveguide. If there is no load to receive and/or dissipate the energy conveyed in a guided electromagnetic wave, then no energy is lost except for that dissipated in the conductivity of the guiding medium. Stated another way, if there is no load for a guided electromagnetic wave, then no energy is consumed. Thus, a generator or other source generating a guided electromagnetic field does not deliver real power unless a resistive load is present.
  • such a generator or other source essentially runs idle until a load is presented. This is akin to running a generator to generate a 60 Hertz electromagnetic wave that is transmitted over power lines where there is no electrical load.
  • a guided electromagnetic field or wave is the equivalent to what is termed a "transmission line mode.” This contrasts with radiated electromagnetic waves in which real power is supplied at all times in order to generate radiated waves. Unlike radiated electromagnetic waves, guided electromagnetic energy does not continue to propagate along a finite length waveguide after the energy source is turned off. Accordingly, the term "guide” in all its forms as used herein refers to this transmission mode of electromagnetic propagation.
  • FIG. 1 depicts graph 100 of field strength in decibels (dB) above an arbitrary reference in volts per meter as a function of distance in kilometers on a log-dB plot.
  • the graph 100 of FIG. 1 depicts a guided field strength curve 103 that shows the field strength of a guided electromagnetic field as a function of distance.
  • This guided field strength curve 103 is essentially the same as a transmission line mode.
  • the graph 100 of FIG. 1 depicts a radiated field strength curve 106 that shows the field strength of a radiated electromagnetic field as a function of distance.
  • the radiated field strength curve 106 falls off geometrically (1/d, where d is distance) and is a straight line on the log-log scale.
  • the guided field strength curve 103 has the characteristic exponential decay of e ⁇ ad / d and exhibits a distinctive knee 109.
  • the field strength of a guided electromagnetic field falls off at a rate of e ⁇ ad / d
  • the field strength of a radiated electromagnetic field falls off at a rate of where d is the distance. Due to the fact that the guided field strength curve 103 falls off exponentially, the guided field strength curve 103 features the knee 109 as mentioned above.
  • the guided field strength curve 103 and the radiated field strength curve 106 intersect at a crossover point 113 which occurs at a crossover distance. At distances less than the crossover distance, the field strength of a guided electromagnetic field is significantly greater at most locations than the field strength of a radiated
  • the guided and radiated field strength curves 103 and 106 further illustrate the fundamental propagation difference between guided and radiated electromagnetic fields.
  • Milligan T., Modern Antenna Design, McGraw-Hill, 1 st Edition, 1985, pp.8-9, which is incorporated herein by reference in its entirety.
  • the wave equation is a differential operator whose
  • antennas excite the continuum eigenvalues of the wave equation, which is a radiation field, where the outwardly propagating RF energy with E z and ⁇ ⁇ in- phase is lost forever.
  • waveguide probes excite discrete eigenvalues, which results in transmission line propagation. See Collin, R. E., Field Theory of Guided Waves, McGraw-Hill, 1960, pp. 453, 474-477. While such theoretical analyses have held out the hypothetical possibility of launching open surface guided waves over planar or spherical surfaces of lossy, homogeneous media, for more than a century no known structures in the engineering arts have existed for accomplishing this with any practical efficiency.
  • various polyphase waveguide probes are described that are configured to excite radial surface currents having resultant fields that synthesize the form of surface-waveguide modes along the surface of a lossy conducting medium.
  • Such guided electromagnetic fields are substantially mode-matched in magnitude and phase to a guided surface wave mode on the surface of the lossy conducting medium.
  • Such a guided surface wave mode can also be termed a Zenneck surface wave mode.
  • the resultant fields excited by the polyphase waveguide probes described herein are substantially mode-matched to a Zenneck surface wave mode on the surface of the lossy conducting medium, a guided electromagnetic field in the form of a Zenneck surface wave is launched along the surface of the lossy conducting medium.
  • the lossy conducting medium comprises a terrestrial medium such as the Earth.
  • FIG. 2 shown is a propagation interface that provides for an examination of the boundary value solution to Maxwell's equations derived in 1907 by Jonathan Zenneck as set forth in his paper Zenneck, J., "On the Propagation of Plane Electromagnetic Waves Along a Flat Conducting Surface and their Relation to Wireless Telegraphy," Annalen der Physik, Serial 4, Vol. 23, September 20, 1907, pp. 846-866.
  • FIG. 2 depicts cylindrical coordinates for radially propagating waves along the interface between a lossy conducting medium specified as Region 1 and an insulator specified as Region 2.
  • Region 1 can comprise, for example, any lossy conducting medium.
  • such a lossy conducting medium can comprise a terrestrial medium such as the Earth or other medium.
  • Region 2 is a second medium that shares a boundary interface with Region 1 and has different constitutive parameters relative to Region 1.
  • Region 2 can comprise, for example, any insulator such as the atmosphere or other medium.
  • the reflection coefficient for such a boundary interface goes to zero only for incidence at a complex Brewster angle. See Stratton, J.A. , Electromagnetic Theory, McGraw-Hill, 1941 , p. 516.
  • the present disclosure sets forth various polyphase waveguide probes that generate electromagnetic fields that are substantially mode-matched to a Zenneck surface wave mode on the surface of the lossy conducting medium comprising Region 1 .
  • such electromagnetic fields substantially synthesize a wave front incident at a complex Brewster angle of the lossy conducting medium that results in zero reflection.
  • u x is the propagation constant in the positive vertical direction in Region 1
  • u 2 is the propagation constant in the vertical direction in Region 2
  • ⁇ is the conductivity of Region 1
  • ⁇ is equal to 2n
  • f is a frequency of excitation
  • ⁇ 0 is the permittivity of free space
  • ⁇ 1 is the permittivity of Region 1
  • A is a source constant imposed by the source
  • z is a vertical coordinate normal to the surface of Region 1
  • y is a surface wave radial propagation constant
  • p is the radial coordinate.
  • Equations (1 )-(3) can be considered to be a cylindrically -symmetric, radially-propagating waveguide mode. See Barlow, H. M., and Brown, J., Radio Surface Waves, Oxford University Press, 1962, pp. 10-12, 29-33.
  • the present disclosure details structures that excite this "open boundary" waveguide mode.
  • a polyphase waveguide probe is provided with charge terminals of appropriate size that are positioned relative to each other and are fed with voltages and/or currents so as to excite the relative phasing of the fields of the surface waveguide mode that is to be launched along the boundary interface between Region 2 and Region 1.
  • Equation (12) implies that the fields specified in Equations (1)-(3) can be obtained by driving a radial surface current density along the boundary interface, such radial surface current density being specified by
  • Equation (13) can be restated as
  • a polyphase waveguide probe 200 that includes a charge terminal Ti and a charge terminal T 2 that are arranged along a vertical axis z.
  • the polyphase waveguide probe 200 is disposed above a lossy conducting medium 203 according to an embodiment of the present disclosure.
  • the lossy conducting medium 203 makes up Region 1 (FIG. 2) according to one embodiment.
  • a second medium 206 shares a boundary interface with the lossy conducting medium 203 and makes up Region 2 (FIG. 2).
  • the polyphase waveguide probe 200 includes a probe coupling circuit 209 that couples an excitation source 213 to the charge terminals T-i and T 2 as is discussed in greater detail with reference to later figures.
  • the charge terminals T-i and T 2 are positioned over the lossy conducting medium 203.
  • the charge terminal Ti can be considered a capacitor, and the charge terminal T 2 can comprise a counterpoise or lower capacitor as is described herein.
  • the charge terminal Ti is positioned at height H-i , and the charge terminal T 2 is positioned directly below Ti along the vertical axis z at height H 2 , where H 2 is less than H-,.
  • the asymptotes representing the radial current close-in and far-out as set forth by Equations (17) and (18) are complex quantities.
  • a physical surface current, J(r) is synthesized to match as close as possible the current asymptotes in magnitude and phase. That is to say close-in,
  • the phase of J(r) should transition from the phase of J-i close-in to the phase of J 2 far-out.
  • phase far-out ⁇ 2
  • phase boost due to the phase of y which is arg(Vy)
  • ⁇ is expressed in Equation (9) above, and depending on the values for ⁇ ⁇ and ⁇ at the site of transmission on the lossy conducting medium and the operating frequency f, arg(Vy), which has two complex roots, is typically on the order of approximately 45° or 225°.
  • far-out should differ from the phase of the surface current
  • the properly adjusted synthetic radial surface current is
  • Equations (1 )-(6) and (20) have the nature of a transmission line mode bound to a lossy interface, not radiation fields such as are associated with groundwave propagation. See Barlow, H. M. and Brown, J., Radio Surface Waves, Oxford University Press, 1962, pp. 1-5. These fields automatically satisfy the complex Brewster angle requirement for zero reflection, which means that radiation is negligible, while surface guided wave propagation is dramatically enhanced, as is verified and supported in the experimental results provided below.
  • phase boost 45° or, equivalent ⁇ A/8.
  • FIG. 4 to further illustrate the phase transition between J-t (FIG. 3) and J 2 (FIG. 3) shown is an illustration of the phases of the surface currents Ji close-in and J 2 far-out relative to a position of a polyphase waveguide probe 200 (FIG. 3).
  • a transition region is located between the observation point Pi and observation point P 2 .
  • the observation point P 0 is located at the position of the polyphase waveguide probe 200.
  • the observation point P-i is positioned "close-in” at a distance R-i from the observation point P 0 that places the observation point P-i between the transition region 216 and the observation point P 0 .
  • the observation point P 2 is positioned "far-out” at a distance R 2 from the observation point P 0 beyond the transition region 216 as shown.
  • the magnitude and phase of the radial current J is expressed as
  • the magnitude and phase of the radial current J is expressed as
  • the magnitude and phase of the radial current J is expressed as
  • the additional phase shift ⁇ & occurs as a property of the Hankel function as mentioned above.
  • the polyphase waveguide probe 200 generates the surface current Ji close-in and then transitions to the J 2 current far-out.
  • the phase of the Zenneck surface-waveguide mode transitions by approximately 45 degrees or - ⁇ .
  • This transition or phase shift can be considered a "phase boost" as the phase of the Zenneck surface-waveguide mode appears to advance by 45 degrees in the transition region 216.
  • the transition region 216 appears to occur somewhere less than 1/10 of a wavelength of the operating frequency.
  • a polyphase waveguide probe can be created that will launch the appropriate radial surface current distribution.
  • a Zenneck waveguide mode is created in a radial direction. If the J(r) given by Equation (20) can be created, it will automatically launch Zenneck surface waves.
  • a lossy conducting medium such as, for example, a terrestrial medium presents phase shifted images. That is to say, the image charges CV and Q 2 ' are at complex depths.
  • the image charges CV and Q 2 ' are at complex depths.
  • the complex spacing of image charges C and Q 2 ' implies that the external fields will experience extra phase shifts not encountered when the interface is either a lossless dielectric or a perfect conductor.
  • ⁇ ⁇ is the complex Brewster angle.
  • the electric field vector E is to be synthesized as an incoming nonuniform plane wave, polarized parallel to the plane of incidence.
  • the electric field vector E can be created from independent horizontal and vertical components as:
  • E p (p, z) E(p, z) cos ⁇ 0 , and (38a) which means that the field ratio is tan ⁇ 0 . (39)
  • Equations mean that if one controls the magnitude of the complex field ratio and the relative phase between the incident vertical and horizontal components E z and E p in a plane parallel to the plane of incidence, then the synthesized E-field vector will effectively be made to be incident at a complex Brewster angle. Such a circumstance will synthetically excite a Zenneck surface wave over the interface between Region 1 and Region 2.
  • FIG. 6 shown is another view of the polyphase waveguide probe 200 disposed above a lossy conducting medium 203 according to an embodiment of the present disclosure.
  • the lossy conducting medium 203 makes up Region 1 (FIG. 2) according to one embodiment.
  • a second medium 206 shares a boundary interface with the lossy conducting medium 203 and makes up Region 2 (FIG. 2).
  • the lossy conducting medium 203 comprises a terrestrial medium such as the planet Earth.
  • a terrestrial medium comprises all structures or formations included thereon whether natural or man-made.
  • such a terrestrial medium can comprise natural elements such as rock, soil, sand, fresh water, sea water, trees, vegetation, and all other natural elements that make up our planet.
  • such a terrestrial medium can comprise man-made elements such as concrete, asphalt, building materials, and other man-made materials.
  • the lossy conducting medium 203 can comprise some medium other than the Earth, whether naturally occurring or man-made.
  • the lossy conducting medium 203 can comprise other media such as man-made surfaces and structures such as automobiles, aircraft, man-made materials (such as plywood, plastic sheeting, or other materials) or other media. .
  • the second medium 206 can comprise the atmosphere above the ground.
  • the atmosphere can be termed an "atmospheric medium” that comprises air and other elements that make up the atmosphere of the Earth.
  • the second medium 206 can comprise other media relative to the lossy conducting medium 203.
  • the polyphase waveguide probe 200 comprises a pair of charge terminals T-i and T 2 . Although two charge terminals T-i and T 2 are shown, it is understood that there can be more than two charge terminals Ti and T 2 . According to one embodiment, the charge terminals Ti and T 2 are positioned above the lossy conducting medium 203 along a vertical axis z that is normal to a plane presented by the lossy conducting medium 203. In this respect, the charge terminal Ti is placed directly above the charge terminal T 2 although it is possible that some other arrangement of two or more charge terminals T N can be used. According to various embodiments, charges Q 1 and Q 2 can be imposed on the respective charge terminals ⁇ and T 2 .
  • the charge terminals T-i and/or T 2 can comprise any conductive mass that can hold an electrical charge.
  • the charge terminal T-i has a self-capacitance C-i
  • the charge terminal T 2 has a self-capacitance C 2 .
  • the charge terminals Ti and/or T 2 can comprise any shape such as a sphere, a disk, a cylinder, a cone, a torus, a randomized shape, or any other shape.
  • the charge terminals l-i and T 2 need not be identical, but each can have a separate size and shape, and be comprises of different conducting materials.
  • the shape of the charge terminal T-i is specified to hold as much charge as practically possible.
  • the field strength of a Zenneck surface wave launched by a polyphase waveguide probe 200 is directly proportional to the quantity of charge on the terminal T-i.
  • the respective self- capacitance C-i and C 2 can be calculated.
  • the polyphase waveguide probe 200 comprises a probe coupling circuit 209 that is coupled to the charge terminals T-i and T 2 .
  • the probe coupling circuit 209 facilitates coupling the excitation source 213 to the charge terminals Ti and T 2 , and facilitates generating respective voltage magnitudes and phases on the charge terminals T-i and T 2 for a given frequency of operation. If more than two charge terminals T N are employed, then the probe coupling circuit 209 would be configured to facilitate the generation of various voltage magnitudes and phases on the respective charge terminals T N relative to each other.
  • the probe coupling circuit 209 comprises various circuit configurations as will be described.
  • the probe coupling circuit 209 is specified so as to make the polyphase waveguide probe 200 electrically half-wave resonant. This imposes a voltage +V on a first one of the terminals T-i or T 2 , and a -V on the second one of the charge terminals Ti or T 2 at any given time. In such case, the voltages on the respective charge terminals T-i and T 2 are 180 degrees out of phase as can be appreciated. In the case that the voltages on the respective charge terminals T-i and T 2 are 180 degrees out of phase, the largest voltage magnitude differential is experienced on the charge terminals ⁇ and T 2 .
  • the probe coupling circuit 209 can be configured so that the phase differential between the charge terminals T-i and T 2 is other than 180 degrees. To this end, the probe coupling circuit 209 can be adjusted to alter the voltage magnitudes and phases during adjustment of the polyphase waveguide probe 200.
  • a mutual capacitance C is created between the charge terminals ⁇ and T 2 .
  • the charge terminal ⁇ has self-capacitance and the charge terminal T 2 has a self- capacitance C 2 as mentioned above.
  • the mutual capacitance C M depends on the distance between the charge terminals T-i and T 2 .
  • the field strength generated by the polyphase waveguide probe 200 will be directly proportional to the magnitude of the charge Qi that is imposed on the upper terminal T-i.
  • an excitation source 213 is coupled to the probe coupling circuit 209 in order to apply a signal to the polyphase waveguide probe 200.
  • the excitation source 213 can be any suitable electrical source such as a voltage or current source capable of generating the voltage or current at the operating frequency that is applied to the polyphase waveguide probe 200.
  • the excitation source 213 can comprise, for example, a generator, a function generator, transmitter, or other electrical source.
  • the excitation source 213 can be coupled to the polyphase waveguide probe 200 by way of magnetic coupling, capacitive coupling, or conductive (direct tap) coupling as will be described.
  • the probe coupling circuit 209 can be coupled to the lossy conducting medium 203.
  • the excitation source 213 can be coupled to the lossy conducting medium 203 as will be described.
  • the polyphase waveguide probe 200 described herein has the property that its radiation resistance R r is very small or even negligible.
  • radiation resistance R r is the equivalent resistance that would dissipate the same amount of power that is ultimately radiated from an antenna.
  • the polyphase waveguide probe 200 launches a Zenneck surface wave that is a guided electromagnetic wave.
  • the polyphase waveguide probes described herein have little radiation resistance R r because the height of such polyphase waveguide probes is usually small relative to their operating wavelengths.
  • the polyphase waveguide probes described herein are "electrically small.”
  • the phrase “electrically small” is defined as a structure such as the various embodiments of polyphase waveguide probes described herein that can be physically bounded by a sphere having a radius equal to ⁇ /2 ⁇ , where ⁇ is the free-space wavelength. See Fujimoto, K., A. Henderson, K. Hirasawa, and J.R. James, Small Antennas, Wiley, 1987, p. 4.
  • ⁇ is provided as one benchmark, it is understood that the ratio of the height h of the transmission structure over the wavelength of the operating signal at the operating frequency can be any value. However, it is understood that, at a given frequency of operation, as the height of a given transmission structure increases, the radiation resistance R r will increase accordingly.
  • the radiation resistance R r can be of a value such that some amount of radiation can occur along with the launching of a Zenneck surface wave.
  • the polyphase waveguide probe 200 can be constructed to have a short height h relative to the wavelength at the frequency of operation so as to ensure that little or substantially zero energy is lost in the form of radiation.
  • the placement of the charge reservoirs T-i and T 2 along the vertical axis z provides for symmetry in the Zenneck surface wave that is launched by the polyphase waveguide probe 200 as described by the Hankel functions in Equations (20)-(23) set forth above.
  • the polyphase waveguide probe 200 is shown with two charge reservoirs Ti and T 2 along the vertical axis z that is normal to a plane making up the surface of the lossy conducting medium 203, it is understood that other configurations can be employed that will also provide for the desired symmetry.
  • additional charge reservoirs T N can be positioned along the vertical axis z, or some other arrangement can be employed.
  • symmetry of transmission may not be desired.
  • the charge reservoirs T N can be arranged in a configuration other than along a vertical axis z to provide for an alternative transmission distribution pattern.
  • the polyphase waveguide probe 200 When properly adjusted to operate at a predefined operating frequency, the polyphase waveguide probe 200 generates a Zenneck surface wave along the surface of the lossy conducting medium 203.
  • an excitation source 213 can be employed to generate electrical energy at a predefined frequency that is applied to the polyphase waveguide probe 200 to excite the structure.
  • the energy from the excitation source 213 is transmitted in the form of a Zenneck surface wave by the polyphase waveguide probe 200 to one or more receivers that are also coupled to the lossy conducting medium 203 or that are located within an effective transmission range of the polyphase waveguide probe 200.
  • the energy is thus conveyed in the form of a Zenneck surface wave which is a surface- waveguide mode or a guided electromagnetic field.
  • a Zenneck surface wave comprises a transmission line mode.
  • the Zenneck surface wave generated by the polyphase waveguide probe 200 is not a radiated wave, but a guided wave in the sense that these terms are described above.
  • the Zenneck surface wave is launched by virtue of the fact that the polyphase waveguide probe 200 creates electromagnetic fields that are substantially mode-matched to a Zenneck surface wave mode on the surface of the lossy conducting medium 203.
  • the electromagnetic fields generated by the polyphase waveguide probe 200 are substantially mode-matched as such, the electromagnetic fields substantially synthesize a wave front incident at a complex Brewster angle of the lossy conducting medium 203 that results in little or no reflection. Note that if the polyphase waveguide probe 200 is not substantially mode-matched to the Zenneck surface wave mode, then a Zenneck surface wave will not be launched since the complex Brewster angle of the lossy conducting medium 203 would not have been attained.
  • the Zenneck surface wave mode will depend upon the dielectric permittivity ⁇ ⁇ and conductivity ⁇ of the site at which the polyphase waveguide probe 200 is located as indicated above in Equations (1)-(11).
  • the phase of the Hankel functions in Equations (20)-(23) above depends on these constitutive parameters at the launch site and on the frequency of operation.
  • the polyphase waveguide probe 200 substantially synthesizes the radial surface current density on the lossy conducting medium of the Zenneck surface wave mode as is expressed by Equation (20) set forth above.
  • Equation (20) set forth above.
  • the electromagnetic fields are then substantially or approximately mode-matched to a Zenneck surface wave mode on the surface of the lossy conducting medium 203.
  • the match should be as close as is practicable.
  • this Zenneck surface wave mode to which the electromagnetic fields are substantially matched is expressed in Equations (21 )-(23) set forth above.
  • the electrical characteristics of the polyphase waveguide probe 200 should be adjusted to impose appropriate voltage magnitudes and phases on the charge terminals Ti and T 2 for a given frequency of operation and given the electrical properties of the site of transmission. If more than two charge terminals T N are employed, then appropriate voltage magnitudes and phases would need to be imposed on the respective charge terminals T N , where N can even be a very large number effectively comprising a continuum of charge terminals. [0079] In order to obtain the appropriate voltage magnitudes and phases for a given design of a polyphase waveguide probe 200 at a given location, an iterative approach can be used.
  • analysis can be performed of a given excitation and configuration of a polyphase waveguide probe 200 taking into account the feed currents to the terminals ⁇ and T 2 , the charges on the charge terminals T-i and T 2 , and their images in the lossy conducting medium 203 in order to determine the radial surface current density generated.
  • This process can be performed iteratively until an optimal configuration and excitation for a given polyphase waveguide probe 200 is determined based on desired parameters.
  • a guided field strength curve 103 (FIG.
  • Equations (1)-(11 ) can be generated using Equations (1)-(11 ) above based on values for the conductivity of Region 1 ( ⁇ ⁇ ) and the permittivity of Region 1 ( ⁇ ⁇ ) at the location of the polyphase waveguide probe 200.
  • Such a guided field strength curve 103 will provide a benchmark for operation such that measured field strengths can be compared with the magnitudes indicated by the guided field strength curve 103 to determine if optimal transmission has been achieved.
  • various parameters associated with the polyphase waveguide probe 200 can be adjusted. Stated another way, the various parameters associated with the polyphase waveguide probe 200 can be varied to adjust the polyphase waveguide probe 200 to a desired operating configuration.
  • One parameter that can be varied to adjust the polyphase waveguide probe 200 is the height of one or both of the charge terminals T-i and/or T 2 relative to the surface of the lossy conducting medium 203.
  • the distance or spacing between the charge terminals T-i and T 2 can also be adjusted. In doing so, one can minimize or otherwise alter the mutual capacitance C M or any bound capacitances between the charge terminals T-i and T 2 and the lossy conducting medium 203 as can be appreciated.
  • another parameter that can be adjusted is the size of the respective charge terminals T-i and/or T 2 .
  • the size of the charge terminals T-i and/or T 2 By changing the size of the charge terminals T-i and/or T 2 , one will alter the respective self-capacitances Ci and/or C 2 , and the mutual capacitance C M as can be appreciated. Also, any bound capacitances that exist between the charge terminals Ti and T 2 and the lossy conducting medium 203 will be altered. In doing so, the voltage magnitudes and phases on the charge terminals T-i and T 2 are altered.
  • the probe coupling circuit 209 associated with the polyphase waveguide probe 200 is another parameter that can be adjusted. This can be accomplished by adjusting the size of the inductive and/or capacitive reactances that make up the probe coupling circuit 209. For example, where such inductive reactances comprise coils, the number of turns on such coils can be adjusted. Ultimately, the adjustments to the probe coupling circuit 209 can be made to alter the electrical length of the probe coupling circuit 209, thereby affecting the voltage magnitudes and phases on the charge terminals T-i and T 2 .
  • a field meter tuned to the transmission frequency can be placed an appropriate distance from the polyphase waveguide probe 200 and adjustments can be made as set forth above until a maximum or any other desired field strength of a resulting Zenneck surface wave is detected.
  • the field strength can be compared with a guided field strength curve 103 (FIG. 1) generated at the desired operating frequency and voltages on the terminals Ti and T 2 .
  • the appropriate distance for placement of such a field meter can be specified as greater than the transition region 216 (FIG. 4) in the "far-out" region described above where the surface current J 2 dominates.
  • polyphase waveguide probes 200 denoted herein as polyphase waveguide probes 200a-j, according to various embodiments of the present disclosure.
  • the polyphase waveguide probes 200a-j each include a different probe coupling circuit 209, denoted herein as probe coupling circuits 209a-j, according to various embodiments.
  • probe coupling circuits 209a-j While several examples of probe coupling circuits 209a-j are described, it is understood that these embodiments are merely examples and that there can be many other probe coupling circuits 209 not set forth herein that can be employed to provide for the desired voltage magnitudes and phases on the charge terminals T-, and T 2 according to the principles set forth herein in order to facilitate the launching of Zenneck surface waves.
  • each of the probe coupling circuits 209a-j can employ, but are not limited to, inductive impedances comprising coils. Even though coils are used, it is understood that other circuit elements, both lumped and distributed, can be employed as reactances. Also, other circuit elements can be included in the probe coupling circuits 209a-j beyond those illustrated herein.
  • the polyphase waveguide probe 200a includes the charge terminals Ti and T 2 that are positioned along a vertical axis z that is substantially normal to the plane presented by the lossy conducting medium 203.
  • the second medium 206 is above the lossy conducting medium 203.
  • the charge terminal T-i has a self-capacitance C-,
  • the charge terminal T 2 has a self-capacitance C 2 .
  • charges Q-i and Q 2 are imposed on the charge terminals T-j and T 2 , respectively, depending on the voltages applied to the charge terminals T-i and T 2 at any given instant.
  • a mutual capacitance C M can exist between the charge terminals Ti and T 2 depending on the distance there between.
  • bound capacitances can exist between the respective charge terminals T-i and T 2 and the lossy conducting medium 203 depending on the heights of the respective charge terminals T-i and T 2 with respect to the lossy conducting medium 203.
  • the polyphase waveguide probe 200a includes a probe coupling circuit 209a that comprises an inductive impedance comprising a coil L 1a having a pair of leads that are coupled to respective ones of the charge terminals Ti and T 2 .
  • the coil L 1a is specified to have an electrical length that is one-half (1 ⁇ 2) of the wavelength at the operating frequency of the polyphase waveguide probe 200a.
  • the coil L a can be specified with an electrical length at other values. According to one embodiment, the fact that the coil L 1a has an electrical length of approximately one-half the wavelength at the operating frequency provides for an advantage in that a maximum voltage differential is created on the charge terminals J- and T 2 . Nonetheless, the length or diameter of the coil
  • L 1a can be increased or decreased when adjusting the polyphase waveguide probe 200a to obtain optimal excitation of a Zenneck surface wave mode.
  • the inductive impedance is specified to have an electrical length that is significantly less than or greater than 1 ⁇ 2 the wavelength at the operating frequency of the polyphase waveguide probe 200a.
  • the excitation source 213 is coupled to the probe coupling circuit 209 by way of magnetic coupling. Specifically, the excitation source 213 is coupled to a coil l_ P that is inductively coupled to the coil L 1a . This can be done by link coupling, a tapped coil, a variable reactance, or other coupling approach as can be appreciated. To this end, the coil L P acts as a primary, and the coil L 1a acts as a secondary as can be appreciated.
  • the heights of the respective charge terminals T-i and T 2 can be altered with respect to the lossy conducting medium 203 and with respect to each other. Also, the sizes of the charge terminals Ti and T 2 can be altered. In addition, the size of the coil L a can be altered by adding or eliminating turns or by changing some other dimension of the coil L 1a .
  • the polyphase waveguide probe 200b includes the charge terminals T-i and T 2 that are positioned along a vertical axis z that is substantially normal to the plane presented by the lossy conducting medium 203.
  • the second medium 206 is above the lossy conducting medium 203.
  • the charge terminals T-i and T 2 are positioned along a vertical axis z to provide for cylindrical symmetry in the resulting Zenneck surface wave as was described above.
  • the charge terminal T has a self-capacitance C-i
  • the charge terminal T 2 has a self-capacitance C 2 .
  • charges Qi and Q 2 are imposed on the charge terminals T 1 and T 2 , respectively, depending on the voltages applied to the charge terminals Ti and T 2 at any given instant.
  • a mutual capacitance C M can exist between the charge terminals Ti and T 2 depending on the distance there between.
  • bound capacitances can exist between the respective charge terminals Ti and T 2 and the lossy conducting medium 203 depending on the heights of the respective charge terminals T-i and T 2 with respect to the lossy conducting medium 203.
  • the polyphase waveguide probe 200b also includes a probe coupling circuit 209b comprising a first coil L 1 and a second coil L 2b .
  • the first coil L 1 is coupled to each of the charge terminals T-i and T 2 as shown.
  • the second coil L 2b is coupled to the charge terminal T 2 and to the lossy conducting medium 203.
  • the excitation source 213 is magnetically coupled to the probe coupling circuit 209b in a manner similar as was mentioned with respect to the polyphase waveguide probe 200a (FIG. 7A) set forth above. To this end, the excitation source 213 is coupled to a coil L P that acts as a primary and the coil L 1b acts as a secondary. Alternatively, the coil L 2b can act as a secondary as well.
  • the heights of the respective charge terminals Ti and T 2 can be altered with respect to the lossy conducting medium 203 and with respect to each other. Also, the sizes of the charge terminals T-i and T 2 can be altered. In addition, the size of each of the coils L b and L 2b can be altered by adding or eliminating turns or by changing some other dimension of the respective coils L 1b or L 2b .
  • the polyphase waveguide probe 200c includes the charge terminals T-i and T 2 that are positioned along a vertical axis z that is substantially normal to the plane presented by the lossy conducting medium 203.
  • the second medium 206 is above the lossy conducting medium 203.
  • the charge terminal T-i has a self-capacitance C-i
  • the charge terminal T 2 has a self-capacitance C 2 .
  • charges Q and Q 2 are imposed on the charge terminals Ti and T 2 , respectively, depending on the voltages applied to the charge terminals T-i and T 2 at any given instant.
  • a mutual capacitance C M can exist between the charge terminals Ti and T 2 depending on the distance there between.
  • bound capacitances can exist between the respective charge terminals T-, and T 2 and the lossy conducting medium 203 depending on the heights of the respective charge terminals T-i and T 2 with respect to the lossy conducting medium 203.
  • the polyphase waveguide probe 200c also includes a probe coupling circuit 209c comprising a coil L 1c .
  • a probe coupling circuit 209c comprising a coil L 1c .
  • One end of the coil L 1c is coupled to the charge terminal Ti as shown.
  • the second end of the coil L c is coupled to the lossy conducting medium 203.
  • a tap that is coupled to the charge terminal T 2 is positioned along the coil L 1c .
  • the excitation source 213 is magnetically coupled to the probe coupling circuit 209c in a manner similar as was mentioned with respect to the polyphase waveguide probe 200a (FIG. 7A) set forth above. To this end, the excitation source 213 is coupled to a coil L P that acts as a primary and the coil L 1c acts as a secondary. The coil L P can be positioned at any location along the coil L c . [0102] In order to adjust the polyphase waveguide probe 200c for the excitation and transmission of a desired Zenneck surface wave, the heights of the respective charge terminals ⁇ and T 2 can be altered with respect to the lossy conducting medium 203 and with respect to each other. Also, the sizes of the charge terminals Ti and T 2 can be altered.
  • the size of the coil L 1c can be altered by adding or eliminating turns, or by changing some other dimension of the coil L 1c .
  • the inductance presented by the portions of the coil L 1c above and below the tap can be adjusted by moving the position of the tap.
  • the polyphase waveguide probe 200d includes the charge terminals ⁇ and T 2 that are positioned along a vertical axis z that is substantially normal to the plane presented by the lossy conducting medium 203.
  • the second medium 206 is above the lossy conducting medium 203.
  • the charge terminal has a self-capacitance C 1 t and the charge terminal T 2 has a self-capacitance C 2 .
  • charges Q-i and Q 2 are imposed on the charge terminals and T 2 , respectively, depending on the voltages applied to the charge terminals Ti and T 2 at any given instant.
  • a mutual capacitance C can exist between the charge terminals Ti and T 2 depending on the distance there between.
  • bound capacitances can exist between the respective charge terminals Ti and T 2 and the lossy conducting medium 203 depending on the heights of the respective charge terminals T-i and T 2 with respect to the lossy conducting medium 203.
  • the polyphase waveguide probe 200d also includes a probe coupling circuit 209d comprising a first coil L 1d and a second coil L 2( j.
  • a first lead of the first coil L 1d is coupled to the charge terminal Ti, and the second lead of the first coil L d is coupled to the lossy conducting medium 203.
  • a first lead of the second coil L 2d is coupled to the charge terminal T 2 , and the second lead of the second coil L 2d is coupled to the lossy conducting medium 203.
  • the excitation source 213 is magnetically coupled to the probe coupling circuit 209d in a manner similar as was mentioned with respect to the polyphase waveguide probe 200a (FIG. 7A) set forth above. To this end, the excitation source 213 is coupled to a coil L P that acts as a primary and the coil L 2d acts as a secondary. Alternatively, the coil l_ d can act as a secondary as well.
  • the heights of the respective charge terminals Ti and T 2 can be altered with respect to the lossy conducting medium 203 and with respect to each other. Also, the sizes of the charge terminals Ti and T 2 can be altered. In addition, the size of each of the coils L 1d and L 2d can be altered by adding or eliminating turns or by changing some other dimension of the respective coils L d or L 2d ,
  • the polyphase waveguide probe 200e includes the charge terminals T-, and T 2 that are positioned along a vertical axis z that is substantially normal to the plane presented by the lossy conducting medium 203.
  • the second medium 206 is above the lossy conducting medium 203.
  • the charge terminals T-i and T 2 are positioned along a vertical axis z to provide for cylindrical symmetry in the resulting Zenneck surface wave as was described above.
  • the charge terminal Ti has a self-capacitance C-i
  • the charge terminal T 2 has a self-capacitance C 2 .
  • charges Q-i and Q 2 are imposed on the charge terminals T-, and T 2 , respectively, depending on the voltages applied to the charge terminals T-i and T 2 at any given instant.
  • a mutual capacitance C M can exist between the charge terminals T-i and T 2 depending on the distance there between.
  • bound capacitances can exist between the respective charge terminals T-i and T 2 and the lossy conducting medium 203 depending on the heights of the respective charge terminals T-i and T 2 with respect to the lossy conducting medium 203.
  • the polyphase waveguide probe 200e also includes a probe coupling circuit 209e comprising a first coil L 1e and a resistor R 2 .
  • a first lead of the first coil L e is coupled to the charge terminal T-i, and the second lead of the first coil L 1e is coupled to the lossy conducting medium 203.
  • a first lead of the resistor R 2 is coupled to the charge terminal T 2 , and the second lead of the resistor R 2 is coupled to the lossy conducting medium 203.
  • the excitation source 213 is magnetically coupled to the probe coupling circuit 209e in a manner similar as was mentioned with respect to the polyphase waveguide probe 200a (FIG. 7A) set forth above. To this end, the excitation source 213 is coupled to a coil L P that acts as a primary and the coil L 1e acts as a secondary.
  • the heights of the respective charge terminals T-i and T 2 can be altered with respect to the lossy conducting medium 203 and with respect to each other. Also, the sizes of the charge terminals Ti and T 2 can be altered. In addition, the size of the coil Lie can be altered by adding or eliminating turns or by changing some other dimension of the respective coils L 1e . In addition, the magnitude of the resistance R 2 can be adjusted as well.
  • the polyphase waveguide probe 200f includes a charge terminal ⁇ , and a ground screen G that acts as a second charge terminal.
  • the charge terminal ⁇ , and the ground screen G are positioned along a vertical axis z that is substantially normal to the plane presented by the lossy conducting medium 203.
  • the second medium 206 is above the lossy conducting medium 203. Note that to calculate the height h of the transmission structure, the height H 2 of the ground screen G is subtracted from the height H-i of the charge terminal ⁇ ,.
  • the charge terminal T-i has a self-capacitance d
  • the ground screen G has a self-capacitance C 2 .
  • charges Qi and Q 2 are imposed on the charge terminal Ti and the ground screen G, respectively, depending on the voltages applied to the charge terminal T-i and the ground screen G at any given instant.
  • a mutual capacitance C M can exist between the charge terminal ⁇ , and the ground screen G depending on the distance there between.
  • bound capacitances can exist between the charge terminal Ti and/or the ground screen G and the lossy conducting medium 203 depending on the heights of the charge terminal T-i and the ground screen G with respect to the lossy conducting medium 203.
  • a bound capacitance will exist between the ground screen G and the lossy conducting medium 203 due to its proximity to the lossy conducting medium 203.
  • the polyphase waveguide probe 200f includes a probe coupling circuit 209f that is made up of an inductive impedance comprising a coil L f having a pair of leads that are coupled to the charge terminal Ti and ground screen G.
  • the coil L 1f is specified to have an electrical length that is one-half (1 ⁇ 2) of the wavelength at the operating frequency of the polyphase waveguide probe 200f.
  • the electrical length of the coil L 1f is specified as approximately one-half (1/2) the wavelength at the operating frequency, it is understood that the coil L f can be specified with an electrical length at other values. According to one embodiment, the fact that the coil L 1f has an electrical length of approximately one-half the wavelength at the operating frequency provides for an advantage in that a maximum voltage differential is created on the charge terminal Ti and the ground screen G. Nonetheless, the length or diameter of the coil L f can be increased or decreased when adjusting the polyphase waveguide probe 200f to obtain optimal transmission of a Zenneck surface wave.
  • the inductive impedance is specified to have an electrical length that is significantly less than or greater than 1 ⁇ 2 the wavelength at the operating frequency of the polyphase waveguide probe 200f.
  • the excitation source 213 is coupled to the probe coupling circuit 209f by way of magnetic coupling. Specifically, the excitation source 213 is coupled to a coil L P that is inductively coupled to the coil L 1f . This can be done by link coupling, a phasor/coupling network, or other approach as can be appreciated. To this end, the coil L P acts as a primary, and the coil L f acts as a secondary as can be appreciated.
  • the heights of the respective charge terminals T-i and T 2 can be altered with respect to the lossy conducting medium 203 and with respect to each other. Also, the sizes of the charge terminals Ti and T 2 can be altered. In addition, the size of the coil L 1f can be altered by adding or eliminating turns or by changing some other dimension of the coil L 1f .
  • the polyphase waveguide probe 200g includes the charge terminals T-i and T 2 that are positioned along a vertical axis z that is substantially normal to the plane presented by the lossy conducting medium 203.
  • the second medium 206 is above the lossy conducting medium 203.
  • the charge terminals T-i and T 2 are positioned along a vertical axis z to provide for cylindrical symmetry in the resulting Zenneck surface wave as was described above.
  • the charge terminal T-i has a self-capacitance C-i
  • the charge terminal T 2 has a self-capacitance C 2 .
  • charges Qi and Q 2 are imposed on the charge terminals Ti and T 2 , respectively, depending on the voltages applied to the charge terminals Ti and T 2 at any given instant.
  • a mutual capacitance C M can exist between the charge terminals Ti and T 2 depending on the distance there between.
  • bound capacitances can exist between the respective charge terminals T-i and T 2 and the lossy conducting medium 203 depending on the heights of the respective charge terminals T-i and T 2 with respect to the lossy conducting medium 203.
  • the polyphase waveguide probe 200g also includes a probe coupling circuit 209g comprising a first coil L 1g , a second coil L 2g , and a variable capacitor C v .
  • the first coil l_i g is coupled to each of the charge terminals T-i and T 2 as shown.
  • the second coil L 2g has a first lead that is coupled to a variable capacitor C v and a second lead that is coupled to the lossy conducting medium 203.
  • the variable capacitor C v is coupled to the charge terminal T 2 and the first coil L 1g .
  • the excitation source 213 is magnetically coupled to the probe coupling circuit 209g in a manner similar as was mentioned with respect to the polyphase waveguide probe 200a (FIG. 7A) set forth above. To this end, the excitation source 213 is coupled to a coil L P that acts as a primary and either the coil L 1g or the coil L 2g can act as a secondary.
  • the heights of the respective charge terminals ⁇ and T 2 can be altered with respect to the lossy conducting medium 203 and with respect to each other. Also, the sizes of the charge terminals and T 2 can be altered.
  • the size of each of the coils L g and L 2g can be altered by adding or eliminating turns or by changing some other dimension of the respective coils L 1g or L 2g .
  • the variable capacitance C v can be adjusted.
  • the polyphase waveguide probe 200h includes the charge terminals ⁇ and T 2 that are positioned along a vertical axis z that is substantially normal to the plane presented by the lossy conducting medium 203.
  • the second medium 206 is above the lossy conducting medium 203.
  • the charge terminal Ti has a self-capacitance C-i
  • the charge terminal T 2 has a self-capacitance C 2 .
  • charges Qi and Q 2 are imposed on the charge terminals J, and T 2 , respectively, depending on the voltages applied to the charge terminals Ti and T 2 at any given instant.
  • a mutual capacitance C M can exist between the charge terminals and T 2 depending on the distance there between.
  • bound capacitances can exist between the respective charge terminals Ti and T 2 and the lossy conducting medium 203 depending on the heights of the respective charge terminals T 1 and T 2 with respect to the lossy conducting medium 203.
  • the polyphase waveguide probe 200h also includes a probe coupling circuit 209h comprising a first coil L 1h and a second coil L 2 h.
  • the first lead of the first coil L 1h is coupled to the charge terminal T-i
  • the second lead of the first coil L h is coupled to the second charge terminal T 2 .
  • a first lead of the second coil L 2h is coupled to a terminal T T
  • the second lead of the second coil L 2h is coupled to the lossy conducting medium 203.
  • the terminal T T is positioned relative to the charge terminal T 2 such that a coupling capacitance C c exists between the charge terminal T 2 and the terminal T T .
  • the excitation source 213 is magnetically coupled to the probe coupling circuit 209h in a manner similar as was mentioned with respect to the polyphase waveguide probe 200a (FIG. 7A) set forth above. To this end, the excitation source 213 is coupled to a coil L P that acts as a primary and the coil L 2h acts as a secondary. Alternatively, the coil L h can act as a secondary as well.
  • the heights of the respective charge terminals T-i and T 2 can be altered with respect to the lossy conducting medium 203 and with respect to each other.
  • the sizes of the charge terminals ⁇ and T 2 can be altered.
  • the size of each of the coils L 1h and L 2h can be altered by adding or eliminating turns or by changing some other dimension of the respective coils L-i h or L 2h .
  • the spacing between the charge terminal T 2 and the terminal T T can be altered, thereby modifying the coupling capacitance C c as can be appreciated.
  • polyphase waveguide probe 200i shown is yet another example of the polyphase waveguide probe 200 (FIG. 6), denoted herein as polyphase waveguide probe 200i, according to one embodiment.
  • the polyphase waveguide probe 200i is very similar to the polyphase waveguide probe 200h (FIG. 7H) except for the fact that the excitation source 213 is series-coupled to the probe coupling circuit 209i as will be described.
  • the polyphase waveguide probe 200i includes the charge terminals Ti and T 2 that are positioned along a vertical axis z that is substantially normal to the plane presented by the lossy conducting medium 203.
  • the second medium 206 is above the lossy conducting medium 203.
  • the charge terminal Ti has a self-capacitance Ci
  • the charge terminal T 2 has a self-capacitance C 2 .
  • charges Q-i and Q 2 are imposed on the charge terminals T-i and T 2 , respectively, depending on the voltages applied to the charge terminals Ti and T 2 at any given instant.
  • a mutual capacitance C M can exist between the charge terminals T-i and T 2 depending on the distance there between.
  • bound capacitances can exist between the respective charge terminals T-i and T 2 and the lossy conducting medium 203 depending on the heights of the respective charge terminals Ti and T 2 with respect to the lossy conducting medium 203.
  • the polyphase waveguide probe 200i also includes a probe coupling circuit 209i comprising a first coil L nj and a second coil L 2i .
  • the first lead of the first coil L rt is coupled to the charge terminal T-i
  • the second lead of the first coil L-n is coupled to the second charge terminal T 2 .
  • a first lead of the second coil L 2i is coupled to a terminal T T
  • the second lead of the second coil L 2i is coupled to an output of the excitation source 213.
  • a ground lead of the excitation source 213 is coupled to the lossy conducting medium 203.
  • the terminal T T is positioned relative to the charge terminal T 2 such that a coupling capacitance C c exists between the charge terminal T 2 and the terminal T T .
  • the polyphase waveguide probe 200i provides one example where the excitation source 213 is series-coupled to the probe coupling circuit 209i as mentioned above. Specifically, the excitation source 213 is coupled between the coil L 2l and the lossy conducting medium 203.
  • the heights of the respective charge terminals Ti and T 2 can be altered with respect to the lossy conducting medium 203 and with respect to each other.
  • the sizes of the charge terminals T-i and T 2 can be altered.
  • the size of each of the coils L-n and L 2 can be altered by adding or eliminating turns or by changing some other dimension of the respective coils L Vl or L 2i .
  • the spacing between the charge terminal T 2 and the terminal T T can be altered, thereby modifying the coupling capacitance C c as can be appreciated.
  • the polyphase waveguide probe 200j includes the charge terminals ⁇ and T 2 that are positioned along a vertical axis z that is substantially normal to the plane presented by the lossy conducting medium 203.
  • the second medium 206 is above the lossy conducting medium 203.
  • the charge terminal T-i comprises a sphere and the charge terminal T 2 comprises a disk.
  • the polyphase waveguide probe 200j provides an illustration that the charge terminals TN can comprise any shape.
  • the charge terminal T- has a self-capacitance Ci
  • the charge terminal T 2 has a self-capacitance C 2 .
  • charges Qi and Q 2 are imposed on the charge terminals T-i and T 2 , respectively, depending on the voltages applied to the charge terminals T-i and T 2 at any given instant.
  • a mutual capacitance C M can exist between the charge terminals Ti and T 2 depending on the distance there between.
  • bound capacitances can exist between the respective charge terminals T-i and T 2 and the lossy conducting medium 203 depending on the heights of the respective charge terminals Ti and T 2 with respect to the lossy conducting medium 203.
  • the polyphase waveguide probe 200j includes a probe coupling circuit 209j comprising an inductive impedance comprising a coil l_i j having a pair of leads that are coupled to respective ones of the charge terminals Ti and T 2 .
  • the coil L-i j is specified to have an electrical length that is one-half (1 ⁇ 2) of the wavelength at the operating frequency of the polyphase waveguide probe 200j. While the electrical length of the coil l_i j is specified as approximately one-half (1/2) the wavelength at the operating frequency, it is understood that the coil U j can be specified with an electrical length at other values as was discussed with reference to the polyphase waveguide probe 200a (FIG. 7A) described above.
  • the probe coupling circuit 209j includes a tap 223 on the coil L
  • the excitation source 213 is magnetically coupled to the probe coupling circuit
  • the excitation source 213 is coupled to a coil L P that acts as a primary and the coil acts as a secondary.
  • the coil L P can be positioned at any location along the coil Li j . Also, the coil L P can be positioned above or below the tap 223.
  • the heights of the respective charge terminals T-i and T 2 can be altered with respect to the lossy conducting medium 203 and with respect to each other. Also, the sizes of the charge terminals ⁇ and T 2 can be altered. In addition, the size of the coil Li, can be altered by adding or eliminating turns or by changing some other dimension of the coil L ⁇ . Further, the position of the tap 223 on the coil can be adjusted.
  • each of the polyphase waveguide probes 200a-j can be excited to transmit energy conveyed in the form of a guided wave, or waveguide mode along the surface of the lossy conducting medium 203.
  • the elements of each of the polyphase waveguide probes 200a-j can be adjusted to impose a desired voltage magnitude and phase on the respective charge terminals T-i and T 2 when the respective polyphase waveguide probe 200a-j is excited.
  • excitation can occur by applying energy from an excitation source 213 to the respective polyphase waveguide probe 200a-j as was described above.
  • the voltage magnitudes and phases imposed on the charge terminals Ti and T 2 can be adjusted in order to substantially synthesize the fields that are substantially mode- matched to the guided or Zenneck surface-waveguide mode of the lossy conducting medium 203 at the site of transmission given the local permittivity ⁇ ⁇ , conductivity ⁇ , and potentially other parameters of the lossy conducting medium 203.
  • the waveguide mode of the surface- guided wave is expressed in Equations (21 ), (22), and (23) set forth above. This surface- waveguide mode has a radial surface current density expressed in Equation (20) in Amperes per meter.
  • a guided surface wave can be launched if such fields at least approximate the surface-waveguide mode.
  • the fields are synthesized to match the surface-waveguide mode within an acceptable engineering tolerance so as to launch a guided surface wave.
  • the polyphase waveguide probes 200 can be adjusted to match the radial surface current density of the guided surface-waveguide mode within an acceptable engineering tolerance so as to launch a Zenneck surface wave mode.
  • the various polyphase waveguide probes 200a-j set forth above excite surface currents, the fields of which are designed to approximately match a propagating Zenneck surface wave mode and a Zenneck surface wave is launched.
  • the guiding interface is the interface between Region 1 (FIG. 2) and Region 2 (FIG. 2) as described above.
  • the guiding interface is the interface between the lossy conducting medium 203 presented by the Earth and the atmospheric medium as described above.
  • FIGS. 8A, 8B, and 8C shown are examples of graphs 300a, 300b, and 300c that depict field strength in Volts per meter as a function of distance in kilometers for purposes of comparison between a Zenneck surface wave and conventionally radiated fields.
  • the various graphs 300a, 300b, and 300c illustrate how the distance of transmission of a Zenneck surface wave varies with the frequency of
  • Each graph 300a, 300b, and 300c depicts a corresponding guided field strength curve 303a, 303b, and 303c and corresponding radiated field strength curves 306a, 306b, and 306c.
  • the guided field strength curves 303a, 303b, and 303c were generated assuming various parameters. Specifically, the graphs 300a, 300b, and 300c were calculated with a constant charge (FIG. 3) applied to the upper terminal T-i (FIG. 3) at frequencies of 10 MHz, 1 MHz, and 0.1 MHz, respectively.
  • the resulting terminal charge Q T i which is the controlling parameter for field strength was kept at the same value for all three guided field strength curve 303a, 303b, and 303c.
  • the Zenneck surface wave for each case is identified as guided field strength curves 303a, 303b, and 303c, respectively.
  • the Norton ground wave field strength in Volts per meter for a short vertical monopole antenna, of the same height as the respective polyphase waveguide probe 200, with an assumed ground loss of 10 ohms, is represented by the radiated field strength curves 306a, 306b, and 306c, respectively. It is asserted that this is a reasonably realistic assumption for monopole antenna structures operating at these frequencies.
  • the critical point is that a properly mode-matched polyphase waveguide probe launches a guided surface wave which dramatically outperforms the radiation field of any monopole at distances out to just beyond the "knee" in the guided field strength curves 303a- c of the respective Zenneck surface waves.
  • the propagation distance of a guided surface wave varies as a function of the frequency of transmission. Specifically, the lower the transmission frequency, the less the exponential attenuation of the guided surface wave and, therefore, the farther the guided surface wave will propagate.
  • each of the guided field strength curves 303a, 303b, and 303c feature a knee as was described above. As the frequency of transmission of a polyphase waveguide probe described herein decreases, the knee of the corresponding guided field strength curve 303a, 303b, and 303c will push to the right in the graph.
  • FIG. 8A shows a guided field strength curve 303a and a radiated field strength curve 306a generated at a frequency of 10 Megahertz.
  • the guided surface wave falls off below 10 kilometers.
  • the guided field strength curve 303b and the radiated field strength curve 306b are generated at a frequency of 1 Megahertz.
  • the guided field strength curve 303b falls off at approximately 100 kilometers.
  • the guided field strength curve 303c and the radiated field strength curve 306c are generated at a frequency of 100 Kilohertz (which is .1 Megahertz).
  • the guided field strength curve 303c falls off at between 4000-7000 Kilometers.
  • the frequency is low enough, it can be possible to transmit a guided surface wave around the entire Earth. It is believed that such frequencies can be at or below approximately 20-25 kilohertz. It should be noted that at such low frequencies, the lossy conducting medium 203 (FIG. 6) ceases to be a plane and becomes a sphere. Thus, when a lossy conducting medium 203 comprises a terrestrial medium, the calculation of guided field strength curves will be altered to take into account the spherical shape at low frequencies where the propagation distances approach size of the terrestrial medium.
  • a polyphase waveguide probe 200 (FIG. 6) using the terrestrial medium of Earth as the lossy conducting medium 203 according to the various embodiments.
  • the frequency of operation and identify the desired field strength of the guided surface wave at a distance of interest from the respective polyphase waveguide probe 200 to be constructed.
  • a smaller self-capacitance C-i can make a given polyphase waveguide probe 200 more sensitive to small variations in the permittivity t r or conductivity ⁇ of the Earth at or near the transmission site.
  • Such variation in the permittivity ⁇ ⁇ or conductivity ⁇ might occur due to variation in the climate given the transition between the seasons or due to changes in local weather conditions such as the onset of rain, drought, and/or other changes in local weather. Consequently, according to one embodiment, the charge terminal ⁇ can be specified so as to have a relatively large self- capacitance C 1 as is practicable.
  • the self-capacitance Ci of the charge terminal ⁇ and the voltage to be imposed thereon are determined, next the self-capacitance C 2 and physical location of the second charge terminal T 2 are to be determined.
  • the self-capacitance C 2 of the charge terminal T 2 it has been found easiest to specify the self-capacitance C 2 of the charge terminal T 2 to be the same as the self-capacitance C-i of the charge terminal TV This can be accomplished by making the size and shape of the charge terminal T 2 the same as the size and shape of the charge terminal T This would ensure that symmetry is maintained and will avoid the possibility of unusual phase shifts between the two charge terminals Ti and T 2 that might negatively affect achieving a match with the complex Brewster angle as described above.
  • the charge terminal T 2 can be positioned directly under the charge terminal Ti along the vertical axis z (FIG. 6) as described above. Alternatively, it can be possible to position the charge terminal T 2 at some other location with some resulting effect.
  • the distance between the charge terminals T-i and T 2 should be specified so as to provide for the best match between the fields generated by the polyphase waveguide probe 200 and the guided surface-waveguide mode at the site of transmission. As a suggested starting point, this distance can be set so that the mutual capacitance C M (FIG. 6) between the charge terminals T-i and T 2 is the same or less than the isolated capacitance C on the charge terminal T-i. Ultimately, one should specify the distance between the charge terminals T-i and T 2 to make the mutual capacitance C M as small as is practicable. The mutual capacitance C M can be determined by measurement, and the charge terminals T-i and T 2 can be positioned accordingly.
  • Another consideration to take into account when determining the height h associated with a polyphase waveguide probe 200 is whether radiation is to be avoided. Specifically, as the height h of the polyphase waveguide probe 200 approaches an appreciable portion of a wavelength at the frequency of operation, the radiation resistance R r will grow quadratically with height h and radiation will begin to dominate over the generation of a guided surface wave as described above.
  • One benchmark set forth above that ensures the Zenneck surface wave will dominate over any radiation is to make sure the height h is less than 10% of the wavelength at the frequency of operation, although other benchmarks can be specified. In some cases, it can be desired to allow some degree of radiation to occur in addition to launching a guided surface wave, where the height h can be specified accordingly.
  • the probe coupling circuit 209 (FIG. 6) is specified to provide for the voltage phase between the charge terminals ⁇ and T 2 .
  • the voltage phase appears to have a significant effect on creating fields that mode-match the guided surface-waveguide mode at the site of transmission.
  • the probe coupling circuit 209 can be specified to provide for a voltage phase differential of 180 degrees on the charge terminals Ti and T 2 . That is to say, the probe coupling circuit 209 is specified so that voltage V on the charge terminal Ti is 180 degrees out of phase with respect to the voltage on the charge terminal T 2 .
  • one example approach is to place a coil L 1a (FIG. 7A) between the charge terminals T-i and T 2 as described above with reference to the polyphase waveguide probe 200a and adjust the coil L 1a until the resulting system is electrically half- wave resonant. This would place a voltage V on the charge terminal Ti and voltage -V on the charge terminal T 2 such that the largest voltages are placed on the charge terminals T-, and T 2 180 degrees out of phase.
  • the excitation source 213 (FIG. 6) can then be coupled to the probe coupling circuit 209 and the output voltage adjusted to achieve the required voltage V to provide for the needed charge Q as described above.
  • the excitation source 213 can be coupled via magnetic coupling, capacitive coupling, or conductive coupling (direct) to the probe coupling circuit 209. Note that the output of the excitation source 213 can be stepped up using a transformer or via some other approach if necessary.
  • the location of the coil L a can be at any location such as down on the ground by the excitation source 213. Alternatively, as per best RF practice, the coil L 1a can be positioned directly between the charge reservoirs ⁇ and T 2 . Principles of impedance matching can be applied when coupling the excitation source 213 to the probe coupling circuit 209.
  • phase differential does not necessarily have to be 180 degrees.
  • FIG. 9 shown is a graph that presents the measured field strength of an electromagnetic field transmitted by one embodiment of an experimental polyphase waveguide probe measured on October 14, 2012 in Madison, New Hampshire.
  • the frequency of transmission was 59 MHz with a voltage of 60 mV imposed on the charge terminal Ti of the experimental polyphase waveguide probe.
  • the self-capacitance of the experimental polyphase waveguide probe was 8.5 pF.
  • the conductivity ⁇ of the ground at the test site is 0.0002 mhos/m, and the permittivity ⁇ ⁇ of the ground at the test site was 5. These values were measured in situ at the frequency in use.
  • the graph includes a guided field strength curve 400 that is labeled a "Zenneck” curve at 80% efficiency and a radiated field strength curve 403 that is labeled a "Norton” curve at 100% radiation efficiency, which is the best possible.
  • the radiated field strength curve 403 represents the radiated electromagnetic fields that would be generated by a 1 ⁇ 4 wavelength monopole antenna operating at a frequency of 59 MHz.
  • the circles 406 on the graph represent measured field strengths produced by the experimental polyphase waveguide probe. The field strength measurements were performed with a NIST-traceable Potomac Instruments FIM-71 commercial VHF field strength meter. As can be seen, the measured field strengths fall along the theoretical guided field strength curve 400. These measured field strengths are consistent with the propagation of a guided or Zenneck surface wave.
  • FIG. 10 shown is a graph that presents the measured phase of the transmitted electromagnetic wave from the experimental polyphase waveguide probe.
  • the curve J(r) indicates the phase of the fields incident to the currents Ji and J 2 with a transition between the currents J-] and J 2 as shown.
  • the curve 503 indicates the asymptote depicting the phase of the current J ( and the curve 506 indicates the asymptote depicting the phase of the current J 2 .
  • a difference of approximately 45 degrees generally exists between the phases of the respective currents and J 2 .
  • the circles 509 indicate measurements of the phase of the current J(r) generated by the experimental polyphase waveguide probe operating at 59 MHz as with FIG. 9. As shown, the circles 509 fall along the curve J(r) indicating that there is a transition of the phase of the current J(r) from the curve 503 to the curve 506.
  • phase of the current J(r) generated by the experimental polyphase waveguide probe transitions from the phase generated by the close-in current J-i to the far-out current J 2 .
  • these phase measurements are consistent with the phase with the presence of a guided or Zenneck surface wave.
  • FIG. 11 shown is a graph of a second set of measured data that depicts the field strength of an electromagnetic field transmitted by a second
  • the frequency of transmission was 1850 kHz with a voltage of 1250 V imposed on the charge terminal T-i of the experimental polyphase waveguide probe.
  • the self- capacitance C- ⁇ of the experimental polyphase waveguide probe in this experiment which was a flat conducting disk of 1 meter radius, was measured to be 70 pF.
  • the average conductivity ⁇ of the ground in the vicinity of experimentation was 0.006 mhos/m, and the relative permittivity ⁇ ⁇ of the ground was on the order of 15. These were determined at the frequency in use.
  • the radiated field strength curve 603 represents the conventional Norton ground wave field radiated from a conventional stub monopole antenna operating at a frequency of 1850 kHz over the lossy Earth.
  • the circles 606 on the graph represent measured field strengths produced by the experimental polyphase waveguide probe.
  • the field strength measurements were performed with a NIST-traceabie Potomac Instruments FIM-41 MF/HF field strength meter.
  • the measured field strength data are consistent with the presence of a guided or Zenneck surface wave. It is apparent from the experimental data that the measured field strengths observed at distances less than 15 miles could not possibly be due to conventional Norton ground wave propagation, and can only be due to guided surface wave propagation launched by the polyphase probe operating as disclosed above. Under the given 1.85 MHz experimental conditions, out at 20 miles it appears that a Norton ground wave component has finally overtaken the Zenneck surface wave component.
  • FIGS. 12A, 12B, and 13 shown are examples of generalized receive circuits for using the surface-guided waves in wireless power delivery systems.
  • FIGS. 12A and 12B include a linear probe 703 and a tuned resonator 706.
  • FIG. 13 is a magnetic coil 709 according to various embodiments of the present disclosure.
  • each one of the linear probe 703, the tuned resonator 706, and the magnetic coil 709 can be employed to receive power transmitted in the form of a guided surface wave on the surface of a lossy conducting medium 203 (FIG. 6) according to various embodiments.
  • the lossy conducting medium 203 comprises a terrestrial medium.
  • the open-circuit terminal voltage at the output terminals 713 of the linear probe 703 depends upon the effective height of the linear probe 703. To this end, the terminal point voltage can be calculated as
  • V T e E inc - dl, (43)
  • E inc the strength of the electric field in vector on the linear probe 703 in Volts per meter
  • dl an element of integration along the direction of the linear probe 703
  • h e the effective height of the linear probe 703.
  • An electrical load 716 is coupled to the output terminals 713 through an impedance matching network 719.
  • the linear probe 703 When the linear probe 703 is subjected to a guided surface wave as described above, a voltage is developed across the output terminals 713 that can be applied to the electrical load 716 through a conjugate impedance matching network 719 as the case may be.
  • the electrical load 716 In order to facilitate the flow of power to the electrical load 716, the electrical load 716 should be substantially impedance matched to the linear probe 703 as will be described below.
  • the tuned resonator 706 includes a charge terminal T R that is elevated above the lossy conducting medium 203.
  • the charge terminal T R has a self- capacitance C R .
  • the bound capacitance should preferably be minimized as much as is practicable, although this may not be entirely necessary in every instance of a polyphase waveguide probe 200.
  • the tuned resonator 706 also includes a coil L R .
  • One end of the coil l_ R is coupled to the charge terminal T R
  • the other end of the coil L R is coupled to the lossy conducting medium 203.
  • the tuned resonator 706 (which can also be referred to as tuned resonator L -C R ) comprises a series-tuned resonator as the charge terminal C R and the coil L R are situated in series.
  • the tuned resonator 706 is tuned by adjusting the size and/or height of the charge terminal T R , and/or adjusting the size of the coil L R so that the reactive impedance of the structure is substantially eliminated.
  • the reactance presented by the self-capacitance C R is calculated as— ⁇ — .
  • the total capacitance of the tuned resonator 706 can also include capacitance between the charge terminal T R and the lossy conducting medium 203, where the total capacitance of the tuned resonator 706 can be calculated from both the self- capacitance C R and any bound capacitance as can be appreciated.
  • the charge terminal T R can be raised to a height so as to substantially reduce or eliminate any bound capacitance. The existence of a bound capacitance can be determined from capacitance measurements between the charge terminal T R and the lossy conducting medium 203.
  • the inductive reactance presented by a discrete-element coil L R can be calculated as 7 ' ⁇ , where L is the lumped-element inductance of the coil L R . If the coil L R is a distributed element, its equivalent terminal-point inductive reactance can be determined by conventional approaches. To tune the tuned resonator 706, one would make adjustments so that the inductive reactance presented by the coil L R equals the capacitive reactance presented by the tuned resonator 706 so that the resulting net reactance of the tuned resonator 706 is substantially zero at the frequency of operation.
  • An impedance matching network 723 can be inserted between the probe terminals 721 and the electrical load 726 in order to effect a conjugate-match condition for maxim power transfer to the electrical load 726.
  • an electrical load 726 can be coupled to the tuned resonator 706 by way of magnetic coupling, capacitive coupling, or conductive (direct tap) coupling.
  • the elements of the coupling network can be lumped components or distributed elements as can be appreciated. In the embodiment shown in FIG.
  • magnetic coupling is employed where a coil L s is positioned as a secondary relative to the coil L R that acts as a transformer primary.
  • the coil L s can be link coupled to the coil L R by geometrically winding it around the same core structure and adjusting the coupled magnetic flux as can be appreciated.
  • the tuned resonator 706 comprises a series-tuned resonator, a parallel-tuned resonator or even a distributed-element resonator can also be used.
  • the magnetic coil 709 comprises a receive circuit that is coupled through an impedance coupling network 733 to an electrical load 736.
  • the magnetic coil 709 can be positioned so that the magnetic flux of the guided surface wave, ⁇ , passes through the magnetic coil 709, thereby inducing a current in the magnetic coil 709 and producing a terminal point voltage at its output terminals 729.
  • the magnetic flux of the guided surface wave coupled to a single turn coil is expressed by
  • ⁇ is the coupled magnetic flux
  • ⁇ ⁇ is the effective relative permeability of the core of the magnetic coil 709
  • ⁇ 0 is the permeability of free space
  • H is the incident magnetic field strength vector
  • n is a unit vector normal to the cross-sectional area of the turns
  • a C s is the area enclosed by each loop.
  • V - ⁇ — - ⁇ ⁇ ⁇ 0 ⁇ ⁇ (45)
  • the magnetic coil 709 can be tuned to the guided wave frequency either as a distributed resonator or with an external capacitor across its output terminals 729, as the case may be, and then impedance-matched to an external electrical load 736 through a conjugate impedance matching network 733.
  • the resulting circuit presented by the magnetic coil 709 and the electrical load 736 are properly adjusted and conjugate impedance matched, via impedance matching network 733, then the current induced in the magnetic coil 709 can be employed to optimally power the electrical load 736.
  • the receive circuit presented by the magnetic coil 709 provides an advantage in that it does not have to be physically connected to the ground.
  • the receive circuits presented by the linear probe 703, the tuned resonator 706, and the magnetic coil 709 each facilitate receiving electrical power transmitted from any one of the embodiments of polyphase waveguide probes 200 described above.
  • the energy received can be used to supply power to an electrical load 716/726/736 via a conjugate matching network as can be appreciated.
  • the receive circuits presented by the linear probe 703, the tuned resonator 706, and the magnetic coil 709 will load the excitation source 213 (FIG. 3) that is applied to the polyphase waveguide probe 200, thereby generating the guided surface wave to which such receive circuits are subjected.
  • the guided surface wave generated by a given polyphase waveguide probe 200 described above comprises a transmission line mode.
  • a power source that drives a radiating antenna that generates a radiated electromagnetic wave is not loaded by the receivers, regardless of the number of receivers employed.
  • a given polyphase waveguide probe 200 and receive circuits in the form of the linear probe 703, the tuned resonator 706, and/or the magnetic coil 709 can together make up a wireless distribution system.
  • the distance of transmission of a guided surface wave using a polyphase waveguide probe 200 as set forth above depends upon the frequency, it is possible that wireless power distribution can be achieved across wide areas and even globally.
  • the conventional wireless-power transmission/distribution systems extensively investigated today include "energy harvesting" from radiation fields and also sensor coupling to inductive or reactive near-fields.
  • the present wireless-power system does not waste power in the form of radiation which, if not intercepted, is lost forever.
  • the presently disclosed wireless-power system limited to extremely short ranges as with conventional mutual-reactance coupled near-field systems.
  • the wireless-power system disclosed herein probe-couples to the novel surface-guided transmission line mode, which is equivalent to delivering power to a load by a wave-guide or a load directly wired to the distant power generator.
  • FIG. 14A shown is a schematic that represents the linear probe 703 and the tuned resonator 706.
  • FIG 14B shows a schematic that represents the magnetic coil 709.
  • the linear probe 703 and the tuned resonator 706 can each be considered a Thevenin equivalent represented by an open-circuit terminal voltage source V s and a dead network terminal point impedance Z s .
  • the magnetic coil 709 can be viewed as a Norton equivalent represented by a short-circuit terminal current source l s and a dead network terminal point impedance Z s .
  • Each electrical load 716/726/736 (FIGS. 12A-B and FIG. 13) can be represented by a load impedance Z L .
  • the electrical load 716/726/736 is impedance matched to each receive circuit, respectively.
  • the conjugate match which states that if, in a cascaded network, a conjugate match occurs at any terminal pair then it will occur at all terminal pairs, then asserts that the actual electrical load 716/726/736 will also see a conjugate match to its impedance, Z L '. See Everitt, W.L. and G.E. Tanner, Communication Engineering, McGraw- Hill, 3 rd edition, 1956, p. 407. This ensures that the respective electrical load 716/726/736 is impedance matched to the respective receive circuit and that maximum power transfer is established to the respective electrical load 716/726/736.
  • Clause 1 A method, comprising the step of: transmitting energy conveyed in a form of a guided surface-waveguide mode along a surface of a terrestrial medium by exciting a polyphase waveguide probe.
  • Clause 2 The method of clause 1 , wherein the step of transmitting energy conveyed in the form of the guided surface-waveguide mode along the surface of the terrestrial medium by exciting the polyphase waveguide probe further comprises the step of synthesizing a plurality of fields that substantially match the guided surface-waveguide mode of the terrestrial medium.
  • ⁇ is a surface wave radial propagation constant given by Y — and u 2 is a
  • ⁇ is equal to 2nf, where f is a frequency of excitation of the polyphase waveguide probe, e 0 is a permittivity of free space, e r is a relative permittivity of the terrestrial medium, and a free-space wave number k 0 is equal to -, where ⁇ 0 is a free-space wavelength of the polyphase waveguide probe, j is equal to V- ⁇ , p is a radial coordinate, z is a vertical coordinate normal to the terrestrial medium, ⁇ is an azimuthal coordinate, l 0 is a net polyphase probe current, and H '(- j y p ) is a Hankel function of a second kind and a first order with a complex argument -j y p for an e +j t time variation, where t is time.
  • ⁇ is an azimuthal magnetic field strength
  • E p is a radial electric field strength
  • E z is a vertical electric field strength
  • ⁇ is a surface wave radial propagation constant given by
  • u 2 , . , where x ⁇ , ⁇ is a conductivity of the terrestrial medium, ⁇ is equal to 2nf, where f is a frequency of excitation of the polyphase waveguide probe, ⁇ 0 is a permittivity of free space, t r is a relative permittivity of the terrestrial medium, and a free-space wave number k 0 is equal to— , where ⁇ 0 is a free-space wavelength of the polyphase waveguide probe, is equal to V-l, p is a radial coordinate, z is a vertical coordinate normal to the terrestrial medium, ⁇ is an azimuthal coordinate, l 0 is a net polyphase probe current, Hi (2) ( -j y p ) is a Hankel function of a second kind and first order with complex argument - j y p , and H 0 ⁇ z) ( -j y p ) is a Hankel function of a second kind and zero order with complex argument - j
  • Clause 5 The method of any one of clauses 2-4, wherein the fields substantially synthesize a wave front incident at a complex Brewster angle of the terrestrial medium, resulting in a negligible reflection.
  • Clause 6 The method of any one of clauses 1-5 wherein the polyphase waveguide probe comprises a plurality of charge terminals, the method further comprising the step of adjusting the polyphase waveguide probe by adjusting a height of at least one of the charge terminals.
  • Clause 7. The method of any one of clauses 1-5, wherein the polyphase waveguide probe comprises a plurality of charge terminals, the method further comprising the step of tuning the polyphase waveguide probe by adjusting a distance between the charge terminals.
  • Clause 8 The method of any one of clauses 1-5, wherein the polyphase waveguide probe comprises a plurality of charge terminals, the method further comprising the step of tuning the polyphase waveguide probe by adjusting a size of at least one of the charge terminals.
  • Clause 9 The method of any one of clauses 1 -5, wherein the polyphase waveguide probe comprises a plurality of charge terminals, the method further comprising the step of tuning the polyphase waveguide probe by adjusting a probe coupling circuit coupled to the charge terminals.
  • An apparatus comprising: a polyphase waveguide probe configured to create a plurality of resultant fields that are substantially mode-matched to a Zenneck surface wave mode on a surface of a lossy conducting medium.
  • Clause 12 The apparatus of any one of clauses 10 or 11 , wherein a radiation resistance of the polyphase waveguide probe is substantially zero.
  • Clause 14 The apparatus of any one of clauses 10-13, wherein the resultant fields substantially synthesize a wave front incident at a complex Brewster angle of the lossy conducting medium, resulting in substantially zero reflection.
  • I + ⁇ e r - j x) O S 0 is a conductivity of the lossy conducting medium, ⁇ is equal to 2nf, where f is a frequency of excitation of the polyphase waveguide probe, ⁇ 0 is a permittivity of free space, e r ⁇ s a relative permittivity of the lossy conducting medium, and a free-space wave number k 0 is equal to ⁇ , where ⁇ 0 is a free-space wavelength of the polyphase waveguide probe, j is equal to V-l, p is a radial coordinate, z is a vertical coordinate normal to the lossy conducting medium, ⁇ is an azimuthal coordinate, l 0 is a net polyphase probe current, and Hi ⁇ 2> (- j y p ) is a Hankel function of a second kind and first order with complex argument -j y p for an e +J ot time variation, where f is time.
  • ⁇ ⁇ is an azimuthal magnetic field strength
  • E p is a radial electric field strength
  • E z is a vertical electric field strength
  • ⁇ is a surface wave radial propagation constant given by
  • ⁇ is equal to 2rrf, where f is a frequency of excitation of the polyphase waveguide probe, ⁇ 0 is a permittivity of free space, e r is a relative permittivity of the conducting lossy medium, and a free-space wave number k 0 is equal to— , where ⁇ 0 is a free-space wavelength of the polyphase waveguide probe, j is equal to V-l, p is a radial coordinate, z is a vertical coordinate normal to the lossy conducting medium, q> is an azimuthal coordinate, l 0 is a net polyphase probe current, H 2) ( -j y p ) is a Hankel function of a second kind and first order with complex argument - j p , and H 0 (2) ( -j y p ) is a Hankel function of a second kind and zero order with complex argument - j y p for an e +J'M time variation, where f is time.
  • Clause 18 The apparatus of any one of clauses 10-17, wherein the polyphase waveguide probe further comprises a plurality of charge terminals, the polyphase waveguide probe being further configured to impose a plurality of voltage magnitudes and a plurality of phases on the charge terminals.
  • Clause 19 The apparatus of any one of clauses 10-18, wherein the polyphase waveguide probe further comprises a probe coupling circuit coupled to the charge terminals, the probe coupling circuit being configured to impose the voltage magnitudes and the phases on the charge terminals.
  • Clause 20 The apparatus of any one of clauses 10-19, wherein both the voltage magnitudes and the phases vary as a function of a geometrical position of the charge terminals relative to each other.
  • Clause 21 The apparatus of any one of clauses 10-20, wherein both the voltage magnitudes and the phases vary as a function of a geometrical position of each of the charge terminals relative to the lossy conducting medium.
  • Clause 22 The apparatus of any one of clauses 10-21 , wherein both the voltage magnitudes and the phases vary as a function of a physical size of the charge terminals.
  • Clause 23 The apparatus of any one of clauses 10-22, wherein both the voltage magnitudes and the phases vary as a function of an electrical circuit.
  • Clause 24 The apparatus of any one of clauses 10-23, wherein the charge terminals are positioned along an axis.
  • Clause 25 The apparatus of any one of clauses 10-24, wherein an excitation source is series-coupled to the polyphase waveguide probe.
  • Clause 26 The apparatus of any one of clauses 10-17, wherein the polyphase waveguide probe further comprises a coil coupled to both a first charge terminal and a second charge terminal.
  • Clause 27 The apparatus of any one of clauses 10-17, wherein the polyphase waveguide probe further comprises a first coil and a second coil, wherein the first coil is coupled to both a first charge terminal and a second charge terminal, and the second coil is coupled to the second charge terminal and the lossy conducting medium.
  • Clause 28 The apparatus of any one of clauses 10-17, wherein the polyphase waveguide probe further comprises: a coil having a first end coupled to a first charge terminal and a second end coupled to the lossy conducting medium; and a tap is coupled to the second charge terminal and positioned along the coil.
  • Clause 29 The apparatus of any one of clauses 10-17, wherein the polyphase waveguide probe further comprises a first coil and a second coil, wherein the first coil is coupled to both a first charge terminal and the lossy conducting medium, and the second coil is coupled to both a second charge terminal and the lossy conducting medium.
  • Clause 30 The apparatus of any one of clauses 10-17, wherein the polyphase waveguide probe further comprises a coil coupled to a first charge terminal and the lossy conducting medium, and a resistor coupled to a second charge terminal and the lossy conducting medium.
  • Clause 32 The apparatus of any one of clauses 10-17, wherein the polyphase waveguide probe further comprises: a first coil coupled to both a first charge terminal and a second charge terminal; a second coil coupled to the lossy conducting medium and a capacitance; and the capacitance being further coupled to the second charge terminal.
  • the polyphase waveguide probe further comprises: a first coil coupled to both a first charge terminal and a second charge terminal; and a second coil coupled to a terminal and the lossy conducting medium, wherein the terminal is positioned relative to the second charge terminal resulting in a coupling capacitance between the terminal and the second charge terminal.
  • the polyphase waveguide probe further comprises: a first coil coupled to both a first charge terminal and a second charge terminal; a second coil coupled to a terminal, wherein the terminal is positioned relative to the second charge terminal resulting in a coupling capacitance between the terminal and the second charge terminal; and wherein the excitation source is coupled to the second coil and the lossy conducting medium.
  • Clause 36 The apparatus of any one of clauses 10-17, wherein the polyphase waveguide probe further comprises a plurality of charge terminals, wherein respective ones of the terminals comprise a sphere or a disk.
  • Clause 37 The apparatus of any one of clauses 10-17, wherein the polyphase waveguide probe further comprises: a coil having a first end coupled to a first charge terminal and a second end coupled to a second charge terminal; and a tap coupled to the lossy conducting medium and positioned along the coil.
  • Clause 38 The apparatus of any one of clauses 26-34, 36, and 37, further comprising an excitation source coupled to a primary coil, wherein the primary coil is magnetically coupled to the polyphase waveguide probe.
  • An apparatus comprising: a polyphase waveguide probe configured to create a plurality of resultant fields; and wherein the resultant fields are substantially mode-matched to a Zenneck surface wave mode on a surface of a terrestrial medium.
  • Clause 40 The apparatus of clause 39, wherein the resultant fields substantially synthesize a wave incident at a complex Brewster angle of the terrestrial medium, resulting in substantially zero reflection.
  • ⁇ is a surface wave radial and u 2 is a
  • I + ⁇ . ⁇ , - jx) ⁇ ⁇ 0 is a conductivity of the terrestrial medium, ⁇ is equal to 2nf, where ⁇ is a frequency of excitation of the polyphase waveguide probe, ⁇ 0 is a permittivity of free space, s r is a relative permittivity of the terrestrial medium, and a free-space wave number k 0 is equal to— , where ⁇ 0 is a free-space wavelength of the polyphase waveguide probe, j is equal to V-l, p is a radial coordinate, z is a vertical coordinate normal to the terrestrial medium, ⁇ is an azimuthal coordinate, l 0 is a net polyphase probe current, and Hi ⁇ 2) ( -j y p ) is a Hankel function of a second kind and first order with complex argument -j ' y p for an ⁇ + > ⁇ time variation, where t is time.
  • ⁇ ⁇ is an azimuthal magnetic field strength
  • E p is a radial electric field strength
  • E z is a vertical electric field strength
  • ⁇ is a surface wave radial propagation constant given by
  • ⁇ is equal to 2nf, where f is a frequency of excitation of the polyphase waveguide probe, ⁇ 0 is a permittivity of free space, ⁇ ⁇ is a relative permittivity of the terrestrial medium, and a free-space wave number k 0 is equal to— , where ⁇ 0 is a free-space wavelength of the polyphase waveguide probe, j is equal to V- ⁇ , p is a radial coordinate, z is a vertical coordinate normal to the terrestrial medium, ⁇ is an azimuthal coordinate, l 0 is a net polyphase probe current, -jy p ) is a Hankel function of a second kind and first order with complex argument -j y p , and H 0 (2) ( -j ' y p ) is a Hankel function of a second kind and zero order with complex argument -j y p for an e +jo)t time variation, where t is time.
  • Clause 43 The apparatus of any one of clauses 39-42, wherein the polyphase waveguide probe further comprises a pair of charge terminals, the polyphase waveguide probe being further configured to impose a plurality of voltage magnitudes and a plurality of phases on the charge terminals.
  • Clause 46 The apparatus of any one of clauses 44 or 45, wherein the distribution circuitry further comprises a coil.
  • Clause 48 The apparatus of clause 43, wherein both the voltage magnitudes and the phases vary as a function of a geometrical position of the charge terminals relative to each other.
  • Clause 50 The apparatus of clause 43, wherein both the voltage magnitudes and the phases vary as a function of a physical size of the charge terminals.
  • Clause 51 The apparatus of clause 43, wherein both the voltage magnitudes and the phases vary as a function of an electrical circuit.
  • Clause 52 The apparatus of any one of clauses 39-44 and 46-51 , wherein an excitation source is electrically coupled to the polyphase waveguide probe.
  • a method comprising the step of: positioning a receive circuit relative to a terrestrial medium; and receiving, via the receive circuit, energy conveyed in a form of a Zenneck surface wave on a surface of the terrestrial medium.
  • Clause 54 The method of clause 53, wherein an electrical load coupled to the receive circuit loads an excitation source coupled to a polyphase waveguide probe that generates the Zenneck surface wave.
  • Clause 55 The method of any one of clauses 53 or 54, wherein the energy further comprises electrical power, and the method further comprises the step of applying the electrical power to an electrical load coupled to the receive circuit, where the electrical power is used as a power source for the electrical load.
  • Clause 56 The method of any one of clauses 53-55, further comprising the step of impedance-matching an electrical load to the receive circuit.
  • Clause 57 The method of any one of clauses 53-56, further comprising the step of establishing a maximum power transfer from the receive circuit to the electrical load.
  • Clause 58 The method of any one of clauses 53-57, wherein the receive circuit further comprises a magnetic coil.
  • Clause 59 The method of any one of clauses 53-57, wherein the receive circuit further comprises a linear probe.
  • Clause 60 The method of any one of clauses 53-57, wherein the receive circuit further comprises a tuned resonator coupled to the terrestrial medium.
  • An apparatus comprising: a receive circuit that receives energy conveyed in a form of a Zenneck surface wave along a surface of a lossy conducting medium.
  • Clause 62 The apparatus of clause 61 , wherein the lossy conducting medium further comprises a terrestrial medium.
  • Clause 63 The apparatus of any one of clauses 61 or 62, wherein an electrical load coupled to the receive circuit loads an excitation source coupled to a polyphase waveguide probe that generates the Zenneck surface wave.
  • Clause 64 The apparatus of any one of clauses 61 or 62, wherein the energy further comprises electrical power, and the receive circuit is coupled to an electrical load, and wherein the electrical power is applied to the electrical load, the electrical power being employed as a power source for the electrical load.
  • Clause 65 The apparatus of any one of clauses 63 or 64, wherein the electrical load is impedance-matched with the receive circuit.
  • Clause 66 The apparatus of any one of clauses 61-65, wherein the receive circuit further comprises a magnetic coil.
  • Clause 67 The apparatus of any one of clauses 61-65, wherein the receive circuit further comprises a linear probe.
  • Clause 68 The apparatus of any one of clauses 61-65, wherein the receive circuit further comprises a tuned resonator.
  • Clause 70 The apparatus of clause 68, wherein the tuned resonator comprises a parallel tuned resonator.
  • a power transmission system comprising: a polyphase waveguide probe that transmits electrical energy in a form of a guided surface wave along a surface of a terrestrial medium; and a receive circuit that receives the electrical energy.
  • Clause 74 The power transmission system of clause 72, wherein an electrical load is coupled to the receive circuit and the electrical energy is used as a power source for the electrical load.
  • Clause 75 The power transmission system of any one of clauses 73 or 74, wherein the electrical load is impedance-matched to the receive circuit.
  • Clause 76 The power transmission system of any one of clauses 73 or 74, wherein a maximum power transfer is established from the receive circuit to the electrical load.
  • Clause 77 The power transmission system of any one of clauses 72-76, wherein the receive circuit further comprises a magnetic coil.
  • Clause 78 The power transmission system of any one of clauses 72-76, wherein the receive circuit further comprises a linear probe.
  • Clause 79 The power transmission system of any one of clauses 72-76, wherein the receive circuit further comprises a tuned resonator.
  • Clause 80 The power transmission system of any one of clauses 72-79, wherein the polyphase waveguide probe is configured to create a plurality of resultant fields that are substantially mode-matched to a guided surface wave mode on the surface of the terrestrial medium.
  • Clause 81 The power transmission system of any one of clauses 72-80, wherein a radiation resistance of the polyphase waveguide probe is substantially zero.
  • Clause 82 The power transmission system of any one of clauses 72-81 , wherein a height of the polyphase waveguide probe is less than ⁇ at an operating frequency of the polyphase waveguide probe, where A is a wavelength at the operating frequency.
  • Clause 83 The power transmission system of clause 80, wherein the resultant fields substantially synthesize a wave front incident at a complex Brewster angle of the lossy medium, resulting in substantially zero reflection.
  • Clause 84 The power transmission system of any one of clauses 72-83, wherein an excitation source is electrically coupled to the polyphase waveguide probe.
  • ⁇ is a surface wave radial propagation constant given by Y — j k 2 0 + and u 2 is a vertical propagation constant given by u 2 - , ⁇
  • ⁇ is a conductivity of the lossy medium
  • ⁇ is equal to 2rrf, where f is a frequency of excitation of the polyphase waveguide probe, ⁇ 0 is a permittivity of free space, z r is a relative permittivity of the lossy medium, and a free-space wave number k 0 is equal to— , where ⁇ 0 is a free-space wavelength of the polyphase waveguide probe, j is equal to - ⁇ , p is a radial coordinate, z is a vertical coordinate normal to the lossy medium, ⁇ is an azimuthal coordinate, l 0 is a net polyphase probe current, and Hf 2) (-j Y p ) ⁇ s a Hankel function of a second kind and first order with complex argument - j y p for an e +]a>t time variation, where t is time.
  • ⁇ ⁇ is an azimuthal magnetic field strength
  • E p is a radial electric field strength
  • E z is a vertical electric field strength
  • u 2 , 0 . , where x ⁇ , ⁇ is a conductivity of the lossy medium, ⁇ is equal to 2nf, where f is a frequency of excitation of the polyphase waveguide probe, ⁇ 0 is a permittivity of free space, z r is a relative permittivity of the lossy medium, and a free- space wave number k 0 is equal to— , where ⁇ 0 is a free-space wavelength of the polyphase waveguide probe, j is equal to ⁇ - ⁇ , p is a radial coordinate, z is a vertical coordinate normal to the lossy medium, ⁇ is an azimuthal coordinate, l 0 is a net polyphase probe current, ⁇ 2) ( -j y p ) is a Hankel function of a second kind and first order with complex argument - j y p , and H 0 (2> ( -j y p ) is a Hankel function of a second kind and zero order with

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  • Variable-Direction Aerials And Aerial Arrays (AREA)
  • Waveguide Connection Structure (AREA)
  • Magnetic Resonance Imaging Apparatus (AREA)
  • Radar Systems Or Details Thereof (AREA)
  • Waveguide Aerials (AREA)
  • Waveguides (AREA)
  • Control Of Motors That Do Not Use Commutators (AREA)
  • Details Of Aerials (AREA)
  • Geophysics And Detection Of Objects (AREA)
  • Optical Modulation, Optical Deflection, Nonlinear Optics, Optical Demodulation, Optical Logic Elements (AREA)
  • Near-Field Transmission Systems (AREA)
  • Investigating Or Analyzing Materials By The Use Of Ultrasonic Waves (AREA)
PCT/US2014/019477 2013-03-07 2014-02-28 Excitation and use of guided surface wave modes on lossy media WO2014137817A1 (en)

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EA201591655A EA201591655A1 (ru) 2013-03-07 2014-02-28 Возбуждение и применение направляемых мод поверхностной волны на средах с потерями
KR1020157024283A KR102137005B1 (ko) 2013-03-07 2014-02-28 손실 매체 상의 유도 표면파 모드의 여기 및 사용
EP14713640.2A EP2932558B1 (en) 2013-03-07 2014-02-28 Excitation and use of guided surface wave modes on lossy media
NZ712566A NZ712566A (en) 2013-03-07 2014-02-28 Excitation and use of guided surface wave modes on lossy media
AU2014226221A AU2014226221B2 (en) 2013-03-07 2014-02-28 Excitation and use of guided surface wave modes on lossy media
JP2015561472A JP6392790B2 (ja) 2013-03-07 2014-02-28 損失性媒体上での誘導表面波モードの励起および使用
BR112015021835A BR112015021835A2 (pt) 2013-03-07 2014-02-28 método, aparelho e sistema de transmissão de energia
CN201480021978.4A CN105164852B (zh) 2013-03-07 2014-02-28 有损介质上的引导表面波模式的激励和使用
DK14713640.2T DK2932558T3 (da) 2013-03-07 2014-02-28 Excitation og anvendelse af førte overfladebølgemodi på tabsgivende medier
CA2902460A CA2902460C (en) 2013-03-07 2014-02-28 Excitation and use of guided surface wave modes on lossy media
MX2015011406A MX355731B (es) 2013-03-07 2014-02-28 Excitación y uso de modos de onda de superficie guiada en medios con pérdida.
AP2015008677A AP2015008677A0 (en) 2013-03-07 2014-02-28 Excitation and use of guided surface wave modes onlossy media
SG11201507166YA SG11201507166YA (en) 2013-03-07 2014-02-28 Excitation and use of guided surface wave modes on lossy media
IL240240A IL240240B (en) 2013-03-07 2015-07-30 Excitation and use of field guided wave modes in energy dissipative media
PH12015501919A PH12015501919A1 (en) 2013-03-07 2015-09-01 Excitation and use guided surface wave modes on lossy media
SA515361007A SA515361007B1 (ar) 2013-03-07 2015-09-07 استثارة واستخدام أنماط موجات سطحية موجهة على أوساط عالية الفقد
HK16105833.2A HK1218024A1 (zh) 2013-03-07 2016-05-23 有損介質上的引導表面波模式的激勵和使用

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Cited By (17)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2016039832A1 (en) * 2014-09-10 2016-03-17 Cpg Technologies, Llc Excitation and use of guided surface wave modes on lossy media
WO2017044274A1 (en) * 2015-09-09 2017-03-16 Cpg Technologies, Llc. Wired and wireless power distribution coexistence
WO2017044273A1 (en) * 2015-09-09 2017-03-16 Cpg Technologies, Llc. Detecting unauthorized consumption of electrical energy
WO2017044281A1 (en) * 2015-09-09 2017-03-16 Cpg Technologies, Llc Guided surface waveguide probes
WO2017044227A1 (en) * 2015-09-08 2017-03-16 Cpg Technologies, Llc. Field strength monitoring for optimal performance
WO2017044295A1 (en) * 2015-09-09 2017-03-16 Cpg Technologies, Llc. Classification of transmission
CN108352727A (zh) * 2015-09-10 2018-07-31 Cpg技术有限责任公司 使用导向表面波的全球时间同步
CN108348757A (zh) * 2015-09-09 2018-07-31 Cpg技术有限责任公司 具有被引导的表面波的电力内部医疗设备
JP2018528752A (ja) * 2015-09-09 2018-09-27 シーピージー テクノロジーズ、 エルエルシーＣｐｇ Ｔｅｃｈｎｏｌｏｇｉｅｓ， Ｌｌｃ 帰路結合無線送電
JP2018528430A (ja) * 2015-09-08 2018-09-27 シーピージー テクノロジーズ、 エルエルシーＣｐｇ Ｔｅｃｈｎｏｌｏｇｉｅｓ， Ｌｌｃ 誘導表面波から受信した電力の測定及び通知
JP2018530231A (ja) * 2015-09-11 2018-10-11 シーピージー テクノロジーズ、 エルエルシーＣｐｇ Ｔｅｃｈｎｏｌｏｇｉｅｓ， Ｌｌｃ 強化された誘導表面導波プローブ
JP2018530819A (ja) * 2015-09-09 2018-10-18 シーピージー テクノロジーズ、 エルエルシーＣｐｇ Ｔｅｃｈｎｏｌｏｇｉｅｓ， Ｌｌｃ 物体識別システム及び方法
JP2018535467A (ja) * 2015-09-09 2018-11-29 シーピージー テクノロジーズ、 エルエルシーＣｐｇ Ｔｅｃｈｎｏｌｏｇｉｅｓ， Ｌｌｃ 物体識別システム及び方法
US10396566B2 (en) 2015-09-10 2019-08-27 Cpg Technologies, Llc Geolocation using guided surface waves
AU2015314931B2 (en) * 2014-09-11 2019-09-26 Cpg Technologies, Llc. Frequency division multiplexing for wireless power providers
US10680306B2 (en) 2013-03-07 2020-06-09 CPG Technologies, Inc. Excitation and use of guided surface wave modes on lossy media
WO2021165889A1 (en) 2020-02-20 2021-08-26 Cpg Technologies, Llc System and method for measuring fields over distance

Families Citing this family (8)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US10063095B2 (en) * 2015-09-09 2018-08-28 CPG Technologies, Inc. Deterring theft in wireless power systems
US20170077714A1 (en) * 2015-09-10 2017-03-16 Cpg Technologies, Llc Flexible network topology and bidirectional power flow
US10312747B2 (en) * 2015-09-10 2019-06-04 Cpg Technologies, Llc Authentication to enable/disable guided surface wave receive equipment
US20180366808A1 (en) * 2016-03-09 2018-12-20 Cpg Technologies, Llc Site specification for directional guided surface wave transmission in a lossy media
CN109196714A (zh) * 2016-03-09 2019-01-11 Cpg技术有限责任公司 引导表面波导探头结构
CN114824754B (zh) * 2019-10-31 2023-08-22 华为技术有限公司 移动终端
CN112886242A (zh) * 2021-01-12 2021-06-01 珠海格力电器股份有限公司 匹配电路、板载天线、板载天线的验证方法以及验证装置
WO2023119429A1 (ja) * 2021-12-21 2023-06-29 日本電信電話株式会社 アンテナ装置、無線電力伝送装置、及び無線電力伝送システム

Citations (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US3123767A (en) * 1964-03-03 Uator

Family Cites Families (9)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPS50103642A (ar) * 1974-01-23 1975-08-15
JPS50103642U (ar) * 1974-01-29 1975-08-26
US4751515A (en) * 1980-07-09 1988-06-14 Corum James F Electromagnetic structure and method
JPS5866428A (ja) * 1981-07-13 1983-04-20 ハネウエル・インコ−ポレ−テツド 送受信機
CN1139194C (zh) * 1998-10-21 2004-02-18 重庆新大地电子有限公司 甚低频地面波电话设备
EP2329505A1 (en) * 2008-08-25 2011-06-08 Governing Dynamics, LLC. Wireless energy transfer system
JP2010063213A (ja) * 2008-09-01 2010-03-18 Serukurosu:Kk 受電装置及び電力伝達システム
JP2011087266A (ja) * 2009-10-15 2011-04-28 Keycom Corp ワイヤレス給電が可能な床面／壁面２次元通信システム
GB2494435B (en) * 2011-09-08 2018-10-03 Roke Manor Res Limited Apparatus for the transmission of electromagnetic waves

Patent Citations (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US3123767A (en) * 1964-03-03 Uator

Non-Patent Citations (20)

* Cited by examiner, † Cited by third party
Title
BARLOW, H. M.; BROWN, J.: "Radio Surface Waves", 1962, OXFORD UNIVERSITY PRESS, pages: 1 - 5
BARLOW, H. M.; BROWN, J.: "Radio Surface Waves", 1962, OXFORD UNIVERSITY PRESS, pages: 10 - 12,29-33
COLLIN R E: "Hertzian dipole radiating over a lossy earth or sea: some early and late 20th-century controversies", IEEE ANTENNAS AND PROPAGATION MAGAZINE IEEE USA, vol. 46, no. 2, April 2004 (2004-04-01), pages 64 - 79, XP002726146, ISSN: 1045-9243 *
COLLIN, R. E.: "Field Theory of Guided Waves", vol. 453, 1960, MCGRAW-HILL, pages: 474 - 477
COLLIN, R. E.: "Hertzian Dipole Radiating Over a Lossy Earth or Sea: Some Early and Late 20th Century Controversies", IEEE ANTENNAS AND PROPAGATION MAGAZINE, vol. 46, no. 2, April 2004 (2004-04-01), pages 64 - 79, XP002726146, DOI: doi:10.1109/MAP.2004.1305535
EVERITT, W.L.; G.E. TANNER: "Communication Engineering", 1956, MCGRAW-HILL, pages: 407
FRIEDMAN, B.: "Principles and Techniques of Applied Mathematics", 1956, WILEY, pages: 214,283 - 286,290,
FUJIMOTO, K.; A. HENDERSON; K. HIRASAWA; J.R. JAMES: "Small Antennas", 1987, WILEV, pages: 4
HARRINGTON, R.F.: "Time-Harmonic Fields", 1961, MCGRAW-HILL, pages: 460 - 463
JAHNKE, E.; F. EMDE: "Tables of Functions", 1945, DOVER, pages: 145
MILLIGAN, T.: "Modern Antenna Design", 1985, MCGRAW-HILL, pages: 8 - 9
REICH, H. J.; ORDNUNG, P.F; KRAUSS, H.L.; SKALNIK, J.G.: "Microwave Theory and Techniques", 1953, VAN NOSTRAND, pages: 291 - 293
SOMMERFELD, A.: "Partial Differential Equations in Physics - Lectures on Theoretical Physics", vol. VI, 1949, ACADEMIC PRESS, article "Problems of Radio", pages: 236 - 289,295-
SOMMERFELD, A.: "Uber die Ausbreitung der Wellen in der Drahtlosen Telegraphie", ANNALEN DER PHYSIK, vol. 28, 1909, pages 665 - 736
STRATTON, J.A.: "Electromagnetic Theory", 1941, MCGRAW-HILL, pages: 516
STUTZMAN, W.L. ET AL.: "Antenna Theory and Desiqn", 1981, WILEY & SONS, pages: 93
WAIT J R ET AL: "Excitation of the HF surface wave by vertical and horizontal antennas", RADIO SCIENCE USA, vol. 14, no. 5, September 1979 (1979-09-01), pages 767 - 780, XP002726145, ISSN: 0048-6604 *
WAIT J R: "Excitation of surface waves on conducting, stratified, dielectric-clad and corrugated surfaces", RESEARCH OF THE NATIONAL BUREAU OF STANDARDS, vol. 59, no. 6, December 1957 (1957-12-01), pages 365 - 377, XP002726147 *
WAIT, J. R.: "Complex Image Theory-Revisited", IEEE ANTENNAS AND PROPAGATION MAGAZINE, vol. 33, no. 4, August 1991 (1991-08-01), pages 27 - 29, XP011419806, DOI: doi:10.1109/74.84529
ZENNECK, J.: "On the Propagation of Plane Electromagnetic Waves Along a Flat Conducting Surface and their Relation to Wireless Telegraphy", ANNALEN DER PHYSIK, SERIAL 4, vol. 23, 20 September 1907 (1907-09-20), pages 846 - 866

Cited By (33)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
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US10998604B2 (en) 2014-09-10 2021-05-04 Cpg Technologies, Llc Excitation and use of guided surface wave modes on lossy media
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US10274527B2 (en) 2015-09-08 2019-04-30 CPG Technologies, Inc. Field strength monitoring for optimal performance
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US10062944B2 (en) 2015-09-09 2018-08-28 CPG Technologies, Inc. Guided surface waveguide probes
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US9887558B2 (en) 2015-09-09 2018-02-06 Cpg Technologies, Llc Wired and wireless power distribution coexistence
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