WO2013060145A1 - 一种隔离驱动电路 - Google Patents

一种隔离驱动电路 Download PDF

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Publication number
WO2013060145A1
WO2013060145A1 PCT/CN2012/076843 CN2012076843W WO2013060145A1 WO 2013060145 A1 WO2013060145 A1 WO 2013060145A1 CN 2012076843 W CN2012076843 W CN 2012076843W WO 2013060145 A1 WO2013060145 A1 WO 2013060145A1
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WO
WIPO (PCT)
Prior art keywords
circuit
switch tube
diode
driving
bleeder
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Application number
PCT/CN2012/076843
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English (en)
French (fr)
Inventor
李俊凯
郑大成
万正海
戴彬传
Original Assignee
中兴通讯股份有限公司
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Publication of WO2013060145A1 publication Critical patent/WO2013060145A1/zh

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Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
    • H02M1/088—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the simultaneous control of series or parallel connected semiconductor devices
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03K—PULSE TECHNIQUE
    • H03K17/00—Electronic switching or gating, i.e. not by contact-making and –breaking
    • H03K17/51—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used
    • H03K17/56—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices
    • H03K17/687—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices the devices being field-effect transistors
    • H03K17/689—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices the devices being field-effect transistors with galvanic isolation between the control circuit and the output circuit
    • H03K17/691—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices the devices being field-effect transistors with galvanic isolation between the control circuit and the output circuit using transformer coupling
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03K—PULSE TECHNIQUE
    • H03K17/00—Electronic switching or gating, i.e. not by contact-making and –breaking
    • H03K17/06—Modifications for ensuring a fully conducting state
    • H03K2017/066—Maximizing the OFF-resistance instead of minimizing the ON-resistance

Definitions

  • the invention relates to an isolated driving circuit applied to a switching power supply power switch tube, in particular to an isolated driving circuit requiring two-way complementary.
  • the switching power supply scheme has been widely used, and its key device power switch tube operates under high frequency and high voltage conditions. Due to the needs of the circuit topology itself or based on safety considerations, it is necessary to isolate the drive pulse signal from the control circuit from the power switch.
  • FIG. 1 shows a conventional isolated driving circuit diagram provided by the prior art.
  • the dotted line frame is an isolated driving circuit of the power switching tube, including a primary side blocking capacitor C1, an isolated driving transformer T1, and a secondary side.
  • the driving pulse from the control circuit is added between point A and point B.
  • the voltage direction of the original secondary winding of the isolated driving transformer T1 is up-down and negative-negative, and is controlled by isolation and negative pressure. After that, it is output at point C and reference ground to drive the power switch tube Qswl.
  • the voltage at point A is the same as the voltage at point B.
  • the DC blocking capacitor C1 forces the isolation of the primary winding and the secondary winding voltage of the drive transformer T1 to change direction, that is, up and down.
  • the isolated drive transformer T1 forms a path through the secondary winding with the bootstrap diode D1 and the bootstrap capacitor C2 to achieve magnetic reset.
  • the voltage at point C is 0V, and the power switch tube Qswl is turned off. Since the power switch Qswl is usually a MOSFET, and the turn-on threshold of the MOSFET is low, when there is electromagnetic disturbance, the power switch Qswl is turned off when it should be turned off, thereby reducing the reliability of the entire switching power supply system. .
  • FIG. 2 shows a complementary conventional isolated driving circuit diagram provided by the prior art.
  • the dotted line frame is a complementary isolated driving circuit, including a primary side blocking capacitor C1, an isolated driving transformer T1 and a secondary side driving.
  • the voltage direction of the primary winding Lp of the isolated drive transformer T1 is up-down and negative-negative, and is isolated and driven by isolation conversion.
  • the voltage direction of the secondary winding Ls1 of the voltage regulator T1 is up and down, and the voltage direction of the secondary winding Ls2 of the isolated driving transformer is upper and lower positive, and a positive pulse signal is output between points C and D to maintain the power switch tube.
  • Qswl is reliably turned on, and a negative pulse signal is output between point E and point F to keep the power switch tube Qsw2 reliably turned off.
  • the voltage direction of the primary winding Lp of the isolated driving transformer T1 is upper and lower positive, and the secondary winding Lsl of the driving transformer T1 is isolated by isolation conversion.
  • the voltage direction is up and down, and the voltage direction of the secondary winding Ls2 of the isolated drive transformer is up and down, and a negative pulse signal is output between point C and point D, keeping the power switch Qswl reliably turned off, at point E.
  • a positive pulse signal is outputted between the point F and the power switch tube Qsw2 is reliably turned on.
  • This circuit can solve the abnormal action caused by the poor working environment of the conventional isolated driving circuit described in FIG.
  • the control circuit that generates the drive pulse consumes a large amount of power and generates a large heat.
  • control circuit configured to generate a drive pulse signal
  • An isolating drive transformer comprising a primary winding and one or more secondary windings; a DC blocking capacitor connecting the control circuit and a primary winding of the isolated drive transformer; and a drive circuit configured to: Between the secondary winding of the isolated drive transformer and the power switch tube, the power switch tube is turned on;
  • a bleeder circuit configured to turn off the power switch by discharging
  • a shutdown circuit is provided to maintain the power switch tube at a negative voltage to ensure that the power switch tube is reliably turned off.
  • an anode of the driving diode is connected to one end of the power switching tube via the secondary winding, and a cathode is connected to the other end of the power switching tube via the driving resistor.
  • an anode of the driving diode is sequentially connected to one end of the power switching tube via the driving resistor and the secondary winding, and a cathode thereof is connected to the other end of the power switching tube.
  • an anode of the driving diode is sequentially connected to one end of the power switching tube via the secondary winding and the driving resistor, and a cathode thereof is connected to the other end of the power switching tube.
  • the bleeder circuit includes:
  • a bleeder resistor one end connected to the emitter of the bleed P-type switch tube, one end connected to one end of the power switch tube;
  • the bleeder diode has an anode connected to the collector of the bleed P-type switch tube, and a cathode connected to the other end of the power switch tube.
  • the shutdown circuit includes:
  • a first voltage dividing resistor one end of which is connected to the anode of the shutdown diode via a secondary winding, and the other end of which is connected to the base of the bleed P-type switching tube;
  • a second voltage dividing resistor one end of which is connected to the cathode of the turn-off diode, and the other end of which is connected to the emitter of the bleeder P-type switch tube via the bleeder resistor;
  • the anode of the shutdown diode is connected to one end of the power switch tube, and the cathode is connected to the other end of the power switch tube via a second voltage dividing resistor.
  • the shutdown circuit further includes:
  • the first anti-saturation diode has an anode connected to the base of the bleed P-type switch tube, a cathode connected to the first voltage dividing resistor, a second anti-saturation diode, an anode connected to the collector of the bleed P-type switch tube, and a cathode connection thereof The cathode of the first anti-saturation diode.
  • the bleed P-type switch tube is a PNP triode or a P-type composite tube.
  • the switch maintains the magnitude of the negative voltage when turned off, thereby controlling the power consumption of the control circuit
  • the embodiment of the present invention retains the vertical blocking capacitance of the primary side, so that the primary winding of the driving transformer can be reset with a very stable voltage, and the output waveform of the isolated driving circuit has no spikes and oscillations.
  • the anti-saturation device can be serially connected in the shutdown circuit, that is, the anti-saturation diode is added to prevent the bleed P-type switch tube from entering deep saturation.
  • Embodiments of the present invention are not limited to single isolated driving, but can also be used for multiple isolated driving, especially dual complementary isolation driving.
  • the embodiments of the present invention not only retain the advantages of the conventional isolated driving circuit, but also solve the problems of the conventional isolated driving circuit.
  • FIG. 3 is a first connection diagram of a driving circuit according to an embodiment of the present invention.
  • FIG. 4 is a second connection diagram of a driving circuit according to an embodiment of the present invention.
  • FIG. 5 is a third connection diagram of a driving circuit according to an embodiment of the present invention.
  • FIG. 6 is a first connection diagram of a bleeder circuit according to an embodiment of the present invention.
  • FIG. 7 is a second connection diagram of a bleeder circuit according to an embodiment of the present invention.
  • FIG. 8 is a connection diagram of a shutdown circuit according to an embodiment of the present invention.
  • FIG. 9 is a connection diagram of a shutdown circuit for increasing saturation resistance according to an embodiment of the present invention.
  • FIG. 10 is a structural diagram of a single isolation driving circuit according to an embodiment of the present invention.
  • FIG. 11 is a structural diagram of a multi-channel isolation driving circuit according to an embodiment of the present invention.
  • FIG. 12 is a structural diagram of a dual-channel complementary isolation driving circuit according to an embodiment of the present invention
  • FIG. 13 is a circuit diagram of an isolated driving circuit according to an embodiment of the present invention
  • FIG. 14 is a diagram showing another isolation driving circuit according to an embodiment of the present invention. Preferred embodiment of the invention
  • the purpose of the embodiment of the present invention is to overcome the prior art that the power switch tube is reliably turned off by the negative pulse drive signal with the same amplitude as the positive pulse drive signal, thereby causing large power consumption and heating of the control circuit of the drive pulse. serious problem.
  • control circuit that generates a drive pulse signal
  • An isolated drive transformer having one primary winding, one or more secondary windings;
  • the isolated driving circuit further includes:
  • the drive circuit includes:
  • the bleeder circuit includes:
  • a bleeder resistor one end connected to the emitter of the bleed P-type switch tube, one end connected to one end of the power switch tube;
  • the bleeder diode has an anode connected to the collector of the bleed P-type switch tube, and a cathode connected to the other end of the power switch tube.
  • the shutdown circuit includes:
  • a first voltage dividing resistor one end of which is connected to the anode of the shutdown diode via a secondary winding, and the other end of which is connected to the base of the bleed P-type switching tube;
  • a second voltage dividing resistor one end of which is connected to the cathode of the turn-off diode, and the other end of which is connected to the emitter of the bleeder P-type switch tube via the bleeder resistor;
  • the anode of the shutdown diode is connected to one end of the power switch tube, and the cathode is connected to the other end of the power switch tube via a second voltage dividing resistor.
  • the shutdown circuit further includes:
  • the first anti-saturation diode has an anode connected to the base of the bleed P-type switch tube, a cathode connected to the first voltage dividing resistor, a second anti-saturation diode, an anode connected to the collector of the bleed P-type switch tube, and a cathode connection thereof The cathode of the first anti-saturation diode.
  • the bleed P-type switch tube is a PNP triode or a P-type composite tube.
  • FIG. 3 to FIG. 5 show a connection manner of a driving circuit provided by an embodiment of the present invention.
  • the driving circuit is used to keep the power switching tube open, and the driving diode, the secondary winding of the driving transformer and the driving resistor are connected in series.
  • the devices in this loop have a variety of connections.
  • the structure is shown in the solid line in Figure 3, Figure 4, and Figure 5.
  • the voltage between C and D is used to drive the power switch.
  • the anode of the driving diode is connected to one end (point D side) of the power switching tube via the secondary winding, and the cathode is connected to the other end of the power switching tube via the driving resistor (point C) side) .
  • the anode of the driving diode is sequentially connected to one end (point D side) of the power switching tube via the driving resistor and the secondary winding, and the cathode thereof is connected to the other end of the power switching tube ( Side C)).
  • the anode of the driving diode is sequentially connected to one end (point D side) of the power switching tube via the secondary winding and the driving resistor, and the cathode thereof is connected to the other end of the power switching tube ( Side C)).
  • FIG. 6 and FIG. 7 show a connection mode of a bleeder circuit according to an embodiment of the present invention.
  • the bleeder circuit is used to turn off a power switch tube, and is connected in series by a bleeder resistor, a bleeder diode, and a bleeder P-type switch tube. Composition, the device of this circuit has various connection modes, and its structure is shown in the solid line part of FIG. 6 and FIG. 7, and the voltage between the C point and the D point is used to drive the power switch tube.
  • the bleeder circuit includes a bleeder resistor connected in series in series, and a bleeder P-type open Close the tube and bleed the diode.
  • One end of the bleeder resistor is connected to the emitter of the bleeder P-type switch tube, and one end is connected to one end of the power switch tube (point C side).
  • the bleeder diode has an anode connected to the collector of the bleed P-type switch tube, and a cathode connected to the other end of the power switch tube (on the D point side).
  • the driving circuit shown in Fig. 6 uses the connection mode shown in Fig. 5. At this time, one end of the bleeder resistor connected to the power switch tube is also connected to the cathode of the driving diode.
  • connection position of the bleeder resistor is different from that of FIG. 6, and the driving circuit shown in FIG. 7 is still exemplified by the connection mode shown in FIG. 5.
  • the bleed is discharged.
  • An end of the resistor connected to the emitter of the bleeder P-switch is also connected to the cathode of the drive diode.
  • FIG. 8 shows a connection mode of a shutdown circuit according to an embodiment of the present invention.
  • the shutdown circuit is used to maintain a certain negative voltage of the power switch tube to ensure reliable shutdown of the power switch tube.
  • the shut-off circuit is composed of a first voltage dividing resistor, a second voltage dividing resistor, a bleeder resistor, a turn-off diode, a bleeder P-type switch tube, and the like, and the solid line portion of FIG. 8 is the shut-off loop. Structure, use the voltage between point C and point D to drive the power switch tube. among them:
  • a first voltage dividing resistor one end of which is connected to the anode of the shutdown diode via a secondary winding, and the other end of which is connected to the base of the bleed P-type switching tube;
  • a second voltage dividing resistor one end of which is connected to the cathode of the turn-off diode, and the other end of which is connected to the emitter of the bleeder P-type switch tube via the bleeder resistor;
  • the diode is turned off, the anode is connected to one end of the power switch tube, and the cathode is connected to the other end of the power switch tube via a second voltage dividing resistor.
  • the shutdown circuit shown in FIG. 8 can also be serially connected to the anti-saturation device. As shown in FIG. 9, the anti-saturation is added to the shutdown circuit shown in FIG. diode. among them:
  • the first anti-saturation diode has an anode connected to the base of the bleed P-type switch tube, a cathode connected to the first voltage dividing resistor, a second anti-saturation diode, an anode connected to the collector of the bleed P-type switch tube, and a cathode connection thereof The cathode of the first anti-saturation diode.
  • the isolated drive transformer may include one or more secondary windings, each of which has a secondary winding connected to a secondary circuit to form a drive loop, a bleed loop, and a shutdown loop.
  • FIG. 13 is a diagram showing an isolated driving circuit according to an embodiment of the present invention.
  • the embodiment is a single isolated driving circuit.
  • the drive circuit uses the connection mode shown in Figure 3, including the drive diode D1 and the drive resistor R1;
  • the bleeder circuit uses the connection method shown in Figure 6, including the bleeder resistor R3, bleed P type
  • the shutdown circuit uses the connection mode shown in FIG. 8, and includes a turn-off diode D3, a second voltage dividing resistor R4, and a first voltage dividing resistor R2.
  • Its working principle is as follows:
  • the voltage direction of the secondary winding Ls is up-down and negative by isolating the isolation of the drive transformer T1.
  • the secondary current flows through the driving diode D1 and the driving resistor R1, that is, the driving circuit, and generates a certain driving voltage between the C point and the D point to drive the power switching tube.
  • the positive drive pulse signal from the control circuit When the positive drive pulse signal from the control circuit is turned off, it enters the dead time, and there is no voltage across the winding of the isolated drive transformer T1.
  • the voltage on the power switch that is, the voltage between point C and point D, is quickly discharged through the bleeder resistor R3, the bleeder P-type switch Q1, and the bleeder diode D2, that is, the bleeder circuit.
  • the voltage direction of the secondary winding Ls is upper and lower positive by isolating the isolation of the drive transformer T1.
  • the secondary current flows through the turn-off diode D3, the second voltage dividing resistor R4, the bleeder resistor R3, the bleeder P-type switch transistor Q1, and the first voltage dividing resistor R2, that is, the circuit is turned off, and is generated between points C and D.
  • a negative voltage of a certain amplitude to ensure reliable shutdown of the power switch.
  • the magnitude of the negative voltage between the C point and the D point can be controlled, thereby controlling the function of the control circuit of the driving pulse. Consumption.
  • FIG. 14 is a diagram showing another isolated driving circuit according to an embodiment of the present invention.
  • the embodiment is a dual isolated complementary driving circuit.
  • the isolated driving transformer T1 has a primary winding Lp and two. Secondary windings Lsl, Ls2.
  • the driving circuit uses the connection mode shown in FIG. 5, and the driving circuit on the side of the secondary winding Ls1 includes the driving diode D1 and the driving resistor R1, and the driving circuit on the side of the secondary winding Ls2 includes the driving diode D4 and the driving.
  • Resistor R5; bleeder circuit In the connection mode shown in FIG.
  • the bleeder circuit on the side of the secondary winding Ls1 includes a bleeder resistor R3, a bleeder P-type switch transistor Q1, a bleeder diode D2, and a bleeder circuit on the side of the secondary winding Ls2 includes a bleeder resistor.
  • the off-circuit of the secondary winding Lsl side includes the turn-off diode D3, the second voltage-dividing resistor R4
  • the first voltage dividing resistor R2 and the turn-off circuit on the side of the secondary winding Ls2 include a turn-off diode D6, a second voltage dividing resistor R8, and a first voltage dividing resistor R6. Its working principle is as follows:
  • the voltage direction of the secondary winding Ls1 is up and down and positive, and the secondary current passes through the shutdown circuit.
  • a certain negative voltage is generated between the point and the point D to ensure that the power switch tube is reliably turned off.
  • the voltage direction of the secondary winding Ls2 is up-down and negative, and the secondary current flows through the drive circuit to generate a driving voltage between points E and F to drive the power switch.
  • each module/unit in the foregoing embodiment may be implemented in the form of hardware, or may use software functions.
  • the form of the module is implemented. The invention is not limited to any specific form of combination of hardware and software.
  • the tube maintains the magnitude of the negative voltage when it is turned off, thereby controlling the power consumption of the control circuit; retaining the vertical blocking capacitance of the primary side, the primary winding of the driving transformer can be reset with a very stable voltage, and the driving circuit is isolated.
  • the output waveform has no spikes and oscillations; the anti-saturation device can be serially connected in the shutdown circuit, that is, the anti-saturation diode is added to prevent the bleed-out p-type switch tube from entering deep saturation; it is not limited to a single isolated drive. It is used for multi-channel isolation drive, especially dual-channel complementary isolation drive; it not only retains the advantages of traditional isolated drive circuit, but also solves the problems of traditional isolated drive circuit.

Abstract

一种应用于开关电源功率开关管的隔离驱动电路，包括：用于产生驱动脉冲信号的控制电路；具有一个原边绕组、一个或者多个副边绕组的隔离驱动变压器（T1）；连接控制电路和隔离驱动变压器（T1）的原边绕组的隔直电容（C1）；连接在隔离驱动变压器（T1）的副边绕组和功率开关管之间的用于使功率开关管导通的驱动电路；使功率开关管关断的泄放回路和关断回路。这种隔离驱动电路能可靠地关断功率开关管，并能控制产生驱动脉宽信号的控制电路的功耗。

Description

一种隔离驱动电路
技术领域
本发明涉及一种应用于开关电源功率开关管的隔离驱动电路， 尤其涉及 一种需要双路互补的隔离驱动电路。 背景技术
开关电源的方案已经被广泛应用， 其关键器件功率开关管工作在高频高 压状态下。 由于电路拓朴本身的需要或者基于安全方面的考虑， 需要将来自 控制电路的驱动脉冲信号与功率开关管进行隔离。
图 1显示了现有技术提供的一种传统的隔离驱动电路图， 如图 1所示， 虚线框内是功率开关管的隔离驱动电路， 包括原边隔直电容 Cl、 隔离驱动变 压器 Tl、 副边自举电容 C2、 自举二极管 Dl。
当驱动脉冲开通时， 来自控制电路的驱动脉冲加在 A点和 B点之间， 此 时隔离驱动变压器 T1的原副边绕组的电压方向是上正下负， 通过隔离变换、 负压自举后， 在 C点和参考地输出， 用来驱动功率开关管 Qswl。
当驱动脉冲关断时， A点电压与 B点电压相同。 隔直电容 C1迫使隔离 驱动变压器 T1的原边绕组和副边绕组电压换方向， 即上负下正。 隔离驱动变 压器 T1通过副边绕组与自举二极管 D1和自举电容 C2构成通路， 实现磁复 位。 此时 C点电压为 0V, 功率开关管 Qswl关断。 由于功率开关管 Qswl通 常是 MOSFET管， 而 MOSFET管的开启阀值低， 当有电磁扰动时， 功率开 关管 Qswl 在本应关断时又会错误开通， 从而降低了整个开关电源系统的可 靠性。
图 2显示了现有技术提供的一种互补的传统隔离驱动电路图， 如图 2所 示， 虚线框内是互补的隔离驱动电路， 包括原边隔直电容 Cl、 隔离驱动变压 器 T1和副边驱动电阻 Rl、 R2, 二极管 Dl、 D2。
当来自控制电路的正驱动脉冲信号加在 A点和 B点之间时， 隔离驱动变 压器 T1的原边绕组 Lp的电压方向是上正下负， 通过隔离变换， 隔离驱动变 压器 Tl的副边绕组 Lsl的电压方向是上正下负，隔离驱动变压器的副边绕组 Ls2的电压方向是上负下正， 在 C点与 D点间输出正脉冲信号， 保持功率开 关管 Qswl可靠导通，在 E点与 F点间输出负脉冲信号，保持功率开关管 Qsw2 可靠关断。
当来自控制电路的负驱动脉冲加在 A点和 B点之间时， 隔离驱动变压器 T1的原边绕组 Lp的电压方向是上负下正， 通过隔离变换， 隔离驱动变压器 T1的副边绕组 Lsl的电压方向是上负下正， 隔离驱动变压器的副边绕组 Ls2 的电压方向是上正下负， 在 C点与 D点间输出负脉冲信号， 保持功率开关管 Qswl可靠关断， 在 E点与 F点间输出正脉冲信号， 保持功率开关管 Qsw2可 靠导通。
此电路可以解决图 1所述传统的隔离驱动电路因工作环境差而导致的异 常动作。 但是， 由于该电路通过与正脉冲驱动信号幅值相同的负脉冲信号来 保持功率开关管的可靠关断， 因此导致产生驱动脉冲的控制电路功耗大， 发 热严重。 发明内容
本发明实施例的目的在于提供一种隔离驱动电路， 用于克服控制电路功 耗大， 发热严重的问题。
本发明实施例提供的一种隔离驱动电路包括：
控制电路， 其设置为产生驱动脉冲信号；
隔离驱动变压器， 其包括一个原边绕组， 以及一个或多个副边绕组； 隔直电容， 连接所述控制电路和所述隔离驱动变压器的原边绕组； 驱动回路， 其设置为： 连接在所述隔离驱动变压器的副边绕组和功率开 关管之间， 使功率开关管导通；
泄放回路， 其设置为通过放电使所述功率开关管关断； 以及
关断回路， 其设置为使所述功率开关管保持负电压， 保证所述功率开关 管可靠关断。 可选地， 所述驱动二极管的阳极经由所述副边绕组连接所述功率开关管 的一端， 阴极经由所述驱动电阻连接所述功率开关管的另一端。
可选地， 所述驱动二极管的阳极依次经由所述驱动电阻和所述副边绕组 连接所述功率开关管的一端， 其阴极连接所述功率开关管的另一端。
可选地， 所述驱动二极管的阳极依次经由所述副边绕组和所述驱动电阻 连接所述功率开关管的一端， 其阴极连接所述功率开关管的另一端。
所述泄放回路包括：
泄放 P型开关管；
泄放电阻， 一端连接所述泄放 P型开关管的发射极， 一端连接功率开关 管的一端；
泄放二极管， 其阳极连接所述泄放 P型开关管的集电极， 其阴极连接功 率开关管的另一端。
所述关断回路包括：
关断二极管； 第一分压电阻， 其一端经由副边绕组连接所述关断二极管的阳极， 其另 一端连接所述泄放 P型开关管的基极；
第二分压电阻， 其一端连接所述关断二极管的阴极， 其另一端经由所述 泄放电阻连接所述泄放 P型开关管的发射极；
其中， 所述关断二极管的阳极连接功率开关管的一端， 阴极经由第二分 压电阻连接功率开关管的另一端。
所述关断回路还包括：
第一抗饱和二极管， 其阳极连接泄放 P型开关管的基极， 其阴极连接第 一分压电阻； 第二抗饱和二极管， 其阳极连接泄放 P型开关管的集电极， 其阴极连接 第一抗饱和二极管的阴极。
可选地， 所述泄放 P型开关管是 PNP三极管或 P型复合管。
与现有技术相比， 本发明实施例的有益效果在于： 关管在关断时保持负压的幅值， 从而控制所述控制电路的功耗；
2、本发明实施例保留了原边的隔直电容， 可以使驱动变压器原边绕组以 很平稳的电压来复位， 隔离驱动电路的输出波形无尖刺和震荡。
3、本发明实施例可以在关断回路中串入抗饱和器件， 即增加抗饱和二极 管， 防止所述的泄放 P型开关管进入深度饱和。
4、 本发明实施例不局限于单路隔离驱动， 也可以用于多路隔离驱动， 尤 其是双路互补隔离驱动。 总之， 本发明实施例既保留了传统隔离驱动电路的优点， 又解决了传统 隔离驱动电路存在的问题。
附图说明
图 1是现有技术提供的一种传统的隔离驱动电路图；
图 2是现有技术提供的一种互补的传统隔离驱动电路图；
图 3是本发明实施例提供的驱动回路的第一种连接方式图；
图 4是本发明实施例提供的驱动回路的第二种连接方式图；
图 5是本发明实施例提供的驱动回路的第三种连接方式图；
图 6是本发明实施例提供的泄放回路的第一种连接方式图；
图 7是本发明实施例提供的泄放回路的第二种连接方式图；
图 8是本发明实施例提供的关断回路的连接方式图；
图 9是本发明实施例提供的增加抗饱和的关断回路的连接方式图； 图 10是本发明实施例提供的单路隔离驱动电路的结构图；
图 11是本发明实施例提供的多路隔离驱动电路的结构图；
图 12是本发明实施例提供的双路互补隔离驱动电路的结构图； 图 13是本发明实施例提供的一种隔离驱动电路图；
图 14是本发明实施例提供的另一种隔离驱动电路图。 本发明的较佳实施方式
下文中将结合附图对本发明的实施例进行详细说明。 需要说明的是， 在 不冲突的情况下， 本申请中的实施例及实施例中的特征可以相互任意组合。
本发明实施例的目的是为了克服现有技术中， 通过与正脉冲驱动信号幅 值相同的负脉冲驱动信号来保持功率开关管可靠关断， 从而导致驱动脉冲的 控制电路的功耗大， 发热严重的问题。
本发明实施例提供的一种隔离驱动电路包括：
产生驱动脉冲信号的控制电路；
具有一个原边绕组、 一个或多个副边绕组的隔离驱动变压器；
连接于所述控制电路和所述隔离驱动变压器的原边绕组之间的隔直电 容；
所述隔离驱动电路还包括：
连接在所述隔离驱动变压器的副边绕组和功率开关管之间的用于使功率 开关管导通的驱动回路、 使功率开关管关断的泄放回路和关断回路。
所述驱动回路包括：
与所述隔离驱动变压器的副边绕组串联连接的驱动电阻和驱动二极管。 所述泄放回路包括：
泄放 P型开关管；
泄放电阻， 一端连接所述泄放 P型开关管的发射极， 一端连接功率开关 管的一端；
泄放二极管， 其阳极连接所述泄放 P型开关管的集电极， 其阴极连接功 率开关管的另一端。
所述关断回路包括：
关断二极管；
第一分压电阻， 其一端经由副边绕组连接所述关断二极管的阳极， 其另 一端连接所述泄放 P型开关管的基极； 第二分压电阻， 其一端连接所述关断二极管的阴极， 其另一端经由所述 泄放电阻连接所述泄放 P型开关管的发射极；
其中， 所述关断二极管的阳极连接功率开关管的一端， 阴极经由第二分 压电阻连接功率开关管的另一端。
所述关断回路还包括：
第一抗饱和二极管， 其阳极连接泄放 P型开关管的基极， 其阴极连接第 一分压电阻； 第二抗饱和二极管， 其阳极连接泄放 P型开关管的集电极， 其阴极连接 第一抗饱和二极管的阴极。
较佳的， 所述泄放 P型开关管是 PNP三极管或 P型复合管。
图 3至图 5显示了本发明实施例提供的驱动回路的连接方式， 所述驱动 回路用于使功率开关管保持开通， 由驱动二级管、 驱动变压器副边绕组和驱 动电阻串联组成。 此回路的器件有多种连接方式， 其结构如图 3、 图 4、 图 5 中实线部分所示， 用 C点与 D点之间的电压来驱动功率开关管。
如图 3所示， 所述驱动二极管的阳极经由所述副边绕组连接所述功率开 关管的一端 （D点侧） ， 阴极经由所述驱动电阻连接所述功率开关管的另一 端 （ C点侧） 。
如图 4所示， 所述驱动二极管的阳极依次经由所述驱动电阻和所述副边 绕组连接所述功率开关管的一端 （D点侧） ， 其阴极连接所述功率开关管的 另一端 （C点侧） 。
如图 5所示， 所述驱动二极管的阳极依次经由所述副边绕组和所述驱动 电阻连接所述功率开关管的一端 （D点侧） ， 其阴极连接所述功率开关管的 另一端 （C点侧） 。
图 6和图 7显示了本发明实施例提供的泄放回路的连接方式， 所述泄放 回路用于使功率开关管关断， 由泄放电阻、 泄放二极管和泄放 P型开关管串 联组成， 此回路的器件有多种连接方式， 其结构如图 6和图 7中实线部分所 示， 用 C点与 D点之间的电压来驱动功率开关管。
如图 6所示， 所述泄放回路包括依次串联连接的泄放电阻、 泄放 P型开 关管和泄放二极管。 所述泄放电阻一端连接所述泄放 P型开关管的发射极， 一端连接功率开关管的一端 （C 点侧） 。 所述泄放二极管， 其阳极连接所述 泄放 P型开关管的集电极， 其阴极连接功率开关管的另一端 （D点侧） 。
图 6所示的驱动回路釆用了图 5所示的连接方式， 此时， 所述泄放电阻 与功率开关管连接的一端还与驱动二极管的阴极相连。
如图 7所示， 图中所述泄放电阻的连接位置与图 6不同， 以图 7所示的 驱动回路依然釆用图 5所示的连接方式为例， 图 7中， 所述泄放电阻与所述 泄放 P型开关管的发射极连接的一端还与驱动二极管的阴极相连。
图 8显示了本发明实施例提供的关断回路的连接方式， 所述关断回路用 于使功率开关管保持一定负电压， 保证功率开关管可靠关断。 所述的关断回 路由第一分压电阻、 第二分压电阻、 泄放电阻、 关断二极管、 泄放 P型开关 管串联等组成， 图 8实线部分是所述的关断回路的结构， 用 C点与 D点之间 的电压来驱动功率开关管。 其中：
第一分压电阻， 其一端经由副边绕组连接所述关断二极管的阳极， 其另 一端连接所述泄放 P型开关管的基极；
第二分压电阻， 其一端连接所述关断二极管的阴极， 其另一端经由所述 泄放电阻连接所述泄放 P型开关管的发射极；
关断二极管， 其阳极连接功率开关管的一端， 阴极经由第二分压电阻连 接功率开关管的另一端。
为了防止所述泄放 P型开关管进入深入饱和， 图 8所示的关断回路也可 以串入抗饱和器件， 如图 9所示， 在图 8所示的关断回路中增加了抗饱和二 极管。 其中：
第一抗饱和二极管， 其阳极连接泄放 P型开关管的基极， 其阴极连接第 一分压电阻； 第二抗饱和二极管， 其阳极连接泄放 P型开关管的集电极， 其阴极连接 第一抗饱和二极管的阴极。
本发明实施例所述的技术方案， 适用于如图 10所示单路隔离驱动电路、 图 11所示的多路隔离驱动电路，尤其是图 12所示的双路互补隔离驱动电路。 也就是说， 隔离驱动变压器可以包括一个或多个副边绕组， 其每个副边绕组 连接一个副边电路， 形成驱动回路、 泄放回路和关断回路。
图 13显示了本发明实施例提供的一种隔离驱动电路图， 如图 13所示， 本实施例是一种单路隔离驱动电路。 其中， 驱动回路釆用了图 3所示的连接 方式， 包括驱动二级管 D1和驱动电阻 R1 ; 泄放回路釆用了图 6所示的连接 方式， 包括泄放电阻 R3、 泄放 P型开关管 Ql、 泄放二极管 D2; 关断回路釆 用了图 8所示的连接方式， 包括关断二极管 D3、 第二分压电阻 R4、 第一分 压电阻 R2。 其工作原理如下：
当来自控制电路的正驱动脉冲信号加在 A点和 B点之间时， 通过隔离驱 动变压器 T1的隔离变换， 副边绕组 Ls的电压方向是上正下负。 副边电流通 过驱动二级管 D1和驱动电阻 R1 , 即驱动回路， 在 C点和 D点之间产生一定 的驱动电压， 驱动功率开关管。
当来自控制电路的正驱动脉冲信号关闭时， 即进入死区时间， 隔离驱动 变压器 T1绕组两端没有电压。 功率开关管上的电压， 即 C点和 D点之间的 电压， 通过泄放电阻 R3、 泄放 P型开关管 Q1、 泄放二极管 D2 , 即泄放回路， 迅速放电。
当来自控制电路的负驱动脉冲信号加在 A点和 B点之间时， 通过隔离驱 动变压器 T1的隔离变换， 副边绕组 Ls的电压方向是上负下正。 副边电流通 过关断二极管 D3、 第二分压电阻 R4、 泄放电阻 R3、 泄放 P型开关管 Ql、 第一分压电阻 R2, 即关断回路， 在 C点和 D点之间产生一定幅值的负电压， 来确保功率开关管可靠关断。
较佳的， 通过调节第一分压电阻 R2和第二分压电阻 R4的阻值分配， 可 以控制在 C点和 D点之间的负电压的幅值，从而控制驱动脉冲的控制电路的 功耗。
图 14显示了本发明实施例提供的另一种隔离驱动电路图，如图 14所示， 本实施例是一种双路隔离互补驱动电路，所述隔离驱动变压器 T1具有一个原 边绕组 Lp和两个副边绕组 Lsl、 Ls2。 其中， 驱动回路釆用了图 5所示的连 接方式， 副边绕组 Lsl侧的驱动回路包括驱动二级管 Dl、 驱动电阻 R1 , 副 边绕组 Ls2侧的驱动回路包括驱动二级管 D4、 驱动电阻 R5; 泄放回路釆用 了图 6所示的连接方式， 副边绕组 Lsl侧的泄放回路包括泄放电阻 R3、 泄放 P型开关管 Ql、 泄放二极管 D2, 副边绕组 Ls2侧的泄放回路包括泄放电阻 R7、 泄放 P型开关管 Q2、 泄放二极管 D5; 关断回路釆用了图 8所示的连接 方式， 副边绕组 Lsl侧的关断回路包括关断二极管 D3、 第二分压电阻 R4、 第一分压电阻 R2 , 副边绕组 Ls2侧的关断回路包括关断二极管 D6、 第二分 压电阻 R8、 第一分压电阻 R6。 其工作原理如下：
当来自控制电路的正驱动脉冲信号加在 A点和 B点之间时， 通过隔离驱 动变压器 T1的隔离变换， 副边绕组 Lsl的电压方向是上正下负， 副边电流通 过驱动回路， 在 C点和 D点之间产生驱动电压， 来驱动功率开关管。 副边绕 组 Ls2的电压方向是上负下正。 副边电流通过关断回路， 在 E点和 F点之间 产生一定的负电压， 来确保驱动功率开关管可靠关断。
当来自控制电路的正驱动脉冲信号关闭时， 即进入死区时间， 变压器 T1 绕组两端没有电压。 C点和 D点之间的电压通过泄放回路迅速放电， E点和 F点之间的电压通过关断回路返回到零伏。
当来自控制电路的负驱动脉冲信号加在 A点和 B点之间时， 通过变压器 T1的隔离变换， 副边绕组 Lsl的电压方向是上负下正， 副边电流通过关断回 路， 在 C点和 D点之间产生一定的负电压， 来确保功率开关管可靠关断。 副 边绕组 Ls2的电压方向是上正下负， 副边电流通过驱动回路， 在 E点和 F点 之间产生驱动电压， 来驱动功率开关管。
本领域普通技术人员可以理解上述方法中的全部或部分步骤可通过程序 来指令相关硬件完成， 所述程序可以存储于计算机可读存储介质中， 如只读 存储器、 磁盘或光盘等。 可选地， 上述实施例的全部或部分步骤也可以使用 一个或多个集成电路来实现， 相应地， 上述实施例中的各模块 /单元可以釆用 硬件的形式实现， 也可以釆用软件功能模块的形式实现。 本发明不限制于任 何特定形式的硬件和软件的结合。
需要说明的是， 本发明还可有其他多种实施例， 在不背离本发明精神及 和变形， 但这些相应的改变和变形都应属于本发明所附的权利要求的保护范 围。 工业实用性
管在关断时保持负压的幅值， 从而控制所述控制电路的功耗； 保留了原边的 隔直电容， 可以使驱动变压器原边绕组以很平稳的电压来复位， 隔离驱动电 路的输出波形无尖刺和震荡； 可在关断回路中串入抗饱和器件， 即增加抗饱 和二极管， 防止所述的泄放 p型开关管进入深度饱和； 不局限于单路隔离驱 动， 也可以用于多路隔离驱动， 尤其是双路互补隔离驱动； 既保留了传统隔 离驱动电路的优点， 又解决了传统隔离驱动电路存在的问题。

Claims

权 利 要 求 书
1、 一种隔离驱动电路， 包括：
控制电路， 其设置为产生驱动脉冲信号；
隔离驱动变压器， 其包括一个原边绕组， 以及一个或多个副边绕组； 隔直电容， 连接所述控制电路和所述隔离驱动变压器的原边绕组； 驱动回路， 其设置为： 连接在所述隔离驱动变压器的副边绕组和功率开 关管之间， 使功率开关管导通；
泄放回路， 其设置为通过放电使所述功率开关管关断； 以及
关断回路， 其设置为使所述功率开关管保持负电压， 保证所述功率开关 管可靠关断。
2、 根据权利要求 1所述的电路， 其中， 所述驱动回路包括与所述隔离驱 动变压器的副边绕组串联连接的驱动电阻和驱动二极管。
3、 根据权利要求 2所述的电路， 其中， 所述驱动二极管的阳极设置为经 由所述副边绕组连接所述功率开关管的一端， 阴极设置为经由所述驱动电阻 连接所述功率开关管的另一端。
4、 根据权利要求 2所述的电路， 其中， 所述驱动二极管的阳极设置为依 次经由所述驱动电阻和所述副边绕组连接所述功率开关管的一端， 其阴极设 置为连接所述功率开关管的另一端。
5、 根据权利要求 2所述的电路， 其中， 所述驱动二极管的阳极设置为依 次经由所述副边绕组和所述驱动电阻连接所述功率开关管的一端， 其阴极设 置为连接所述功率开关管的另一端。
6、 根据权利要求 1-5任意一项所述的电路， 其中， 所述泄放回路包括： 泄放 P型开关管；
泄放电阻， 其一端连接所述泄放 P型开关管的发射极， 一端设置为连接 功率开关管的一端； 以及
泄放二极管， 其阳极连接所述泄放 P型开关管的集电极， 其阴极设置为 连接功率开关管的另一端。
7、 根据权利要求 6所述的电路， 其中， 所述泄放 P型开关管是 PNP三 极管或 P型复合管。
8、 根据权利要求 6所述的电路， 其中， 所述关断回路包括：
关断二极管； 第一分压电阻， 其一端经由副边绕组连接所述关断二极管的阳极， 其另 一端连接所述泄放 P型开关管的基极； 以及
第二分压电阻， 其一端连接所述关断二极管的阴极， 其另一端经由所述 泄放电阻连接所述泄放 P型开关管的发射极；
其中， 所述关断二极管的阳极设置为连接功率开关管的一端， 阴极设置 为经由第二分压电阻连接功率开关管的另一端。
9、 根据权利要求 8所述的电路， 其中， 所述关断回路还包括： 第一抗饱和二极管， 其阳极连接所述泄放 P型开关管的基极， 其阴极连 接第一分压电阻；
第二抗饱和二极管， 其阳极连接所述泄放 P型开关管的集电极， 其阴极 连接所述第一抗饱和二极管的阴极。
10、 根据权利要求 9所述的电路， 其中， 所述泄放 P型开关管是 PNP三 极管或 P型复合管。
PCT/CN2012/076843 2011-10-24 2012-06-13 一种隔离驱动电路 WO2013060145A1 (zh)

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