WO2012028540A1 - Convertisseur multiphase à phases magnétiquement couplées - Google Patents

Convertisseur multiphase à phases magnétiquement couplées Download PDF

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Publication number
WO2012028540A1
WO2012028540A1 PCT/EP2011/064680 EP2011064680W WO2012028540A1 WO 2012028540 A1 WO2012028540 A1 WO 2012028540A1 EP 2011064680 W EP2011064680 W EP 2011064680W WO 2012028540 A1 WO2012028540 A1 WO 2012028540A1
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WO
WIPO (PCT)
Prior art keywords
phase
phases
coupling means
coupling
current
Prior art date
Application number
PCT/EP2011/064680
Other languages
German (de)
English (en)
Inventor
Nils Draese
Mirko Schinzel
Original Assignee
Robert Bosch Gmbh
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Robert Bosch Gmbh filed Critical Robert Bosch Gmbh
Publication of WO2012028540A1 publication Critical patent/WO2012028540A1/fr

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Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H02M3/1584—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load with a plurality of power processing stages connected in parallel
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01F—MAGNETS; INDUCTANCES; TRANSFORMERS; SELECTION OF MATERIALS FOR THEIR MAGNETIC PROPERTIES
    • H01F38/00—Adaptations of transformers or inductances for specific applications or functions
    • H01F38/02—Adaptations of transformers or inductances for specific applications or functions for non-linear operation
    • H01F38/023—Adaptations of transformers or inductances for specific applications or functions for non-linear operation of inductances
    • H01F2038/026—Adaptations of transformers or inductances for specific applications or functions for non-linear operation of inductances non-linear inductive arrangements for converters, e.g. with additional windings
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0064—Magnetic structures combining different functions, e.g. storage, filtering or transformation
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H02M3/1584—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load with a plurality of power processing stages connected in parallel
    • H02M3/1586—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load with a plurality of power processing stages connected in parallel switched with a phase shift, i.e. interleaved

Definitions

  • the invention is based on a multi-phase converter according to the preamble of the independent claim.
  • a generic multiphase converter is known for example from WO 2009/114873 AI.
  • the DC / DC converter described therein comprises a non-linear inductive resistor coil, a switching system and an output filter. In the process, adjacent phases are coupled with each other.
  • independent claim 1 has the advantage of a contrast
  • Multiphase converter since in particular two-dimensional phase shapes can be used.
  • the coupling agents can also be arranged in a matrix.
  • a complex three-dimensional structure can be avoided.
  • At least one phase is U-shaped, rectangular and / or meander-shaped.
  • all couplings of the preferably six phases can be carried out with only two phase shapes, namely U-shaped and rectangular and / or meandering.
  • the phases are constructed as stamped grid and / or as part of a printed circuit board. This type of production is particularly cost-effective.
  • further electronic components such as the switching means can be arranged there.
  • the circuit board comprises at least two, preferably three recesses for receiving the coupling means. This simplifies the correct position arrangement of
  • the rectangular and / or meander-shaped phase has at least one chamfer in the area of the corner.
  • at least one of the phases outside the area enclosed by the coupling means provides a folding area.
  • Substantially has a flat, U-shaped course, while a second phase has a substantially rectangular, planar course.
  • These phases thus formed can be enclosed by coupling agents, preferably commercially available ferrite cores. As a result, in a very simple manner, resorting to a female structure, the desired
  • the phases are formed as stamped grid. This type of production is characterized by low production costs. In a six-phase system, three phases may be rectangular and three phases U-shaped. In essence, the same geometric shapes can be used, so that the production further reduced.
  • at least two phases to be coupled are at least partially enclosed by a coupling means, wherein the phases to be coupled can preferably be driven with different current direction.
  • the phases to be coupled preferably run at least partially approximately parallel in the region enclosed by the coupling means. In a particularly convenient
  • the coupling means encloses at least two phases to be magnetically coupled in each case in a first area and in a second area.
  • this selected type of coupling standard parts such as planar ferrite cores can be used as a coupling agent. These could have a rectangular or double-rectangular cross-section.
  • the coupling means are arranged in a matrix.
  • the coupling means comprises at least two parts, wherein one of the parts has a U, O, I or E-shaped cross section. With this structure, it is particularly easy to surround the phases to be coupled by the coupling means. In an expedient development it is provided that between two parts, a gap, preferably an air gap is provided. In this way, it is particularly easy to influence the inductance. In an expedient development it is provided that a plurality of coupling means consisting of at least two parts have at least one common part, preferably a metal plate. This could facilitate assembly, since all coupling means could be closed in just one step by placing the plate.
  • the phases are part of a multilayer printed circuit board.
  • the phases to be coupled to each other can be introduced electrically isolated from each other on at least two levels.
  • a printed circuit board preferably has corresponding recesses, in which the legs of the respective coupling means are introduced for the magnetic coupling of the respective phases.
  • a phase is coupled to a further phase for the at least partial compensation of the DC component of the current profile.
  • a phase is magnetically coupled with at least one further phase, which is essentially about 180 °
  • the coupling means can be smaller or it can be dispensed with an air gap.
  • the coupling means can be provided in a geometrically advantageous matrix arrangement. This is characterized by simple construction, the use of simple coupling means such as planar Ferrite cores and small spatial extent. In addition, filters can be made smaller.
  • the switching means control the phases sequentially and that a phase is magnetically coupled to at least one further phase, which is activated immediately before and / or after.
  • a phase is magnetically coupled to at least one further phase whose turn-on or turn-off instant lies immediately before and / or after.
  • a phase is magnetically coupled with at least two further phases, which are respectively controlled immediately before and after.
  • three coupling means are provided to magnetically couple one of the phases with three further phases.
  • the coupling means magnetically couple each of the six phases with three other of the six phases. This type of coupling on the one hand ensures that the individual phases can still be controlled independently of each other. In addition, the reliability of the multi-phase converter can be increased due to the stronger networking of the phases.
  • the phases to be coupled are selected so that an optimal compensation can be achieved. This is done in particular by an opposing current profile.
  • the goal here is that the phases are magnetically coupled so that the resulting magnetic field is minimized due to the coupled phases.
  • This makes it possible to resort to a space-small coupling means such as a ferrite core for coupling the magnetic fluxes.
  • the magnetic field could be greatly reduced, so that the corresponding Coupling means, such as a ferrite core, can be reduced in a corresponding manner in its mass.
  • the phases can be controlled in sequence. This results in relatively simple and thus easily controllable current characteristics.
  • one phase - in the case of an arrangement with six phases - is coupled to the two respectively adjacent phases and also to a phase shifted by 180 degrees.
  • An adjacent phase is understood to be one which is actuated immediately preceding or subsequently. In the proposed magnetic coupling beyond an independent control of the individual phases is possible from each other.
  • coupling means are provided which couple at least one phase magnetically with at least three further phases, can also be
  • the coupling means can be smaller or it can be dispensed with an air gap.
  • At least two, in particular three coupling means are provided to magnetically couple one of the phases with two further phases, wherein at least one of the two coupling means has a lower inductance than the other coupling means.
  • a lower inductance can serve as saturation protection.
  • coupling means with a lower inductance only saturate later at higher currents, so that the multiphase converter still reacts in the event of a fault can be operated longer in a stable operating condition.
  • a high inductance reduces the current ripple, ie the ripple of the current.
  • the coupling means which couples a phase with a phase which is driven substantially phase-shifted by approximately 180 ° has a lower inductance than at least one of the other coupling means.
  • three coupling means are provided to magnetically couple one of the phases with three further phases, wherein at least one of the three coupling means has a lower
  • a coupling means with lower inductance should be provided for each of the preferably six phases.
  • the coupling means is provided with an air gap. In a particularly simple manner, this can influence the inductance of the coupling agent. If an air gap is provided with otherwise identical construction of the coupling means, the inductance is reduced compared to the version without an air gap. This can be done particularly suitably by the middle of the three legs of the
  • Coupling means is shortened relative to the two outer, so that there forms an air gap.
  • FIG. 1 shows a circuit arrangement
  • Figure 2 is a schematic representation of the respective coupling of
  • FIG. 3 shows the spatial arrangement of the various phases and coupling means
  • FIG. 4 shows a section through a coupling means with two coupled phases
  • FIG. 5 shows two typical embodiments of the phases according to FIG. 5
  • FIG. 8 shows the temporal current curves of the first phase 11 and fourth
  • FIG. 9 shows a principal possibility of coupling three phases
  • FIG. 10 shows an alternative exemplary embodiment with folded-down phases and below the associated plan view
  • FIG. 11 shows a further alternative exemplary embodiment
  • FIG. 12 shows an alternative embodiment of a coupling means with an air gap as well
  • FIG. 13 shows a possible realization of the exemplary embodiment
  • FIG. 3 with a printed circuit board.
  • FIG. 1 The structure of a multi-phase converter 10 is shown in FIG. 1
  • Multiphase converter 10 consists of six phases 11 to 16. Each of the phases
  • a first coupling means 31 couples the first phase 11 with the second phase 12 magnetically, so that results for the first phase 11 an inductance L12, for the second phase 12, an inductance L21.
  • a sixth coupling means 36 magnetically couples the first phase 11 with the sixth phase 16 so that an inductance L16 results for the first phase 11, and an inductance L61 for the sixth phase 16.
  • a seventh coupling means 37 magnetically couples the first phase 11 with the fourth phase 14, so that an inductance L14 results for the first phase 11, and an inductance L41 for the sixth phase 16.
  • a second coupling means 32 magnetically couples the second phase 12 with the third phase 13, so that an inductance L23 for the second phase 12, and an inductance L32 for the third phase 13 results.
  • a ninth coupling means 39 magnetically couples the second phase 12 to the fifth phase 15, so that an inductance L25 is produced for the second phase 12, and an inductance L52 for the fifth phase 15.
  • a third coupling means 33 magnetically couples the third phase 13 with the fourth phase 14, so that an inductance L34 results for the third phase 13, and an inductance L43 for the fourth phase 14.
  • An eighth coupling means 38 magnetically couples the third phase 13 with the sixth phase 16 so that an inductance L36 is produced for the third phase 13 and an inductance L63 for the sixth phase 16.
  • a fourth coupling means 34 magnetically couples the fourth phase 14 to the fifth phase 15, so that an inductance L45 results for the fourth phase 14, an inductance L54 for the fifth phase 15.
  • a fifth coupling means 35 magnetically couples the fifth phase 15 with the sixth phase 16, so that an inductance L56 results for the fifth phase 15, and an inductance L65 for the sixth phase 16.
  • An input current I E is distributed over the six phases 11 to 16.
  • a capacitor is connected as a filter medium to ground.
  • the outputs of phases 11 to 16 are at a common summation point
  • FIG. 2 is shown systematically how the six phases 11 to 16 are coupled together by respective coupling means 31 to 39.
  • both adjacent phases are coupled together as well as in addition the phase offset by 180 degrees.
  • An adjacent phase is understood to be one which is actuated chronologically immediately preceding or following, that is to say whose turn-on times are immediately before or after it. in the
  • the designation of the phases 11 to 16 is selected so that the phases 11 to 16 are controlled sequentially according to the numbering, that is in the order (information corresponding to
  • Phases of phases 11 - 12 - 13 - 14 - 15 - 16 - 11 and so on, each phase shifted by 60 degrees or by T / 6 (360 degrees / number of phases), where T represents the period of a drive cycle.
  • T represents the period of a drive cycle.
  • the respective phase is switched off again after the time duration T / 6 (PWM ratio 1/6).
  • FIG. 3 schematically depicts the matrix-like spatial structure of the concept shown in FIG.
  • the coupling means 31 to 39 are preferably designed as planar coil cores, for example ferrite cores, each having two cavities. In these cavities of the
  • Coupling means 31 to 39 are each two conductors or phase sections of two phases to be coupled enclosed, which have different current directions in these sections, as indicated by the arrows.
  • phase 11 to 16 two geometric shapes of the phases 11 to 16 or busbars or conductors of the phases 11 to 16 can be made.
  • the first phase 11, third phase 13 and fifth phase 15 are U-shaped. These three phases 11, 13, 15 preferably all run in the same plane.
  • second, fourth and sixth phases 12, 14, 16 extend.
  • Second, fourth and sixth phases 12, 14, 16 are rectangular or meander-shaped. They are in this case arranged so that they are enclosed in the respective coupling means 31 to 39 with the respective phase to be coupled U-shaped phase 11, 13, 15 at different current direction.
  • the first coupling means 31 consists of an E-shaped first part 44 and a plate-shaped second part 43, which form the coil cores.
  • the legs of the first part 44 with E-shaped cross-section are all the same length, so that they can be closed by the plate-shaped (I-shaped cross-section) second part 43 without air gap.
  • the preferably band-shaped section of the first phase 11 is respectively introduced in the lower region of the coupling means 31. These shown portions of the first phase 11 are in the same plane, so they are planar to each other.
  • Coupling means 31 now comes the second phase 12, preferably also band-shaped, to lie. On the other side of the first
  • Coupling means 31 are carried out in its further cavity first and second phases 11, 12 in each case opposite to the current direction in the other cavity opposite current direction. This is done in the case of the first coupling means 31 in that both the first phase 11 and the second phase 12 at the upper end face of the first coupling means 11 in a 180 degree bend are returned through the other cavity again. Also, the two sections of the second phase 12, which are enclosed by the first coupling means 31, are in the same plane, are therefore formed planar. The plane of the first phase 11 and the plane of the second phase 12 are at least in the inner region of the first
  • Coupling means 31 formed parallel and spaced from each other.
  • the first phase 11 and the second phase 12 are now magnetically coupled together.
  • an insulation 45 is provided between the first phase 11 and the second phase 12 for the electrical separation of the two phases 11, 12 from each other and each to the coupling means 31.
  • the second phase 12 is coupled to the third phase 13 via the second coupling means 32.
  • the second phase 12 is coupled to the fifth phase 15 by means of the ninth coupling means 39.
  • the further corresponding couplings can be seen in FIG. 3 and will not be described again specifically.
  • the exemplary embodiment according to FIG. 6 differs from that according to FIG. 3 only in that a further seventh phase 17 is provided.
  • This seventh phase 17 is replaced by the tenth coupling means 40 with the first
  • Phase 11 with the eleventh coupling means 41 with the third phase 13 and with the twelfth coupling means 42 with the fifth phase 15 are each magnetically coupled.
  • the diagram according to FIG. 7 shows the time profiles of the drive signals 52 for the respective switching means 21 to 26 of the corresponding phases 11 to 16 and the current courses in phases 11 to 16.
  • the switching means 21 to 26 energize the associated phases 11 to 16 in succession for each one sixth of a period T, for example, by a PWM signal, and are then in the freewheel.
  • the resulting current waveforms of the individual phases 11 to 16 are shown below by way of example.
  • Drive signals 52 is for example in the order of 0.01 ms.
  • the starting times for the various phases 11 to 16 are phase-shifted by 60 degrees and offset by T / 6 in time.
  • the starting time of the third phase 13 adjacent to the second phase 12 is T / 6
  • the starting time of the fourth phase 14 is 2T / 6, and so on.
  • the respective phase is switched off again after T / 6 (PWM ratio 1/6).
  • PWM ratio 1/6 Depending on the desired
  • the shutdown could be sooner or later, up to permanent on, depending on the desired PWM signal (between 0%
  • FIG. 8 shows the temporal current characteristics of the first phase 11 and the fourth phase 14 and below this the difference of the two currents I res. It can be seen here that, compared with the first phase 11, the current characteristic of the fourth phase 14 is characterized by a large degree of opposition of the DC components. The DC fields largely cancel each other out as the lower curve I res of Figure 8 can be seen. Therefore, a coupling of the first phase 11 - in addition to a coupling with the adjacent phases 12, 16 - with the fourth phase is particularly advantageous.
  • FIG. 9 shows a further basic possibility of coupling three phases 11, 14, 16.
  • the first phase 11 and the counter current-energized sixth phase 16 are enclosed by a sixth coupling means 36 'surrounding these two conductor sections.
  • the first phase 11 and the counter-energized fourth phase 14 are enclosed by a seventh coupling means 37 '.
  • the coupling means 36 ', 37' have an O or
  • the meandering phases 12, 14, 16 are provided at the corners with chamfering areas 62, so that preferably straight sections are formed in order to guide adjacent phases 12, 16 parallel to one another in these chamfering areas 62.
  • the coupling means 32, 38 and 39, 35 also push together closer together.
  • Figure 12 differs from that of Figure 4 in that the middle leg of the E-shaped first part 44 a
  • Air gap 64 toward the second part 43 has.
  • first, third and fifth phases 11, 13, 15 are integrated, which are essentially in accordance with FIG. 3.
  • Figure 5 run U-shaped.
  • the printed circuit board 70 has a multiplicity of rectangular recesses 72.
  • Three recesses 72 are each tuned to the geometry of the three legs of the coupling means 31 to 42.
  • Recesses 72 plugged and protrude above the PCB level upwards.
  • the meander of the second phase 12 is guided for magnetic coupling with the U-shaped third phase 13 located in the printed circuit board 70.
  • the magnetic circuit of the coupling means 31 is closed by placing the second part 43. This is shown by way of example for the first coupling means 31, in which the plate-shaped second part 43 is already placed on the three legs of the first part 44.
  • Multiphase converters 10 or DC / DC converters with high powers without special isolation requirements can preferably be realized in multi-phase arrangements.
  • the high input current I E for example, in the amount of 300 A distributed to the various six phases 11 to 16 in the amount of 50A.
  • the corresponding input or output filter according to Figure 1 for example, drawn as capacitors, correspondingly small.
  • the control of the phases 11 to 16 is carried out sequentially, that is, one after the other, so that the switch-on times each 60 degrees (or.
  • the respective phases 11 to 16 are energized with different durations.
  • the corresponding high-side switch of the switching means 21 to 26 is closed for this purpose.
  • the phase 11 to 16 is not energized when the corresponding low-side switch of the switching means 21 to 26 is closed.
  • those phases 11 to 16 could be considered to be adjacent, whose turn-off is immediately before or after. Then the corresponding switch-on points would be variable depending on the desired PWM signal.
  • a phase 11 with at least three further phases 12, 14, 16 is magnetically coupled to one another in such a way that the DC components of the individual phases are respectively compensated as strongly as possible by other phases.
  • the third phase to be coupled is now preferably selected such that an interfering mutual
  • FIG. 8 shows the temporal current curves of the first phase 11 and fourth phase 14 and below this the difference I res of the two currents. It can be seen here that, compared to the first phase 11, the current characteristic of the fourth phase 14 is characterized by a large degree of opposition of the DC component. Therefore, a corresponding further magnetic coupling of the first phase 11 with the fourth phase 14 is suitable.
  • the two currents through the coupled phases 11, 14 flow oppositely in the seventh coupling means 37.
  • the resulting current I res for the magnetization of the coupling means 37 is only by the difference of the currents I res triggered.
  • the dc fields mostly cancel each other out.
  • the reduced DC component has a positive effect on the geometry of the coupling means 31 to 39, which can now manage with a smaller volume.
  • the coupling shown in Figures 1 to 3 has been found to be particularly suitable.
  • two phases can be magnetically coupled by passing the two phases with antiparallel current conduction through a rectangular or annular coupling means 31 to 41. It is essential that the coupling means 31 to 41 is capable of forming a magnetic circuit. This is possible with a substantially closed structure, which may also include an air gap. Furthermore, the coupling means 31 to 41 consists of a magnetic field conducting material with suitable permeability.
  • FIG. 9 shows a basic possibility of coupling three phases 11, 14, 16. In this case, the first phase 11 and the counter current-energized sixth phase 16 are enclosed by a sixth coupling means 36 'surrounding these two conductor sections. The first phase 11 and the counter-energized fourth phase 14 are enclosed by a seventh coupling means 37 '. In this coupling possibility in each case half a turn of two phases 11, 16; 11, 14 coupled together.
  • the coupling means 36 ', 37' can
  • FIG. 3 The coupling concept on which FIG. 3 is based can be explained by way of example with reference to FIG. It is essential that the phases to be coupled - according to Figure 4, there are first phase 11 and second phase 12 - with
  • the corresponding coupling means 31 to 41 can be smaller or it can be dispensed with an air gap.
  • a possible realization concept of the embodiment according to FIG. 3 could consist of a printed circuit board 70 into which the nine coupling means 31 to 39, here preferably planar cores, are embedded as shown in FIG.
  • all switching means 21 to 26, each consisting of high-side and low-side MOSFETs can be integrated as possible embodiments.
  • the windings for the first, third and fifth phases 11, 13, 15 can also be integrated into this printed circuit board 70.
  • the other windings of the second, fourth and sixth phases 12, 14, 16 could have a
  • a further advantage of the structure according to FIG. 3 is the short paths of the phases 11 to 16 through all coupling means 31 to 39 as well as the simple construction without
  • the coupling means 31 to 41 are inductive coupling means, such as an iron or ferrite core of a transformer, on which the phases 11 to 16 to be coupled generate a magnetic field.
  • the coupling means 31 to 42 closes the magnetic circuit of the two
  • coupling agent 31 to 38 material and permeability is not as important to coupling. If no air gap is used, the permeability of the magnetic circuit increases, which increases the inductance of the coil. As a result, the current increase is flatter and the current forms approach more to the ideal direct current. The closer the waveforms to a DC current, the lower the resulting current difference between the two phases that are (oppositely) passed through a core as coupling means 31-42. The effort for filters is thereby reduced. On the other hand, a system without an air gap reacts very sensitively
  • air gaps with different dimensions can be chosen so as to distribute the losses uniformly over the coupling means 31 to 42.
  • Coupling means 31 to 42 with lower inductance L also have lower power dissipation in principle.
  • the power losses of the coupling means 31 to 42 can be influenced so that desired criteria (for example, uniform distribution of power dissipation) are met.
  • desired criteria for example, uniform distribution of power dissipation
  • Embodiment of Figures 1-3 these are the coupling means with the reference numerals 37, 38, 39), due to the 180-degree phase-offset drive (as in the embodiment of Figures 1-3 by coupling the first phase 11 with the fourth phase 14 by the seventh coupling means 37, coupling of the second phase 12 to the fifth phase 15 by the ninth coupling means 39, coupling of the third phase 13 to the sixth phase 16 by the eighth coupling means 38) could be loaded with a greater increased magnetization Example be reduced by adapting or providing an air gap in their load. This would reduce the total core losses.
  • Coupling means 31 to 42 to be provided with a larger air gap or gap.
  • this coupling means 31 to 42 provided with an air gap would only saturate at higher currents, so that a further improved stability results in the event of a fault.
  • Air gap could be achieved.
  • an example of a coupling means 31 provided with an air gap 64 is shown.
  • the middle one is
  • the use of only two geometric shapes of the phases 11 to 16 as shown in Figure 5 in plan view is particularly advantageous in terms of manufacturing technology.
  • the one basic shape in this case has a U-shaped course and lie in the same plane.
  • the second basic shape is substantially rectangular or meander-shaped, also lying in the same plane.
  • Sections can be used as strip conductors in the form of punched grids or in
  • the U-shaped phases 11, 13, 15 are arranged relative to one another such that they come to lie on a first plane. Accordingly, the rectangular or meandering phases 12, 14,
  • Coupling means 31 to 42 can be surrounded.
  • phase forms would be conceivable without departing from the basic idea of the preferably planar structure.
  • certain adjustments are conceivable in order to further reduce the space requirement of the overall arrangement.
  • Corresponding variants are sketched schematically in FIGS. 10 and 11.
  • Embodiment of the geometry of the phases 11 to 17 is to be achieved, that the coupling means 31 to 42 can be arranged closer to the respective adjacent coupling means 31 to 42.
  • This can be achieved, for example, according to the embodiment of Figure 10, characterized in that the ends of the busbars of the phases 11 to 16 are folded down in by arrows
  • Coupling means 35 are also folded down by 45 °, so that contact with the second phase 12 is avoided. This can be ninth
  • Coupling means 39 and fifth coupling means 35 are arranged with a smaller distance to each other, as if the phase sections are led out without folding.
  • the meandering busbars of the respective phases 11 to 16 can also be bent up on the sides.
  • the meander can also slide into each other as shown in the left side sketch with top view.
  • the U-shaped punched grid of the third and fifth phase 13, 15 would then have to be laid in different levels, for example by appropriate bending.
  • the meandering phases 12, 14, 16 are provided at the curves or corners with chamfering areas 62, so that preferably straight sections are formed in parallel to closely adjacent phases 12, 16 in these chamfering areas 62
  • the multiphase converter 10 described is particularly suitable for use in a motor vehicle electrical system, in which in particular dynamic load requirements are of minor importance. In particular, for such relatively slow systems, the structure described is suitable.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Inverter Devices (AREA)

Abstract

L'invention concerne un convertisseur multiphase comprenant plusieurs phases électriques (11 à 16) qui peuvent être respectivement commandées par des moyens de commutation (21 à 26). Ledit convertisseur comporte des moyens de couplage (31, 36, 37) qui couplent magnétiquement au moins une première phase (11) avec au moins une autre phase (12, 14, 16). Au moins deux phases (11, 12) à coupler sont entourées au moins en partie par un moyen de couplage (31). Au moins deux phases (11, 13, 15), de préférence trois phases, s'étendent spatialement dans un premier plan et au moins deux autres phases (12, 14, 16), de préférence trois phases, s'étendent spatialement dans un deuxième plan qui est parallèle au premier plan et espacé de celui-ci.
PCT/EP2011/064680 2010-09-03 2011-08-25 Convertisseur multiphase à phases magnétiquement couplées WO2012028540A1 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
DE102010040222A DE102010040222A1 (de) 2010-09-03 2010-09-03 Multiphasenwandler
DE102010040222.2 2010-09-03

Publications (1)

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WO2012028540A1 true WO2012028540A1 (fr) 2012-03-08

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Families Citing this family (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE102012202578A1 (de) 2012-02-20 2013-08-22 Robert Bosch Gmbh Multiphasenwandler
DE102013202712A1 (de) 2013-02-20 2014-08-21 Robert Bosch Gmbh Multiphasenwandler
DE102013202698A1 (de) 2013-02-20 2014-08-21 Robert Bosch Gmbh Multiphasenwandler
DE102021126628A1 (de) 2021-10-14 2023-04-20 Dr. Ing. H.C. F. Porsche Aktiengesellschaft Elektrische Maschine

Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP1145416B1 (fr) 1999-10-01 2003-09-03 Robert Bosch Gmbh Convertisseurs pour la transformation d'energie electrique
US20080303495A1 (en) * 2007-06-08 2008-12-11 Intersil Americas Inc. Power supply with a magnetically uncoupled phase and an odd number of magnetically coupled phases, and control for a power supply with magnetically coupled and magnetically uncoupled phases
US20090179723A1 (en) * 2002-12-13 2009-07-16 Volterra Semiconductor Corporation Method For Making Magnetic Components With M-Phase Coupling, And Related Inductor Structures
WO2009114873A1 (fr) 2008-03-14 2009-09-17 Volterra Semiconductor Corporation Inducteur convertisseur de tension ayant une valeur d’inductance négative

Patent Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP1145416B1 (fr) 1999-10-01 2003-09-03 Robert Bosch Gmbh Convertisseurs pour la transformation d'energie electrique
US20090179723A1 (en) * 2002-12-13 2009-07-16 Volterra Semiconductor Corporation Method For Making Magnetic Components With M-Phase Coupling, And Related Inductor Structures
US20080303495A1 (en) * 2007-06-08 2008-12-11 Intersil Americas Inc. Power supply with a magnetically uncoupled phase and an odd number of magnetically coupled phases, and control for a power supply with magnetically coupled and magnetically uncoupled phases
WO2009114873A1 (fr) 2008-03-14 2009-09-17 Volterra Semiconductor Corporation Inducteur convertisseur de tension ayant une valeur d’inductance négative

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