WO2011160330A1 - 跟踪电源装置及其控制方法 - Google Patents

跟踪电源装置及其控制方法 Download PDF

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Publication number
WO2011160330A1
WO2011160330A1 PCT/CN2010/075917 CN2010075917W WO2011160330A1 WO 2011160330 A1 WO2011160330 A1 WO 2011160330A1 CN 2010075917 W CN2010075917 W CN 2010075917W WO 2011160330 A1 WO2011160330 A1 WO 2011160330A1
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Prior art keywords
voltage source
voltage
signal
source
current
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PCT/CN2010/075917
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English (en)
French (fr)
Inventor
谢戡
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中兴通讯股份有限公司
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Publication of WO2011160330A1 publication Critical patent/WO2011160330A1/zh

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Classifications

    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F1/00—Details of amplifiers with only discharge tubes, only semiconductor devices or only unspecified devices as amplifying elements
    • H03F1/02—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation
    • H03F1/0205—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation in transistor amplifiers
    • H03F1/0261—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation in transistor amplifiers with control of the polarisation voltage or current, e.g. gliding Class A
    • H03F1/0266—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation in transistor amplifiers with control of the polarisation voltage or current, e.g. gliding Class A by using a signal derived from the input signal
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H02M3/1584—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load with a plurality of power processing stages connected in parallel
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F1/00—Details of amplifiers with only discharge tubes, only semiconductor devices or only unspecified devices as amplifying elements
    • H03F1/02—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation
    • H03F1/0205—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation in transistor amplifiers
    • H03F1/0261—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation in transistor amplifiers with control of the polarisation voltage or current, e.g. gliding Class A
    • H03F1/0272—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation in transistor amplifiers with control of the polarisation voltage or current, e.g. gliding Class A by using a signal derived from the output signal
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F3/00—Amplifiers with only discharge tubes or only semiconductor devices as amplifying elements
    • H03F3/189—High-frequency amplifiers, e.g. radio frequency amplifiers
    • H03F3/19—High-frequency amplifiers, e.g. radio frequency amplifiers with semiconductor devices only
    • H03F3/193—High-frequency amplifiers, e.g. radio frequency amplifiers with semiconductor devices only with field-effect devices
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0003—Details of control, feedback or regulation circuits
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F2200/00—Indexing scheme relating to amplifiers
    • H03F2200/408—Indexing scheme relating to amplifiers the output amplifying stage of an amplifier comprising three power stages
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F2200/00—Indexing scheme relating to amplifiers
    • H03F2200/451—Indexing scheme relating to amplifiers the amplifier being a radio frequency amplifier

Definitions

  • the present invention relates to the field of power supply control, and in particular to a tracking power supply device and a control method therefor.
  • BACKGROUND OF THE INVENTION In modern wireless communication technology, there is a technology for changing the drain voltage of a radio frequency power amplifier.
  • the technology can quickly adjust the drain voltage of the power amplifier tube according to the requirements of the system, and the adjustment range can reach several tens of volts. Less than 100 nanoseconds, and high adjustment accuracy is guaranteed.
  • This technology enables the wireless power amplifier to be in a high efficiency state without losing the radio frequency index during operation, especially when the peak power and the average power ratio are large, thereby greatly reducing the energy consumption of the radio frequency power amplifier.
  • Switching power supplies although more efficient, have a regulation bandwidth that is usually only within a level of ⁇ and cannot meet the requirements of rapid change. Although the switching power supply is high frequency, the adjustment bandwidth can be further increased.
  • the semiconductor device is limited by the process, power, packaging technology, and switching loss. The switching power supply switching frequency is difficult to reach above 10 MHz, and the switching power supply cannot balance high bandwidth. And high efficiency.
  • the high-frequency noise of the switching power supply is modulated to the RF carrier, which deteriorates the RF linearity index.
  • the switch current source is a current source controlled controlled current source for the conversion of the RF input to the RF output.
  • the control signal comes from the output current of the linear amplifying circuit, and the output current of the linear amplifying circuit needs to be detected, and the corresponding current detecting and amplifying circuit needs to be customized, and the implementation is complicated.
  • Controlled Switching Current Sources Use Hysteresis Pulse Frequency Modulation PFM control, resulting in large switching losses due to uncontrolled switching frequency.
  • Figure 2 shows the control diagram of the voltage source.
  • the required voltage 304 consists of multiple independent voltage sources.
  • the voltage source 302 and the voltage source 303 are obtained by high-speed switching.
  • the output voltage accuracy depends on the number of switching levels, and the number of switching levels is related to the number of independent voltage sources, and the tracking accuracy of the output voltage is limited.
  • the tracking bandwidth is also limited by the response delay time and switching speed of the switch. Higher switching frequency Will result in large switching losses.
  • the control implementation since the controlled switching current source is controlled by hysteresis PFM, the control implementation is complicated; the scheme in Fig. 2, the tracking accuracy is limited by the number of multilevel voltage sources, and there is a comparison Large high frequency switching losses.
  • a main object of the present invention is to provide a tracking power supply device and a control method thereof, which are capable of solving at least the above-mentioned voltage and current adjusting device with complicated structure, limited tracking accuracy, and a large high-frequency switching loss problem.
  • a tracking power supply device including: a signal generator, an operating voltage source, a tracking voltage source, and a current source; and an operating voltage source for providing a first bias voltage to the tracking voltage source and Corresponding power; a signal generator for emitting an input signal to the tracking voltage source and emitting a current adjustment signal to the current source; a tracking voltage source for amplifying the input signal according to the first bias voltage provided by the working voltage source; The source is used to output current and corresponding power according to the current adjustment signal; according to the amplified input signal of the tracking voltage source and the current output by the current source and the corresponding power, the power supply voltage and power for the RF power amplifier are generated.
  • a control method based on the above apparatus comprising: a signal generator that sends an input signal to a tracking voltage source and a current adjustment signal to a current source; and the tracking voltage source uses an operating voltage source to provide a A bias voltage and a corresponding power amplification input signal; the current source outputs a current and a corresponding power according to the current adjustment signal, and the current and the corresponding power are combined with the amplified input signal to obtain a supply voltage and a corresponding power for the RF power amplifier.
  • the tracking device and method of the present invention according to a real-time voltage signal, emits a tracking signal and emits corresponding electric power.
  • the invention has simple structure, improved tracking precision and avoids high frequency switching loss. It can quickly track the tracking signal sent by the digital signal processing unit, generate corresponding electric power, and improve the efficiency of the RF power amplifier.
  • BRIEF DESCRIPTION OF THE DRAWINGS The accompanying drawings, which are set to illustrate,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,,
  • FIG. 2 is a schematic structural view of a second power supply device in the related art
  • Embodiment 3 is a schematic structural view of Embodiment 1 of a power supply device according to the present invention.
  • Embodiment 4 is a schematic structural view of Embodiment 2 of a power supply device according to the present invention.
  • FIG. 5 is a schematic structural diagram of a first signal conditioning unit in an embodiment of a power supply device according to the present invention
  • FIG. 6 is a schematic structural diagram of a second signal conditioning unit in an embodiment of a power supply device according to the present invention
  • FIG. 8 is a schematic structural diagram of a first tracking voltage source in an embodiment of a power supply device according to the present invention
  • FIG. 9 is a second tracking voltage in an embodiment of a power supply device according to the present invention
  • FIG. 10 is a schematic structural view of a third tracking voltage source in an embodiment of a power supply device according to the present invention
  • FIG. 11 is a schematic structural view of a first linear regulating tube in an embodiment of a power supply device according to the present invention
  • FIG. 13 is a schematic structural view of a third type of linear adjustment tube in an embodiment of a power supply device according to the present invention
  • FIG. 13 is a schematic structural view of a third type of linear adjustment tube in an embodiment of a power supply device according to the present invention
  • FIG. 15 is a schematic structural view of a fourth linear regulating tube in the embodiment of the power supply device of the present invention
  • FIG. Figure 16 is a schematic structural view of a sixth linear regulating tube in the embodiment of the power supply device of the present invention
  • Figure 17 is a schematic structural view of a seventh linear regulating tube in the embodiment of the power supply device of the present invention
  • FIG. 19 is a schematic structural view of Embodiment 3 of the power supply device of the present invention
  • Figure 20 is a schematic structural view of Embodiment 4 of the power supply device of the present invention.
  • Figure 21 is a schematic structural view of Embodiment 5 of the power supply device of the present invention.
  • Figure 22 is a schematic structural view of Embodiment 6 provided by the power supply device of the present invention
  • 23 is a schematic structural view of Embodiment 7 of a power supply device according to the present invention
  • FIG. 24 is a schematic structural view of Embodiment 8 of a power supply device according to the present invention
  • FIG. 25 is a first schematic diagram of an operating voltage source isolation network in an embodiment of a power supply device according to the present invention
  • FIG. 26 is a second schematic structural diagram of an operating voltage source isolation network in an embodiment of a power supply device according to the present invention
  • FIG. 27 is a third structural diagram of an operating voltage source isolation network in an embodiment of a power supply device according to the present invention
  • 28 is a flow chart of a control method according to an embodiment of the present invention.
  • Embodiment 1 Referring to the structural diagram of an embodiment 1 provided by the power supply device of the present invention shown in FIG. It includes a signal generator, a trace voltage source 117, an operating voltage source 116-1, an auxiliary voltage source 116-2, and a current source 118. Represents 120 of the RF power amplifier load impedance.
  • the signal generator includes: a digital signal processing unit 110, a digital to analog converter 112, and a tracked signal conditioning unit 114.
  • the digital processing unit 110 completes the occurrence of the traced signal 111, and generates a first voltage adjustment signal 210-1 of the working voltage source 116-1, respectively, which may also be defined as a voltage regulation signal 210-1; the auxiliary voltage source 116-2
  • the second voltage regulation signal 210-2 can also be defined as a voltage regulation signal 210-2.
  • the operating voltage source 116-1 and the auxiliary voltage source 116-2 are caused to change following the regulated voltage signal 210-2.
  • the digital processing unit 110 also generates an electrical signal 310 of the source 118 such that the output of the source 118 changes following the adjustment signal.
  • the tracked signal 111 is converted to a tracked analog signal 113 by a digital to analog converter 112.
  • the tracked analog signal 113 is further converted by a signal conditioning unit 114 into a signal 115 suitable for power amplification.
  • the amplified signal 115 is further passed through a tracking voltage source 117. Amplifying and carrying the power output becomes the supply voltage 119 required by the RF power amplifier.
  • the tracking voltage source 117 is a linear amplification unit. In addition to the input and output, the tracking voltage source 117 has a high-end, low-end two external ports 117-H, 117-L.
  • the high-side port 117-H of the tracking voltage source 117 is connected to the operating voltage source 116-1 for which it operates, and the low-side port 117-L of the tracking voltage source 117 can be left floating, or connected to the system reference ground 121, or connected to the auxiliary voltage source 116. -2.
  • the auxiliary voltage source 116-2 is applied to the terminal port 117-L of the trace voltage source 117 and is in series with the tracking voltage source 117.
  • the auxiliary voltage source 116-2 may be a preset constant DC voltage source or an adjustable dynamic voltage source.
  • the auxiliary voltage source 116-2 can be the bias voltage of the trace voltage source 117 to ensure that the tracking voltage source 117 is functioning properly.
  • the auxiliary voltage source 116-2 may also be part of the load 120 supply voltage 119.
  • the auxiliary power source 116-2 and the trace voltage source 117 are connected in series, and the respective output voltages are superimposed and combined by the series connection relationship.
  • the auxiliary voltage source 116-2 can also be part of both the bias voltage that causes the tracking voltage source 117 to operate properly and the load 120 supply voltage 119.
  • the operating voltage source 116-1 is applied to the high side port 117-H of the tracking voltage source 117, which is the bias voltage of the tracking voltage source 117 to ensure proper operation of the tracking voltage source 117.
  • the operating voltage source 116-1 may be a predetermined constant DC voltage source or an adjustable dynamic voltage source.
  • the adjustment signal 210-1 is from the digital signal processing unit 110, and the adjustment speed is also variable.
  • FIG. 4 is a structural diagram of Embodiment 2 of a power supply device according to the present invention.
  • the working voltage source, the auxiliary voltage source and the current source are increased.
  • working voltage source 1 to working voltage source ⁇ respectively, working voltage source 116-11, working voltage Source 116-12, ... working voltage source 116-ln; n i-assisted voltage source, i-assisted voltage source 116-21, # assist voltage source 116-22, ... auxiliary voltage source 116-2n and other voltage sources simultaneously
  • the voltage source 117 is traced.
  • 210-11, 210-12....210-In, 210-21, 210-22, ... 210-2n are respective adjustment signals, which are generated by the digital signal processing unit 110.
  • n current sources namely, the power source, the source 118-1, the power source, the source 118-2, and the source 118-n, which simultaneously act on the load 120.
  • 310-1, 310-2, ... 310-n are respective adjustment signals, which are generated by the digital signal processing unit 110.
  • Library i booster source 116-21, i booster source 116-22, ...i booster source 116-2n and power supply source 118-1, source 3 ⁇ 43 ⁇ 4 source 118-2, ....electric 3 ⁇ 43 ⁇ 4 source 118 - ⁇ and jt ⁇ can be unrelated or can be combined by series connection.
  • the signal conditioning unit can be in various forms, as shown in FIG.
  • FIG. 6 is a schematic structural diagram of a second signal conditioning unit in an embodiment of a power supply device according to the present invention.
  • the conditioning unit 114 is formed by connecting two amplification filter circuits and one bias circuit in series.
  • FIG. 7 is a schematic structural diagram of a third signal conditioning unit in an embodiment of a power supply device according to the present invention.
  • the conditioning unit 114 is formed by connecting a plurality of amplification filtering units 114-1 to 114-(2n-1) and a plurality of bias circuit units 114-2 to 114-2n in series.
  • the tracked analog signal 113 passes through the amplification filter unit 1, the bias circuit 1, the amplification filter unit 2, the bias circuit 2, the amplification filter unit ⁇ , and the bias circuit ⁇ , respectively, and finally obtains the input signal 115 of the tracking voltage source 117.
  • This embodiment is not limited to the amplification filtering unit and the bias circuit interleave processing, and may be a plurality of combinations of the amplification filtering unit and the bias circuit, and the embodiment is not enumerated here.
  • the signal conditioning unit can also take a variety of forms, as described in more detail below.
  • FIG. 8 is a schematic structural diagram of a first type of trace voltage source in an embodiment of a power supply device according to the present invention.
  • Linear amplification is open loop control, the amplified signal 115 passes through a plurality of linear amplification filtering units 117-1, 117-2, ... 117-n, and finally 4 passes the linear adjustment tube 117-0 for power amplification, linear adjustment tube
  • the output is the supply voltage 119 required by the load 120.
  • 117-1, 117-2, ... 117-n put The large unit can be a high speed operational amplifier, a differential amplification structure consisting of discrete components, or a CLASS A, CLASS B, CLASS AB type amplification structure. They form a cascade relationship by series.
  • the operating voltage source 116-1 and the auxiliary voltage source 116-2 act directly on the linear regulator 117-0.
  • FIG. 9 is a schematic structural diagram of a second trace voltage source in an embodiment of a power supply device according to the present invention.
  • the tracking voltage source 117 is closed-loop controlled, and the output voltage 119 is divided and sampled by the feedback network 117-111.
  • the amplified signal 115 also acts on the error amplifier, and the two are compared for amplification.
  • the output of the error amplifier is an error amplification signal 117-11, and the error amplification signal passes through the multi-stage linear amplification filtering unit 117-2, 117-3...117- ⁇ , and finally becomes the driving signal 117-00 of the linear adjustment tube 117-0.
  • the output of the linear regulator 117-0 is the supply voltage 119 required by the load.
  • the error amplifier 117-1 and the respective linear amplification filtering units constitute a cascade relationship by being connected in series.
  • the operating voltage source 116-1 and the auxiliary voltage source 116-2 act directly on the linear regulator 117-0.
  • compensation networks 117-112 are also required. Compensation networks 117-112 act on feedback networks 117-111, while also acting on error amplifier 117-1, linear amplification filtering units 117-2, 117-3. , ... 117- ⁇ , also acts on the linear adjustment tube 117-0.
  • the compensation network can be implemented in the form of a circuit, which is generally a passive network composed of a resistor and a capacitor.
  • the tracking voltage source 117 is closed loop control and is dual closed loop control. There are two independent feedback networks 117-111, 117-211. Two sets of compensation networks 117-112, 117-212. The output voltage 119 is simultaneously passed through the feedback networks 117-111, 117-211 to obtain respective sampling signals, which are respectively applied to the respective error amplifiers 117-11, 117-21 as their input signals, and the amplified signals 115 simultaneously act on the error amplifier. 117-11, 117-21, as its other input signal.
  • the error amplification signals output by the error amplifiers 117-11, 117-21 are respectively passed through respective multi-stage linear amplification filtering units 117-11, 117-12, ... 117-In, 117-21, 117-22, ... 117-2n, after being multistage amplified, is the push signals 117-10 and 117-20 of the linear adjustment tube 117-0, which simultaneously act on the linear adjustment tube 117-0.
  • the compensation networks 117-112, 117-212 respectively act on the respective feedback loop unit, the envelope feedback network, the error amplifier, the linear amplification filter unit, and the linear adjustment tube. The entire tracking voltage source stability and the necessary performance specifications are guaranteed by the compensation network.
  • the linear adjustment tube 117-0 can also take a variety of forms, as described in detail below.
  • FIG. 11 is a schematic structural view of a first linear adjustment tube in an embodiment of a power supply device according to the present invention.
  • the linear regulator is a single tube structure and is an N-channel MOSFET.
  • FIG. 12 is a schematic structural view of a second linear regulating tube in the embodiment of the power supply device of the present invention.
  • the linear regulator is a single tube structure and is a P-channel MOSFET.
  • FIG. 13 it is a schematic structural diagram of a third linear regulating tube in the embodiment of the power supply device of the present invention; the linear regulating tube is a double tube structure, and both tubes are N-channel MOSFETs.
  • FIG. 14 it is a schematic structural diagram of a fourth linear adjustment tube in the embodiment of the power supply device of the present invention; the linear adjustment tube is a double tube structure, and the high side tube 117-01 is an N-channel MOSFET, and the end tube 117 -02 is a P-channel MOSFET.
  • FIG. 14 it is a schematic structural diagram of a fourth linear adjustment tube in the embodiment of the power supply device of the present invention; the linear adjustment tube is a double tube structure, and the high side tube 117-01 is an N-channel MOSFET, and the end tube 117 -02 is a P-channel MOSFET.
  • FIG. 14 it is a schematic structural diagram of a fourth linear adjustment tube in the embodiment of the power supply device of the present invention; the linear adjustment tube is a double tube structure, and the high side tube 117-01 is an N-channel MOSFET, and the end tube 117 -02 is a P-channel MOSFET.
  • FIG. 14 it is a schematic structural diagram of a fourth linear adjustment tube
  • FIG. 15 is a schematic structural view of a fifth linear adjustment tube in the embodiment of the power supply device of the present invention.
  • the linear regulator is a double tube structure, the high side tube 117-01 is a P-channel MOSFET, and the end transistor 117-02 is an N-channel MOSFET.
  • FIG. 16 is a schematic structural view of a sixth linear regulating tube in the embodiment of the power supply device of the present invention.
  • the linear regulator is a double tube structure with its high side tube 117-01 being a P-channel MOSFET and the second end tube 117-02 being a P-channel MOSFET.
  • the operating voltage source 116-1 and the auxiliary power source 116-2 directly act on the source or drain of the linear regulator 117-0.
  • FIG. 17 is a schematic structural view of a seventh linear adjusting tube in the embodiment of the power supply device of the present invention.
  • the linear regulator tube is a double tube structure, the high end tube 117-01 is an NPN triode, and the low end tube 117-02 is a PNP triode.
  • 18 is a schematic structural view of an eighth linear regulating tube in the embodiment of the power supply device of the present invention.
  • the linear regulator tube is a double tube structure, the high end tube 117-01 is an NPN triode, and the low end tube 117-02 is an NPN triode.
  • FIG. 19 is a schematic structural view of an embodiment 3 provided by the power supply device of the present invention. Tracking voltage source 117 is powered by an operating voltage source 116-1. The reference ground 121 of the low termination system of the voltage source 117 is tracked.
  • the current source 118 is connected to the output 119 of the tracking voltage source 117 and the other end is connected to the reference ground 121 of the system.
  • the digital signal processing unit 110 emits an adjustment signal 310 of the current source 118 to cause the output of the current source 118 to track the adjustment signal.
  • the operating voltage source 116-1 is simultaneously regulated by the digital signal processing unit 110 to ensure that the operating voltage source 116-1 outputs the tracking adjustment signal 210-1.
  • FIG. 20 is a schematic structural view of an embodiment 4 provided by the power supply device of the present invention. Tracking voltage source 117 is powered by an operating voltage source 116-1. The low end of the tracking voltage source 117 is left unconnected.
  • the current source 118 is connected to the output 119 of the tracking voltage source 117 and the other end is connected to the reference ground 121 of the system.
  • the digital signal processing unit 110 emits an adjustment signal 310 of the current source 118 to cause the output of the current source 118 to coincide with the adjustment signal.
  • the operating voltage source 116-1 is also regulated by the digital signal processing unit 110 to ensure that the operating voltage source 116-1 outputs the tracking adjustment signal 210-1.
  • FIG. 21 is a schematic structural view of an embodiment 5 provided by the power supply device of the present invention.
  • the high voltage of the tracking voltage source 117 is connected to the working voltage source 116-1, and the ⁇ terminal of the tracking voltage source 117 is connected to the auxiliary voltage source 116-2.
  • the current source 118 is connected to the output 119 of the tracking voltage source 117 and the other end is connected to the reference ground 121 of the system.
  • the digital signal processing unit 110 emits an adjustment signal 310 of the current source 118 to cause the output of the current source 118 to track the adjustment signal.
  • the digital signal processing unit 110 respectively outputs the adjustment signals 210-1, 210-2 of the working voltage source 116-1, i auxiliary voltage source 116-2, so that the operating voltage source and the auxiliary voltage source output respectively track the respective adjustment signals.
  • FIG. 22 a schematic structural diagram of a sixth embodiment of the power supply device of the present invention is provided.
  • the high-voltage connected operating voltage source 116-1 of the tracking voltage source 117 and the low-side auxiliary voltage source 116-2 of the tracking voltage source 117 are connected.
  • the current source 118 is connected to the output 119 of the tracking voltage source 117, and the other end is connected to the output of the auxiliary voltage source 116-2.
  • the output terminal can be either a positive terminal or a negative terminal.
  • the digital signal processing unit 110 emits an adjustment signal 310 of the current source 118 to cause the output of the current source 118 to track the adjustment signal.
  • Operating voltage source 116-1 and auxiliary voltage source 116-2 are also regulated by digital signal processing unit adjustment signals 210-1, 210-2, respectively. So that the voltage source output tracking adjustment signal. As shown in FIG.
  • FIG. 23 it is a schematic structural diagram of an embodiment 7 provided by the power supply device of the present invention.
  • the high-voltage operating voltage source 116-1 of the tracking voltage source 117 is connected to the low-voltage end of the tracking voltage source 117. , 116-22, ... 116-2 ⁇ , wherein the plurality of library i-assisted voltage sources are in a series relationship.
  • Multiple electrical sources 118-1, 118-2, ... 118-n act on load 120 at the same time, one end of which is connected at the same time At output 119, the other end is coupled to the positive or negative terminals of voltage sources 116-21, 116-22, ... 116-2n, respectively.
  • the digital signal processing unit 110 independently adjusts the current sources 118-1, 118-2, ..., 118-n, respectively, to cause the current source to trace the current adjustment signal.
  • the digital signal processing unit 110 independently adjusts the operating voltage source 116-1 and the auxiliary voltage sources 116-21, 116-22, ... 116-2n to cause the voltage source to trace the voltage regulating signal.
  • the above multiple voltage regulation signals and multiple current regulation signals - corresponding to their respective voltage sources and power sources.
  • FIG. 24 it is a schematic structural diagram of an embodiment 8 provided by the power supply device of the present invention.
  • the high-voltage source 117 of the tracking voltage source 117 is connected to a plurality of operating voltage sources 116-11, 116-12, 116-13...116-In, Low-term termination of multiple i-assisted voltage sources 116-21, 116-22, ... 116-2n.
  • the plurality of i-assisted voltage sources are in a series relationship, and the plurality of working voltage sources are in a parallel relationship.
  • a plurality of current sources 118-1, 118-2, ... 118-n simultaneously act on the load 120, one end of which is connected to the output 119 at the same time, and the other end is respectively connected to the auxiliary voltage source 116-21, 116-22, ...
  • the positive or negative terminals of 116-2n are connected, and the plurality of working voltage sources 116-11, 116-12, ... 116- In are connected in parallel through a plurality of isolation networks 116-110, 116-120, 116-130...116-lnO, respectively. Together, the power supply to the high-voltage source 117 is connected in parallel.
  • the digital signal processing unit 110 sends voltage adjustment signals 210-11, 210-12, ... 210-In, respectively, through the respective isolation networks 116-110, 116-120, ... 116-lnO to the working voltage source, so that A determined time is supplied to the tracking voltage source 117 by one of the various operating voltage sources 116-11, 116-12, ...
  • the digital signal processing unit 110 independently adjusts the current sources 118-1, 118-2, ... 118-n and the auxiliary voltage sources 116-21, 116-22, ... 116-2n, respectively, so that the auxiliary current source outputs
  • the current regulating signals 310-1, 310-2, ... 310- ⁇ are traced, and the auxiliary voltage source outputs the tracking voltage adjustment signals 210-21, 210-22, ... 210-2n.
  • the multi-channel voltage adjustment signal and the multi-channel current adjustment signal sent by the digital signal processing unit 110 correspond to respective auxiliary voltage sources and current sources.
  • 116-lnO are corresponding switches 117-1101, 116-1201, ... 116-1 ⁇ 01, respective drive circuits 116-1103, 116-1203, .. .116-ln03 and an active network composed of individual isolation diodes 116-1102, 116-1202, ... 116-ln02.
  • the switch and the isolation diode are in series relationship.
  • the driving device controls the switching switch to be turned on or off.
  • the voltage regulating signal 210 from the digital signal processing unit 110 switches the operating voltage sources 116-11, 116-12, ... 116-ln to the tracking voltage source 117 by acting on the driving means.
  • the isolated network can also take a variety of forms, as described in more detail below. As shown in FIG.
  • FIG. 25 it is the first junction of the working voltage source isolation network in the embodiment of the power supply device of the present invention.
  • the digital signal processing unit 110 connects the respective respective switch switches 116-1101 to 1161n01 and the respective working voltage sources 116-11 to 116-In through the respective drivers 116-1103 to 1161n03, and the respective switch switches 116-1101 Connect to the respective isolation diodes 116-1102 to 1161n02 to 1161n01.
  • FIG. 26 is a second schematic structural diagram of an operating voltage source isolation network in an embodiment of a power supply device according to the present invention. The difference from the isolated network shown in FIG. 25 is that the switching switch connected to each driving circuit in the isolated network of FIG.
  • FIG. 25 is between the working voltage source and the diode; the diode in the isolated network shown in FIG. 26 is at the working voltage source and Switch between switches.
  • FIG. 27 is a schematic structural view of Embodiment 3 further disclosed by the operating voltage source isolation network 116-lnO in the power supply device of the present invention.
  • a diode 116-1103 completes the level switching of the two operating voltage sources 116-11, 116-12.
  • the operating voltage source 116-11 is higher and in series with the switching transistor 116-1101, and the operating voltage source 116-12 is relatively low and in series with the diode 116-1103.
  • the switch 116-1101 can be an N-channel MOSFET or a P-channel MOSFET.
  • the digital signal processing unit 110 issues a voltage adjustment signal 210-1 to ensure an output tracking voltage adjustment signal by acting on the drivers 116-1102.
  • the present invention also provides a control method based on the above tracking device. Referring to the flowchart shown in FIG. 28, the following steps are included:
  • S281 the signal generator sends an input signal to the tracking voltage source, and sends a current adjustment signal to the current source;
  • S282 the tracking voltage source provides a first bias voltage to amplify the input signal through the working voltage source;
  • the current source outputs the current and the corresponding power according to the current adjustment signal, and combines with the amplified input signal to obtain a power supply voltage and a supplied power for the radio frequency power amplifier.
  • the method further includes: the signal generator further issuing a first voltage adjustment signal, and controlling the first bias voltage generated by the working voltage source.
  • the method further includes: an auxiliary voltage source that supplies a second bias voltage and a corresponding power to the tracking voltage source, the signal generator also sends a second voltage adjustment signal to the auxiliary voltage source to control the second bias voltage .
  • the auxiliary voltage source also provides power to the radio frequency power amplifier along with the current source.
  • the tracking apparatus and method of the present invention are applicable Used in various electronic devices, such as base stations, transmitters, and other radio frequency devices, when applied in a base station device, the base station signal processing unit calculates a voltage signal representing different transmission powers in real time according to the current load, and issues a tracking signal. The corresponding electrical power is emitted by the device of the invention.
  • the invention has simple structure, improved tracking precision and avoids high frequency switching loss. It can quickly track the tracking signal sent by the digital signal processing unit, generate corresponding electric power, and improve the efficiency of the base station RF power amplifier.
  • modules or steps of the present invention can be implemented by a general-purpose computing device, which can be concentrated on a single computing device or distributed over a network composed of multiple computing devices. Alternatively, they may be implemented by program code executable by the computing device, such that they may be stored in the storage device by the computing device and, in some cases, may be different from the order herein.
  • the steps shown or described are performed, or they are separately fabricated into individual integrated circuit modules, or a plurality of modules or steps are fabricated as a single integrated circuit module.
  • the invention is not limited to any specific combination of hardware and software.
  • the above is only the preferred embodiment of the present invention, and is not intended to limit the present invention, and various modifications and changes can be made to the present invention. Any modifications, equivalent substitutions, improvements, etc. made within the scope of the present invention are intended to be included within the scope of the present invention.

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Description

跟踪电源装置及其控制方法 技术领域 本发明涉及电源控制领域， 具体而言， 涉及一种艮踪电源装置及其控制 方法。 背景技术 现代无线通讯技术中， 具有改变射频功率放大器漏极电压的技术， 该技 术能根据系统的要求对功率放大管的漏极电压做出快速调节， 其调节范围可 达几十伏， 调节时间小于 100纳秒， 且保证较高的调节精度。 该技术可使得 无线功率放大器在运行过程中在不丧失射频指标的同时始终处于较高的效率 状态， 尤其适合在峰值功率和平均功率比值较大的情况， 从而大大减少射频 功率放大器能源消耗。 目前的电压调节功率装置如线性调压器， 虽然可以保证快速精确的调节 电压， 但是效率较低， 从而无法提高整个功率放大器的效率。 而开关电源， 虽然效率较高， 但其调节带宽通常只有 ΙΟΟΚΗζ以内的水平， 无法满足快速 变化的要求。 虽然将开关电源高频化， 使其调节带宽可以进一步增大， 但是 半导体器件受工艺， 功率， 封装技术， 开关损耗限制， 开关电源开关频率很 难故到 10MHz 以上， 开关电源无法兼顾到高带宽和高效率。 此外开关电源 高频噪声会被调制到射频载波， 恶化射频线性度指标。 对于电流源、 电压源的调节， 可参见图 1、 图 2所示的示意图， 图 1 中 所示， 为实现 RF输入到 RF输出的转换， 开关电流源是一个电流源控制的受 控电流源， 控制信号来自线性放大电路输出电流， 需要检测线性放大电路的 输出电流， 且需要定制相应的电流检测和放大电路， 实施复杂。 受控的开关 电流源釆用滞环脉冲频率调制 PFM 控制， 由于其开关频率不受控， 导致较 大的开关损耗。 图 2所示的电压源的控制示意图， 需要的电压 304由多个独立的电压源
301、 电压源 302、 电压源 303通过高速切换而得， 输出电压精度依赖切换电 平数， 而切换电平数和独立电压源个数有关， 输出电压的跟踪精度受限。 而 艮踪带宽也受限于切换开关的响应延迟时间和切换速度。 较高的切换频率也 会导致较大的切换损耗。 上述图 1 中的方案， 由于受控的开关电流源釆用滞环 PFM控制， 其控 制实现比较复杂； 图 2中的方案， 其跟踪精度受限于多电平电压源的数量， 且存在较大的高频切换损耗。 发明内容 本发明的主要目的在于提供一种跟踪电源装置及其控制方法， 以至少解 决上述电压、 电流的调节装置结构复杂， 跟踪精度受限， 存在较大的高频切 换损耗的问题。 根据本发明的一个方面， 提供一种跟踪电源装置， 包括： 信号发生器、 工作电压源、 艮踪电压源和电流源； 工作电压源， 用于向 艮踪电压源提供第 一偏置电压及相应的功率； 信号发生器， 用于发出输入信号至跟踪电压源， 并发出电流调节信号至电流源； 跟踪电压源， 用于根据工作电压源提供的第 一偏置电压， 放大输入信号； 电流源， 用于才艮据电流调节信号输出电流及相 应的功率； 根据跟踪电压源输出的放大后的输入信号及电流源输出的电流及 相应的功率， 产生用于射频功率放大器的供电电压及功率； 其中， 艮踪电压 源与电¾¾源并联。 根据本发明的另一个方面，还提供一种基于上述装置的控制方法， 包括： 信号发生器发出输入信号至跟踪电压源， 并发出电流调节信号至电流源； 跟 踪电压源使用工作电压源提供第一偏置电压及相应的功率放大输入信号； 电 流源根据电流调节信号输出电流及相应的功率， 电流及相应的功率与放大的 输入信号合并得到用于射频功率放大器的供电电压及相应的功率。 本发明的跟踪装置和方法， 按照实时的电压信号， 并发出跟踪信号， 并 发出相应的电功率。 本发明结构简单、 提高了跟踪精度， 避免了高频切换损 耗。 能快速跟踪数字信号处理单元发出的跟踪信号， 产生相应的电功率， 提 高了射频功率放大器的效率。 附图说明 此处所说明的附图用来提供对本发明的进一步理解， 构成本申请的一部 分， 本发明的示意性实施例及其说明用于解释本发明， 并不构成对本发明的 不当限定。 在附图中： 图 1为相关技术中的第一种电源装置结构示意图；
图 2为相关技术中的第二种电源装置结构示意图；
图 3为本发明电源装置提供的实施例 1的结构示意图；
图 4为本发明电源装置提供的实施例 2结构示意图；
图 5为本发明电源装置实施例中的第一种信号调理单元的结构示意图； 图 6为本发明电源装置实施例中的第二种信号调理单元的结构示意图； 图 7为本发明电源装置实施例中的第三种信号调理单元的结构示意图； 图 8为本发明电源装置实施例中的第一种跟踪电压源的结构示意图； 图 9为本发明电源装置实施例中的第二种跟踪电压源的结构示意图； 图 10为本发明电源装置实施例中的第三种跟踪电压源的结构示意图； 图 11为本发明电源装置实施例中的第一种线性调节管的结构示意图； 图 12为本发明电源装置实施例中的第二种线性调节管的结构示意图； 图 13为本发明电源装置实施例中的第三种线性调节管的结构示意图； 图 14为本发明电源装置实施例中的第四种线性调节管的结构示意图； 图 15为本发明电源装置实施例中的第五种线性调节管的结构示意图； 图 16为本发明电源装置实施例中的第六种线性调节管的结构示意图； 图 17为本发明电源装置实施例中的第七种线性调节管的结构示意图； 图 18为本发明电源装置实施例中的第八种线性调节管的结构示意图； 图 19为本发明电源装置提供的实施例 3的结构示意图；
图 20为本发明电源装置提供的实施例 4结构示意图；
图 21为本发明电源装置提供的实施例 5结构示意图；
图 22为本发明电源装置提供的实施例 6结构示意图； 图 23为本发明电源装置提供的实施例 7结构示意图； 图 24为本发明电源装置提供的实施例 8结构示意图； 图 25 为本发明电源装置实施例中的工作电压源隔离网络的第一种结构 示意图； 图 26 为本发明电源装置实施例中的工作电压源隔离网络的第二种结构 示意图； 图 27 为本发明电源装置实施例中的工作电压源隔离网络的第三种结构 示意图； 以及 图 28为本发明实施例的控制方法的流程图。 具体实施方式 下文中将参考附图并结合实施例来详细说明本发明。 需要说明的是， 在 不冲突的情况下， 本申请中的实施例及实施例中的特征可以相互组合。 下面结合本发明的附图， 详细说明本发明的各个实施例。 实施例 1 参见图 3所示的本发明电源装置提供的一个实施例 1结构示意图。 包括 信号发生器， 艮踪电压源 117, 工作电压源 116-1 , 辅助电压源 116-2, 电流 源 118。 代表射频功率放大器负载阻抗的 120。 信号发生器包括： 一个数字信 号处理单元 110, 数模转换器 112, 被艮踪信号调理单元 114。 数字处理单元 110完成被艮踪信号 111的发生， 并分别产生工作电压源 116-1 的第一电压调节信号 210-1 , 也可定义为调压信号 210-1; 辅助电压源 116-2的第二电压调节信号 210-2, 也可定义为调压信号 210-2。 使得工作电 压源 116-1 , 辅助电压源 116-2输出跟随调压信号 210-2而改变。 数字处理单元 110还产生电¾¾源 118的电 ¾ϊ调节信号 310, 使得电 ¾ϊ源 118的输出跟随调节信号而改变。 被跟踪信号 111经过数模转换器 112被转 换成被跟踪模拟信号 113 , 被跟踪模拟信号 113经过信号调理单元 114进一 步转换成适合功率放大的信号 115 , 被放大信号 115经过跟踪电压源 117被 进一步放大并携带功率输出成为射频功率放大器所需要的供电电压 119。 为保证高跟踪带宽和高跟踪精度，跟踪电压源 117是一个线性放大单元。 跟踪电压源 117除了输入，输出外还有高端，低端两个对外端口 117-H, 117-L。 跟踪电压源 117的高端端口 117-H接其使之工作的工作电压源 116-1 , 跟踪 电压源 117的低端端口 117-L可以悬空， 或连接系统参考地 121 , 或连接辅 助电压源 116-2。 辅助电压源 116-2施加在艮踪电压源 117的氏端端口 117-L上， 而且和 跟踪电压源 117是串联的关系。 辅助电压源 116-2可以是预设定的恒定直流 电压源， 也可以是可调节的动态电压源。 辅助电压源 116-2可以是艮踪电压 源 117的偏置电压以保证跟踪电压源 117正常工作。 辅助电压源 116-2也可 以是负载 120供电电压 119组成的一部分，辅助电源 116-2和艮踪电压源 117 是串联联接的关系， 并通过串联联接关系将各自的输出电压叠加在一起合并 输出负载 120所需的供电电压 119。 辅助电压源 116-2还可以既是使跟踪电 压源 117正常工作的偏置电压又是负载 120供电电压 119组成的一部分。 工作电压源 116-1施加在艮踪电压源 117的高端端口 117-H上， 工作电 压源 116-1是跟踪电压源 117的偏置电压， 以保证跟踪电压源 117正常工作。 工作电压源 116-1可以是预设定的恒定直流电压源， 也可以是可调节的动态 电压源， 调节信号 210-1来自数字信号处理单元 110,而且调节速度也是可变 化的。 电流源 118输出与 艮踪电压源 117输出 119连接在一起作用于负载 120, 和负载 120是并联的关系。 电流源 118和辅助电压源 116-2可以是无关联的 两个装置， 也可以通过串联联接组合在一起。 电流源 118可以是预先设定的 恒定直流源， 也可以是可调节的动态电流源。 调节信号 310来自数字信号处 理单元 110,而且调节速度也是可变化的。 工作电压源 116-1和辅助电压源 116-2可以是高效率的开关模式电压源， 电流源 118可以是高效率的开关模式电流源。 这样可保证整个电源装置的高 效率。 实施例 2 实施例 2的结构图如图 4所示， 为本发明电源装置提供的一个实施例 2 结构示意图。 与实施例 1相比， 增加了工作电压源， 辅助电压源和电流源个 数。 有工作电压源 1至工作电压源 η, 分别为工作电压源 116-11 , 工作电压 源 116-12, …工作电压源 116-ln; n个 i助电压源， i助电压源 116-21, # 助电压源 116-22, …辅助电压源 116-2n 等多个电压源同时作用于 艮踪电压 源 117。 210-11,210-12....210- In, 210-21,210-22,...210-2n分别是各自的调节 信号， 这些调节信号都由数字信号处理单元 110产生而得。 有 n个电流源， 分别为电¾¾源 118-1, 电¾¾源 118-2, ....电¾¾源 118-n 同时作用于负载 120。 310-1, 310-2, ...310-n分别是各自的调节信号， 这些调节信号都是由数字信 号处理单元 110产生而得。 库 i 助电压源 116-21, i 助电压源 116-22, ...i 助电压源 116-2n和电 ¾ϊ源 118-1, 电¾¾源 118-2, ....电¾¾源 118-η彼 jt匕之间可以是无关联的也可以分别 通过串联连接关系组合在一起。 在本发明的各个实施例中，信号调理单元可以有多种形式，如图 5所示， 为本发明电源装置实施例中的第一种信号调理单元的结构示意图。 调理单元 114 由两个偏置电路和一个放大滤波电路串联而成。 被跟踪模拟信号 113先 经过偏置电路 114-1,再经过放大滤波单元 114-2,最后经过偏置电路 114-3 成 为 艮踪电压源 117的输入信号 115。 如图 6所示， 为本发明电源装置实施例中的第二种信号调理单元的结构 示意图。 调理单元 114由两个放大滤波电路和一个偏置电路串联而成。 被艮 踪模拟信号 113先经过放大滤波电路 114-1, 再经过偏置电路 114-2, 最后经 过放大滤波电路 114-3 成为 艮踪电压源 117的输入信号 115。 如图 7所示， 为本发明电源装置实施例中的第三种信号调理单元的结构 示意图。 调理单元 114由多个放大滤波单元 114-1至 114- (2η-1 ) 和多个偏 置电路单元 114-2至 114-2η串联而成。 被跟踪模拟信号 113分别经过放大滤 波单元 1,偏置电路 1, 放大滤波单元 2, 偏置电路 2, 放大滤波单元 η, 偏置电路 η, 最终得到跟踪电压源 117的输入信号 115。该实施例不限于放大 滤波单元和偏置电路交错处理， 还可以是放大滤波单元和偏置电路多种组合 方式， 这里实施例不再 枚举。 在本发明的各个实施例中， 信号调理单元也可以有多种形式， 下面详细 说明。 如图 8所示， 为本发明电源装置实施例中的第一种艮踪电压源的结构 示意图。 线性放大为开环控制， 被放大的信号 115经过多个线性放大滤波单 元 117-1, 117-2,...117-n, 最后 4舞动线性调节管 117-0进行功率放大， 线性调 节管的输出就是负载 120需要的供电电压 119。 这里 117-1,117-2,...117-n放 大单元可以是高速运算放大器， 由分立器件组成的差分放大结构， 或是 CLASS A, CLASS B, CLASS AB类放大结构。 它们之间通过串联组成级联的 关系。 工作电压源 116-1和辅助电压源 116-2直接作用于线性调节管 117-0。 如图 9所示， 为本发明电源装置实施例中的第二种艮踪电压源的结构示 意图。 艮踪电压源 117为闭环控制， 输出电压 119被反馈网络 117-111分压 取样后。 作用于误差放大器 117-1 , 被放大信号 115 也作用于误差放大器， 两者做比较放大。 误差放大器的输出是误差放大信号 117-11 , 误差放大信号 经过多级线性放大滤波单元 117-2, 117-3... 117-η, 最终成为线性调节管 117-0 的驱动信号 117-00。 线性调节管 117-0的输出就是负载需要的供电电压 119。 误差放大器 117-1和各个线性放大滤波单元通过串联组成级联的关系。 工作 电压源 116-1和辅助电压源 116-2直接作用于线性调节管 117-0。 为了保证系统性能和稳定性，还需要补偿网络 117-112,补偿网络 117-112 作用于反馈网络 117-111 , 同时还作用于误差放大器 117-1 , 线性放大滤波单 元 117-2, 117-3 , ... 117-η, 此外还作用于线性调节管 117-0。 补偿网络可釆 用电路的形式实现， 一般是由电阻、 电容构成的无源网络。 如图 10 所示， 为本发明电源装置实施例中的第三种跟踪电压源的结构 示意图。 跟踪电压源 117为闭环控制， 且为双闭环控制， 存在两套独立的反 馈网络 117-111 , 117-211。 两套 卜偿网络 117-112, 117-212。 输出电压 119 同时经过反馈网络 117-111, 117-211,得到各自的取样信号，分别作用于各自的 误差放大器 117-11, 117-21 , 作为其输入信号， 被放大信号 115同时作用于误 差放大器 117-11, 117-21,作为其另一输入信号。 误差放大器 117-11, 117-21输 出的误差放大信号分别经过各自的多级线性放大滤波单元 117-11 , 117-12, ... 117- In, 117-21 , 117-22, ... 117-2n, 被多级放大后为线性调节管 117-0的推动信号 117-10和 117-20, 这两个推动信号同时作用于线性调节管 117-0。 补偿网络 117-112, 117-212分别作用于各自的反馈环路单元， 包络反 馈网络， 误差放大器， 线性放大滤波单元， 线性调节管。 通过补偿网络保证 整个跟踪电压源稳定性和必须的性能指标。 在本发明的各个实施例中， 线性调节管 117-0也可以有多种形式， 下面 详细说明。如图 11所示， 为本发明电源装置实施例中的第一种线性调节管的 结构示意图。 线性调节管是一个单管结构， 且是 N沟道 MOSFET。 如图 12 所示， 为本发明电源装置实施例中的第二种线性调节管的结构 示意图。 线性调节管是一个单管结构， 且是 P沟道 MOSFET。 如图 13 所示， 为本发明电源装置实施例中的第三种线性调节管的结构 示意图； 线性调节管是一个双管结构， 双管都是 N沟道 MOSFET。 117-001 是高端调节管 117-01的驱动信号， 117-002是低端调节管 117-02的驱动信号。 工作电压源 116-1作用于高端调节管 117-01 , 辅助电压源 116-2作用于氐端 调节管 117-02。 下面描述的实施例与此相同或近似， 不再——赘述。 如图 14 所示， 为本发明电源装置实施例中的第四种线性调节管的结构 示意图； 线性调节管是一个双管结构， 其高端管 117-01是 N沟道 MOSFET, 氐端管 117-02是 P沟道 MOSFET。 如图 15 所示， 为本发明电源装置实施例中的第五种线性调节管的结构 示意图。 线性调节管是一个双管结构， 其高端管 117-01是 P沟道 MOSFET, 氐端管 117-02是 N沟道 MOSFET。 如图 16 所示， 为本发明电源装置实施例中的第六种线性调节管的结构 示意图。 线性调节管是一个双管结构， 其高端管 117-01是 P沟道 MOSFET, 氐端管 117-02是 P沟道 MOSFET。 以上， 工作电压源 116-1和辅助电源 116-2直接作用于线性调节管 117-0 源极或漏极。 工作电压源 116-1直接作用于高端线性调节管 117-01源极或漏 级。 辅助电源 116-2直接作用于低端线性调节管 117-02源极或漏极。 如图 17 所示， 为本发明电源装置实施例中的第七种线性调节管的结构 示意图。 线性调节管是一个双管结构， 其高端管 117-01是 NPN三极管， 低 端管 117-02是 PNP三极管。 如图 18 所示， 为本发明电源装置实施例中的第八种线性调节管的结构 示意图。 线性调节管是一个双管结构， 其高端管 117-01是 NPN三极管， 低 端管 117-02是 NPN三极管。除以上列举的两个实施例外， NPN三极管和 PNP 三极管还可以有其他多种组合， 在 jt匕不再——枚举。 以上， 工作电压源 116-1 和辅助电压源 116-2 直接作用于线性调节管 117-0集电级或发射级。工作电压源 116-1直接作用于高端线性调节管 117-01 集电级或发射级。 辅助电源 116-2直接作用于氏端线性调节管 117-02集电级 或发射级。 如图 19所示， 为本发明电源装置提供的一个实施例 3结构示意图。 跟 踪电压源 117由一个工作电压源 116-1供电。 跟踪电压源 117的低端接系统 的参考地 121。 电流源 118—端与 艮踪电压源 117输出 119相连， 另一端连 接系统的参考地 121。数字信号处理单元 110发出电流源 118的调节信号 310, 以使电流源 118的输出 艮踪调节信号。 工作电压源 116-1 同时受数字信号处 理单元 110的调节， 保证工作电压源 116-1输出跟踪调节信号 210-1。 如图 20所示， 为本发明电源装置提供的一个实施例 4结构示意图。 跟 踪电压源 117由一个工作电压源 116-1供电。 跟踪电压源 117的低端悬空不 接。 电流源 118—端与 艮踪电压源 117输出 119相连， 另一端连接系统的参 考地 121。数字信号处理单元 110发出电流源 118的调节信号 310, 以使电流 源 118的输出与调节信号相一致。 工作电压源 116-1 同时也受数字信号处理 单元 110的调节， 保证工作电压源 116-1输出跟踪调节信号 210-1。 如图 21 所示， 为本发明电源装置提供的一个实施例 5结构示意图。 跟 踪电压源 117的高端接工作电压源 116-1 , 艮踪电压源 117的氐端接辅助电压 源 116-2。 电流源 118—端与 艮踪电压源 117输出 119相连， 另一端接系统的 参考地 121。数字信号处理单元 110发出电流源 118的调节信号 310, 以使电 流源 118的输出跟踪调节信号。 数字信号处理单元 110分别发出工作电压源 116-1 , i 助电压源 116-2的调节信号 210-1 , 210-2, 以使工作电压源， 助 电压源输出分别跟踪各自的调节信号。 如图 22所示， 为本发明电源装置提供的一个实施例 6结构示意图， 跟 踪电压源 117的高端接工作电压源 116-1 ,跟踪电压源 117的低端接辅助电压 源 116-2。 电流源 118—端与 艮踪电压源 117输出 119相连， 另一端接辅助电 压源 116-2的输出端， 所接的输出端可以是正端， 也可以是负端。 数字信号 处理单元 110发出电流源 118的调节信号 310, 以使电流源 118的输出 艮踪 调节信号。 工作电压源 116-1和辅助电压源 116-2亦分别受数字信号处理单 元调节信号 210-1,210-2调节。 以使电压源输出跟踪调节信号。 如图 23所示， 为本发明电源装置提供的一个实施例 7结构示意图， 跟 踪电压源 117的高端接工作电压源 116-1 ,跟踪电压源 117的低端接多个辅助 电压源 116-21 , 116-22, ... 116-2η, 其中这多个库 i 助电压源是串联的关系。 多个电¾¾源 118-1, 118-2,... 118-n同时作用于负载 120, 它们的一端同时汇接 于输出 119,另一端分别与电压源 116-21,116-22,...116-2n的正端或负端相连。 数字信号处理单元 110分别对电流源 118-1,118-2,...118-n 故出独立调节， 以 使电流源 艮踪电流调节信号。 数字信号处理单元 110 分别对工作电压源 116-1, 辅助电压源 116-21,116-22,...116-2n 故出独立调节， 以使电压源 艮踪 电压调节信号。 以上多路电压调节信号和多路电流调节信号——对应各自的 电压源和电¾¾源。 如图 24所示， 为本发明电源装置提供的一个实施例 8结构示意图， 跟 踪电压源 117高端接多个工作电压源 116-11, 116-12, 116-13...116- In, 其低 端接多个 i 助电压源 116-21, 116-22, ...116-2n。 其中这多个 i 助电压源是 串联的 关 系 ， 这多 个工作电压源是并联的 关 系 。 多 个电流源 118-1,118-2,...118-n同时作用于负载 120, 它们的一端同时汇接于输出 119, 另一端分别与库 i 助电压源 116-21,116-22,...116-2n的正端或负端相连，多个工 作电压源 116-11,116-12,...116- In分别通过多个隔离网络 116-110,116-120, 116-130...116-lnO并联在一起， 并联后给艮踪电压源 117高端供电。 数字信 号处理单元 110发出电压调节信号 210-11,210-12, ...210- In, 分别通过各个 隔离网络 116-110, 116-120, ...116-lnO作用于工作电压源， 使得在某个确定 的时刻由各个工作电压源 116-11,116-12,...116-ln 中的一个 给艮踪电压源 117供电， 从而给跟踪电压源 117供电的是一组确定的多电平序列。 数字信号处理单元 110分别对电流源 118-1,118-2,...118-n和辅助电压源 116-21, 116-22,...116-2n 故出独立调节， 以使辅助电流源输出 艮踪电流调节 信号 310-1 , 310-2,...310-η , 辅助电压源输出 艮踪电压调节信号 210-21,210-22,...210-2η。 以上数字信号处理单元 110发出的多路电压调节信 号和多路电流调节信号——对应各自的辅助电压源和电流源。 各个隔离网络 116-110,116-120,...116-lnO 是相应的各个由切换开关 116-1101,116-1201 , ...116-1η01 , 各 个 驱 动 电 路 116-1103 , 116-1203, ...116-ln03 和各个隔离二极管 116-1102, 116-1202, ...116-ln02 组成的有源网络。 切换开关和隔离二极管是串联的关系。 驱动装置是控制切 换开关导通或关断的。 数字信号处理单元 110发出的电压调节信号 210通过 作用于驱动装置来切换工作电压源 116-11,116-12,...116-ln 到 艮踪电压源 117。 在本发明的各个实施例中， 隔离网络也可以有多种形式， 下面详细说明。 如图 25所示,为本发明电源装置实施例中的工作电压源隔离网络的第一种结 构示意图。在此实施例中，数字信号处理单元 110分别通过各个驱动 116-1103 至 1161n03连接相应的各个切换开关 116-1101至 1161n01和各个工作电压源 116-11至 116- In,各个切换开关 116-1101至 1161n01连接相应的隔离二极管 116-1102至 1161n02。 如图 26 所示， 为本发明电源装置实施例中的工作电压源隔离网络的第 二种结构示意图。 与图 25所示的隔离网络的不同在于， 图 25的隔离网络中 的各个驱动电路连接的切换开关在工作电压源与二极管之间； 图 26 所示的 隔离网络中的二极管在工作电压源与切换开关之间。 如图 27所示,为本发明电源装置中的工作电压源隔离网络 116-lnO进一 步揭示的实施例 3 结构示意图。 只用一个切换开关 116-1101 , —个二极管 116-1103就完成了两个工作电压源 116-11 , 116-12的电平切换。 其中工作电 压源 116-11较高且与切换开关管 116-1101 串联， 工作电压源 116-12较氐且 与二极管 116-1103 串联。这里切换开关 116-1101可以是 N沟道 MOSFET或 是 P沟道 MOSFET。 数字信号处理单元 110发出电压调节信号 210-1通过作 用于驱动 116-1102保证输出跟踪电压调节信号。 本发明还提供一种基于上述跟踪装置的控制方法， 参见图 28 所示的流 程图， 包括以下步 4聚：
S281 : 信号发生器发出输入信号至跟踪电压源， 并发出电流调节信号至 电流源； S282: 跟踪电压源通过工作电压源提供第一偏置电压放大输入信号；
S283： 电流源才艮据所述电流调节信号输出电流及相应功率， 与所述放大 的输入信号合并得到用于射频功率放大器的供电电压及供应的功率。 在上述的控制方法的步骤 S281 中， 还包括： 信号发生器还发出第一电 压调节信号， 控制所述工作电压源发出的第一偏置电压。 还包括： 向所述跟踪电压源提供第二偏置电压及相应的功率的辅助电压 源， 所述信号发生器还向所述辅助电压源发出第二电压调节信号控制其发出 第二偏置电压。 所述辅助电压源还与所述电流源一同向所述射频功率放大器 提供供电功率。 上面详细描述了本发明的各个实施例， 本发明的跟踪装置和方法， 可应 用到各种电子设备中， 如基站、 发射机、 等无线射频设备， 当应用在基站设 备中时， 基站信号处理单元按照当前的负载实时计算出代表不同发射功率的 电压信号， 并发出跟踪信号， 通过本发明的装置发出相应的电功率。 本发明 结构简单、 提高了跟踪精度， 避免了高频切换损耗。 能快速跟踪数字信号处 理单元发出的跟踪信号， 产生相应的电功率， 提高了基站射频功率放大器的 效率。 显然， 本领域的技术人员应该明白， 上述的本发明的各模块或各步骤可 以用通用的计算装置来实现， 它们可以集中在单个的计算装置上， 或者分布 在多个计算装置所组成的网络上， 可选地， 它们可以用计算装置可执行的程 序代码来实现， 从而， 可以将它们存储在存储装置中由计算装置来执行， 并 且在某些情况下， 可以以不同于此处的顺序执行所示出或描述的步骤， 或者 将它们分别制作成各个集成电路模块， 或者将它们中的多个模块或步骤制作 成单个集成电路模块来实现。 这样， 本发明不限制于任何特定的硬件和软件 结合。 以上所述仅为本发明的优选实施例而已， 并不用于限制本发明， 对于本 领域的技术人员来说， 本发明可以有各种更改和变化。 凡在本发明的 ^"神和 原则之内， 所作的任何修改、 等同替换、 改进等， 均应包含在本发明的保护 范围之内。

Claims

权 利 要 求 书
1. 一种跟踪电源装置， 其特征在于， 包括： 信号发生器、 工作电压源、 跟 踪电压源和电流源；
所述工作电压源， 用于向所述艮踪电压源提供第一偏置电压及相应 的功率；
所述信号发生器， 用于发出输入信号至所述跟踪电压源， 并发出电 流调节信号至所述电流源；
所述跟踪电压源， 用于根据所述工作电压源提供的所述第一偏置电 压， 放大所述输入信号；
所述电流源， 用于才艮据所述电流调节信号输出电流及相应的功率； 根据所述跟踪电压源输出的放大后的所述输入信号及所述电流源输 出的所述电流及相应的功率， 产生用于射频功率放大器的供电电压及功 率； 其中， 所述艮踪电压源与所述电流源并联。
2. 根据权利要求 1所述的装置， 其特征在于，
所述信号发生器，还用于向所述工作电压源发出第一电压调节信号； 所述工作电压源， 还用于按照所述第一电压调节信号向所述艮踪电 压源提供相应的所述第一偏置电压。
3. 根据权利要求 1所述的装置， 其特征在于， 所述信号发生器包括：
数字信号处理单元， 用于生成数字形式的跟踪信号、 所述电流调节 信号、 和所述第一电压调节信号；
D/A转换单元， 用于将所述跟踪信号转换为模拟信号； 信号调理单元， 包括放大滤波器和偏置电路； 其中， 所述放大滤波 器用于放大滤波所述模拟信号得到所述输入信号； 所述偏置电路， 用于 向所述放大滤波器提供偏置电压。
4. 根据权利要求 1所述的装置， 其特征在于， 还包括： 辅助电压源， 用于 根据所述信号发生器发出的第二电压调节信号， 输出提供给所述跟踪电 压源的第二偏置电压及相应功率， 以及通过所述电流源连接所述艮踪电 压源的输出， 与所述电流源一同输出提供射频功率放大器的供电功率； 所述信号发生器还用于发出所述第二电压调节信号。
5. 根据权利要求 4所述的装置， 其特征在于， 所述跟踪电压源还用于将所 述电流源的输出的电流， 部分返回给所述电流源。
6. 根据权利要求 4所述的装置， 其特征在于， 所述跟踪电压源包括：
多个级联的放大单元， 用于逐级地放大所述输入信号， 所述放大单 元的最后一级的输出端连接线性调节管；
所述线性调节管， 用于在所述工作电压源提供的第一偏置电压和所 述辅助电压源提供的第二偏置电压下， 放大所述逐级放大的输入信号， 得到所述用于射频功率放大器的供电电压。
7. 根据权利要求 6所述的装置， 其特征在于， 所述放大单元为线性放大滤 波器、 或运算放大器。
8. 根据权利要求 6所述的装置， 其特征在于， 还包括误差放大器和反馈电 路； 所述反馈电路， 用于反馈所述跟踪电压源输出电压至所述误差放大 器， 所述误差放大器， 用于将所述反馈电路反馈的信号和所述输入信号 比较， 比较出的误差信号发送至所述放大单元。
9. 根据权利要求 8所述的装置， 其特征在于， 还包括补偿电路， 用于为所 述反馈电路、 误差放大器、 放大单元、 和线性放大管提供信号的补偿。
10. 根据权利要求 5所述的装置， 其特征在于， 所述工作电压源的数量为多 个、 且相互并联， 所述装置还包括隔离电路、 第一数字信号处理单元； 所述第一数字信号处理单元， 用于为每个所述工作电压源分别发出 相应的第一电压调节信号；
所述隔离电路，连接在每个所述工作电压源与所述跟踪电压源之间， 用于导通或断开所述工作电压源和所述艮踪电压源之间的连接；
所述辅助电压源的数量为多个、 且相互串联， 所述电流源的数量为 多个、 且并联在相应的每个所述辅助电压源与所述艮踪电压源的输出之 间；
所述装置还包括第二数字信号处理单元； 所述第二数字信号处理单元， 用于为每个辅助电压源分别发出相应 的第二电压调节信号， 为每个电流源发出相应的电流调节信号。
11. 根据权利要求 10所述的装置，其特征在于，所述隔离电路包括切换开关、 马区动电路、 和隔离二极管；
所述驱动电路， 用于发出控制所述切换开关的导通或截止的控制信 号；
所述切换开关， 用于在所述驱动电路的触发下导通或截止； 所述隔离二极管， 用于与所述切换开关串联。
12. 一种基于权利要求 1所述装置的控制方法， 其特征在于， 包括：
信号发生器发出输入信号至跟踪电压源， 并发出电流调节信号至电 流源；
所述艮踪电压源使用工作电压源提供第一偏置电压及相应的功率放 大所述输入信号；
电流源才艮据所述电流调节信号输出电流及相应的功率， 所述电流及 相应的功率与所述放大的输入信号合并得到用于射频功率放大器的供电 电压及相应的功率。
13. 根据权利要求 12所述的控制方法， 其特征在于， 还包括：
所述信号发生器还发出第一电压调节信号， 控制所述工作电压源发 出的第一偏置电压；
还包括： 向所述跟踪电压源提供第二偏置电压及相应的功率的辅助 电压源， 所述信号发生器还向所述辅助电压源发出第二电压调节信号控 制其发出第二偏置电压；
所述辅助电压源与所述电流源一同向所述射频功率放大器提供供电 功率。
PCT/CN2010/075917 2010-06-23 2010-08-11 跟踪电源装置及其控制方法 WO2011160330A1 (zh)

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