WO2010062201A1 - Régulation de puissance côté primaire pour transfert d'énergie par induction - Google Patents

Régulation de puissance côté primaire pour transfert d'énergie par induction Download PDF

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Publication number
WO2010062201A1
WO2010062201A1 PCT/NZ2009/000263 NZ2009000263W WO2010062201A1 WO 2010062201 A1 WO2010062201 A1 WO 2010062201A1 NZ 2009000263 W NZ2009000263 W NZ 2009000263W WO 2010062201 A1 WO2010062201 A1 WO 2010062201A1
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WO
WIPO (PCT)
Prior art keywords
output voltage
conductive path
voltage
pick
power supply
Prior art date
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PCT/NZ2009/000263
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English (en)
Inventor
Udaya Kumara Madawala
Duleepa Jayanath Thrimawithana
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Auckland Uniservices Limited
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Filing date
Publication date
Priority claimed from NZ573241A external-priority patent/NZ573241A/en
Application filed by Auckland Uniservices Limited filed Critical Auckland Uniservices Limited
Priority to US13/131,153 priority Critical patent/US8923015B2/en
Publication of WO2010062201A1 publication Critical patent/WO2010062201A1/fr
Priority to US14/584,320 priority patent/US9461480B2/en
Priority to US15/281,591 priority patent/US10432026B2/en

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Classifications

    • B—PERFORMING OPERATIONS; TRANSPORTING
    • B60—VEHICLES IN GENERAL
    • B60L—PROPULSION OF ELECTRICALLY-PROPELLED VEHICLES; SUPPLYING ELECTRIC POWER FOR AUXILIARY EQUIPMENT OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRODYNAMIC BRAKE SYSTEMS FOR VEHICLES IN GENERAL; MAGNETIC SUSPENSION OR LEVITATION FOR VEHICLES; MONITORING OPERATING VARIABLES OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRIC SAFETY DEVICES FOR ELECTRICALLY-PROPELLED VEHICLES
    • B60L53/00—Methods of charging batteries, specially adapted for electric vehicles; Charging stations or on-board charging equipment therefor; Exchange of energy storage elements in electric vehicles
    • B60L53/10—Methods of charging batteries, specially adapted for electric vehicles; Charging stations or on-board charging equipment therefor; Exchange of energy storage elements in electric vehicles characterised by the energy transfer between the charging station and the vehicle
    • B60L53/12—Inductive energy transfer
    • B60L53/122—Circuits or methods for driving the primary coil, e.g. supplying electric power to the coil
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J50/00—Circuit arrangements or systems for wireless supply or distribution of electric power
    • H02J50/10—Circuit arrangements or systems for wireless supply or distribution of electric power using inductive coupling
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J50/00—Circuit arrangements or systems for wireless supply or distribution of electric power
    • H02J50/10—Circuit arrangements or systems for wireless supply or distribution of electric power using inductive coupling
    • H02J50/12—Circuit arrangements or systems for wireless supply or distribution of electric power using inductive coupling of the resonant type
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J50/00—Circuit arrangements or systems for wireless supply or distribution of electric power
    • H02J50/40—Circuit arrangements or systems for wireless supply or distribution of electric power using two or more transmitting or receiving devices
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
    • Y02T10/00—Road transport of goods or passengers
    • Y02T10/60—Other road transportation technologies with climate change mitigation effect
    • Y02T10/70—Energy storage systems for electromobility, e.g. batteries
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
    • Y02T10/00—Road transport of goods or passengers
    • Y02T10/60—Other road transportation technologies with climate change mitigation effect
    • Y02T10/7072—Electromobility specific charging systems or methods for batteries, ultracapacitors, supercapacitors or double-layer capacitors
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
    • Y02T90/00—Enabling technologies or technologies with a potential or indirect contribution to GHG emissions mitigation
    • Y02T90/10—Technologies relating to charging of electric vehicles
    • Y02T90/14—Plug-in electric vehicles
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
    • Y02T90/00—Enabling technologies or technologies with a potential or indirect contribution to GHG emissions mitigation
    • Y02T90/10—Technologies relating to charging of electric vehicles
    • Y02T90/16—Information or communication technologies improving the operation of electric vehicles

Definitions

  • This invention relates to an apparatus and method for controlling power in an inductive power transfer system. More specifically, the invention enables the control or regulation of the output of a pick-up from the primary side of the IPT system.
  • IPT Inductive power transfer
  • ICPT inductively coupled power transfer
  • a typical IPT system consists of three main components; an AC power supply, a primary conductive path, and one or more electrically isolated pick-ups coupled with a load and provided substantially adjacent the primary conductive path. Together, the power supply and primary conductive path form the primary side of an inductive power transfer system, while the pickup and associated circuitry forms the secondary side.
  • the primary conductive path typically in the form of an elongated conductive loop or track, is energised by the AC power supply to create a continuously varying magnetic field about the track.
  • the or each pick-up includes an inductive coil, in which a voltage is induced by the changing magnetic flux passing through the coil in accordance with Faraday's law of induction, thereby achieving contactless inductive power transfer.
  • the or each pick-up will include some form of controller circuit to control the transfer of power to the load, including a switched-mode controller such as a boost converter, for example, to supply the relatively constant output voltage required by the load, thereby providing secondary-side output power control.
  • a switched-mode controller such as a boost converter
  • the output power of the pickup may be controlled from the primary side of the system. This may be due to the additional cost and complexity of the additional components required for a pick-up side controller or due to limitations on the physical size of the pick-up, for example.
  • Power supplied to a load associated with a pick-up may be controlled from the primary side of an IPT system by modulating the amplitude, phase or frequency of the current in the primary conductive path to reduce power at partial loads and minimise losses, or to increase the current in the primary conductive path and therefore the magnetic flux when the pick-up coil is not ideally aligned, for example, to ensure the required power is supplied to the load.
  • Providing primary-side power control can help reduce costs by eliminating the power conditioner and switched-mode controller from the pick-up circuit.
  • IPT inductive power transfer
  • the invention may broadly be said to consist in a method of controlling the output voltage of a pickup in an inductive power transfer (IPT) system comprising the pickup, a power supply, and a primary conductive path, the method comprising the steps of: deriving an estimate of the output voltage of the pickup from the voltage across the primary conductive path; and adjusting the current in the primary conductive path so that the estimated pick-up output voltage matches a required pick-up output voltage, by controlling the voltage supplied to the primary conductive path by the power supply.
  • IPT inductive power transfer
  • the estimate of the output voltage takes into account changes in both an output load and a mutual coupling between the pickup and the primary conductive path.
  • the step of deriving an estimate of the output voltage of the pickup comprises determining the phase angle between the voltage and current in the primary conductive path, and using the phase angle to calculate the real component of the voltage across the primary conductive path.
  • the step of deriving an estimate of the output voltage of the pickup further comprises using the phase angle to calculate the imaginary component of the voltage across the primary conductive path, using the imaginary component to calculate the mutual inductive coupling between the pickup and the primary conductive path, and using the phase angle and mutual inductive coupling to derive an estimate of the output voltage of the pickup.
  • the step of adjusting the current in the primary conductive path comprises adjusting the current such that the estimated pick-up output voltage matches the required output voltage.
  • the invention may broadly be said to consist in a power controller adapted to perform the method according to any of the preceding statements.
  • the invention may broadly be said to consist in a power supply including the power controller of the second aspect.
  • the invention may broadly be said to consist in an IPT system including the power supply of the third aspect.
  • the invention may broadly be said to consist in a power supply .for inductive coupling with a pickup via a conductive path in an inductive power transfer (IPT) system, the power supply comprising: an inverter; a resonant tank electrically coupled with the output of the inverter and comprising a tuning capacitor and the conductive path; and a power controller adapted to estimate the output voltage of a pick-up inductively coupled with the power supply in use, by determining the phase angle between the voltage and current in the primary conductive path, calculating the real component of the voltage across the conductive path using the phase angle, deriving an estimate of the output voltage from the real component, and controlling the current supplied to the conductive path by varying the inverter output voltage such that the estimated output voltage matches a required pick-up output voltage.
  • IPT inductive power transfer
  • the power controller is further adapted to use the phase angle to calculate the imaginary component of the voltage across the primary conductive path, use the imaginary component to calculate the mutual inductive coupling between the pickup and the primary conductive path, and use the phase angle and mutual inductive coupling to derive an estimate of the output voltage of the pickup.
  • the inverter comprises two pairs of switches in an H-bridge configuration, wherein the power controller operates each pair of switches using symmetric square wave driving signals and is adapted to control the inverter output voltage by phase shifting one driving signal with respect to the other by an angle of between 180° and 360°.
  • the inverter output voltage may be controlled using pulse-width modulation.
  • the inverter output voltage may be controlled using a pre-regulator before the inverter.
  • a simple switched-mode DC/DC converter to regulate the inverter input voltage so that the inverter output voltage can be varied as desired.
  • the invention may broadly be said to consist in an inductive power transfer (IPT) system comprising a power supply according to the fifth aspect, a conductive path, and a pick-up inductively coupled with the power supply via the conductive path.
  • IPT inductive power transfer
  • Figure 1 is a schematic of an IPT system according to the prior art
  • Figure 2 is a schematic of an IPT system according to the preferred embodiment of the present invention
  • Figure 3 is a phasor diagram illustrating the track voltage and current for the system of Figure
  • Figure 4 shows the ideal voltage/current characteristics of IPT systems of both the prior art and the present invention
  • FIG. 5 is a block diagram of a controller according to the preferred embodiment of the present invention.
  • Figure 6 is a graph showing the response of a pickup to a load transient
  • Figure 7 is a graph showing the response of the track to a load transient
  • Figure 8 is a graph showing the system voltages and currents of an example embodiment of the present invention under a light load
  • Figure 9 is a graph showing the system voltages and currents of an example embodiment of the present invention under a heavy load
  • Figure 10 is a graph showing the measured and estimated voltages of an example IPT system according to the present invention.
  • Figure 11 is a graph showing the system voltages and currents of an example embodiment of an example embodiment of the present invention at a high load
  • Figure 12 is a graph showing the system voltages and currents of the example embodiment of the present invention at a light load.
  • Figure 13 is a graph showing the system voltages and currents of the example embodiment of the present invention at a light load with a restored output voltage.
  • Fig. 1 shows a typical IPT system according to the prior art, with controllers employed on each side of an air-gap across which the power is transferred.
  • the primary side controller generally operates the inverter to maintain a constant current in the primary winding, which is referred to as the track, compensating for any variations in input supply and pick-up load (R L ).
  • a resonant converter is generally used to generate the track current at the desired frequency, which ranges from 10-40 kHz in typical IPT systems.
  • a constant track current is generally necessary but a varying track current may be employed for single pick-up systems.
  • a resonant circuit, tuned to the same track frequency, is usually employed in the pickup system to provide compensation for power factor improvement and maximum power delivery.
  • the pick-up side controller operates the pick-up side circuit as a boost converter, using switch S, to regulate the amount of power extracted from the track through magnetic coupling, M, and transferred to the load.
  • the pick-up behaves as a constant current source feeding the load.
  • the amount of the current fed to the load is controlled by the duty cycle of the switch, which essentially decouples the load from the track when 'on', and is operated at a moderate frequency to lower switching losses.
  • a typical pick-up that has a winding inductance L 2 , which if not compensated (not tuned or does not contain a resonant circuit), can be represented by the following two equations:
  • V 0C JMTJTI 1 (1)
  • V 00 and U c are the open circuit voltage and short-circuit current, respectively, of a pick-up which is magnetically coupled through a mutual inductance of M to a primary track that carries a current of I 1 at frequency ⁇ .
  • the V-I characteristic of the pick-up changes with the primary current I 1 , if other parameters are kept constant.
  • both the open circuit voltage and short circuit current in the pick-up are directly proportional to the current I 1 in the primary conductive path.
  • I 1 SC ⁇ L 2 1, 1 ( v 4) '
  • Equation (7) suggests that the AC load voltage or the voltage across V c2 is produced by a current source l sc , which in fact is the Norton equivalent current of the pick-up coil L 2 . Therefore the pick-up coil can be represented by its Norton equivalent circuit, and any pick-up side analysis can simply be performed by treating the pick-up essentially as a parallel resonant circuit - L 2 in parallel with C 2 and fed by the current source l S c- Under this condition, the power delivered to the load by the pick-up in Fig. 1, can be expressed by
  • the present invention provides a method, apparatus and system for controlling the output of a pick-up solely from the primary side of an IPT system, without any form of communications between the pick-up and power supply. This is achieved by monitoring changes in the track voltage, which can be measured directly by the power supply on the primary (powering) side of the system.
  • the load that each pick-up supplies will typically fluctuate or vary, and this load change is reflected through the mutual inductive coupling M back to the power supply, which affects the voltage across the primary tank, V c i.
  • An estimate of the pickup output voltage V 0 may therefore be derived from the reflected voltage across the primary conductive path, V 1 -, or the resonant tank capacitor V c1 , which can be detected from the primary side of the system.
  • the real (as opposed to the imaginary) component of the resonant tank voltage V c1 has been found to be proportional to, or at least indicative of, the pick-up output voltage V 0 , and therefore provides a way of estimating the output voltage to allow control thereof to account for changes in the load without any feedback from the secondary side of the system. This will be described in further detail herein below.
  • the present invention is therefore employed in the powering (or primary) side of the IPT system, and regulates or otherwise controls the output voltage of the pick-up, controlling the power transfer from the primary side to the load associated with the pick-up as effectively as that achieved in typical IPT systems with two controllers, or a single controller with secondary-side feedback.
  • An inductive power transfer (IPT) system with a single controller without secondary side feed-back may lower the overall system cost, complexity and/or size, and may also improve the efficiency and reliability of the system compared to the prior art.
  • Embodiments of the invention will be described herein below by way of example with respect to regulating the output voltage of a pick-up from the primary side of the IPT system, however it is to be appreciated that the same control technique can be adapted to regulate the output power or current. For example, in some applications such as battery or capacitor charging, a constant pick-up output current or power may be preferable.
  • a power controller is provided only on the primary side of the system, coupled with the power supply.
  • the IPT system comprises the power controller coupled with an inverter, which in turn is electrically coupled through the series inductor L 1 with a resonant tank comprising the primary conductive path or track L 1 and a tuning capacitor C 1 .
  • the inverter is preferably adapted to generate an alternating current output at the frequency to which the primary resonant tank and the pick-up are tuned.
  • that frequency will be in the range of 10-40 kHz.
  • the output of the inverter may be a symmetric square wave voltage to minimise switching losses. This requires only a simple circuit to achieve, as shown in Figure 1.
  • the inverter may be modified for pulse width modulation (PWM) control to vary the amplitude of the output, or the inverter may provide a sinusoidal output voltage.
  • PWM pulse width modulation
  • regulation of the pick-up output is achieved by varying the track current using amplitude modulation, although other techniques known in the art may alternatively be used without departing from the scope of the invention.
  • the inverter comprises four switches in a bridge configuration each shunted by diodes.
  • the switches may be manipulated to produce a square- wave output, which is preferably symmetric with a 50% duty cycle and a substantially fixed frequency.
  • the track current is controlled using a form of amplitude modulation wherein the duty cycle of the inverter output is varied by adjusting the pulse width of high and low levels in a three-level inverter (high being a positive voltage, low being a negative voltage, and the middle level being zero according to the preferred embodiment).
  • the invention may further comprise any other suitable DC-AC converter capable of allowing control of the track current.
  • the power supply is depicted as being supplied by a DC power source, it should be appreciated that the power supply may alternatively include an AC to DC converter or rectifier, or an AC-AC converter, such that the system may alternatively be supplied by a single- or multi-phase AC power source such as that available from an outlet coupled to an electricity supply network or grid.
  • the power controller, inverter, resonant tank, series inductor and primary conductive path may be referred to as the "primary side" of the IPT system.
  • the secondary side of the IPT system comprises a single pick-up circuit.
  • the pick-up circuit is relatively simple as the output of the circuit may be controlled from the primary side.
  • the pick-up circuit comprises a pick-up coil L 2 , a tuning capacitor C 2 forming a resonant circuit with the pickup coil, and additional circuitry to supply power to a load associated with the pick-up such as a rectifier and filter where a DC output is required by the load R L .
  • the pick-up coil is inductively coupled with the primary conductive path or track, as shown by the mutual inductance M, causing a current to be induced in the pick-up coil as it intercepts the continuously varying magnetic field produced by an alternating current passing through the primary conductive path.
  • the inductive pick-up circuit of Figure 1 is depicted as being parallel tuned and having a DC output for the purposes of this example, the actual design of the pick-up circuit will depend on the application of the IPT system and the requirements of the load associated with the circuit.
  • the pick-up circuit may be series-tuned (i.e. the tuning capacitor C 2 provided in series with the pick-up coil L 2 ), or may have an AC output.
  • the pick-up circuit may be series-tuned (i.e. the tuning capacitor C 2 provided in series with the pick-up coil L 2 ), or may have an AC output.
  • the power required by a load associated with the pick-up generally fluctuates or varies with respect to time.
  • the power controller 101 of the present invention provides a means for doing this, controlling the track current to match the required output power by altering the pick-up V-I (voltage-current) characteristic.
  • the voltage, V n reflected in the track due to pick-up current, I 2 can be expressed by
  • the input current, l in , and track current, I 1 can be expressed by
  • Equation (14) implies that the track current, in this particular inductor-capacitor-inductor (LCL) resonant circuit configuration, is unaffected by the load for a given input voltage.
  • the track current may be considered as being constant, the output voltage, V 0 , of the pick-up is given by
  • V 0 I 0 R L (16)
  • Equation (18) implies that for a given pick-up design and track current, the output voltage depends on the load impedance, and can be controlled by the track current, using the input voltage as given in (14), to compensate for any variations of the load impedance.
  • Such control has traditionally required some form of 'wireless' feed-back of the output voltage or load impedance, which is cumbersome and expensive, requiring additional components and control.
  • control can be implemented without any wireless feed-back of the output voltage but only utilizing the track voltage itself as described below.
  • a closed-loop controller can thus be implemented in such a way to generate an input voltage, which forces the predicted V 0 to be as same as the actual V 0 , regardless of changes in the load or the magnetic coupling.
  • the proposed single controller regulates the output power by changing the track current, which is unique for each load.
  • the required track current could be maintained by controlling the input voltage as per (14).
  • the pick-up characteristics under this control strategy for different load conditions are shown in Fig. 4.
  • the proposed controller forces the pick-up to operate at a point, instead of forcing to follow a trajectory.
  • the track current is also varied in such a manner that the pick-up moves on to a new operating point with a different Q 2 , which will maintain the required output voltage.
  • the pick-up operates with a variable Q 2 , which is high for light loads and low for high loads.
  • a control strategy according to the invention will be described below with reference to one possible example embodiment.
  • a diagram of the controller 101 is shown in Fig. 5 and is simulated using The MathWorks, Inc.'s Simulink ® .
  • the time average of the phase difference ⁇ , between the track voltage and the track current is calculated.
  • the cosine value of this phase angle is then calculated and multiplied by the RMS value of the track voltage to obtain 9te:(V c1 ).
  • This is followed by the estimation of the output voltage by multiplying the calculated 9te:(V c1 ) with a constant, k, which is equivalent to (2V2L 2 )/( ⁇ M) and unique to the system (assuming a constant mutual coupling M).
  • the estimated output voltage, (V 0 , e s t ) > is compared with a reference (V o ref ), which represents the required output voltage, and the error is fed through a Pl controller to derive a phase delay angle ( ⁇ de ia y ) that can be used to control the inverter voltage, which in turn determines the track current in order to maintain the required output voltage.
  • the phase delay ⁇ de ⁇ ay is limited to between 0 and ⁇ , and is used to derive the drive signals for the two legs of the H-bridge inverter, which are ordinarily driven with a phase delay of ⁇ radians or 180° to obtain the maximum output voltage (i.e.
  • the additional phase delay ⁇ de ia y forces one of the legs in the H- bridge inverter to be driven with an additional phase delay (in addition to the normal 180°) with respect to the other leg, thus creating a square wave voltage output with two voltage levels (positive and negative) plus an intermediate ground level equal to the ⁇ de ⁇ a y angle, to control the effective input voltage, V 1n , supplied to the resonant tank to regulate the track current.
  • the controller therefore controls the pulse width of the high (positive) and low (negative) outputs of the inverter by varying the proportion of time that the inverter output is grounded, thereby creating a stepped waveform.
  • the pulse widths of the inverter are thus variable, the output frequency preferably remains substantially equal to that to which the resonant tank and pick-up are each tuned.
  • Fig. 6 shows the response of output voltage and output current to a change in load at 20 ms.
  • the primary converter has been delivering approximately 110 W at 35V to the pick-side load, and at 20 ms the load has been switched to 70 W, which has caused the output current to decrease from about 3 A to 2 A.
  • An instantaneous rise in output voltage can be observed but at about 120 ms the output voltage comes back to its original steady state value of approximately 35 V.
  • the initial rise in output voltage is caused by the slow response of the controller, which may be optimized. In practice, the settling time and the voltage transients can be minimized by increasing the gain of the controller and using a larger output capacitor. Also the slight error in steady state output voltage can be attributed to losses in the output stage, which has not been taken into account in this example voltage estimation algorithm.
  • the two legs of the H-bridge inverter are driven by square wave signals V m and V H2 each having a 50% duty cycle at the required frequency, separated by the phase delay ⁇ de i a y to produce a stepped square wave input V in to the resonant tank circuit.
  • the phase delay ⁇ de ⁇ ay between V H i and V H2 is determined by the Pl controller and when the phase delay produced by the Pl controller approaches 0, the phase shift between V m and V H2 approaches 180°.
  • the phase delay ⁇ de ⁇ ay is added to a default delay of ⁇ such that V H2 always lags (or alternatively leads) V H i by an angle of between ⁇ and 2 ⁇ .
  • Fig. 7 illustrates the delay ⁇ de iay generated by the PID controller and the resulting track current profile for the same load transient shown in Fig. 6.
  • the phase delay is increased to reduce the track current, through which the reduction in power demand can be met.
  • the increased delay between V H i and V H2 i.e. T ⁇ + ⁇ d eiay
  • V in reducing the pulse width of the high and low level outputs of the inverter and increasing the period during which the inverter output is zero
  • the load current drops from about 3 A to 2 A to maintain the required output voltage of 35 V.
  • the output of the inverter (Vm), track current (I 1 ), pickup voltage (V st ) and the output voltage (V 0 ) of the system for light (16 ⁇ ) and heavy (10 ⁇ ) loads are shown in Fig. 8 and Fig. 9, respectively.
  • the load is increased from 16 ⁇ to 10 ⁇ , the power drawn from the pickup unit increases, and to meet this increase in power demand the track current has to increase.
  • This is achieved by reducing the phase delay ⁇ de ⁇ ay so that the delay between V m and V H2 tends towards the default delay of ⁇ , which causes V, n to increase as evident from Fig. 8 and Fig. 9.
  • the output voltage is kept constant at 35 V for both loads.
  • the example single controller IPT system of the present invention was experimentally tested on a 150 Watt laboratory prototype IPT system, again using the parameters given in Table 1 , above.
  • the primary side was energized by a 20V/10A H-bridge three-level inverter to generate a track current that was required for maintaining an output voltage of 35V, under varying load conditions.
  • An open loop controller was used in the example for demonstration purposes.
  • harmonics are expected to be present in the track current, affecting the accuracy of the analysis presented above which assumed sinusoidal excitation.
  • Table 2 shows the measured voltages, currents and phase angle, ⁇ of the prototype 150 Watt IPT system with a mutual coupling M of 8.2uH, under varying load conditions but at constant input voltage of 20V.
  • est> and the output voltage, V 0 , est> are given in the last two columns of Table 2.
  • the track current should remain constant for a given input voltage. This is true for ideal conditions, under which the resistive losses in the windings and deviations of component values can be neglected.
  • the track current is not constant at the constant voltage of 20V but decreases as the power output increases.
  • Q 2 is high and, consequently, as per (13) the input current increases and, as such, the on state voltage drop across inverter switches and voltage drops across winding resistances of the primary side invariably increase, causing a reduction in track current. It is important to note that the reduction in track current has no impact on the accuracy of the predicted voltage values.
  • Fig. 11 shows the measured output voltage, voltage generated by the inverter, track voltage and track current under steady state conditions for a high load. While the prototype was operating under this condition, the load impedance was increased. As described above, the pick-up is essentially a current source, and thus the increase in load impedance resulted in a subsequent increase in output voltage and output power, owing to the load being supplied by a constant current source. This is clearly evident from Fig. 12, which shows an increase in output voltage, and more importantly a reduction in phase angle between track voltage and current in accordance with Fig. 3. The track current remains approximately constant as the voltage generated by the inverter was unaltered.
  • the present invention may be said to consist in a method of controlling power in an IPT system using only a single power controller on the primary/powering side of the system, a power controller performing the aforementioned method, an IPT power supply comprising at least the power controller, and/or an IPT system comprising at least the IPT power supply of the present invention.
  • the primary- side power controller of the present invention may be used in certain circumstances in systems having multiple pickups inductively coupled with a single power supply and/or including secondary-side controllers without departing from the scope of the invention.
  • the proposed method which requires only a single controller located on the powering side to effectively control the output voltage of receiving side, is simple and cost effective in comparison to existing techniques.
  • the proposed single controller is suitable for IPT systems with approximately constant magnetic coupling but can easily be modified to applications with variable coupling.
  • IPT systems with the proposed controller may offer the advantages of being efficient, reliable and low in cost while offering the same or a similar level of controllability as IPT control systems of the prior art.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Transportation (AREA)
  • Mechanical Engineering (AREA)
  • Inverter Devices (AREA)

Abstract

La présente invention concerne un procédé de régulation de la tension de sortie d’un capteur dans un système de transfert d'énergie par induction (IPT) sans aucune forme supplémentaire de communications pour une rétroaction du capteur à l'alimentation électrique. Le procédé comprend les étapes consistant à déterminer une estimation de la tension de sortie du capteur à partir de la tension dans le trajet conducteur primaire, et à ajuster le courant passant dans le trajet conducteur primaire afin que la tension de sortie estimée du capteur corresponde à une tension de sortie requise du capteur. En particulier, une estimation de la tension de sortie du capteur est dérivée de l'amplitude et de l'angle de phase de la tension dans le trajet conducteur primaire.
PCT/NZ2009/000263 2008-11-26 2009-11-26 Régulation de puissance côté primaire pour transfert d'énergie par induction WO2010062201A1 (fr)

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US13/131,153 US8923015B2 (en) 2008-11-26 2009-11-26 Primary-side power control for inductive power transfer
US14/584,320 US9461480B2 (en) 2008-11-26 2014-12-29 Primary-side power control for inductive power transfer
US15/281,591 US10432026B2 (en) 2008-11-26 2016-09-30 Primary-side power control for inductive power transfer

Applications Claiming Priority (6)

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NZ573241 2008-11-26
NZ573241A NZ573241A (en) 2008-11-26 2008-11-26 Estimating pickup output voltage by voltage across the primary conductive path
NZ579498 2009-09-03
NZ579499 2009-09-03
NZ57949909 2009-09-03
NZ57949809 2009-09-03

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US13/131,153 A-371-Of-International US8923015B2 (en) 2008-11-26 2009-11-26 Primary-side power control for inductive power transfer
US14/584,320 Continuation US9461480B2 (en) 2008-11-26 2014-12-29 Primary-side power control for inductive power transfer

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PCT/NZ2009/000263 WO2010062201A1 (fr) 2008-11-26 2009-11-26 Régulation de puissance côté primaire pour transfert d'énergie par induction

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