WO2007142009A1

WO2007142009A1 - Power conversion apparatus and compressor

Info

Publication number: WO2007142009A1
Application number: PCT/JP2007/060248
Authority: WO
Inventors: Hitoshi Haga
Original assignee: Daikin Industries, Ltd.
Priority date: 2006-06-07
Filing date: 2007-05-18
Publication date: 2007-12-13
Also published as: JP2007330023A

Abstract

A power conversion apparatus (1a) is provided with a matrix converter (11), reactors (L1-L3) and capacitors (C1-C3). The matrix converter (11) is provided with input terminals (111-113), output terminals (114-116) and bidirectional switches (SRU, SRV, SRW, SSU, SSV, SSW, STU, STV, STW). The input terminals (111-113) are supplied with three-phase alternating current voltages (VR, VS, VT) from a three-phase alternating power supply (V). All of the bidirectional switches are capable of reverse blocking, and convert the three-phase alternating current voltages (VR, VS, VT) inputted to the input terminals (111-113) into desired three-phase alternating current voltages (VU, VV, VW). The reactors (L1-L3) are connected to the input terminals (111-113). The capacitors (C1-C3) are connected at ends on one side and other ends are connected to the output terminals (114-116).

Description

Specification

Power converter and compressor

Technical field

TECHNICAL FIELD [0001] The present invention relates to a power conversion device, and more particularly to a matrix converter.

Background art

Conventionally, as a power conversion device that converts AC power to desired AC power (AC-AC conversion), conversion to AC power DC power (AC-DC conversion) and conversion from DC power to AC power A combination of (DC-AC conversion) is used. For example, a rectifier circuit is used for AC-DC conversion, and an inverter is used for DC-AC conversion.

[0003] Techniques related to the present invention are shown below.

[0004] Non-Patent Document 1: Sato et al., 3 others, “Method of improving the voltage utilization rate of matrix converters”, Proceedings of the Institute of Electrical Engineers of Japan 2003, March 2003, p. 95- 96 Non-Patent Document 2: Satoshi Ito, 2 others “Improvement method of input / output waveform of matrix converter by virtual ACZDCZAC conversion method”, IEEJ Technical Report, Semiconductor Power Conversion 'Industrial Power Electrical Application Joint Study Group, 2002 November, p. 75-80

Disclosure of the invention

Problems to be solved by the invention

[0005] However, for example, when converting three-phase AC power into desired three-phase AC power, the rectifier circuit requires at least six switching element forces, and the inverter also requires at least six switching elements. . For this reason, the loss generated in the power converter increased.

[0006] The present invention has been made in view of the above-described circumstances, and an object of the present invention is to reduce the number of switching elements and to reduce the loss generated in the power converter.

Means for solving the problem

[0007] A first aspect of the power conversion device according to the present invention includes first to third input terminals (111 to 113), first to third output terminals (114 to 116), and reverse blocking capability. Bi-directional switches (S, S, S, S, S, S, S, S, S;) having the first to third inputs. AC voltage (V, V, V) input to the power terminal is exchanged as desired using the bidirectional switch.

R S T

A matrix converter (11) for converting current voltages (V 1, V 2, V 3), and the first to third inputs

U V W

The first to third rear tutors (L1 to L3) connected to each of the force terminals and the respective one ends thereof are connected to each other, and the respective other ends are connected to the first to third output terminals.

1 to 3 capacitors (C1 to C3).

[0008] A second aspect of the power converter according to the present invention is (la), the first aspect of the power converter, and the switching operation of the matrix converter (11) is combined with the power converter and It is determined based on the switching operations of the rectifier circuit (12) and the inverter (13) that constitute an equivalent circuit.

[0009] A third aspect of the power converter according to the present invention is the second aspect of the power converter, wherein the rectifier circuit (12) and the inverter (13) are a voltage type and a current type, respectively. is there.

[0010] A fourth aspect of the power conversion device according to the present invention includes first to third input terminals (111 to 113), first to third output terminals (114 to 116), and reverse blocking capability. Bi-directional switches (S, S, S, S, S, S, S, S, S;) having the first to third inputs.

RU RV RW SU SV SW TU TV TW

AC voltage (V, V, V) input to the power terminal is exchanged as desired using the bidirectional switch.

R S T

U V W

First to third rear tutors (L1 to L3) connected to each of the power terminals, and first to third capacitors (C1 to C3) each having one end connected to each other. The other end of each of the third to third capacitors is selectably connected to any one of the first to third input terminals and the first to third output terminals.

A fifth mode (lb) of the power converter according to the present invention is the fourth mode of the power converter, and the switching operation of the matrix converter (11) is combined with the power converter and It is determined based on each switching operation of the rectifier circuit (12; 121) and the inverter (13; 13 1) constituting the equivalent circuit.

[0012] A sixth aspect of the power converter according to the present invention is a fifth aspect of the power converter, wherein each of the first to third capacitors (C1 to C3) is the first to third. When connected to the third output terminal (114 to 116), the rectifier circuit (12) and the input The barter (13) is a voltage type and a current type, respectively, and when each of the first to third capacitors is connected to the first to third input terminals (111 to 113), the rectifier The circuit and the inverter are current type and voltage type, respectively.

[0013] A seventh aspect of the power converter according to the present invention is any one of the first to sixth aspects of the power converter, wherein the first to third input terminals (111 to 113) and And a clamp circuit (2) connected between the first to third output terminals (114 to 116).

[0014] A compressor according to the present invention is equipped with any one of the first to seventh aspects (la; lb) of the power converter.

The invention's effect

According to the first aspect of the power conversion device of the present invention, a three-phase AC power source is connected to the first to third input terminals, and the first to third rear tuttles are connected via the matrix converter. By short-circuiting, energy can be stored in the first to third rear tuttles, and thus the voltage across the first to third capacitors can be boosted. In addition, since each of the first to third capacitors constitutes the first to third reactors and the LC filter, it is possible to reduce the high frequency component included in the voltage output to the first to third output terminals. it can. As compared with an AC-AC conversion circuit using a rectifier circuit and an inverter, the number of switching elements is small and the loss generated in the power conversion device can be reduced.

[0016] Furthermore, since the bidirectional switch has a reverse blocking capability, it is possible to prevent a current from flowing backward in the bidirectional switch. By preventing the backflow of current, an element such as an interphase reactor is not required to prevent the backflowed current from flowing to other bidirectional switches. Therefore, the number of elements can be reduced, and thus loss generated in the elements can be reduced.

[0017] According to the second, third, fifth and sixth aspects of the power conversion device according to the present invention, the generation of the switching pattern is relatively easy.

[0018] According to the fourth aspect of the power conversion device of the present invention, each of the other ends of the first to third capacitors is connected to the first to third input terminals, thereby the power conversion device. Can function as a step-down converter. On the other hand, the first to third capacitors By connecting each of the other ends to the first to third output terminals, the power conversion device can function as a boost converter. Therefore, the variable region of the voltage output to the first to third output terminals can be expanded.

[0019] According to the seventh aspect of the power conversion device of the present invention, it is possible to absorb the surge voltage generated by the switching of the bidirectional switch. Further, the clamp circuit is claimed in claim

When applied to the power converter according to No. 2, the overvoltage generated at the time of switching the connection of one end of the first to third capacitors can be absorbed.

[0020] According to the compressor of the present invention, the efficiency of the compressor can be increased.

[0021] The objects, features, aspects, and advantages of the present invention will become more apparent from the following detailed description and the accompanying drawings.

Brief Description of Drawings

FIG. 1 is a diagram conceptually showing a power conversion device described in a first embodiment.

FIG. 2 is a circuit diagram conceptually showing a bidirectional switch.

FIG. 3 is a circuit diagram conceptually showing a bidirectional switch.

FIG. 4 is a circuit diagram conceptually showing a clamp circuit.

FIG. 5 is a circuit diagram conceptually showing an equivalent circuit.

FIG. 6 is a diagram conceptually showing a power conversion device described in a second embodiment.

FIG. 7 is a diagram conceptually showing a control circuit.

FIG. 8 is a circuit diagram conceptually showing an equivalent circuit.

FIG. 9 is a block diagram conceptually showing a control unit.

BEST MODE FOR CARRYING OUT THE INVENTION

[0023] First Embodiment.

FIG. 1 conceptually shows the power conversion device la according to the present embodiment. The power conversion device 1 a includes a matrix converter 11, rear tuttles L1 to L3, and capacitors C1 to C3.

. FIG. 1 further shows a three-phase AC power source V, a motor 4 and a clamp circuit 2.

The matrix converter 11 has input terminals 111 to 113, output terminals 114 to 116, and bidirectional switches S 1, S 2, S 3, S 3, S 3, S 3, S 3, S 5 and S 5. Input terminal 111-

RU RV RW SU SV SW TU TV TW

113 is supplied with three-phase AC voltages V 1, V 2 and V from a three-phase AC power source V. [0025] Bidirectional switches S, S, S, S, S, S, S, S, S, S are all reverse blocking ability

RU RV RW SU SV SW TU TV TW

Have power. And the bidirectional switches s, s, s, s SU, s SV, s SW, s TU, s TV, s are

RU RV RW TW

The three-phase AC voltages v, V and V input to the input terminals 111 to 113 are changed to the desired three-phase AC voltage V.

R S T U

, V, V to convert.

V W

Both FIG. 2 and FIG. 3 are bidirectional switches S 1, S 2, S 3, S 3, S 3, S 3, S 3,

RU RV RW SU SV SW TU TV

The specific circuit employ | adopted as each of S is illustrated. The circuit shown in Figure 2 is IGBT (ln

TW

sulated Gate Bipolar Transistor) 61 and 62, diodes Dl and D2, and terminals a and b. In the IGBT 61, the emitter E is connected to the terminal a, and the collector C is connected to the terminal b via the diode D1. At this time, the power sword of the diode D1 is connected to the collector C. In IBGT62, emitter E is connected to terminal b, and collector C is connected to terminal a via diode D2. At this time, the power sword of the diode D2 is connected to the collector C. One of the terminals a and b is connected to any one of the input terminals 111 to 113, and the other is connected to any force of the output terminals 114 to 116, respectively.

[0027] According to the power circuit, by controlling IGBT 61 on and IGBT 62 off (control A1), current flows from terminal b to terminal a through diode D1 and IGBT 61 in this order. Can do. At this time, the current flow (reverse flow) from the terminal a to the terminal b is blocked by the diode D1. On the other hand, by controlling the IGBT 61 to be turned off and the IGBT 62 to be turned on (control B1), a current can flow from the terminal a to the terminal b through the diode D2 and the IGBT 62 in this order. At this time, the current flow (reverse flow) from the terminal b to the terminal a is blocked by the diode D2. Regardless of the control Al or B1, the circuit can prevent backflow. The power of the circuit is called reverse blocking capability.

[0028] The circuit shown in FIG. 3 includes IGBTs 63 and 64, diodes D3 and D4, and terminals a and b. The collector C of the IGBT 63 is connected to the terminal a. The anode and the power sword of the diode D3 are connected to the emitter E and the collector C of the IGBT 63, respectively. In IGBT64, collector C is connected to terminal b and emitter E is connected to emitter E of IGBT63. The anode and the power sword of the diode 4 are connected to the emitter E and the collect C of the IGBT 64, respectively.

[0029] According to the power circuit, the IGBT 63 is controlled to be on and the IGBT 64 is controlled to be off. (Control A2), current can flow from terminal a to terminal b through IGBT 63 and diode D4 in this order. At this time, the current flow (reverse flow) from the terminal b to the terminal a is blocked by the diode D4. On the other hand, by controlling IGBT 63 off and IGBT 64 on (control B2), current can flow from terminal b to terminal a through IGBT 64 and diode D3 in this order. At this time, the current flow (reverse flow) from the terminal a to the terminal b is blocked by the diode D3. In both control A2 and B2, the circuit can prevent backflow.

[0030] Bidirectional switches S, S, S, S, S, S having the circuit shown in FIG. 2 and FIG.

RU RV RW SU SV SW

, S 1, S 2, S prevents reverse current flow, so the R-phase bidirectional switch S 1,

TU TV TW RU

Bidirectional switch S, S, S, S, S, S

RV RW SU SV SW TU TV TW

Can be prevented from flowing into The same applies to the other phases. Therefore, for example, an element such as an interphase reactor is not required, and the number of elements can be reduced. However, by reducing the number of elements, it is possible to reduce the loss caused by the elements.

[0031] A capacitor may be connected between each of the emitters E and the collectors C of the IGBTs 61 to 64. In this case, the bidirectional switches S, S, S, S, S, S, S, S, S,

RU RV RW SU SV SW TU TV

The surge voltage generated by the switching of S can be absorbed by the capacitor.

TW

[0032] Bidirectional switch S

RU, S

RV, S

RW, S

SU, S

SV, S

SW, S

TU, S

TW obtained by conversion with TV and S TW

The desired three-phase AC voltages v, V, and V

Supplied to motor 4 via U V W ~ 116.

[0033] Rear tuttles L1 to L3 are connected to input terminals 111 to 113, respectively.

[0034] Capacitors C1 to C3 have one ends connected to each other and the other ends connected to output terminals 114 to 116, respectively.

[0035] According to the power converter la described above, the energy supplied from the three-phase AC power source V can be stored in the rear tuttles L1 to L3 by short-circuiting the rear tuttles L1 to L3 via the matrix converter 11. Therefore, the voltage across the capacitors C1 to C3 can be boosted. Therefore, the voltage utilization factor can be 1 or more. At this time, voltage-type three-phase AC voltages V, V, V are input to the input terminals 111 to 113, and power is output from the output terminals 114 to 116.

R S T

Current-type three-phase AC voltages V, V, and V are output.

UVW [0036] In addition, since each of the capacitors C1 to C3 constitutes an LC filter with the rear tuttles L1 to L3, it is possible to reduce high-frequency components included in the voltages output to the output terminals 114 to 116, and thus the motor 4 The pulsation component of the torque generated in the noise and the noise can be reduced. For example, if the torque pulsation reduction method introduced in Non-Patent Document 1 is applied, the harmonic component can be reduced more effectively.

[0037] As compared with an AC-AC conversion circuit using a rectifier circuit and an inverter, the number of switching elements is smaller and the loss generated in the power conversion device la can be reduced.

[0038] The clamp circuit 2 can be connected to the power converter la. In FIG. 1, the clamp circuit 2 is connected between the input terminals 111 to 113 and the output terminals 114 to 116.

FIG. 4 illustrates a specific configuration of the clamp circuit 2. The clamp circuit 2 includes diodes 21 to D32, a capacitor C21, and terminals 21 to 26. The terminal 21 is connected to the anode of the diode D21 and the force sword of the diode D22. The terminal 22 is connected to the anode of the diode D23 and the force sword of the diode D24. Terminal 23 is connected to the anode of diode D25 and the force sword of diode D26. The force swords of the diodes D21, D23, and D25 are connected to one end 211 of the capacitor 21, respectively. The anodes of the diodes D22, D24, and D26 are connected to the other end 212 of the capacitor 21.

[0040] The terminal 24 is connected to the anode of the diode D27 and the force sword of the diode D28. Terminal 25 is connected to the anode of diode D29 and the force sword of diode D30. Terminal 26 is connected to the anode of diode D31 and the force sword of diode D32. Each force sword of the diodes D27, D29, and D31 is connected to one end 211. The anodes of the diodes D28, D30, D32 are connected to the other end 212.

[0041] Terminals 21 to 23 are connected to input terminals 111 to 113, respectively, and terminals 24 to 26 are connected to output terminals 114 to 116, respectively.

[0042] According to the clamp circuit 2, the bidirectional switches S 1, S 2, S 3, S 3, S 3, S 5, S 5, 6

RU RV RW SU SV SW TU

Switching between S and S between input terminals 111 to 113 and output terminals 114 to 116

TV TW

The generated surge voltage can be absorbed by capacitor C21. [0043] The power conversion device la according to the present embodiment can be mounted on, for example, a compressor having a motor. A powerful compressor can increase efficiency. This is because the power conversion device la can supply a voltage larger than the power supply voltage to the motor, so that a predetermined motor output can be obtained even if the current flowing through the power conversion device la and the motor is small. . In other words, since the current may be small, it is a force that can reduce the loss generated in the power converter la and the motor.

[0044] <Switching pattern generation>

Controls switching of bidirectional switches S, S, S, S, S, S, S, S, S, S

RU RV RW SU SV SW TU TV TW

The signal (switching pattern) to be given to each gate G for this purpose is determined based on, for example, a circuit equivalent to the power conversion device la (hereinafter referred to as “equivalent circuit”).

[0045] FIG. 5 shows an equivalent circuit. The equivalent circuit is obtained by replacing the matrix converter 11 with a circuit composed of the rectifier circuit 12 and the inverter 13 in the power conversion device 1a shown in FIG. Specifically, since the rectifier circuit 12 and the inverter 13 are configured as follows, the rectifier circuit 12 and the inverter 13 together form a circuit equivalent to the power conversion device la.

The rectifier circuit 12 has switches S 1, S 2, S 3, S *, S *, and S *. Switch S, S, S, S

R S T R S T R S T R

*, S *, S * are both composed of IGBT and diode. Anode of the diode

S T

And the power sword are connected to the emitter E and collector C of the IGBT, respectively. For switches S, S, S, each IGBT emitter E is connected to input terminals 111-113.

R S T

Continued. For switches S *, S *, S *, the collector C of each IGBT is connected to the input terminal.

R S T

Connected to children 111-113. Switch S and switch S * are complementary to each other.

R R

Is called. That is, when switch S is on (off), switch S * is controlled off (on).

R R

It is controlled. The same applies to switch S and switch S *, and switch S and switch S *.

S S T T

The Therefore, the rectifier circuit 12 functions as a voltage type rectifier circuit.

The inverter 13 has switches S 1, S 2, S 3, S *, S *, and S *. Switch S, S, S

U V W U V W U V W

, S *, S *, and S * are each composed of an IGBT and a diode. The diode cathode

U V W

The node is connected to the collector C of the IGBT. For switches S, S, S

U V W

Each IGBT emitter is connected to output terminals 114-116, and each diode The anode is connected to the collector C of each IGBT of the switches S 1, S 2 and S. Suites

R S T

H For S *, S *, S *, the anode of each diode is the output terminal 114 ~ 11

U V W

Each IGBT emitter E force switch S *, S *, S *

R S T

Connected to GBT emitter E. Switch S and Switch S * have complementary switching

U U

Done. The same applies to switch S and switch S *, and switch S and switch S *.

V V W W

is there. Therefore, the inverter 13 functions as a current type inverter.

Based on the switching pattern of the rectifier circuit 12 of the equivalent circuit and the switching pattern of the inverter 13, the switching pattern of the matrix converter 11 can be obtained by Expression (1). Where M (S) (S = S, S, S, S, S, S, S

RU RV RW SU SV SW

, S, S) are those of the bidirectional switches S, S, S, S, S, S, S, S, S

TU TV TW RU RV RW SU SV SW TU TV TW

Represents the signal given to each gate G. The code M (S) (S = S, S, S, S *, S *, S *) is

R S T R S T

Rectifier circuit 12 switch S

R, S

S, S

T, S *

R, S *

S, S *

T

Signal. The code M (S) (S = S, S, S, S *, S *, S *)

U V W U V W

Indicates the signal given to the gate G of each IGBT of switches S, S, S, S *, S *, S *

U V W U V W

. M (S) is a switch s (s = s RU, s RV, s RW, s SU, s SV, s SW, s TU, s TV, s;

TW s

= S, S, S, S *, S *, S *; S = S, S, S, S *, S *, S *) is 1

U V W U V W R S T R S T

Shows 0 when off.

[0049] [Equation 1]

f (() i () l (ls_! s2AAΛ1

[0050] According to the generation of a powerful switching pattern, the generation of the switching pattern of the matrix converter 11 becomes relatively easy.

[0051] Second embodiment.

FIG. 6 conceptually shows the power converter lb according to the embodiment of the present invention. The power conversion device 1 b includes a matrix converter 11, rear tuttles L1 to L3, and capacitors C1 to C3. . Since the configuration of the matrix converter 11 and the connection relationship between the rear tuttles L1 to L3 and the matrix converter 11 are the same as those in the first embodiment, the description thereof is omitted. Further, FIG. 3 further shows the three-phase AC power source V, the motor 4 and the clamp circuit 2 which are the same as those in the first embodiment.

Capacitors C1 to C3 have one ends connected to each other and the other ends connected selectively to one of input terminals 111 to 113 and output terminals 114 to 116.

Specifically, the switch S is connected between the other ends of the capacitors C1 to C3 and the input terminals 111 to 113 and the output terminals 114 to 116. The switch S includes a set of terminals A connected to the input terminals 111 to 113, a set of terminals B connected to the output terminals 114 to 116, and a set of terminals P connected to the capacitors C1 to C3. Have The switch S can switch the connection between the terminal P and the terminal A (connection P—A) and the connection between the terminal P and the terminal B (connection P—B).

[0054] The switch S is switched, for example, by bidirectional switches S, S, S, S, S, S, S, S, S

RU RV RW SU SV SW TU

, S duty ratio, three-phase AC voltage output from output terminals 114 to 116 V, V, V

TV TW U V W

, And at least one of the rotational speeds ω of the motor 4 can be executed. For example, three-phase AC voltages V, V, V and currents i, i, i flowing through the input terminals 111 to 113

R S T R S T

The switch S is switched based on the currents i, i, i, etc. flowing through the output terminals 114 to 116.

U V W

You may do it.

[0055] FIG. 7 shows switching of the switch S based on one of the three-phase AC voltages V 1, V 2, and V.

U S T U

8 shows a control circuit 8 for executing the control. The control circuit 8 has a comparator 81. A predetermined value νθ of the voltage is given to one input terminal of the comparator 81, and the actually measured voltage V is given to the other input terminal. The comparator 81 compares the voltage V with a predetermined value νθ and switches the switch S.

U U

A signal Sig is output to give to the switch S.

[0056] Specifically, when the voltage V is greater than or equal to a predetermined value νθ, the signal Sig indicating the connection PA

U

Output (PA). On the other hand, if the voltage V is less than the predetermined value νθ, indicate connection P-B.

U

Output signal Sig (PB). Switch S performs switching based on the applied signal Sig. [0057] Similarly, even if switch S is switched using other voltages v and V of the three-phase AC voltage,

S T

good.

[0058] For example, the switch S may be switched based on the rotational speed ω! More specifically, the actually measured rotational speed ω is compared with a predetermined rotational speed value ωθ using, for example, a comparator. When the rotational speed ω is equal to or higher than the predetermined value ωθ, the signal Sig (PB) is output. When the rotational speed ω is smaller than the predetermined value ω0, the signal Sig (PA) is output.

[0059] According to the power converter lb, the power converter lb is stepped down by connecting the terminal P to the terminal A, that is, by connecting the other ends of the capacitors C1 to C3 to the input terminals 111 to 113, respectively. It can function as a converter. At this time, current-type three-phase AC voltages V, V, V are input to the input terminals 111 to 113, and voltage-type 3 is output from the output terminals 114 to 116.

R S T

Phase AC voltages V, V, V are output. In addition, each of capacitors C1 to C3

U V W

Since the tolls L1 to L3 and the LC filter are configured, the high frequency components contained in the voltage output to the output terminals 114 to 116 can be reduced.

[0060] On the other hand, by connecting the terminal P to the terminal B, that is, by connecting each of the other ends of the capacitors C1 to C3 to the output terminals 114 to 116, the power converter lb is connected to the first implementation. It is possible to function as the power conversion device la described in the embodiment. Therefore, output terminal 114 ~

The variable region of the voltage output to 116 can be expanded.

[0061] The power converter lb can be mounted on a compressor. Such a compressor can be operated variably from low speed to high speed. Moreover, in the high speed range, the power conversion device lb functions as the power conversion device la described in the first embodiment, so the efficiency of the compressor is high.

[0062] For example, after switch S is switched, it may be determined whether or not switch S needs to be switched after a predetermined time has elapsed, and the next switch may be executed.

[0063] <Generation of switching pattern>

When the connection P-B is executed by the switch S, the power conversion device lb functions as the power conversion device la. Therefore, the power conversion device lb is the same as that described in the first embodiment. The switching pattern of the matrix converter 11 can be generated by this method. [0064] On the other hand, when the connection P-A is executed by the switch S, the power converter lb functions as a step-down converter. Therefore, the switching pattern can be determined based on a circuit equivalent to the step-down converter. it can.

FIG. 8 shows a working equivalent circuit. The equivalent circuit is obtained by replacing the matrix converter 11 with a circuit composed of a rectifier circuit 121 and an inverter 131 for the step-down converter. Specifically, since the rectifier circuit 121 and the inverter 131 are configured as follows, the rectifier circuit 121 and the inverter 131 combine with each other and are equivalent to the power converter lb when functioning as a step-down converter. Configure the circuit.

The rectifier circuit 121 includes switches S 1, S 2, S 3, S *, S *, and S *. Switches S, S, S,

R S T R S T R S T

Each of S *, S *, and S * is composed of an IGBT and a diode. The diode ano

R S T

Is connected to the emitter E of the IGBT. For switches S, S and S, respectively

R S T

IGBT collector C is connected to input terminals 111-113. Switch S *, S *, S *

R S T

In this case, the force sword of each diode is connected to the input terminals 111 to 113. Switch S and switch S * are complementarily switched. Switch S and Switch S *

The same applies to R R S S, and switch S and switch S *. Therefore, the rectifier circuit 121 is a current type

T T

Functions as a rectifier circuit.

Inverter 131 has switches S 1, S 2, S 3, S *, S *, and S *. Switch S, S, S

U V W U V W U V

, S *, S *, and S * are each composed of an IGBT and a diode. The diode is

W U V W

The anode is connected to the emitter E of the IGBT and the force sword is connected to the collector C of the IGBT. For switches S 1, S 2, S, each IGBT emitter E is the output terminal

U V W

114-116 connected to each IGBT collector C force switch S, S, S of that

R S T

Connected to the power sword of each diode. For switches S *, S *, S *

U V W

The collector C of each IGBT is connected to the output terminals 114 to 116, and the emitter E of each IGBT is connected to the emitter C of each of the switches S *, S *, and S *. Suites

R S T

The switch S * and the switch S * are complementarily switched. Switch S and Switch S *, and

U U V V

The same applies to switch S and switch S *. Therefore, the inverter 131 is a voltage type

W W

Functions as an inverter.

[0068] The switching pattern of the rectifier circuit 12 of the equivalent circuit and the switch of the inverter 13 Based on the switching pattern, the switching pattern of the matrix converter 11 can be obtained using the equation (1) described in the first embodiment.

FIG. 9 conceptually shows a control unit that acquires the switching pattern of the matrix converter 11. The control unit includes a switching determination unit 31, an equivalent circuit acquisition unit 32, and a generation unit 33.

[0070] The switching determination unit 31 determines whether the switch S is executing the connection P-A or the connection P-B. This is given to the equivalent circuit selector 32.

The equivalent circuit selection unit 32 includes a rectifier circuit selection unit 321 and an inverter selection unit 322.

The rectifier circuit selection unit 321 selects one of the rectifier circuit 12 (FIG. 5) and the rectifier circuit 121 (FIG. 8) based on the signals Rl and R2. FIG. 9 shows a case where either the rectifier circuit 12 or the rectifier circuit 121 is selected by the switch 323.

[0072] Inverter selection section 322 selects one of inverter 13 (Fig. 5) and inverter 131 (Fig. 8) based on signals Rl and R2. FIG. 9 shows the case where one of the inverter 13 and the inverter 131 is selected by the switch 324!

Specifically, when the signal R1 is input to the equivalent circuit selection unit 32, the rectification circuit selection unit 321 selects the rectification circuit 121, and the inverter selection unit 322 selects the inverter 131. On the other hand, when the signal R2 is input to the equivalent circuit selection unit 32, the rectification circuit selection unit 321 selects the rectification circuit 12, and the inverter selection unit 322 selects the inverter 13. The selected rectifier circuits 12, 121 and inverters 13, 131 are connected to the generation unit 33.

The generation unit 33 switches the matrix converter 11 based on the equivalent circuit (FIGS. 5 and 8) configured by the rectifier circuits 12 and 121 and the inverters 13 and 131 selected by the equivalent circuit selection unit 32. Form a pattern. Specifically, the switching pattern is calculated using the above-described equation (1). Therefore, as in the first embodiment, the generation of the switching pattern of the matrix converter 11 is relatively easy.

[0075] Although the present invention has been described in detail, the above description is illustrative in all aspects, and the present invention is not limited thereto. Innumerable variations not illustrated The power of the scope of the present invention It is understood that the power can be assumed without departing.

Claims

The scope of the claims

[1] First to third input terminals (111 to 113), first to third output terminals (114 to 116), and bidirectional switches (S 1, S 2, S 3, S 5, S, S, S, S, S

RU RV RW SU SV SW TU TV TW

), And the AC voltage (V, v. V) input to the first to third input terminals is

R S T

Matrix comparator that converts to the desired AC voltage (V, V, V) using a bidirectional switch

U V W

(11),

First to third rear turtles (L1 to L3) connected to the first to third input terminals,

First to third capacitors (C1 to C3) each having one end connected to each other and each other connected to the first to third output terminals

A power conversion device comprising:

[2] A power conversion device (la) according to claim 1,

The switching operation of the matrix converter (11) is determined based on the respective switching operations of the rectifier circuit (12) and the inverter (13) that together form a circuit equivalent to the power converter. apparatus.

[3] The power converter according to claim 2, wherein the rectifier circuit (12) and the inverter (13) are a voltage type and a current type, respectively.

[4] First to third input terminals (111 to 113), first to third output terminals (114 to 116),

, Bidirectional switch with reverse blocking capability (S, S, S, S, S, S, S, S, S, S

RU RV RW SU SV SW TU TV TW

), And the AC voltage (V, v. V) input to the first to third input terminals is

R S T

U V W

(11),

First to third capacitors (C1 to C3) each having one end connected to each other,

The other end of each of the first to third capacitors is selectively connected to any one of the first to third input terminals and the first to third output terminals. Conversion device.

[5] The power converter (lb) according to claim 4,

The switching operation of the matrix converter (11) is based on the switching operation of the rectifier circuit (12; 121) and the inverter (13; 131), which together constitute a circuit equivalent to the power converter. The power conversion device to be determined.

[6] When each of the first to third capacitors (C1 to C3) is connected to the first to third output terminals (114 to 116), the rectifier circuit (12) and the The inverter (13) is voltage type and current type respectively.

Each of the first to third capacitors is connected to the first to third input terminals (111 to

113. The power conversion device according to claim 5, wherein the rectifier circuit and the inverter are each of a current type and a voltage type when connected to 113).

[7] The first to third input terminals (111 to 113) and the first to third output terminals (114

~ 116) between the clamp circuit (2)

The power conversion device according to claim 1, further comprising:

[8] The first to third input terminals (111 to 113) and the first to third output terminals (114

~ 116) between the clamp circuit (2)

The power conversion device according to claim 4, further comprising:

[9] A compressor equipped with the power conversion device (la; lb) according to any one of claims 1 to 8.