WO2006087808A1 - 干渉低減受信装置 - Google Patents
干渉低減受信装置 Download PDFInfo
- Publication number
- WO2006087808A1 WO2006087808A1 PCT/JP2005/002621 JP2005002621W WO2006087808A1 WO 2006087808 A1 WO2006087808 A1 WO 2006087808A1 JP 2005002621 W JP2005002621 W JP 2005002621W WO 2006087808 A1 WO2006087808 A1 WO 2006087808A1
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- WO
- WIPO (PCT)
- Prior art keywords
- timing
- weight
- signal
- received signal
- interference
- Prior art date
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Classifications
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
- H04B1/69—Spread spectrum techniques
- H04B1/707—Spread spectrum techniques using direct sequence modulation
- H04B1/7097—Interference-related aspects
- H04B1/711—Interference-related aspects the interference being multi-path interference
- H04B1/7115—Constructive combining of multi-path signals, i.e. RAKE receivers
- H04B1/712—Weighting of fingers for combining, e.g. amplitude control or phase rotation using an inner loop
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B2201/00—Indexing scheme relating to details of transmission systems not covered by a single group of H04B3/00 - H04B13/00
- H04B2201/69—Orthogonal indexing scheme relating to spread spectrum techniques in general
- H04B2201/707—Orthogonal indexing scheme relating to spread spectrum techniques in general relating to direct sequence modulation
- H04B2201/7097—Direct sequence modulation interference
- H04B2201/709727—GRAKE type RAKE receivers
Definitions
- the present invention relates to an interference reduction receiving apparatus used in a communication system using a CDMA (Code Division Multiple Access) system.
- CDMA Code Division Multiple Access
- FIG. 1 is a diagram showing an overview of a conventional equalizer.
- each digit of the shift register 11 corresponds to the time axis of the delay profile 15 (impulse response) of the multipath signal
- the appropriate weight w—w for which the channel estimation power of the pilot signal was determined is selected. By doing so, it is possible to reduce interference due to multipath signals.
- Such an equalizer has the best characteristics, but has the disadvantage of increasing the amount of calculation because it is necessary to multiply weights in units of sample data.
- FIG. 2 is a diagram showing an outline of a conventional RAKE receiver.
- Sample data obtained by AZD conversion of a CDMA received signal is input to a shift register 11, and a delay profile of each digit of the shift register 11 is input.
- the value of the digit corresponding to the time (timing) at which the peak was detected in 15 is also despread with a predetermined spreading code in the correlator 14 and multiplied by an appropriate weight w, w. These are added by adder 13 to obtain the output. is there.
- Such a RAKE receiver has the advantage of reducing the amount of calculation of weight multiplication compared to the equalizer described above, but has the disadvantage that the characteristics are slightly reduced.
- FIG. 3 is a diagram showing an overview of a conventional G-RAKE (Generalized RAKE) receiver.
- G-RAKE Generalized RAKE
- the weight is higher than that of the equalizer described above. While maintaining the advantage of reducing the amount of calculation of multiplication, it has the advantage that the characteristics are close to the best, and is regarded as a promising technique for reducing interference.
- the weight w in the G-RAKE receiver is derived as follows. That is, let y be an outer element having the output signals (complex signals) of multiple correlators 14 as elements, z be the output signal of the adder 13 (complex signals), and w be a weight vector.
- H Hermitian transpose
- h is a vector of channel estimation values
- n is a noise vector including thermal noise and multipath interference
- FIG. 4 is a diagram showing an example of a circuit configuration for obtaining the element R of the covariance matrix in the conventional G—RAKE receiver.
- the received data (chip data) force is also supplied to the correlator 21 by the pilot signal (CPICH (Common Pilot CHannel) is despread at timing t, and the same signal is averaged by the averaging unit 22 from the despread signal and subtracted by the adder 23.
- the received data power is also de-spread at the timing tj in the correlator 24, and the adder 26 subtracts the de-spread signal averaged by the averaging unit 25 from the de-spread signal.
- the output signal of the adder 26 are multiplied by the multiplier 27 and averaged by the averaging unit 28 to obtain the element R of the covariance matrix.
- the RAKE receiver despreads the timing (MICT: Multipath Interference Correlative Timing) that is symmetrical to the other path timing centered on the path timing of one path by the delay time between any two paths.
- MICT Multipath Interference Correlative Timing
- Patent Document 1 Japanese Translation of Special Publication 2002-527927
- Patent Document 2 Special Table 2003-503879
- Patent Document 3 Japanese Patent Laid-Open No. 2003-133999
- Patent Document 4 Japanese Patent Application No. 2004—173793
- the G-RAKE receiver described above has a smaller amount of calculation than an equalizer, and is close to the best characteristics, and is therefore promising as a technology for reducing interference 1S
- HSDPA High Speed Downlink Packet Access
- the pilot signal has a spreading factor of 256, for example, it is not possible to obtain one data power per 256 chips. Therefore, a sufficiently accurate covariance matrix or a way can be obtained in a short time. It is something that cannot be obtained.
- Non-Patent Document 1 has no specific suggestion about the timing effective for interference cancellation, and whether to determine the timing effective for interference cancellation is also a problem. And
- the present invention has been proposed in view of the above-described conventional problems, and an object of the present invention is to obtain a sufficiently accurate weight in a short time, and to achieve a further high-speed and large-capacity wireless method.
- An object of the present invention is to provide an interference reduction receiver that can contribute to the realization of the equation. It also aims to provide a method for determining effective timing for interference removal.
- the received signal power is despread at a plurality of predetermined timings, and the despread signal is multiplied by a predetermined weight and summed.
- the gist of the present invention is a receiving apparatus that demodulates a signal by using an interference reduction receiving apparatus that includes weight generation means for obtaining the weight based on a product of a signal correlation matrix of the received signal and a channel response vector.
- the signal correlation matrix and thus the weight can be obtained without using a known pilot signal.
- An accuracy value can be obtained. That is, in the case of a conventional G-RAKE receiver using a known pilot signal, for example, when the spreading factor is 256, the powerful power that cannot obtain one data power in 256 chips
- the signal correlation matrix of the present invention In the method using, 256 data can be used per 256 chips, and a sufficiently accurate value can be obtained in a short time. Also, in the case of downlink CDMA signals, all channels have the same signal correlation, so all channel signals can be used, and the accuracy of the signal correlation matrix can be improved.
- FIG. 1 is a diagram showing an outline of a conventional equalizer.
- FIG. 2 is a diagram showing an outline of a conventional RAKE receiver.
- FIG. 3 is a diagram showing an outline of a conventional G-RAKE receiver.
- FIG. 5 is a diagram illustrating a circuit configuration example of a CDMA transceiver device according to an embodiment of the present invention.
- FIG. 6 is a diagram illustrating a more detailed circuit configuration example of the timing generation unit, the despreading unit, and the signal synthesis unit.
- FIG. 7 is a diagram illustrating a more detailed circuit configuration example of the weight generation unit.
- FIG. 8 is a diagram showing a more detailed circuit configuration example of a signal correlation matrix generation unit.
- FIG. 9 is a diagram showing an example of the relationship between the averaging time of chips and the reliability of matrix calculation values.
- FIG. 10 is a conceptual diagram of multipath between a base station and a mobile terminal.
- FIG. 11 is a diagram showing an example of the relationship between the impulse response of a path and the despread timing.
- FIG. 12 is a diagram showing an example of timing.
- FIG. 13 is a diagram showing an example of a table for defining timing.
- FIG. 14 is a diagram illustrating another configuration example of the weight generation unit.
- FIG. 5 is a diagram showing a circuit configuration example of a CDMA transceiver device according to an embodiment of the present invention.
- a radio signal received by an antenna 101 is demodulated by a radio reception unit 103 via a duplexer 102 and converted into a digital signal (sample data) by an AZD conversion unit 104.
- This sample data is given to the timing generation unit 105 and the despreading unit 106, and is despread by a plurality of fingers in the despreading unit 106 in accordance with a predetermined despreading timing generated by the timing generation unit 105.
- the sample data of the AZD conversion unit 104 and the timing of the timing generation unit 105 are also supplied to the weight generation unit 107, and weights corresponding to the plurality of fingers of the despreading unit 106 are generated. Then, the despread output signals of the plurality of fingers of the despreading unit 106 are combined by the signal combining unit 108 according to the weight given from the weight generating unit 107, and the signal processing unit 109 performs channel decoding or the like to become received data. .
- the despread output signal of despreading section 106 is given to level measuring section 110, and feedback control is applied to signal combining section 108 according to the signal level, and duplexer 102 is modulated by modulating transmission data.
- the transmission power of the wireless transmission unit 111 transmitted via the antenna 101 is controlled.
- FIG. 6 is a diagram illustrating a more detailed circuit configuration example of the timing generation unit 105, the despreading unit 106, and the signal synthesis unit 108 in FIG.
- the timing generator 105 is a timing corresponding to the delay time of the impulse response generated by one or more paths from the sample data output from the AZ D converter 104 (because it is a timing in a normal RAKE receiver). , Hereinafter referred to as “RAKE timing”.)
- the timing (MICT) t Based on the AKE timing, the timing (MICT) t,,,,,,
- the 12 includes a MICT generation unit 122 that generates t 21, and a timing selection unit 123 that selects an appropriate timing from among the RAKE timing of the searcher 121 and the MICT of the MICT generation unit 122.
- despreading unit 106 includes despreading units 124-1, 124-2, “which constitute a plurality of fingers.
- the signal synthesis unit 108 multiplies the despread output of the despread units 124-1, 124-2,... Of the despread unit 106 and the weight given from the weight generation unit 107 for each finger.
- a calorie calculator 126 for adding the outputs of the multipliers 125-1, 125-2,.
- FIG. 7 is a diagram showing a more detailed circuit configuration example of the weight generation unit 107 in FIG.
- a weight generation unit 107 performs channel estimation based on the timing given from the timing generation unit 105 and the sample data given from the AZD conversion unit 104, and generates a channel response vector h.
- a signal correlation matrix generator 132 for obtaining the element R ′ of the signal correlation matrix,
- the channel response vector h generated by the channel estimation unit 131 and the signal correlation matrix R ′ force generated by the signal correlation matrix generation unit 132 are also generated by R′— 1 and multiplied to generate a weight w. I have.
- FIG. 8 is a diagram showing a more detailed circuit configuration example of the signal correlation matrix generation unit 132 in FIG.
- the signal correlation matrix generation unit 132 applies the difference between the first timing t and the second timing t based on the timing t provided from the timing generation unit 105 to the sample data provided from the AZD conversion unit 104.
- a delay unit 141 that gives a time delay
- a multiplier 142 that takes the product of the sample data given from the AZD conversion unit 104 and the output signal of the delay unit 141, and an average of the output signal of the multiplier 142
- an average unit 143 for obtaining an element R ′ of the correlation matrix.
- the signal correlation matrix generation unit 132 obtains samples at predetermined time intervals from all sample data, in addition to obtaining the signal correlation matrix element R for all sample data, and performs signal correlation based on the obtained samples. The amount of calculation can be reduced by obtaining the matrix element R ′. In other words, if the sample data number is p and the sample data signal is v (p), the element R 'of the signal correlation matrix is calculated for all sample data.
- V is expressed by the following equation (1).
- V is the sum of the impulse responses of each chip signal.
- ⁇ x> represents the average value of x, and the fact that a, a, n, and n are uncorrelated with each other
- the interference and noise component I are the ones excluding the V force a.
- I is i i 0 i in the following equation (4)
- the correlation of noise was obtained from the signal before despreading, but it can be obtained in the same way even after despreading, and as a whole, it is simply multiplied by the spreading factor (SF). There is no essential difference.
- both weights are multiplied by a scalar and are equivalent to each other. Therefore, the convergence speed with respect to the average number of matrix elements is of the same order, and the signal correlation matrix can be obtained at a higher speed in the order of the diffusion ratio than the covariance matrix.
- FIG. 9 is a diagram showing an example of the relationship between the averaging time of the chip and the reliability of the matrix calculation value, and the force of the present invention indicated by a solid line in an environment where three paths having the same intensity exist.
- the signal correlation matrix R ′ has a high accuracy even when it is averaged in a short time.
- timing selection in the timing generation unit 105 in FIGS. 5 and 6 will be described. Light up.
- FIG. 10 is a conceptual diagram of multipath between a base station and a mobile terminal, and shows a case where two paths 1 and 2 exist between the base station and the mobile terminal.
- Fig. 11 shows an example of the relationship between the impulse response of paths 1 and 2 and the despread timing in the environment of Fig. 10.
- the timing t, t can be detected as the RAKE timing, and the timing t, t can be detected as the MICT.
- the timing t is the timing of the delay time between the two paths 1 and 2.
- the timing is symmetrical with respect to the timing t around the timing t, and despreading at the timing t
- the interference component that despreads the chip Z force of nose 2 also includes the interference component, but by picking up the despreading finger at timing t, path 1
- the chip Z force of the back can also obtain the despread interference component, and the chip Z force of pass 2 has the same content as the despread interference component, it can be used to cancel it.
- the relationship between timing t and timing t is the same.
- FIG. 12 is a diagram showing an example of the timing when there are three paths 1, 2, and 3.
- the timing selection unit 123 (Fig. 6) of the timing generation unit 105 determines the above according to the number of available fingers.
- the optimal timing can be achieved by assigning them in the order of the timing force specified at the top of the table.
- FIG. 14 is a diagram showing another configuration example of the weight generation unit 107 in FIGS. 5 to 7.
- the weight generation unit 107 determines the timing t corresponding to fingers # 1 to # 4.
- a RAKE weight generation unit 152 for generating a weight.
- finger # 1 which is the RAKE timing out of fingers # 1 1 # 4 , Timing corresponding to # 3 t Wait by normal rake method
- the RAKE weight generation unit 153 to be generated, and the ratio of the absolute value between the weight obtained by the signal correlation matrix weight generation unit 151 and the weight obtained by the RAKE weight generation unit 153 based on the same timing are calculated, and the multiplier 155 —1— 155— 4 is provided with a level compensation unit 154 that performs level compensation.
- the calculation of the ratio in the level correction unit 154 is performed by the following equation.
- the denominator indicates the total power of the weight at the RAKE timing among the weights generated based on the signal correlation matrix
- the numerator is the weight generated by the normal rake method at the RAKE timing corresponding to the denominator.
- the total power is shown.
- b is an appropriate coefficient and is a constant such as “1Z2” or “2”.
- the level correction is generated based on a highly accurate signal correlation matrix rather than completely equalizing the level of the weight generated based on the signal correlation matrix and the weight generated by the normal rake method. It is preferable to make the weights a little larger.
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- Computer Networks & Wireless Communication (AREA)
- Signal Processing (AREA)
- Noise Elimination (AREA)
- Mobile Radio Communication Systems (AREA)
Abstract
Description
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Priority Applications (4)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
PCT/JP2005/002621 WO2006087808A1 (ja) | 2005-02-18 | 2005-02-18 | 干渉低減受信装置 |
JP2007503546A JP4364274B2 (ja) | 2005-02-18 | 2005-02-18 | 干渉低減受信装置 |
EP20050719291 EP1850494B1 (en) | 2005-02-18 | 2005-02-18 | Interference-reduced receiver apparatus |
US11/889,654 US7953141B2 (en) | 2005-02-18 | 2007-08-15 | Interference reduction receiver |
Applications Claiming Priority (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
PCT/JP2005/002621 WO2006087808A1 (ja) | 2005-02-18 | 2005-02-18 | 干渉低減受信装置 |
Related Child Applications (1)
Application Number | Title | Priority Date | Filing Date |
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US11/889,654 Continuation US7953141B2 (en) | 2005-02-18 | 2007-08-15 | Interference reduction receiver |
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WO2006087808A1 true WO2006087808A1 (ja) | 2006-08-24 |
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PCT/JP2005/002621 WO2006087808A1 (ja) | 2005-02-18 | 2005-02-18 | 干渉低減受信装置 |
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US (1) | US7953141B2 (ja) |
EP (1) | EP1850494B1 (ja) |
JP (1) | JP4364274B2 (ja) |
WO (1) | WO2006087808A1 (ja) |
Cited By (1)
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WO2008136079A1 (ja) * | 2007-04-20 | 2008-11-13 | Fujitsu Limited | イコライザの制御装置及び制御方法並びに前記制御装置をそなえた無線端末 |
Families Citing this family (4)
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TWI404380B (zh) * | 2010-04-30 | 2013-08-01 | Mstar Semiconductor Inc | 訊號選擇裝置及其方法 |
JP5599677B2 (ja) * | 2010-08-18 | 2014-10-01 | ラピスセミコンダクタ株式会社 | ダイバシティ受信装置及びダイバシティ受信方法 |
JP5505242B2 (ja) * | 2010-10-07 | 2014-05-28 | 富士通株式会社 | 通信装置および制御方法 |
US9595988B2 (en) * | 2014-12-10 | 2017-03-14 | Intel Corporation | Communication device and method for receiving a signal |
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2005
- 2005-02-18 EP EP20050719291 patent/EP1850494B1/en not_active Expired - Fee Related
- 2005-02-18 JP JP2007503546A patent/JP4364274B2/ja not_active Expired - Fee Related
- 2005-02-18 WO PCT/JP2005/002621 patent/WO2006087808A1/ja active Application Filing
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2007
- 2007-08-15 US US11/889,654 patent/US7953141B2/en not_active Expired - Fee Related
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Cited By (4)
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WO2008136079A1 (ja) * | 2007-04-20 | 2008-11-13 | Fujitsu Limited | イコライザの制御装置及び制御方法並びに前記制御装置をそなえた無線端末 |
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Also Published As
Publication number | Publication date |
---|---|
JPWO2006087808A1 (ja) | 2008-07-03 |
JP4364274B2 (ja) | 2009-11-11 |
EP1850494A1 (en) | 2007-10-31 |
EP1850494B1 (en) | 2013-06-19 |
US20070291827A1 (en) | 2007-12-20 |
US7953141B2 (en) | 2011-05-31 |
EP1850494A4 (en) | 2012-01-11 |
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