WO2004064240A1 - Procede pour reduire les courants parasites en mode commun dans un systeme d'entrainement electrique, et systeme d'entrainement electrique correspondant - Google Patents

Procede pour reduire les courants parasites en mode commun dans un systeme d'entrainement electrique, et systeme d'entrainement electrique correspondant Download PDF

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Publication number
WO2004064240A1
WO2004064240A1 PCT/EP2004/000166 EP2004000166W WO2004064240A1 WO 2004064240 A1 WO2004064240 A1 WO 2004064240A1 EP 2004000166 W EP2004000166 W EP 2004000166W WO 2004064240 A1 WO2004064240 A1 WO 2004064240A1
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WO
WIPO (PCT)
Prior art keywords
pulse
winding
drive system
electrical
common
Prior art date
Application number
PCT/EP2004/000166
Other languages
German (de)
English (en)
Other versions
WO2004064240A9 (fr
Inventor
Hans-Jürgen TÖLLE
Reinhard Vogel
Peter Wengler
Original Assignee
Siemens Aktiengesellschaft
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Siemens Aktiengesellschaft filed Critical Siemens Aktiengesellschaft
Priority to BR0406791-6A priority Critical patent/BRPI0406791A/pt
Priority to EP04701595.3A priority patent/EP1584134B1/fr
Priority to KR1020057013181A priority patent/KR101144364B1/ko
Priority to ES04701595.3T priority patent/ES2629016T3/es
Publication of WO2004064240A1 publication Critical patent/WO2004064240A1/fr
Publication of WO2004064240A9 publication Critical patent/WO2004064240A9/fr

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Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P6/00—Arrangements for controlling synchronous motors or other dynamo-electric motors using electronic commutation dependent on the rotor position; Electronic commutators therefor
    • H02P6/08—Arrangements for controlling the speed or torque of a single motor
    • H02P6/085—Arrangements for controlling the speed or torque of a single motor in a bridge configuration
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
    • H02P27/04—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage
    • H02P27/06—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters
    • H02P27/08—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters with pulse width modulation

Definitions

  • the common-mode interference currents generated by the two pulse inverters are directed opposite one another via the parasitic capacitances of the windings against ground potential and thus largely oppose one another, in particular in the DC voltage supply device cancel.
  • the output voltages of the pulse inverters which are decisive for the drive function of the induction machine, ie the differential voltages between the output terminals in each inverter, remain unchanged.
  • the common mode interference currents are reduced solely by correspondingly controlling the pulse converter. Special components, such as additional inductors, are not required. This saves costs and expenses for space, weight, assembly and wiring compared to using additional inductors.
  • control or modulation of the pulse converters is advantageous both with online-working modulation methods (e.g. sine-triangle modulation, space vector modulation, etc.) and with offline working modulation method. e.g. pulse patterns calculated offline.
  • online-working modulation methods e.g. sine-triangle modulation, space vector modulation, etc.
  • offline working modulation method e.g. pulse patterns calculated offline.
  • a particularly simple, clear and advantageous embodiment of the solution according to the invention results from A modulation is reversed using a triangular auxiliary function in the sense of a sine-triangular modulation, the triangular auxiliary function of one of the two pulse inverters being inverted compared to the triangular auxiliary function of the other of the two pulse inverters.
  • the use of this modulation is particularly advantageous because it can be done in a particularly advantageous embodiment with the aid of a programmable hardware module, in particular LCA; or if this is not possible or is not desired, can advantageously also be implemented using conventional hardware in analog and / or digital technology.
  • a good synchronization of the control pulses of the two pulse converters " fed from a common DC voltage supply device " can be ensured by) providing a common control device for each two pulse converters.
  • the electric drive system according to the invention can be used in a particularly advantageous manner in an on-board electrical system, in particular an on-board electrical DC system on ships, in particular on submarines, since there are particularly high demands on common-mode interference currents in such on-board systems.
  • the electrical drive system according to the invention can be designed with one or more electrical induction machines which are designed as synchronous machines with electrical or permanent magnetic excitation or as asynchronous machines.
  • FIG. 1 time diagrams of the course of the pulse converter output voltages, with both converters being controlled in accordance with the solution according to the invention in such a way that the common-mode interference currents generated by both converters cancel each other out via the parasitic capacitances of the winding phases with respect to ground potential;
  • FIG 3 timing diagrams of the course of the pulse converter output voltages, wherein according to the solution according to the invention, both converters are controlled so that the common mode interference currents generated by both converters cancel each other out via the parasitic capacitances of the winding systems with respect to ground potential;
  • the single-phase pulse converter 1 in FIG. 5 has two half bridges Wla and Wlb, each with two switches Sla, Sla 'and Slb, Slb'.
  • the switches Sla, Sla 'and Slb, Slb' are controlled by means of a suitable control device 51 in such a way that a desired voltage U1 is set at the output terminals la and lb of the pulse converter 1 and thus at the winding phase 31 of the induction machine 3 connected there.
  • the pulse converter output voltage Ul arises as the differential voltage of the output potentials Ula and Ulb of the two half bridges Wla and Wlb.
  • the parasitic capacitance of the winding phase 31 with respect to earth potential is represented in a simplified manner by the capacitor Cp31.
  • the capacitor Cp4 represents in a simplified manner the parasitic capacitance of the DC voltage supply device 4 against ground potential.
  • the voltage Uc31 denotes the voltage drop across the parasitic capacitance Cp31 of the winding phase 31 with respect to earth
  • FIG. 6 shows the time profiles of the relevant pulse converter output voltages for the circuit shown in FIG. 5.
  • the switches Sla, Sla 'and Slb, Slb' are activated in an exemplary manner with the aid of a triangle auxiliary function U ⁇ l in the sense of the known sine-triangle modulation.
  • a triangular auxiliary function U ⁇ l in the control device 51 in a known manner with a control voltage Ustl and -Ustl determining the pulse converter control, in order to determine the switching times for the switches Sla, Sla 'and Slb, Slb'.
  • this voltage Uc31 changes periodically as a function of the output potentials Ula and Ulb.
  • the entire winding strand 31 at negative potential UDC- of the DC voltage supply device and in time segments tb at positive potential UDC + of the DC voltage supply device is associated with a periodic reloading of the earth capacitance Cp31, which is dependent on the time profile of the voltage Uc31, with corresponding charging or recharging currents Icml.
  • FIGS. 1 and 2 show a simplified representation of an electrical induction machine 3 with two winding phases 31, 32, each of which is fed by a common DC voltage supply device 4 via a single-phase pulse converter 1, 2.
  • Both pulse inverters 1, 2 are operated with the same modulation and generate at least approximately the same output voltages U1 and U2 at their output terminals la, lb or 2a, 2b.
  • the pulse converters 1 and 2 each have the same basic circuit, which corresponds to that of the pulse converter 1 from FIG 5.
  • Each of the pulse converters 1, 2 has 5, two half bridges Wla, Wlb and W2a, W2b each with two switches (Sla, Sla 'and Slb, Slb' or S2a, S2a 'and S2b, S2b').
  • the pulse inverters 1, 2 are clocked with essentially the same switching frequency, so that the switching processes in the pulse inverters 1, 2 almost simultaneously occur.
  • the reference numerals have been adapted to suit their function and meaning.
  • the pulse converter 1 generates a voltage drop Uc31 and thus a common-mode interference current Icml in the DC voltage supply device on the earth capacitance Cp31 of the winding strand 31 it feeds, on account of its switching actions and the associated changes in its output potentials Ula, Ulb 4.
  • the pulse converter 2 causes a voltage drop Uc32 and thus a common-mode interference current Icm2 in the DC voltage supply device 4
  • a total common-mode interference current Icmg thus results from the DC voltage supply device 4, which is obtained from the sum of the common-mode interference currents Icml and Icm2 of the two individual pulse inverters 1 and 2:
  • Icmg Icml + Icm2 ,
  • the parasitic winding capacitances Cp31, Cp32 of the winding phases 31, 32 are at least approximately the same size, so that the two common-mode interference currents Icm1 and Icm2 are also the same size when the voltages Uc31 and Uc32 are the same.
  • the two pulse inverters 1, 2 are controlled by control devices 51, 52 in such a way that in the case of both pulse inverters 1, 2 at their outputs la, lb and 2a , 2b the potentials Ula, Ulb or U2a, U2b, which are relevant for the creation of the common mode currents Icml, Icm2, are switched at least approximately simultaneously to the winding phases 31, 32 of the induction machine 3 such that the voltage potentials Uc31, Uc33 are parasitic Capacities Cp31, Cp32 of the winding strands 31, 32 are directed opposite to ground potential and thus the common mode interference currents Icml and Icm2 cancel each other out.
  • the two control devices 51, 52 are linked to one another in a suitable manner in terms of signal technology, in particular synchronized with one another.
  • a common control device 5 can be provided instead of the control devices 51, 52 synchronized with one another.
  • the voltage changes across the parasitic capacitances Cp31 and Cp32 thus also run in opposite directions to one another, as can be seen in FIG. 2 on the basis of the time profiles of the voltages Uc31 and Uc32 and is also evident from the sum of the two voltages Uc31 + Uc32, which are zero at all times is.
  • the control of the pulse inverters 1, 2 can, as already shown in connection with the explanations for FIGS. 5 and 6, for example with the aid of a triangular Auxiliary function U ⁇ in the sense of the known sine-triangle modulation.
  • a triangular Auxiliary function U ⁇ in the sense of the known sine-triangle modulation.
  • FIG. 3 shows a simplified representation of two winding systems 33, 34 of an electrical induction machine 3, each of which is fed by a common DC voltage supply device 4 via a three-phase pulse converter 1, 2.
  • the three phases are marked with the letters a, b and c.
  • the DC voltage supply device 4 in turn comprises a DC voltage source 40 and current and voltage-carrying conductors 41, 42, as already described in the explanations for FIGS. 1 and 5.
  • Cp4 in turn denotes the parasitic capacitance of the DC voltage supply device against earth potential.
  • the two winding systems 33, 34 of the induction machine 3 are arranged such that they are electrically offset from one another by 180 °. With the same winding direction of the motor windings, this can be done by suitable interconnection of the winding starts or winding ends of the winding strands 33a, 33b, 33c or 34a, 34b, 34c.
  • the winding beginnings are indicated by a point • in the same winding direction as usual in FIG.
  • control device or control devices required for controlling the pulse converters have the designations 5 and 51, 52.
  • a control method using triangular auxiliary functions in the sense of the known is again used in the example Sine-triangle modulation is used.
  • the two pulse inverters 1, 2 are controlled by the control devices 51, 52 or by the control device 5 in such a way that their outputs la, lb, lc or 2a, 2b, 2c are used to generate the common mode Currents Icml, Icm2 of relevant potentials Ula, Ulb, Ulc or U2a, U2b, U2c are connected to the winding systems 33, 34 at least approximately at the same time in such a way that the voltage potentials Uc33, Uc34 via the parasitic capacitances Cp33, Cp34 of the winding systems 33, 34 are directed opposite to each other with respect to earth potential and thus the common mode interference currents ICml and Icm2 cancel each other out.
  • this is achieved in that the output potentials Ula, U2a or Ulb, U2b or Ulc, U2c W2b are in opposite directions by driving the half bridges Wla, Wlb and How of the converter 1 in opposite directions to the half bridges W2a, W2b and W2c of the converter 2 change to each other.
  • the switching times for triggering the pulse converter are again formed in an exemplary manner with the aid of a triangle auxiliary function U ⁇ in the sense of the known sine-triangle modulation.
  • the switching times for the pulse converter 2 are determined in the control device 52 according to the same principle.
  • control device (5) or the control devices (51, 52) are more advantageous. as implemented in at least one programmable hardware module, in particular LCA, and / or by means of software in digital signal processing with at least one digital processor and / or as conventional hardware in analog and / or digital technology.
  • Such induction machines in particular designed as permanent magnet magnetically excited synchronous machines, can be designed for high drive powers due to the individual feeding of their winding strands or by using a plurality of multi-phase winding systems, such as those e.g. for the propulsion drive of a ship, especially a submarine, is required.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Control Of Ac Motors In General (AREA)
  • Inverter Devices (AREA)
  • Pharmaceuticals Containing Other Organic And Inorganic Compounds (AREA)

Abstract

L'objectif de l'invention est de réduite les courants parasites en mode commun dans un système d'entraînement électrique comportant au moins deux convertisseurs d'impulsions (1, 2) qui sont alimentés par un dispositif d'alimentation en tension continue (4) commun et servent à alimenter une machine électrique à champ magnétique rotatif (3) comportant au moins deux faisceaux d'enroulements (31, 32) ou au moins deux systèmes d'enroulements (33, 34). Cet objectif est atteint par le fait qu'au moins chacun des convertisseurs d'impulsions (1, 2) est commandé par un dispositif de commande (5) de telle sorte qu'au niveau des sorties (1a, 1b, 1c ou 2a, 2b, 2c) des deux convertisseurs d'impulsion (1, 2), les potentiels (U1a, U1b, U1c ou Uta, U2b, U2c) prépondérant pour la formation de courant en mode commun (Icml, Icm2) sont au moins presque simultanément appliqués aux faisceaux d'enroulement (31, 32) présentant des condensateurs parasitaires (Cp31, Cp32) de la machine à champ magnétique rotatif (3) ou bien aux systèmes d'enroulements (33, 34) présentant des condensateurs parasitaires (Cp33, Cp34) de ladite machine, cela de façon que les potentiels de tension (Uc31, Uc32 ou Uc33, Uc34) sont dirigés dans des sens opposés par l'intermédiaire des condensateurs parasitaires (Cp31, Cp32) des faisceaux d'enroulements (31, 32) ou bien par l'intermédiaire des condensateurs parasitaires (Cp33, Cp34) des systèmes d'enroulements (33, 34).
PCT/EP2004/000166 2003-01-15 2004-01-13 Procede pour reduire les courants parasites en mode commun dans un systeme d'entrainement electrique, et systeme d'entrainement electrique correspondant WO2004064240A1 (fr)

Priority Applications (4)

Application Number Priority Date Filing Date Title
BR0406791-6A BRPI0406791A (pt) 2003-01-15 2004-01-13 Processo para redução de correntes parasitas "common-mode" em um sistema de acionamento elétrico bem como correspondente sistema de acionamento elétrico
EP04701595.3A EP1584134B1 (fr) 2003-01-15 2004-01-13 Procede pour reduire les courants parasites en mode commun dans un systeme d'entrainement electrique, et systeme d'entrainement electrique correspondant
KR1020057013181A KR101144364B1 (ko) 2003-01-15 2004-01-13 전기 추진 시스템의 공통 모드 간섭전류를 감소시키기 위한방법 및 이에 상응하는 전기 추진 시스템
ES04701595.3T ES2629016T3 (es) 2003-01-15 2004-01-13 Procedimiento para la reducción de corrientes parásitas en modo común en un sistema de accionamiento eléctrico así como el respectivo sistema de accionamiento eléctrico

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
DE10301275.3 2003-01-15
DE10301275.3A DE10301275B4 (de) 2003-01-15 2003-01-15 Verfahren zur Verringerung von Common-Mode-Störströmen in einem elektrischen Antriebssystem sowie entsprechendes elektrisches Antriebssystem

Publications (2)

Publication Number Publication Date
WO2004064240A1 true WO2004064240A1 (fr) 2004-07-29
WO2004064240A9 WO2004064240A9 (fr) 2005-08-04

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PCT/EP2004/000166 WO2004064240A1 (fr) 2003-01-15 2004-01-13 Procede pour reduire les courants parasites en mode commun dans un systeme d'entrainement electrique, et systeme d'entrainement electrique correspondant

Country Status (8)

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EP (1) EP1584134B1 (fr)
KR (1) KR101144364B1 (fr)
CN (1) CN100397773C (fr)
BR (1) BRPI0406791A (fr)
DE (1) DE10301275B4 (fr)
ES (1) ES2629016T3 (fr)
PT (1) PT1584134T (fr)
WO (1) WO2004064240A1 (fr)

Families Citing this family (9)

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Publication number Priority date Publication date Assignee Title
DE102006007610A1 (de) 2006-02-14 2007-08-16 Brose Fahrzeugteile Gmbh & Co. Kommanditgesellschaft, Coburg Antriebseinrichtung für eine Verstelleinrichtung zum Verstellen eines Fahrzeugteils und Verfahren zum Betrieb einer Antriebseinrichtung
US7928592B2 (en) 2008-06-30 2011-04-19 General Electric Company Wind turbine with parallel converters utilizing a plurality of isolated generator windings
DE102009007626B4 (de) 2009-02-05 2015-06-18 Siteco Beleuchtungstechnik Gmbh Leuchte zur Verminderung der Effekte der Lichtrückreflexion
EP2927044B1 (fr) * 2014-03-31 2017-02-22 Siemens Aktiengesellschaft Procédé de fonctionnement d'un convertisseur auxiliaire parallèle dans un véhicule sur rail
CN107223307B (zh) * 2015-02-05 2020-12-08 奥的斯电梯公司 具有可忽略的共模电压的六相电动机器的驱动和控制
DE102016116069A1 (de) * 2016-08-29 2018-03-01 Volkswagen Aktiengesellschaft Vorrichtung zum Vermindern hochfrequenter Störströme sowie Fahrzeug
DE102016224916A1 (de) 2016-12-14 2018-06-14 Bayerische Motoren Werke Aktiengesellschaft Rotor und Rotorschaltung für einen Elektromotor
DE102019115516A1 (de) * 2019-06-07 2020-12-10 Webasto SE Verfahren zur Verringerung von Gleichtakt-Störungen von durch Hochvoltkomponenten gesteuerten ohmschen Lasten mit kapazitivem Belag
DE102021211779A1 (de) 2021-10-19 2023-04-20 Baumüller Nürnberg GmbH Verfahren zum Betrieb einer Anlage

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EP0898359A2 (fr) 1997-08-22 1999-02-24 Asea Brown Boveri AG Onduleur
DE10040851A1 (de) 2000-08-21 2002-03-07 Siemens Ag Elektrische Maschine mit isoliertem Maschinengehäuse
DE10043934A1 (de) 2000-09-06 2002-03-14 Gebhardt Ventilatoren Steuerungsmodul für einen Brückenumrichter

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DE3637479A1 (de) * 1986-11-04 1988-05-05 Bosch Gmbh Robert Servoantrieb mit einer wechselstrommaschine
DE58908893D1 (de) * 1988-03-21 1995-03-02 Siemens Ag Pulsumrichtergespeiste Drehfeldmaschine.
CN1069343A (zh) * 1991-08-08 1993-02-24 陈飞 运流电流的检测方法及其装置
DE10059332A1 (de) * 2000-11-29 2002-06-13 Siemens Ag Bedämpfung von Resonanzüberhöhungen bei einem an einem Umrichter mit Spannungszwischenkreis betriebenen elektrischen Motor durch transformatorisch eingekoppelten Dämpfungswiderstand sowie korrespondierender elektrischer Motor

Patent Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP0898359A2 (fr) 1997-08-22 1999-02-24 Asea Brown Boveri AG Onduleur
DE10040851A1 (de) 2000-08-21 2002-03-07 Siemens Ag Elektrische Maschine mit isoliertem Maschinengehäuse
DE10043934A1 (de) 2000-09-06 2002-03-14 Gebhardt Ventilatoren Steuerungsmodul für einen Brückenumrichter

Also Published As

Publication number Publication date
WO2004064240A9 (fr) 2005-08-04
KR101144364B1 (ko) 2012-05-11
EP1584134B1 (fr) 2017-03-22
CN100397773C (zh) 2008-06-25
DE10301275B4 (de) 2016-06-16
PT1584134T (pt) 2017-05-30
CN1739233A (zh) 2006-02-22
ES2629016T3 (es) 2017-08-07
KR20050097945A (ko) 2005-10-10
DE10301275A1 (de) 2004-08-05
BRPI0406791A (pt) 2006-01-17
EP1584134A1 (fr) 2005-10-12

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