WO2003041256A2 - Convertisseur et procede permettant de determiner un vecteur spatial de courant - Google Patents

Convertisseur et procede permettant de determiner un vecteur spatial de courant Download PDF

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Publication number
WO2003041256A2
WO2003041256A2 PCT/EP2002/011172 EP0211172W WO03041256A2 WO 2003041256 A2 WO2003041256 A2 WO 2003041256A2 EP 0211172 W EP0211172 W EP 0211172W WO 03041256 A2 WO03041256 A2 WO 03041256A2
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WO
WIPO (PCT)
Prior art keywords
current
pulse width
width modulation
pair
modulation period
Prior art date
Application number
PCT/EP2002/011172
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German (de)
English (en)
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WO2003041256A3 (fr
Inventor
Harald Wolf
Ralph Mayer
Original Assignee
Sew-Eurodrive Gmbh & Co
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
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Application filed by Sew-Eurodrive Gmbh & Co filed Critical Sew-Eurodrive Gmbh & Co
Priority to PCT/EP2002/011685 priority Critical patent/WO2003041258A2/fr
Priority to CNB028209427A priority patent/CN100361381C/zh
Priority to EP02782953.0A priority patent/EP1446866B1/fr
Publication of WO2003041256A2 publication Critical patent/WO2003041256A2/fr
Publication of WO2003041256A3 publication Critical patent/WO2003041256A3/fr

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Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H02M7/5387—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
    • H02M7/53871—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration with automatic control of output voltage or current
    • H02M7/53873—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration with automatic control of output voltage or current with digital control

Definitions

  • the invention relates to a converter and a method for determining a current space vector.
  • a converter is known from the writing by Francesco Parasiliti, "Low cost current Sensing in DSP Based Drives", Industrial Electronics, 1999, ISIE'99, Proceedings of the IEEE, Volume 3, 1999, International Symposium, Volume 3, 1999, in which shunt resistors are arranged in all lower branches of the half bridges as a means for detecting the respective currents All three current measured values are recorded, the measurement impulses being in the middle of the time period within a pulse width modulation period in which the discrete switching state (000), ie the Zero vector v 0 is present (page 1287, left column and Figure 7.) In the specific embodiment there is a small time offset to this center due to consideration of dead times, signal propagation times and the like.
  • the current space pointer is then determined from the associated measured values however, that in the shaded areas of the hexagon (page 1287, left column, last ter section and Figure 8) no or only an inaccurate determination of the current space vector is possible, since either no zero vector is used in these shaded areas or only very briefly. If the zero vector is not present or is only present for a very short time, there is automatically no or only a very short current measurement signal in one phase, which is therefore for one
  • a converter is known from US Pat. No. 5,815,391, in which means for detecting the respective currents are arranged in all lower branches of the half bridges (FIG. 2A).
  • the corresponding table ( Figure 2B) explains that the current in phase A can be measured depending on the switching states (example 1st line: measurable;) or can be calculated from the two other current measured values (5th line: calculable;) , If However, if the lower switch of phase A and another lower switch are open, the measured current value of phase A cannot be determined.
  • Such switching states are identified in this document as "unknown" in phase A.
  • the table 2B and the problem described relate to the switching states, that is to say the respective instantaneous state of the converter.
  • the table 2B mentioned only relates to phase A.
  • the associated tables for phases B and C can be drawn up. It is easy to see that with some switching states, namely (111), (110), (101), (011), no or only a current measurement value can be determined and therefore in no case a current space pointer for these instantaneous states.
  • US Pat. No. 5,815,391 does not therefore show how to determine a current space pointer which corresponds to the mean value of the actually existing current space pointer formed over a pulse width modulation period. In particular, it is not shown how to proceed so that the current space pointer is not falsified by current ripples.
  • the duration of a "known" switching state within a pulse width modulation period depends on the following factors: carrier frequency of the pulse width modulation, type of pulse width modulation method. If this duration of a "known" switching state is too short, the current space pointer cannot be determined.
  • the invention is therefore based on the object of developing a converter in which as many expensive parts as possible can be dispensed with and in particular
  • Mass production an inexpensive manufacture can be achieved and nevertheless a method for determining a current space vector can be carried out.
  • the object is achieved in a method according to the features specified in claim 1 or 16 and in a converter according to the features specified in claim 12.
  • Essential features of the invention in the method are that for determining a current space vector for a converter which can be operated with pulse width modulation, comprising signal electronics and a power output stage which comprises power switches arranged in three half bridges, each comprising a lower and an upper branch,
  • means for detecting the respective currents are arranged either in all three lower or in all three upper branches of the half bridges,
  • At least one associated current sample value is determined with two of the three means for detecting the currents within a period of time that is a pulse width modulation period,
  • a first and a second associated current sample value are provided with a second means of the pair before and after the detection of a current sample value acquired with a first means of the pair, a current space pointer is formed from the current samples determined with this pair of means or the current values are formed in the output branches, in particular for use in a control and / or regulating method, and
  • the mean output voltage space vector is determined by the output potentials of the three averaged over a pulse width modulation period
  • the invention is based on the surprising finding that the information about the current space vector is contained in the time course of the two most suitable current measurement signals. It is even permitted that even switching states may occasionally occur within this pulse width modulation period, which in themselves would not allow the current space vector to be determined, that is to say are “unknown” states in the sense of US Pat. No. 5,815,391!
  • the associated current samples are not recorded simultaneously within the pulse width modulation period and / or the associated measurement impulses are not carried out simultaneously.
  • the advantage here is that a microcontroller with only a single analog-digital converter and no additional sample-hold circuit can be used with the converter, that is, no sample-hold circuit arranged externally from the microcontroller.
  • At least one of the two means detects a current sample more than once per pulse width modulation period and / or provides more than one measurement trigger within a pulse width modulation period.
  • a current sample is detected exactly twice per pulse width modulation period with a first of the two means and the measurement impulse for the second of the two means lies in the middle of the pulse width modulation period.
  • the two measurement impulses of the first of the two means are advantageously equidistant from the center of the pulse width modulation period, that is to say that the time interval from the first measurement impulse of the first means to the first measurement impulse of the second means is the same as the time interval from the measurement impulse of the second means to the second measurement impulse of the first mean and the last-mentioned measurement impulse of the second mean lies in the middle of the pulse width modulation period.
  • the temporal center of the pulse width modulation period denotes the temporal center of the respective LOW states. During these states, current measurement signals are present on the means for detecting the respective currents.
  • the current measured values of the phases belonging to the two means mentioned are sufficient to determine the current space vector.
  • the total of three current measured values of the two means are always available because the invention uses an advantageous pulse width modulation method, such as a symmetrical pulse width modulation method, and the output voltage space vector is limited to the inner circle of the hexagon. This also means, for example, that no corner vectors of the hexagon occur permanently over an entire pulse width modulation period.
  • Pulse width modulation period Pulse width modulation period. Then, however, either two A / D converters or external sample-hold circuits would be necessary, which would be expensive.
  • two temporally staggered measurement impulses are carried out with the first means.
  • the time at which the second agent starts to measure is in the middle of the pulse width modulation period.
  • the times of the two measurement impulses of the first means each have the same time interval from the center of the pulse width modulation period.
  • a current measurement value is determined using the first average, which is equal to that current measurement value which is based on the first average Time of the middle of the pulse width modulation period would be measurable.
  • the current space vector is determined for each pulse width modulation period.
  • the advantage here is that the most frequent possible determination of the current space vector can be provided even at a low pulse width modulation frequency in order to improve the control quality of the control method of the converter.
  • the current measurement signals are formed at the lower intermediate circuit potential, current measurement values assigned to the respective half bridges being determined from current sampled values which are derived from the current measurement signals.
  • the reference potential of the signal electronics which comprises a control and regulating device of the converter, corresponds to the reference potential on which the current measurement signals are formed. The advantage here is that optocouplers for electrical isolation can be saved.
  • the reference potential of the signal electronics also has the lower intermediate circuit potential. A significant advantage here is that the control signals of the lower circuit breakers in the half bridges can be generated by the signal electronics without a high voltage gap occurring, which would make complex electrical isolation necessary. Only the control signals of the upper one
  • Circuit breakers must be controlled via optocouplers or other potential-isolating devices.
  • optocouplers or other potential-isolating devices.
  • an important step towards saving costs and reducing the number of parts can be achieved.
  • Power semiconductor switches such as IGBT of the npn type, which can be controlled with control voltages which have the lower intermediate circuit potential as a reference potential, can advantageously be used as lower circuit breakers in the half-bridges.
  • complementary power semiconductor switches such as IGBT of the pnp type
  • the upper intermediate circuit potential must then be selected as the reference potential for the current measurement and for the signal electronics and the converter designed accordingly.
  • the pair is dependent on the angle of the
  • a period of two or more pulse width modulation periods is used instead of the one pulse width modulation period.
  • the advantage here is that the current space vector can be determined even at a high switching frequency. There is a slight falsification, but this is low at a high switching frequency.
  • the detection of the current sample value detected with the first current measuring means is carried out centrally in the pulse width modulation period.
  • a first and a second associated current sample value are recorded symmetrically before and after the acquisition of a current sample value acquired with the first current measurement means.
  • the associated current sample values could be acquired simultaneously and / or the associated measurement impulses could be carried out simultaneously using the two of the three means for acquiring the currents.
  • the measurement impulses would be carried out centrally in the pulse width modulation period. The advantage here would be that the determination of the current measured values is particularly simple and yet there are no falsifications caused by current ripples.
  • an associated current sample is acquired at least one pulse width modulation period after the acquisition of a current sample associated with the second means for detecting the currents.
  • the measurement impulses associated with the two means for detecting the currents lie in different pulse width modulation periods.
  • the first current sample value of the pair is recorded more than once per pulse width modulation period and a value interpolated and / or mean value is formed from the recorded values according to the times of the respective acquisition.
  • a first current sample of the pair associated with a first half bridge is acquired before and after the second current sample of the pair associated with a second half bridge.
  • the detected current space vector corresponds to the mean value of the current space vector over a pulse width modulation period.
  • the converter comprising a signal electronics and a power output stage, which in three, each a lower and an upper branch comprehensive circuit breakers arranged half bridges, wherein the converter can be operated pulse width modulated, are that
  • means for detecting the respective currents are arranged either in all three lower or in all three upper branches of the half bridges,
  • the means for current detection comprise resistors, in particular shunt resistors.
  • resistors in particular shunt resistors.
  • the means for current detection are arranged in the half bridges in such a way that they are connected either to the upper or to the lower intermediate circuit potential.
  • the signal electronics have a reference potential, which is also the reference potential for the means for current detection. If this reference potential is Uz-, the means for potential isolation for the control signals of the lower circuit breakers of the half bridges can be saved. If this reference potential is Uz +, then the means for
  • the signal electronics have a reference potential, which is also the reference potential for the means for current detection.
  • a reference potential which is also the reference potential for the means for current detection.
  • each means for current detection can be assigned to a single analog-digital converter by means of a multiplexer and / or switch. The advantage here is that the converter can be carried out inexpensively, in particular by saving additional analog-digital converters.
  • the signal electronics could further preferably have a microcontroller which has a single analog-digital converter and a sample hold circuit which is not included in the microcontroller, that is to say an additional external one.
  • the advantage here would be that an inexpensive microcontroller can be used, which comprises only a single analog-to-digital converter.
  • the signal electronics comprise means for generating pulse-width-modulated control signals for the circuit breakers, and the signal electronics have a reference potential, which is also the reference potential for the means for current detection.
  • a respective means for current detection can be assigned to a single analog-digital converter by means of a multiplexer and / or switch. Costly further analog-digital converters can then be dispensed with.
  • the essential features are that means for detecting the respective currents are arranged either in all three lower or in all three upper branches of the half bridges,
  • the pulse width modulation frequency is greater than a minimum frequency
  • At least one associated current sample value is determined with two of the three means for detecting the currents, and the same average output voltage space vector is output in both pulse width modulation periods,
  • a first current sample in the middle of the first of the two pulse width modulation periods is detected with a first average of the pair and an associated current sample in the middle of the second, ie immediately following, with a second average of the pair
  • Pulse width modulation period is recorded
  • a current space pointer is formed from the current samples determined with this pair of means or the current values are formed in the output branches, in particular for use in a control and / or regulating method, and
  • mean output voltage space vector is determined by the differences between the output potentials of the three output phases, which are averaged over a pulse width modulation period.
  • a power output stage for a three-phase converter is schematically outlined in FIG.
  • the circuit breakers with associated freewheeling diodes are identified by six switch symbols S Ro , S So , S To , S Rll , S Su and S Tu .
  • S Ro switch symbols
  • S So switch symbols
  • S To S To
  • S Rll switch symbols
  • Half bridges are shunt resistors R R , R S and as means for current detection
  • the resistors are connected to amplifier circuits V R , V s and V ⁇ , which each generate a current measurement signal I m , I SM and I m on the output side. From the three
  • the control method of the converter determines a current space pointer as a computing variable once per pulse width modulation period, which represents the mean value of the physical current space pointer formed over a pulse width modulation period.
  • the pulse width modulation signals PWM R (t), PWM s (t) and PWM ⁇ (t) generated by the control and regulating device 1 determine the state of the circuit breakers
  • the pulse width modulation signals are provided as follows: If the respective pulse width modulation signal, for example PWM R (t), is 1, the associated upper power switch, for example S Ro , closed and the associated lower circuit breaker, for example S Ru , opened. In this case, the associated output voltage potential is U z + . Is that
  • Pulse width modulation signal 0 that is to say in the LOW state, the associated circuit breakers are in the respective other state and the associated output voltage potential is U z _.
  • the so-called dead time inserted in the practical implementation, during which the respective upper and lower switch is open, is not relevant for the basic function of the invention.
  • the associated motor current flows in the lower branch of the associated half bridge and thus via the respective shunt resistor.
  • the associated motor current In order to record the current measured values precisely, the associated motor current must flow through the shunt resistor for longer than a minimum period.
  • the minimum duration is dependent on the filter effect of the measuring amplifier circuits, including amplifier circuits V R , V s and V ⁇ .
  • a filter effect is achieved by appropriate circuitry to suppress noise components or interference components in the current measurement values. For example, with a pulse width modulation frequency of 16 kHz, a filter time constant in the range from 0.5 ⁇ s to 2 ⁇ s is advantageous.
  • the invention therefore relates only to those converters which are operated in such a way that pulse width modulation means that in no pulse width modulation period is there such a high modulation that only a single active one Switching state occurs for a full pulse width modulation period.
  • the pulse width modulation signals PWM R (t), PWM s (t) and PWM ⁇ (t) take the values (110), (101), (100), (001), (010) or ( 011), which are also referred to as discrete active output voltage space pointers.
  • Active switching states therefore do not include switching states (111) and (000). The last two switching states mentioned are each also referred to as a discrete zero-voltage space vector or vector.
  • edge vectors are those output voltage space pointers averaged over a pulse width modulation period which, when a single one of the active switching states is theoretically applied, over a whole
  • Pulse width modulation period would result.
  • the output voltage space pointer averaged over a pulse width modulation period never takes on the value of such an edge vector because of the above-mentioned limitation of the working range.
  • a current space pointer can be determined for each pulse width modulation period by skillfully selecting the times for the measurement impulses within a pulse width modulation period.
  • the alternating states include, among other things, states in which the determination of a current space vector would not be possible if they were applied continuously over a pulse width modulation period, such as state (101) according to the last line of Table 2B from US Pat. No. 5,815 391.
  • a measurement initiation is carried out at a first time in a first phase, a second measurement initiation at another second time in a second phase and a third at a third time in the first phase Measuring offense.
  • the ascertainable current space pointer is not falsified by current ripples in the pulse width modulation method permissible for the invention, in particular symmetrical pulse width modulation methods in which the output voltage space pointer is limited to the inner circle of the hexagon. This means that only a single analog-to-digital converter is necessary, in particular without additional external sample-hold circuits.
  • FIG. 2 shows a feasible variant for part of the control and regulating device 1 from FIG. 1.
  • This comprises a sample-hold circuit 21, to which the three current measurement signals are fed, and a microcontroller 22 with an integrated analog-to-digital converter.
  • the microcontroller 22 uses the signals S / H1, S / H2 and S / H3 to control the sampling times, which are also referred to as measurement impulses, at which the sample-hold circuit 21 holds current measurement signals until analog-to-digital conversion.
  • the microcontroller 22 then only has to comprise a single analog-digital converter together with an analog multiplexer or switch 23.
  • the advantage here is that simultaneous acquisition of current samples is achieved with only a single analog-digital converter, although a sequential analog-digital conversion takes place.
  • microcontroller 22 current measurement values or a current space pointer are then determined from the current samples.
  • the microcontroller 22 controls the sample-hold circuit and thus the measurement impulses via the signals S / H1, S / H2 and S / H3 in accordance with the method described below.
  • the sample hold circuit 21 can be saved in accordance with FIG. 3, in contrast to the variant in accordance with FIG. However, it is necessary to record the current samples one after the other in accordance with the method described below.
  • FIG. 4 shows exemplary time profiles of the motor-side output potentials U R , U s and averaged over a respective pulse width modulation period
  • U ⁇ of the converter is shown over an output voltage period, the motor-side output potentials U R , U s and U ⁇ are shown in a standardized manner and the output voltage angle extends over the range from 0 to 2 ⁇ .
  • the potential value U z _ corresponds to the value -1 and U z + to the value +1. It can be seen in FIG. 4 that the mean values of the output potentials contain a third harmonic.
  • FIG. 4 shows angular ranges 1 to 6 of the output voltage vector, in which various means for current detection are used according to the method according to the invention.
  • the mean value of the output potential U s is zero.
  • the mean value of the output potential U R is in the vicinity of the positive maximum value 1.
  • the mean value of the output potential U ⁇ is in the vicinity of the minimum value -1.
  • the associated circuit breakers change into the respective other state and the associated output voltage potential is U z _.
  • the so-called dead time inserted in the practical implementation, during which the respective upper and lower switch is open, is in principle not relevant for the function of the invention. 5 shows two pulse width modulation periods in the abscissa direction.
  • FIG. 6 shows the exemplary motor currents I R (t), I s (t) and I ⁇ (t) associated with the two pulse width modulation periods mentioned in the output branches. In addition, the current ripple resulting from the pulse width modulated output potentials is indicated.
  • FIG. 7 shows the idealized temporal profile of the current measurement signals I m (f), I SM ( ⁇ ) and ⁇ ⁇ I JM Q) associated with the two pulse width modulation periods without the filtering effect of the amplifier circuits V R , V s and V ⁇ , A non-zero
  • the “optimal” pair that has the respectively wider pulse width modulation signals is selected from the three half bridges, ie only current measurement signals of these two special half bridges are used.
  • the selection is made in such a way that the current measurement signal is not is used, the lower switch within a respective Pulse width modulation period has a shorter time the closed state than the other two lower switches.
  • FIG. 7 shows an operating state for two pulse width modulation periods in which the selected pair is I SM (t) and I m (t). For these, the times at which the current samples are recorded and which are also referred to as measurement impulses are indicated by jagged arrows.
  • the lugs are drawn with solid, not jagged arrows.
  • the current samples for the selected pair I SM (t) and I TM (t) are recorded simultaneously. Here are different
  • each current sample is formed by a separate analog-to-digital converter.
  • the three current measurement signals according to FIG. 2 are each fed to a sample-hold amplifier of the sample-hold circuit 21, the sample-hold amplifiers changing to the hold state at the time of the sampling.
  • the analog-digital converter can convert the fixed current measurement signals one after the other by means of the multiplexer or switch.
  • two analog-digital converters and corresponding changeover switches are used. In other versions, mixed forms are also possible.
  • a symmetrical pulse width modulation method is advantageously used, the switching frequency not being selected to be higher than 20 kHz and the maximum modulation described above not being exceeded.
  • the switching frequency not being selected to be higher than 20 kHz and the maximum modulation described above not being exceeded.
  • Pulse width modulation period measurement impulse for I m of the first method according to the invention replaced by two measurement impulses, each with a time offset ⁇ t.
  • the time offset .DELTA.t is as small as possible, but larger than the analog-digital converter time.
  • the mean value is formed from the first and second current sample values for I m and is used to determine the current space vector.
  • This mean value formed in this way corresponds to that fictitious current sample value for I m , which would be detectable at the same time for detecting the current sample value I SM .
  • the current space pointer determined in this way is thus free from the influence of the current ripple. This makes it possible to determine the current space vector with only a single analog-digital converter without being distorted by current ripples. Additional sample-hold circuits are not necessary. Additional sample-hold circuits are not to be understood as those sample-hold circuits that are an integral part of conventional analog-digital converters.
  • a symmetrical pulse width modulation method is also advantageously used in the second method, the switching frequency not being selected to be higher than 20 kHz and the maximum modulation described above not being exceeded.
  • the switching frequency not being selected to be higher than 20 kHz and the maximum modulation described above not being exceeded.
  • a correct determination of the current space vector is thus always ensured in the present invention, provided that the respective type of pulse width modulation method ensures that the pulse width modulation signals have a sufficient pulse width.
  • flat-top methods are generally symmetrical pulse width modulation methods, they cannot be used advantageously for small output voltages.
  • the current samples are not determined in the same pulse width modulation period, but the first current sample is recorded in a first pulse width modulation period and the second current sample in one of the subsequent pulse width modulation periods.
  • the first current sample is recorded in a first pulse width modulation period and the second current sample in one of the subsequent pulse width modulation periods.
  • Angular ranges the pair to be used indicated by jagged arrows. For example, only S and T, ie I SM and I m , should be used in angular range 1. In the angular range 2 only R and T, i.e. I m and I m , should be used
  • the measurement impulse symmetrically in the middle of the pulse width modulation period for a current sample value of the first method according to the invention is replaced by two measurement impulses which each have a time offset ⁇ t.
  • FIG. 9 shows how the measurement impulses are to be carried out as a function of the angular ranges of the output voltage space vector. In particular, it is shown in which half-bridge two measurement impulses and in which half-bridge the individual measurement imposition in the middle are to be carried out. In the angular range 1 there is therefore a first measurement initiation for I m , then a single, central measurement initiation for I SM and finally a second measurement initiation for I m .
  • the measurement impulses have a time interval of ⁇ t.
  • the two current samples of the current measurement signal I TM are not recorded symmetrically around the measurement initiation for recording the current sample value of the current measurement signal I SM , that is to say not with a time interval ⁇ t before and after the detection of I SM , but with different time intervals.
  • an interpolated value is formed, which takes into account the corresponding time intervals, whereby, however, variables that characterize the motor and also the type and duration of the switching states are to be taken into account when interpolating.
  • each current sample can in principle be replaced by several current samples. A further reduction in measurement noise can thus be provided.
  • Amplifier circuits V R , V s and ⁇ are taken into account in that all measurement impulses are delayed by the filter time constant of the amplifier circuits.
  • the filter time constant is less than half the minimum duration.
  • a so-called symmetrical pulse width modulation method is advantageously used in the present invention.
  • the temporal mean value which is formed from the value of the time of a first switching state change of the pulse width modulation signal in a first phase and the value of the time of the subsequent switching state change associated in the same phase, has the same value as the correspondingly formed one Averages of the other two phases. Therefore, the switching state changes from HIGH to LOW and back in all three phases are symmetrical to the middle of the pulse width modulation period.

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  • Inverter Devices (AREA)
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Abstract

L'invention concerne un convertisseur et un procédé de détermination d'un vecteur spatial de courant conçu pour un convertisseur modulable en largeur d'impulsion, comprenant un dispositif électronique de signaux ainsi qu'un étage final de puissance pourvu d'un disjoncteur se présentant sous la forme de trois demi-ponts comprenant respectivement une branche inférieure et une branche supérieure. Des moyens de détection des courants respectifs sont disposés soit dans l'ensemble des trois branches inférieures, soit dans l'ensemble des trois branches supérieures des demi-ponts. Respectivement au moins une valeur de détection du courant correspondante est déterminée au cours d'un créneau temporel à l'aide de deux desdits trois moyens de détection des courants. Les valeurs de détection du courant déterminées à l'aide de ces deux moyens permettent de générer un vecteur spatial de courant ou des valeurs de courant dans les branches de sortie, en particulier pour être utilisé(es) dans un procédé de commande et/ou de régulation. Les deux moyens sont sélectionnés de manière diverse en fonction du vecteur spatial de la tension de sortie.
PCT/EP2002/011172 2001-11-08 2002-10-04 Convertisseur et procede permettant de determiner un vecteur spatial de courant WO2003041256A2 (fr)

Priority Applications (3)

Application Number Priority Date Filing Date Title
PCT/EP2002/011685 WO2003041258A2 (fr) 2001-11-08 2002-10-18 Convertisseur et procede pour determiner un indicateur spatial de courant
CNB028209427A CN100361381C (zh) 2001-11-08 2002-10-18 变流器和确定电流空间矢量的方法
EP02782953.0A EP1446866B1 (fr) 2001-11-08 2002-10-18 Procede pour determiner un indicateur spatial de courant

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Application Number Priority Date Filing Date Title
DE10154478 2001-11-08
DE10154478.2 2001-11-08

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WO2003041256A2 true WO2003041256A2 (fr) 2003-05-15
WO2003041256A3 WO2003041256A3 (fr) 2003-09-25

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PCT/EP2002/011172 WO2003041256A2 (fr) 2001-11-08 2002-10-04 Convertisseur et procede permettant de determiner un vecteur spatial de courant
PCT/EP2002/011685 WO2003041258A2 (fr) 2001-11-08 2002-10-18 Convertisseur et procede pour determiner un indicateur spatial de courant

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WO2003041256A3 (fr) 2003-09-25
CN1575539A (zh) 2005-02-02
WO2003041258A2 (fr) 2003-05-15
DE10248375C2 (de) 2003-09-18
DE10248375A1 (de) 2003-05-28
WO2003041258A3 (fr) 2003-09-25
CN100361381C (zh) 2008-01-09

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