WO2002050987A1 - Alimentation en mode commute a fort rendement - Google Patents

Alimentation en mode commute a fort rendement Download PDF

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Publication number
WO2002050987A1
WO2002050987A1 PCT/KR2001/002189 KR0102189W WO0250987A1 WO 2002050987 A1 WO2002050987 A1 WO 2002050987A1 KR 0102189 W KR0102189 W KR 0102189W WO 0250987 A1 WO0250987 A1 WO 0250987A1
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WO
WIPO (PCT)
Prior art keywords
switching
current
output
signal
power conversion
Prior art date
Application number
PCT/KR2001/002189
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English (en)
Inventor
Joon-Ho Park
Original Assignee
Joon-Ho Park
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Joon-Ho Park filed Critical Joon-Ho Park
Priority to AU2002216449A priority Critical patent/AU2002216449A1/en
Publication of WO2002050987A1 publication Critical patent/WO2002050987A1/fr

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Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/285—Single converters with a plurality of output stages connected in parallel
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements

Definitions

  • the present invention relates to a switching mode power supply, and more particularly, to a switching mode power supply capable of minimizing energy loss
  • a switching frequency f s is maximized to reduce the size of a transformer and the number of turns of a coil, in order to reduce energy loss caused by the resistance of the coil
  • losses caused by transistors or transformers of the power supply cannot be prevented
  • a switching mode power supply which is capable of minimizing power loss by forming multiple paths through which current flows, and to disperse the current
  • a switching mode power supply includes a switching signal generating portion, which outputs a switching signal having a predetermined frequency, at least two switching elements, which turn on or off in response to the switching signal, power conversion elements, which are connected between the switching elements and an input DC power, through which current flows or is cut off according to the on or off state of the switching elements, to generate a square wave signal, and an output rectifier into which the square wave signal generated by the power conversion elements is transmitted, which rectifies the square wave signal and outputs a DC power
  • a switching mode power supply includes a switching signal generating portion, which outputs a switching signal having a predetermined frequency, a switching element, which turns on or off operation in response to the switching signal, t least two power conversion elements, which are connected between the switching elements and an input DC power, through which current flows or is cut off according to the on or off state of the switching element, thereby generating a square wave signal, and an output rectifier into which the square wave signal generated by the power conversion element is transmitted, which rectifies the square wave signal and outputs a DC power
  • FIG 1 illustrates the structure of a forward-type switching mode power supply (SMPS) according to a first embodiment of the present invention
  • FIG 2 illustrates the structure of a flyback-type SMPS according to a second embodiment of the present invention
  • FIG 3 is an example illustrating the structure of a pulse width modulation (PWM) control circuit shown in FIG 1 or 2
  • PWM pulse width modulation
  • FIG 4 is a schematic block diagram illustrating the structure of the SMPS according to the present invention
  • FIG 4 is a schematic block diagram illustrating the structure of a switching mode power supply (SMPS) according to the present invention
  • SMPS switching mode power supply
  • Direct current (DC) power is input into the SMPS If the original power is alternating current (AC) power, then the AC power is converted into DC power through a rectifier, and then input into the power supply
  • a switching controller 42 generates a switching signal which operates at a predetermined frequency, for chopping an input DC voltage V ⁇ n into a high frequency square wave, and an inverter 44 generates a square wave according to the switching frequency of the switching controller 42 by inverting the input DC voltage V ⁇ n
  • a current feedback unit 48 detects the output current of the inverter 44 and feeds back the detected output current into the switching controller 42
  • a final output voltage V out of an output rectifier 47 is fed back into the switching controller 42
  • the switching controller 42 compares a reference signal with feedback signals which are fed back into the switching controller 42 by the current feedback unit 48 and fed back by the final output voltage V out of the output rectifier 47, adjusts the pulse phase of the switching signal and adjusts (pulse width modulation (PWM)-controls) the magnitudes of the current and voltage, and thereby the voltage of the final output of the power supply is maintained at a predetermined level
  • PWM pulse width modulation
  • Elements which cause energy loss in the SMPS include a transistor, a transformer, a diode, and a PWM integrated circuit (IC)
  • a field effect transistor FET
  • energy loss may occur due to R DS(ON) which is an internal resistance component
  • energy loss may occur due to a DC resistance component of a coil
  • energy loss may occur due to a forward voltage V F component
  • PWM IC energy loss may occur due to output current of the switching signal
  • FIG 1 illustrates the structure of the SMPS according to a first embodiment of the present invention, as an example of a forward-type power supply
  • the SMPS according to the first embodiment of the present invention includes an input filter 10, a PWM controller 11 , an inverter 15, a current feedback unit 13, and an output rectifier 17
  • a plurality of switching transistors Q 17 Q 2 , and Q 3 and a plurality of transformers T ⁇ , T 2 , and T 3 for an inverter are controlled by the PWM controller 1 1 in order to increase efficiency and save energy
  • the input filter 10 is formed of a low pass filter having a pi ( ⁇ ) shape in which capacitors d, C l2 , and C l3 are connected to an inductor L to eliminate noise from the input DC voltage V ⁇ n
  • circuit elements for generating a high frequency square wave voltage signal according to a switching operation include a PWM controller 11 for generating a switching signal, transistors Q ⁇ Q 2 , and Q 3 , transformers T ⁇ T 2 , and T 3 , and a transformer T s for sensing current Source terminals of the transistors Q ⁇ Q 2 , and Q 3 are coupled to one another, and a switching signal SW 0Ut that is output from the PWM controller 11 is input into gate terminals of the transistors Q ⁇ , Q 2 , and Q 3 , and dram terminals of the transistors Qi, Q 2 , and Q 3 are connected to primary windings of the transformers T ⁇ T 2 , and T 3 , respectively
  • the transistors Q ⁇ , Q 2 , and Q 3 are simultaneously turned on or off by the switching signal SW 0Ut that is generated in the PWM controller 11 , and thereby current flowing through the primary windings of the transformers T ⁇ , T 2 , and T 3 is cut on or off
  • the SMPS includes a plurality of switching transistors and a plurality of transformers, and a case where a transformer is connected to a switching transistor is illustrated
  • a transformer is connected to a switching transistor
  • the energy saving effect in the present invention can also be achieved using a plurality of transformers connected to one switching transistor, or one transformer connected to a plurality of switching transistors
  • Such design specifications can be varied as needed by those skilled in the art, according to the operating conditions and environment of the SMPS This also applies to the SMPS shown in FIG 2
  • the current feedback unit 13 is connected between a common source terminal of the transistors Q ⁇ , Q 2 , and Q 3 and a negative terminal of an input voltage V ⁇ n , and thereby a signal that is generated according to current when the transistors Q ⁇ Q 2 , and Q 3 are turned on is fed back into the PWM controller 11
  • the current feedback unit 13 senses variation in input current according to variation in the input voltage V, n , or according to variation in output load, and then feeds back the variation in input current into the PWM controller 11 In order to compensate for a phenomenon caused by the variation in input current, the PWM controller 1 1 controls a switching operation in response to a sensing signal
  • the current feedback unit 13 senses that current l pp flowing through transistors varies according to variation in the input voltage V ⁇ n or variation in load, converts the current l pp into a voltage signal, and then feeds back the voltage signal into the PWM controller 11
  • the PWM controller 11 adjusts pulse duration of a positive phase of the switching signal SW out according to the variation in the input voltage V ⁇ n or the variation in load, thereby controlling to maintain a predetermined output voltage
  • the current l pp is increased, the voltage of a current sensing signal that is detected by the current feedback unit 13 and is fed back into the PWM controller 11 is increased, and the PWM controller 11 adjusts the pulse duration of the switching signal SW 0Ut so that the current l pp is decreased on the basis of the voltage of the current sensing signal
  • the ratio of the primary winding to the second winding of the transformer T s is 1 50 ⁇ 200
  • the primary winding of the transformer T s is a single turn coil
  • the secondary winding is a 100 turn coil
  • the core material of the transformer T s is the same as that of the transformers T 1 ( T 2 , and T 3
  • the PWM controller 11 receives an output voltage +FB of a converter, receives the sensing voltage SENSE that is generated by the input current, and thereby generates the switching signal SW out for turning the switching transistors Qi, Q 2 , and Q 3 on and off
  • the detailed structure thereof will be described with reference to FIG 3
  • a self-bias circuit for supplying an operating voltage V cc to an electronic element (see output amplifier 35 of FIG 3) for outputting the switching signal SW 0U , in the PWM controller 11 includes a primary feedback winding N FB of the transformer Ti and a diode D, A voltage induced in a primary feedback winding N FB of the transformer Ti is applied to a V cc terminal of the PWM controller 11 through the diode Di
  • the capacitor C ⁇ ⁇ is used to eliminate ripple Power is supplied to elements in the PWM controller 1 1 , except for the switching signal output unit in the PWM controller 11 , by the input voltage V ⁇ n
  • current l Pdc represents continuous current of a switching current signal, also referred to as DC current, and is differentiated from peak current l pp . That is, the heat loss of the transistor is calculated by a current value in which the peak current l pp is multiplied by 0 4.
  • Equation 8 the total heat loss P To tai oss due to three transistors is calculated by Equation 8.
  • the internal resistance of the transformer coils may be reduced by decreasing the number of turns in the switching transformer coils, and thickening the wire of the coils, thereby reducing heat loss due to resistance of coils
  • energy loss may be reduced by reducing the current flowing through the coils. It has been already described above how the current flowing through each transformer may be reduced by connecting the switching transistors to one another in parallel and by connecting each transformer to one transistor Thus, even though the coil resistance of each transformer is the same, heat loss may be reduced There is a case where the number of turns of the coil must be increased as the current flowing through the coil decreases In this case, the number of turns of the coil may be reduced by increasing the switching frequency
  • Inductance L p the number of turns N p and the size of a core of a primary coil of the switching transformer of the inverter may be expressed by Equations 9, 10, and 11
  • the switching transistors operate as a switching element for turning on or off in response to the switching signal SW 0Ut output from the PWM controller 1 1
  • the primary windings N p of the transformers T ⁇ T 2 , and T 3 are connected between the input DC voltage V, n and the transistors Q , Q 2 , and Q 3 , and thereby a high frequency square wave power signal is generated in the primary windings by turning the switching signal SW 0Ut on and off, and is supplied to the secondary windings of the transformers
  • the current feedback unit 13 senses the current flowing through the primary windings of the transformers Ti, T 2 , and T 3 according to the switching operation of the switching transistors Q ⁇ Q 2 , and Q 3 , and feeds back the sensed current signal into the PWM controller 11
  • the number of the transistors or transformers may be selected according to the number of outputs and rated power
  • the PWM controller 11 receives the output DC voltage signal +FB and controls the on and off duration of the switching signal SW 0Ut according to an error signal that is generated by comparing the output DC voltage signal +FB with the reference voltage, and a voltage level obtained from the operating current of the inverter 15 that is detected according to the variation in the input voltage V ⁇ n or the load by the current feedback unit 13, so that current amount flowing through the primary winding is controlled
  • the output rectifier 17 that is connected to the secondary windings of the transformers T1 , T2, and T3 and converts the square wave into a DC voltage is further provided, and thereby one or more predetermined voltages may be output
  • the output rectifier 17 may include one or more rectifying modules for generating an output voltage as a unit, and each rectifying module may be constituted according to the output voltage or rated power Examples of the rectifying modules are shown in drawings In addition, output modules may be connected in various forms to the plurality of transformers included in the inverter 15
  • the output rectifier 17 is connected to the secondary windings of the transformers T , T 2 , and T 3 That is, a first rectifying module 171 is connected to the secondary winding of the transformer Ti outputting a first output voltage V out1 , second and third rectifying modules 172 and
  • each of first through fourth rectifying modules 171 through 174 may be varied according to the rated output power
  • the output rectifier 17 may form an output voltage for each transformer, or an output voltage for at least two transformers, or at least two output voltages for one transformer
  • the first rectifying module 171 is an example illustrating a case where a transistor is used as a rectifying element
  • the second and third rectifying modules 172 and 173 are examples illustrating a case where diodes are used as rectifying elements
  • 174 is an example illustrating a case where output ports of two modules having the same structure as the first rectifying module 171 are connected to each other in parallel
  • the first rectifying module 171 includes rectifying transistors Q 6 and Q 7 that are turned on and off in response to the square wave signal transmitted from the transformer T a transformer T 5 in which current transmitted from the transformer T is charged and discharged according to the switching of the transistors Q 6 and Q 7 to generate an output voltage, and a capacitor C 0 ⁇
  • the first rectifying module 171 While the transistors Q 6 and Q 7 are alternately turned on and off in response to the switching signal transmitted to the secondary winding of the transformer T ⁇ , charge is charged and discharged in the transformer T 5 , generating the output voltage
  • the primary winding N 0 of the transformer T 5 is charged
  • the output voltage is generated from the charge in the primary winding N 0 of the transformer T 5
  • the secondary winding N s of the transformer T 5 is charged in
  • the transistor Q 6 is turned on and the transistor Q 7 is turned off
  • the output voltage is generated from the charge in the secondary winding N s of the transformer T 5
  • the continuous output voltage is obtained by repeating the above procedure
  • a snubber circuit is provided around the transistor Q 6
  • An RC element comprised of a resistor R s ⁇ and a capacitor C s ⁇ , is a first snubber circuit for preventing parasitic oscillation due to leakage inductance L ⁇ of the primary coil of the transformer T, and capacitance C G s between the gate and source of the transistor Q 6
  • An RC element comprised of a resistor R s2 and a capacitor C s2 , is a second snubber circuit for preventing oscillation that occurs between the leakage inductance L ⁇ of the primary coil of the transformer T and capacitance Coss between the drain and source of the transistor Q 6
  • a gate resistor R g is added to the gate terminal of the transistor Q 6 so that the rise time of the square wave transmitted from the transformer Ti matches the rise time of the transistor Q 6
  • One or both of the first and second snubber circuits may be included in the first rectifying module 171 In the
  • an output voltage may be obtained from charge in an inductor L o2 while diodes D 5 and D 6 are alternately turned on and off
  • diodes D 5 and D 6 are alternately turned on and off
  • the diode D 5 is turned on and the diode D 6 is turned off, and thereby, an inductor L 0 ⁇ is charged
  • the diode D 5 is turned off and the diode D 6 is turned on, and thereby, the inductor L 0 ⁇ is charged
  • Charge in the inductor L 01 is discharged by the capacitor C 0 ⁇ , thereby producing an output voltage
  • the fourth rectifying module 174 is an example illustrating a case where two of the first rectifying modules 171 are connected to the secondary winding of the transformer T 3 in parallel, and has a structure in which output terminals of two rectifying module M11 having the same structure are connected to each other in parallel, thereby allowing a larger output power to be obtained
  • the primary winding of the transformer T ⁇ T 2 , or T 3 includes an auxiliary winding N ⁇ with a primary winding N p
  • the auxiliary winding N ⁇ stores energy while the switching transistors Q,, Q 2 , and Q 3 are turned off and returns the stored energy to output when the transistors Qi, Q 2 , and Q 3 are turned on, thereby transmitting a down portion of a square wave, that is, the energy of the low level signal, to the output, and thus increasing an off signal level
  • the primary winding N p stores energy while the transistors Q ⁇ Q 2 , and Q 3 are turned on, thereby transmitting the stored energy to the output when the transistors Qi, Q
  • the function of the coils wound at first and second sides of the transformer J will be summarized as follows
  • the primary winding N p is connected between the positive terminal of the input voltage V ⁇ n and the drain terminal of the switching transistor, to store power and transmit the stored energy to the secondary coil
  • the auxiliary winding N ⁇ supplies energy to a filtering coil of an output terminal from a forward-type converter, and has the opposite polarity to the primary winding N p and the same number of turns as the primary winding N p
  • the feedback winding N FB supplies power to an output transistor that is used to generate the switching signal in the PWM controller 11
  • a first winding N G of the secondary coil supplies the square wave signal to the gate terminal of the transistor, which is a rectifying element having a synchronous rectifying method at an output port, and a second winding N s supplies a rectified DC voltage that is applied to the load of the output terminal
  • the thickness of the second winding N s is determined by the load current
  • the first winding N G of the secondary coil is calculated by Equation 17 according to a voltage V GS between a gate and a source, which is an input voltage level of the rectifying transistor
  • the second winding N s of the secondary coil has a close relation with the output voltage V out and is calculated by Equation 18
  • the value of a choke coil L 0 is calculated by Equation 19 according to the output voltage V out and an off time (off time of the switching transistor)
  • V x t I ⁇ — °Y- (19)
  • V AV 0 29 l on XY ⁇ ⁇ Y ⁇ Y (20)
  • the inductance of the choke coil L 0 is determined by the output voltage V ou t and the current, and the size of the core is determined by Equation 1 1
  • Equation 22 a parameter with respect to the primary winding N 01 of the transformer T 5 that is included in the first rectifying module 171 is obtained by Equations 20 and 21 , and the number of turns of the secondary winding N s1 is calculated by Equation 22
  • Capacitance of the filter capacitor C 0 that is connected to the output terminal is calculated by Equation 23
  • a negative output voltage may be obtained at an opposite polarity to that of the rectifying diode, such as a third output voltage V out3
  • FIG 2 illustrates the structure of the SMPS according to a second embodiment of the present invention, as an example of a flyback-type power supply
  • the SMPS according to the second embodiment of the present invention includes an input filter 20, a PWM controller 21 , an inverter 25, a current feedback unit 23, and an output rectifier 27
  • a plurality of switching transistors Q ⁇ Q 2 , and Q 3 and a plurality of transformers T ⁇ , T 2 , and T 3 for an inverter are controlled by the PWM controller 21 in order to increase efficiency and save energy
  • the overall structure is similar to that of the forward-type SMPS shown in FIG 1 , but there are differences in the structure of the transformers T ⁇ T 2 , and T 3 and the output rectifier.
  • the input filter 20, the PWM controller 21 , and the current feedback unit 23 have substantially the same functions as those of the input filter 10, the PWM controller 1 1 , and the current feedback unit 13 shown in FIG 1 , and the functions of the switching transistors Q T , Q 2 , and Q 3 are substantially the same as those of the switching transistors Q T , Q 2 , and Q 3 shown in FIG 1 , and thus a detailed description thereof will be omitted
  • FIG 2 illustrates a structure in which output terminals of the SMPS are connected to each other in parallel, to thereby generate an output voltage V out ⁇
  • an output voltage may be generated by an output module
  • two output modules may be connected to the secondary winding of one transformer
  • the current flowing through the transistors and the transformers may be reduced using a plurality of switching transistors and a plurality of transformers, thereby reducing the total power loss
  • the peak current flowing through the primary windings of the transistor and the transformer is expressed by Equation 24
  • the peak current in the circuit of FIG 2 is only about half the peak current in the circuit of FIG 1 , and thus, the inductance L p of the transformer is decreased and the size of the transformer core is reduced Thus, the circuit of FIG 2 is more economical, and needs less space than the circuit of FIG 1
  • Equation 26 The formula used in the circuit of FIG 1 is similarly used to determine the size of the core when designing the transformer Only the number of turns of the primary winding of the transformer is calculated by Equation 26
  • the output rectifier 27 includes a first output module 271 in which the two output modules 271 a and 271 b are connected to each other in parallel and which generates one output, and second and third output modules 273 and 274 that are connected to the secondary winding of the transformer T 3 , respectively While a transistor is used as a rectifying element of the first output module 271 , a diode is used as a rectifying element of the second or third output module 273 or 274
  • the connection of diodes in the second and third output modules 273 and 274 is different That is, the diode D 5 of the second output module 273 is connected to a terminal having no dotted mark of the secondary winding N G3 of the transformer T 3 , whereas the diode D 6 of the third output module 274 is connected to a terminal having a dotted mark of the secondary winding N G4 of the transformer T 3
  • the output V out3 of the second output module 273 may be a positive voltage
  • the output V ou t 4 of the third output module 274 may be a negative voltage
  • a plurality of diodes may be connected to one another in parallel, or a plurality of capacitors at an output terminal may be connected to one another in parallel, allowing diodes or capacitors having a lower rating to be used, and thus reducing the volume or price of the element
  • the first output module 271 includes an upper module 271 a and a lower module 271 b having substantially the same structure, and a positive (+) output terminal and a negative (-) output terminal of each module are connected to each other, thereby generating an output voltage
  • the upper module 271 a and the lower module 271 b are connected to the secondary windings of the transformers T, and T 2 , respectively, and thereby rectifying is performed by the transistors Q 5 and Q 6
  • a snubber circuit is included around each of the transistors Q 5 and Q 6
  • the function and design criteria of a first snubber circuit, comprised of a resistor RS T and a capacitor Cs ⁇ , and a second snubber circuit, comprised of a resistor Rs 2 and a capacitor Cs 2 are the same as those of the first and second snubber circuits shown in FIG 1
  • FIG 3 is an example of the structure of the PWM controller shown in FIG 1 or 2, and illustrates a current-mode controlling method
  • the voltage V cc that is induced by the feedback winding N FB of the primary winding of the transformer Ti supplies power to an amplifier 35 for outputting the switching signal SW out , and operating power is supplied to circuits such as a clock generator 33, a flip-flop 34, an error amplifier 31 , and a comparator 32, from the input voltage V ⁇ n that is applied through a regulator 37
  • the error amplifier 31 compares the output signal +FB with the reference voltage V ref to generate an error signal, and the error signal is input into the comparator 32
  • the sensing signal SENSE which is a voltage signal converted from the sensed output current of the inverter is input into the comparator 32
  • the comparator 32 compares the sensing signal SENSE due to the peak switching current with the error signal related to the output signal and inputs the comparison result signal SENSE into the RS flip-flop (latch) 34
  • the clock generator 33 generates a clock signal, which is a square wave signal corresponding to the switching frequency f s
  • the RS flip-flop 34 receives the output of the comparator 32 and the clock signal and generates the switching signal SW 0U , for turning on and off a switching element
  • the switching element (transistor) that is connected to the amplifier 35 is turned on and off by the switching signal SW 0U , according to its logic level
  • a main output voltage +FB that is fed back from the final output port is compared with the reference voltage V ref by the error amplifier 31 , and the current feedback signal SENSE is compared with a reference voltage (1 2V) by the comparator 32, and the comparison result is input into the flip-flop 34
  • the flip-flop 34 increases or decreases the phase (or width) of the clock signal that is generated in the oscillator 33 in response to an output signal of the comparator 32, that is, generates a pulse-width-modulated signal in which the duty cycle of the clock signal is varied, to generate the switching signal SW 0Ut , and thus increases or decreases the current flowing through the transformer Ti according to the variation in the input voltage and load, thereby maintaining a predetermined output voltage at the final output port
  • the current flowing in an inverter is dispersed into a plurality of paths and flows through a plurality of switching transistors and/or a plurality of transformers, thereby reducing power loss due to the transistors and/or transformers and allowing the use of smaller transformers Accordingly, the SMPS can operate stably even without a heat sink, and the total volume or size of the SMPS can be greatly reduced
  • the SMPS can be practically applied to power supplies for mobile phones, portable computers, electromotive toys, and electronic devices for cars

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Abstract

L'invention porte sur une alimentation en mode commuté limitant les pertes d'énergie comportant un générateur (11) de signaux de commutation d'un première fréquence; au moins deux commutateurs Q1, Q3 coupant ou rétablissement le fonctionnement en réponse au signal de commutation; des convertisseurs de puissance T1, T2 placés entre les commutateurs et l'alimentation c.c. et laissant passer ou bloquant le courant selon l'état des commutateurs de manièreà produire une onde carrée; et un redresseur (17) de sortie recevant l'onde carrée et émettant un courant c.a. Le courant traversant un convertisseur est dirigé via plusieurs canaux vers plusieurs transistors de commutation et/ou plusieurs transformateurs ce qui réduit les pertes d'énergie dues aux transistors et/ou aux transformateurs, et permet d'utiliser de petits transformateurs.
PCT/KR2001/002189 2000-12-18 2001-12-17 Alimentation en mode commute a fort rendement WO2002050987A1 (fr)

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AU2002216449A AU2002216449A1 (en) 2000-12-18 2001-12-17 Switching mode power supply with high efficiency

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KR10-2000-0077680A KR100387381B1 (ko) 2000-12-18 2000-12-18 고효율의 스위칭모드 전원공급장치
KR2000/77680 2000-12-18

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WO2006055598A1 (fr) * 2004-11-16 2006-05-26 Power Integrations, Inc. Procede et dispositif de fabrication et de realisation d'un transformateur
WO2024092953A1 (fr) * 2022-11-01 2024-05-10 深圳国爱全电化智慧科技有限公司 Circuit de rétroaction de courant et cuisinière électrique

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