WO1995031033A1 - Convertisseur continu/continu comprenant une chaine de retour a transfert de charge assurant une tres forte isolation - Google Patents

Convertisseur continu/continu comprenant une chaine de retour a transfert de charge assurant une tres forte isolation Download PDF

Info

Publication number
WO1995031033A1
WO1995031033A1 PCT/EP1995/001698 EP9501698W WO9531033A1 WO 1995031033 A1 WO1995031033 A1 WO 1995031033A1 EP 9501698 W EP9501698 W EP 9501698W WO 9531033 A1 WO9531033 A1 WO 9531033A1
Authority
WO
WIPO (PCT)
Prior art keywords
converter
capacitor
voltage
electronic switches
load
Prior art date
Application number
PCT/EP1995/001698
Other languages
English (en)
Inventor
Fabrizio Montauti
Renato Vai
Original Assignee
Italtel S.P.A.
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Italtel S.P.A. filed Critical Italtel S.P.A.
Priority to EP95919397A priority Critical patent/EP0759222A1/fr
Priority to AU25252/95A priority patent/AU2525295A/en
Publication of WO1995031033A1 publication Critical patent/WO1995031033A1/fr

Links

Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/337—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only in push-pull configuration
    • H02M3/3376—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only in push-pull configuration with automatic control of output voltage or current
    • H02M3/3378—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only in push-pull configuration with automatic control of output voltage or current in a push-pull configuration of the parallel type
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33507—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters
    • H02M3/33523—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters with galvanic isolation between input and output of both the power stage and the feedback loop

Definitions

  • DC/DC converter comprising a high-insulation charge-transfer feedback network
  • the present invention relates to the field of DC/DC converters and specifically to a DC/DC converter comprising a high-insulation charge-transfer feedback network.
  • Said circuits comprise essentially, (a) a presettable frequency oscillator from which are taken the waveforms useful for controlling electronic switches, (b) a constant temperature-stabilized reference voltage generator, c) an operational amplifier calculating the difference between the constant reference voltage and the voltage on the load obtaining an error signal, and d) a feedback network which, on the basis of the error signal, produces a modulation of the duration of the oscillator pulses to stabilize the voltage on the load.
  • a first known solution uses an auxiliary primary winding on the transformer connected to a bridge, and to a low-pass filter. At the output of the filter is a d.c. voltage whose level varies in proportion to the secondary voltage, and it can therefore be used for generation of the error signal.
  • the main shortcoming of this first solution is that if there is a variation in the direct junction voltage of the diodes which rectify the secondary current, or in the voltage at the terminals of any components in series with the load, the voltage on the load also varies without the feedback network detecting the variation, because the feedback network is sensitive only to the sum of these voltages.
  • a second known solution uses an optical coupler to transfer the voltage error to the rest of the feedback network.
  • the main shortcoming of this second solution is the fact that the optical coupler introduces a low-frequency pole in the closed-loop response, linked to the low operating speed of these components typically below 10kHz. Owing to the known stability criteria, it is advisable to have a converter loop-gain frequency response behaviour similar to that of a single-pole function. It is therefore necessary to neutralize the pole introduced by the optical coupler by means of the introduction in the feedback loop of a dominant-zero network, but this is difficult to implement for the following reasons: (a) the broad variability of the physical parameters found in optical coupler production batches, and (b) the strong dependence on temperature of the optical coupler pole frequency.
  • a practical way to compensate for the variability of type (a) above is to generate an error signal upstream of the optical coupler to force the feedback loop to activate the above mentioned compensation automatically. By so doing however, it is no longer possible to use the differential comparator and reference voltage generator in the integrated circuit controlling the converter, and it thus becomes necessary to use further electronic components. Contrary to what takes place for (a) above, it is difficult to compensate for the thermal effects mentioned under (b) above, and in any case the compensation introduced is only partial and not repetitive.
  • the basic problem solved by the optical coupler and which must be solved by any device or circuit replacing it, is to transfer a slowly varying voltage, like the error voltage, between two mutually decoupled points.
  • the decoupling stage described in the PCT patent transfers a voltage in an essentially discontinuous manner. Indeed, when one double switch is closed towards the main lines, the other is open and the load is not powered for the duration of a half-wave. This type of operation is not limiting in slow applications, such as for example in the case of igniting a lamp, but can be unacceptable if the duration of the closing of the switches can be very short in relation to their open time, as takes place in the context of the present invention.
  • the purpose of the present invention is to overcome all the above shortcomings and indicate a DC/DC converter comprising a high-insulation charge-transfer feedback network.
  • the object of the present invention is a DC/DC converter using a transformer to galvanically insulate the load from the primary power supply source, while ensuring said insulation along the feedback path also, thanks to a charge-transfer network inserted along said path.
  • the network consists essentially of two capacitors and two pairs of electronic switches provided by means of solid-state devices. A first pair of switches, when closed, connects a first capacitor in parallel to the load. The second pair connects the first capacitor in parallel to the second which has one end connected to the primary ground.
  • the two pairs of electronic switches are controlled by two respective periodic signals decoupled from each other through the transformer and corresponding to the signals used for the switching of two power transistors of the converter in a push-pull configuration.
  • each period of the control signals there succeed four phases in which: in a first phase the first capacitor is charged at the value of the voltage at the ends of the load; in a second phase the two pairs of switches are both open; in a third phase the charge of the first capacitor is partly transferred to the second; and in a fourth phase the two pairs of switches are still both open. At the ends of the second capacitor there is thus created a fraction of the load voltage even though the capacitor is insulated galvanically from the load as it is explained in claim 1.
  • the DC/DC converter which is the subject matter of the present invention exhibits the basic advantage of always ensuring perfect galvanic insulation between the load and the primary source.
  • insulation is achieved thanks to the use of enhancement MOSFETs in the charge-transfer network.
  • insulation is achieved thanks to the particular circuit structure of the charge-transfer network and to the use of control signals decoupled from each other by means of the transformer.
  • the use of optical couplers is thus entirely superfluous for control of the electronic switches.
  • the control signals are mutually phase by shifted one half period and have a duty cycle below 0.5, all possibility of simultaneous closing of the two switch pairs is eliminated due to the finite time taken by the active devices to change over from conduction to interdiction. Specifically, closing of a generic switch pair is always preceded and followed by phases in which both switch pairs are open.
  • a second advantage of the converter which is the subject matter of the present invention lies in its intrinsic stability due to the fact that the charge control network works at a frequency of about 120kHz, without introducing appreciable phase delay in the loop band, which is typically 12kHz wide. There is therefore no low-frequency pole to be neutralized and compensated thermally. It is also possible, given the invariance of the physical parameters of the charge-transfer network, to use the reference voltage and the differential comparator in the integrated circuit which controls the converter.
  • a third advantage is due to the fact that each switch is provided by means of two MOSFETs having their source connected to the respective substrates. The same channel current flows in the transistors, one in direct- and the other reverse- conduction. Consequently the diodes formed between the drain-substrate junctions are back-to-back connected. This ensures insulation even through the substrate.
  • FIG. 1 shows an indicative circuit diagram of the DC/DC converter which is the subject matter of the present invention wherein the charge- transfer network TRFC included in the feedback path is clearly shown.
  • the DC/DC converter of FIG. 1 comprises two power transistors TR1 and TR2 respectively connected between the two ends of the primary winding of a transformer TRS and a primary ground common to the negative terminal of a battery (not shown in the FIG.) supplying a continuous voltage ⁇ Vbat.
  • the positive terminal of the battery is connected to one end of an inductor Li whose other end is connected to a central tap of the TRS primary.
  • the latter divides the primary in two half-windings P1 and P2.
  • the central tap of the primary is also connected to one end of a capacitor Ci which has its other end connected to the primary ground.
  • the secondary of the transformer is also divided in two half-windings S1 and S2 by a central tap connected to a secondary ground galvanically insulated from the primary ground.
  • the two ends of S1 and S2 are respectively connected to the anodes of two diodes D1 and D2 whose cathodes are both connected to one end of and inductor Lo which has the other end connected to the output terminal of the DC/DC converter.
  • a capacitor Co is connected between the output terminal and the secondary ground, and in parallel with Co is visible a load resistance Ro at whose ends the continuous output voltage Vout is present.
  • the transformer TRS has another primary winding P3 which supplies a rectifier circuit RD, which supplies a d.c. voltage +V to an integrated circuit PWM which generates two signals indicated by Q(t) and Q(t+T/2) respectively, and applied to the control electrodes of the transistors TR1 and TR2.
  • the voltage +V is also used by converter protection circuits connected like PWM to the primary ground and not shown in the figure for the sake of simplicity.
  • an operational amplifier OP whose non-inverting input is connected to the cathode of a Zener diode Z (which diagrams a reference voltage generator), and whose inverting input is connected to the output of a charge-transfer network TRFC optionally through a potentiometric voltage divider not shown in the figure.
  • the anode of the Zener diode Z is connected internally to the primary ground and the cathode is connected to the power supply +V by means of circuits diagrammed with a resistance.
  • an error signal e used in the integrated circuit PWM to generate the signals Q(t) and Q(t+T/2).
  • the charge-transfer network TRFC consists of two integrated circuits IC1 and IC2, two capacitors C1 and C2 and two resistors R1 and R2.
  • Each integrated circuit IC1 and IC2 comprises four identical n-channel enhancement MOSFET transistors respectively indicated by 1 , 2, 3, 4 and 5, 6, 7, 8.
  • Use of the p-channel MOSFETs instead of n-channel MOSFETs does not change operation of the network. All the transistors have their substrate (type p) connected to the respective source.
  • IC1 and IC2 are also visible diodes (1 * 8') corresponding to those existing between the drain and the substrate of respective transistors.
  • the gates of the MOSFETs 1, 2, 3 and 4 are all connected together and to one end of the secondary S2 connected to the diode D2.
  • the gates of the MOSFETs 5, 6, 7 and 8 are all connected together and to one end of the primary winding P3.
  • the MOSFETs 1 and 2 have their sources connected together and the MOSFETs 3 and 4 have their drains connected together.
  • the MOSFETs 5 and 6 have their sources connected together as do the MOSFETs 7 and 8.
  • the resistance R1 is connected between the output terminal of the converter and the drain of the MOSFET 1.
  • the capacitor C1 has one end connected to the drains of the MOSFETs 2 and 5 and the other end connected to the drain electrode of the MOSFET 8 and the source of the MOSFET 3.
  • the source of the MOSFET 4 is connected to the secondary ground.
  • the capacitor C2 has one end connected to the drain of the MOSFET 6 while the other end of C2 is connected to the drain of the MOSFET 7 and to the primary ground.
  • the resistance R2 is connected in parallel with C2 and with the inverting input of the operational amplifier OP in the integrated circuit PWM.
  • the integrated circuit PWM of the example is UC1846 of UNITRODE but today there are many circuits capable of fulfilling equivalent functions.
  • these include an oscillator generating a periodic signal with presettable frequency from which are taken two identical pulsed periodic wave forms of period T, and phase-shifted with each other by T/2 which corresponds to the signals Q(t) and Q(t+T/2).
  • the width of the pulses is controlled in negative feedback on the basis of the error signal e with the restraint that it should always be less than T/2.
  • the UC1846 has a pin to act as described in the application notes thereof.
  • the error amplifier OP calculates the difference between the reference voltage present at the ends of the Zener diode Z which is reverse polarized and a fraction of the voltage Vout present at the ends of C2.
  • the network TRFC makes available the above mentioned fraction of Vout, without breaking the galvanic insulation existing between the primary side circuits and the secondary side circuits and between the respective grounds. This is made possible by the particular circuit configuration of TRFC together with the forms of the signals which control the MOSFETs of IC1 and IC2 and with the choice of suitable points for the application of control signals.
  • IC1 comprises a first pair of synchronous electronic switches of which one consists of the MOSFETs 1 and 2 and another of the MOSFETs 3 and 4.
  • IC2 comprises a second pair of synchronous electronic switches, of which one consists of the MOSFETs 5 and 6 and another of the MOSFETs 7 and 8.
  • a valid and more general alternative consists of connecting the control input of IC2 to an output of the integrated circuit PWM while keeping unchanged the connection between the control input of IC1 and the end of the secondary winding S2 which supplies the suitable signal.
  • the form of the control signals of IC1 and IC2 is that produced at the ends of the primary and secondary windings of the transformer TRS due to the switching effect of TR1 and TR2.
  • the voltages at the ends of P1 , P2, P3, S1 and S2 are pulses of the same width as those belonging to Q(t) and Q(t+T/2) but with polarities inverting every half-period T/2.
  • an active control pulse reaches IC1 producing closing of the respective switch pair, and connecting one end of C1 to the output terminal of the converter and the other end to the secondary ground.
  • C1 is charged at the value Vout through the resistance R1.
  • the control signal on IC2 is null and the switch pair IC2 is open and insulates C1 from the circuits connected to the primary of TRS.
  • the charge time constant R1C1 is small enough to allow complete charging of C1, even if the control pulse has minimal duration.
  • the two control signals are both null, and in this case
  • an active control pulse reaches IC2 producing closing of the respective switch pair and connecting C1 in parallel with C2 and allowing charge-transfer between C1 and C2.
  • the control signal on IC1 is null and the switch pair IC1 is open and insulates C1 and C2 from the secondary side circuits of TRS.
  • the charge-transfer takes place almost instantaneously and the duration is limited only by the very low channel resistance of the MOSFETs 5, 6, 7 and 8.
  • the parallel between the two capacitors remains for the entire duration of the active pulse, and during this time the charge accumulated in the two capacitors is discharged through R2 with a time constant given by the product of R2 times C1+C2.
  • a first requirement is that the time constants R1C1 and R2C2 be small so that the respective poles introduced in the frequency response of the system will fall far above the upper end of the loop band, which in the example is approximately 12 kHz. In this manner their existence does not disturb the stability of the converter. In practice, considering the Bode diagram of the loop gain, it is sufficient that these poles be at least one decade higher than the band end.
  • a second requirement is that the voltage Vout on C1 be not reduced too much on the parallel of C1 with C2, and this limits the value of C2. This value should however always be greater than that of C1 to cause the charge to be accumulated predominantly on C2 after completion of the transfer.
  • C2 can act as a "memory" when the connection with C1 is broken before completion of the discharge, and this occurs when the duration of the control pulses of IC2 is minimal.
  • the value of R2 should be such as to not allow a too fast discharge of the capacitor equivalent of the parallel C1 and C2, or of only C2 compatibly with the period T, because otherwise there would derive therefrom an error signal consisting of narrow pulses. In this case the energy would fall predominantly on the components placed outside the loop band.
  • the remarks made for the DC/DC converter of the example are also applicable for circuit configurations other than push-pull, provided they include a transformer to insulate the load from the primary power supply source.
  • Configurations comprising a single power transistor have primary and secondary voltages in which the pulse in the half period fails.
  • the fact causes no particular problem concerning control of the TRFC network since it is only necessary to connect the control input of IC2 directly to the control output of PWM which does not pilot the power transistor, while for control of IC1 the signal is taken at the secondary as in the example.
  • Devices different from those indicated can be used as electronic switches and the remarks made are in all cases sufficient for one of ordinary skill in the art to seek the wave form each time most suitable for control of the charge-transfer network using the selected devices.

Landscapes

  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)
  • Semiconductor Integrated Circuits (AREA)

Abstract

Convertisseur continu/continu dans lequel on utilise un transformateur afin d'isoler de façon galvanique la charge provenant de la première source d'alimentation, de manière à assurer l'isolation même le long du circuit de contre-réaction, grâce à l'insertion d'une chaîne de retour à transfert de charge le long de ce circuit. Cette chaîne de retour est essentiellement composée de deux condensateurs (C1 et C2) ainsi que de deux paires de commutateurs électroniques synchrones (IC1 et IC2) pourvus de transistors à effet de champ MOS. Lorsque la paire IC1 est fermée, elle connecte C1 en parallèle avec la charge Ro, tandis que lorsque la paire IC2 est fermée, elle connecte C1 en parallèle avec C2, qui possède une extrémité connectée à la première mise à la masse. Les paires IC1 et IC2 sont commandées par deux signaux périodiques respectifs, mutuellement découplés à travers le transformateur, correspondant aux signaux utilisés pour commuter les deux transistors d'alimentation du convertisseur dans une configuration symétrique.
PCT/EP1995/001698 1994-05-10 1995-05-04 Convertisseur continu/continu comprenant une chaine de retour a transfert de charge assurant une tres forte isolation WO1995031033A1 (fr)

Priority Applications (2)

Application Number Priority Date Filing Date Title
EP95919397A EP0759222A1 (fr) 1994-05-10 1995-05-04 Convertisseur continu/continu comprenant une chaine de retour a transfert de charge assurant une tres forte isolation
AU25252/95A AU2525295A (en) 1994-05-10 1995-05-04 Dc/dc converter comprising a high-insulation charge-transfer feedback network

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
ITMI940917A IT1269736B (it) 1994-05-10 1994-05-10 Convertitore dc/dc comprendente una rete di retroazione a trasferimento di carica ad alto isolamento
ITMI94A000917 1994-05-10

Publications (1)

Publication Number Publication Date
WO1995031033A1 true WO1995031033A1 (fr) 1995-11-16

Family

ID=11368868

Family Applications (1)

Application Number Title Priority Date Filing Date
PCT/EP1995/001698 WO1995031033A1 (fr) 1994-05-10 1995-05-04 Convertisseur continu/continu comprenant une chaine de retour a transfert de charge assurant une tres forte isolation

Country Status (6)

Country Link
EP (1) EP0759222A1 (fr)
CN (1) CN1152374A (fr)
AU (1) AU2525295A (fr)
IT (1) IT1269736B (fr)
WO (1) WO1995031033A1 (fr)
ZA (1) ZA953675B (fr)

Cited By (8)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO1999031790A1 (fr) * 1997-12-16 1999-06-24 Volterra Semiconductor Corporation Echantillonnage de donnees en temps discret pour regulateurs de commutation
US6100676A (en) * 1998-10-30 2000-08-08 Volterra Semiconductor Corporation Method and apparatus for digital voltage regulation
US6160441A (en) * 1998-10-30 2000-12-12 Volterra Semiconductor Corporation Sensors for measuring current passing through a load
US6198261B1 (en) 1998-10-30 2001-03-06 Volterra Semiconductor Corporation Method and apparatus for control of a power transistor in a digital voltage regulator
US6268716B1 (en) 1998-10-30 2001-07-31 Volterra Semiconductor Corporation Digital voltage regulator using current control
CN1314190C (zh) * 2001-11-29 2007-05-02 Lg电子株式会社 等离子显示板的持续脉冲发生器
EP2601667A1 (fr) * 2010-08-02 2013-06-12 Compagnie Generale Des Etablissements Michelin Dispositif de connexion d'une batterie à un véhicule électrique ou hybride, et coffre à batterie comprenant ledit dispositif de connexion.
US8933520B1 (en) 2007-12-27 2015-01-13 Volterra Semiconductor LLC Conductive routings in integrated circuits using under bump metallization

Families Citing this family (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN100361190C (zh) * 2004-10-11 2008-01-09 南京Lg同创彩色显示系统有限责任公司 显示器的电源电路
US7245510B2 (en) * 2005-07-07 2007-07-17 Power Integrations, Inc. Method and apparatus for conditional response to a fault condition in a switching power supply
US7746674B2 (en) * 2007-02-22 2010-06-29 Leader Electronics Inc. Self-oscillating power converter
CN102624236A (zh) * 2011-01-26 2012-08-01 陈冠豪 车用大功率dc/dc驱动电源及驱动方法
US10277141B2 (en) * 2016-09-15 2019-04-30 Psemi Corporation Current protected integrated transformer driver for isolating a DC-DC convertor

Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO1987003150A1 (fr) * 1985-11-19 1987-05-21 Motorola, Inc. Alimentation en retour
EP0484610A1 (fr) * 1990-11-08 1992-05-13 BULL HN INFORMATION SYSTEMS ITALIA S.p.A. Alimentation à découpage en courant continu avec tension de sortie contrôlée et isolation entre sortie et entrée
EP0547916A2 (fr) * 1991-12-18 1993-06-23 Texas Instruments Incorporated Circuit de contrôle d'un régulateur de tension

Patent Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO1987003150A1 (fr) * 1985-11-19 1987-05-21 Motorola, Inc. Alimentation en retour
EP0484610A1 (fr) * 1990-11-08 1992-05-13 BULL HN INFORMATION SYSTEMS ITALIA S.p.A. Alimentation à découpage en courant continu avec tension de sortie contrôlée et isolation entre sortie et entrée
EP0547916A2 (fr) * 1991-12-18 1993-06-23 Texas Instruments Incorporated Circuit de contrôle d'un régulateur de tension

Cited By (13)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US6225795B1 (en) 1997-12-16 2001-05-01 Volterra Semiconductor Corporation Discrete-time sampling of data for use in switching regulations
US6020729A (en) * 1997-12-16 2000-02-01 Volterra Semiconductor Corporation Discrete-time sampling of data for use in switching regulators
WO1999031790A1 (fr) * 1997-12-16 1999-06-24 Volterra Semiconductor Corporation Echantillonnage de donnees en temps discret pour regulateurs de commutation
US6268716B1 (en) 1998-10-30 2001-07-31 Volterra Semiconductor Corporation Digital voltage regulator using current control
US6198261B1 (en) 1998-10-30 2001-03-06 Volterra Semiconductor Corporation Method and apparatus for control of a power transistor in a digital voltage regulator
US6160441A (en) * 1998-10-30 2000-12-12 Volterra Semiconductor Corporation Sensors for measuring current passing through a load
US6100676A (en) * 1998-10-30 2000-08-08 Volterra Semiconductor Corporation Method and apparatus for digital voltage regulation
US6445244B1 (en) 1998-10-30 2002-09-03 Volterra Semiconductor Corporation Current measuring methods
US6590369B2 (en) * 1998-10-30 2003-07-08 Volterra Semiconductor Corporation Digital voltage regulator using current control
CN1314190C (zh) * 2001-11-29 2007-05-02 Lg电子株式会社 等离子显示板的持续脉冲发生器
US8933520B1 (en) 2007-12-27 2015-01-13 Volterra Semiconductor LLC Conductive routings in integrated circuits using under bump metallization
EP2601667A1 (fr) * 2010-08-02 2013-06-12 Compagnie Generale Des Etablissements Michelin Dispositif de connexion d'une batterie à un véhicule électrique ou hybride, et coffre à batterie comprenant ledit dispositif de connexion.
US9461454B2 (en) 2010-08-02 2016-10-04 Compagnie Generale Des Establissements Michelin Device for connecting a battery to an electric or hybrid vehicle, and battery housing comprising said connection device

Also Published As

Publication number Publication date
ITMI940917A0 (it) 1994-05-10
AU2525295A (en) 1995-11-29
ITMI940917A1 (it) 1995-11-10
IT1269736B (it) 1997-04-15
CN1152374A (zh) 1997-06-18
EP0759222A1 (fr) 1997-02-26
ZA953675B (en) 1996-01-12

Similar Documents

Publication Publication Date Title
KR100707763B1 (ko) 2차 펄스폭 변조 제어를 가지는 플라이백 컨버터를 위한시동 회로
US5099410A (en) Single phase ac power conversion apparatus
EP0188839B1 (fr) Dispositif d'alimentation en auto-oscillation
US7123490B2 (en) Synchronous rectifying switching power source circuit
EP0759222A1 (fr) Convertisseur continu/continu comprenant une chaine de retour a transfert de charge assurant une tres forte isolation
KR0147051B1 (ko) 전원회로
JP2000278945A (ja) スイッチング電源装置
EP1034614B1 (fr) Convertisseur de frequence et alimentation electrique sans coupure
US6462966B1 (en) Power supply circuit and method
KR20050050674A (ko) 용량성 연결된 전원 공급기
JPH11113254A (ja) スイッチング電源、及び二次巻線の電圧整流方法
JP2888729B2 (ja) 出力短絡保護回路
US20140098571A1 (en) Saturation prevention in an energy transfer element of a power converter
JPH11299092A (ja) 電源供給アダプタ
Mweene The design of front-end dc-dc converters of distributed power supply systems with improved efficiency and stability
FI94686C (fi) Jännitteenmittauspiiri
JP2003259639A (ja) スイッチング電源装置
US20090251928A1 (en) Switching power supply circuit
KR100394660B1 (ko) 전기 자동차 배터리의 충전 회로
JPH0320046Y2 (fr)
FI113916B (fi) Tasasuuntauksen ohjauskytkentä
RU2094936C1 (ru) Преобразователь постоянного напряжения в постоянное
JP4304743B2 (ja) 補助電源なしでオンオフ制御を可能にするスイッチング電源装置
RU2043695C1 (ru) Импульсный источник вторичного электропитания
JPH07236272A (ja) 電源装置

Legal Events

Date Code Title Description
WWE Wipo information: entry into national phase

Ref document number: 95194018.X

Country of ref document: CN

AK Designated states

Kind code of ref document: A1

Designated state(s): AU BR CN FI JP KR NO US

AL Designated countries for regional patents

Kind code of ref document: A1

Designated state(s): AT BE CH DE DK ES FR GB GR IE IT LU MC NL PT SE

DFPE Request for preliminary examination filed prior to expiration of 19th month from priority date (pct application filed before 20040101)
121 Ep: the epo has been informed by wipo that ep was designated in this application
WWE Wipo information: entry into national phase

Ref document number: 1995919397

Country of ref document: EP

WWP Wipo information: published in national office

Ref document number: 1995919397

Country of ref document: EP

WWR Wipo information: refused in national office

Ref document number: 1995919397

Country of ref document: EP

WWW Wipo information: withdrawn in national office

Ref document number: 1995919397

Country of ref document: EP