WO1995008862A1 - Procede et systeme de commutation pour la mise en service d'une alimentation - Google Patents

Procede et systeme de commutation pour la mise en service d'une alimentation Download PDF

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Publication number
WO1995008862A1
WO1995008862A1 PCT/FI1994/000422 FI9400422W WO9508862A1 WO 1995008862 A1 WO1995008862 A1 WO 1995008862A1 FI 9400422 W FI9400422 W FI 9400422W WO 9508862 A1 WO9508862 A1 WO 9508862A1
Authority
WO
WIPO (PCT)
Prior art keywords
constant
input
circuit
voltage
load
Prior art date
Application number
PCT/FI1994/000422
Other languages
English (en)
Inventor
Matti Havukainen
Original Assignee
Nokia Telecommunications Oy
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Nokia Telecommunications Oy filed Critical Nokia Telecommunications Oy
Priority to GB9606136A priority Critical patent/GB2297874B/en
Priority to DE4497069T priority patent/DE4497069T1/de
Priority to AU76993/94A priority patent/AU7699394A/en
Publication of WO1995008862A1 publication Critical patent/WO1995008862A1/fr

Links

Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/36—Means for starting or stopping converters
    • G—PHYSICS
    • G05—CONTROLLING; REGULATING
    • G05F—SYSTEMS FOR REGULATING ELECTRIC OR MAGNETIC VARIABLES
    • G05F1/00—Automatic systems in which deviations of an electric quantity from one or more predetermined values are detected at the output of the system and fed back to a device within the system to restore the detected quantity to its predetermined value or values, i.e. retroactive systems
    • G05F1/10—Regulating voltage or current
    • G05F1/46—Regulating voltage or current wherein the variable actually regulated by the final control device is dc
    • G05F1/56—Regulating voltage or current wherein the variable actually regulated by the final control device is dc using semiconductor devices in series with the load as final control devices
    • G05F1/565—Regulating voltage or current wherein the variable actually regulated by the final control device is dc using semiconductor devices in series with the load as final control devices sensing a condition of the system or its load in addition to means responsive to deviations in the output of the system, e.g. current, voltage, power factor
    • G05F1/569—Regulating voltage or current wherein the variable actually regulated by the final control device is dc using semiconductor devices in series with the load as final control devices sensing a condition of the system or its load in addition to means responsive to deviations in the output of the system, e.g. current, voltage, power factor for protection
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02H—EMERGENCY PROTECTIVE CIRCUIT ARRANGEMENTS
    • H02H9/00—Emergency protective circuit arrangements for limiting excess current or voltage without disconnection
    • H02H9/001—Emergency protective circuit arrangements for limiting excess current or voltage without disconnection limiting speed of change of electric quantities, e.g. soft switching on or off

Definitions

  • the invention relates to a method according to the preamble of the appended claim 1 and a circuit arrangement according to the preamble of the appended claim 4, for switching on an electric load, in particular a power supply.
  • the purpose of the method and the device according to the invention is to limit the starting current supplied to the load at the start-up.
  • the method and the circuit arrangement according to the invention are intended for use in particular in power supplies for telecommunication devices, which convert a direct voltage supplied by a battery or some other corresponding direct voltage source to a stabilized form by means of, for example, a switched-mode power supply.
  • the input terminals of the power supply comprise one or more input capacitors.
  • NTC resistor NTC resistor
  • PTC resistor PTC resistor
  • US Patent 4,678,984 discloses a circuit arrangement limiting a power supply current, the arrangement having three operating modes: inrush mode, normal mode and overcurrent mode.
  • inrush mode where the voltage controlling the gate of a FET on the current path between the input voltage supply and the power supply is gradually increased.
  • the control voltage has exceeded its threshold value, a current begins to flow between the voltage supply and the power supply, and when the control voltage reaches its normal-mode value, a transition from the inrush mode to the normal mode occurs.
  • the purpose of the present invention is to eliminate the above disadvantages and to provide a solution which makes it possible to start a power supply in a controlled and safe manner by means of simple equipment.
  • This is achieved by means of a method according to the invention, which is characterized by what is described in the characterizing portion of the appended claim 1.
  • a circuit arrangement according to the invention is characterized by what is described in the characterizing portion of the appended claim 4.
  • the idea of the invention is to derive information about the charging of input capacitor(s) from a change caused in the constant-current generator circuit by a drop in the charging current, and to utilize this change to effect the actual switching on of the load, i.e. the transition to normal mode.
  • Figure 1 is a block diagram of a circuit arrangement according to the invention
  • Figure 2 represents one possible implementation of the constant-current generator circuit shown in Figure 1
  • FIGS 3a to 3f illustrate voltages/currents occurring in the circuit arrangement shown in Figure 1,
  • FIG 4 is a more detailed representation of the time-constant circuit shown in Figure 1, and
  • Figure 5 shows a voltage limit circuit added to the constant-current generator circuit.
  • Figure 1 shows a functional block diagram of a circuit arrangement according to the invention, which operates as a current limit circuit when a power supply 107 is being started, the power supply being typically a switched-mode power supply, used widely at present due to their advantages, which include for example a high efficiency, a wide input voltage range and a possibility to implement compact and light power supplies.
  • switched-mode power supplies utilize flyback topology more and more often (topology refers to the circuit configuration which determines how power is transferred in a power supply).
  • topology refers to the circuit configuration which determines how power is transferred in a power supply.
  • the greatest advantage of a flyback-type power supply is its simple and inexpensive structure, which is also applicable in multiple-output power supplies.
  • the operating voltages required by the circuit are formed in an operating voltage unit 101 from a direct voltage Uac (supplied e.g. from a battery) used as the input voltage.
  • An over/undervoltage unit 102 which is also connected between the battery voltage terminals, checks by means of a comparator whether the input voltage Uac is within an allowable range.
  • the over/undervoltage unit 102 controls a time-constant circuit 105 through its outputs Uu and Uo, and a time- delay circuit 103 through its output Uo.
  • a control signal is obtained at the output Uo if the input voltage is too high and at the output Uu if the input voltage is higher than the minimum input voltage.
  • the output Uu is connected to a starting input S in the time-constant circuit, and the output Uo is connected to the first resetting input R in the time-constant circuit and to a starting input S in the time-delay circuit.
  • a starting signal is generated from the outputs Uu and Uo to the time-constant circuit 105, when the input voltage is within its allowable range.
  • the output Uo controls the power supply by means of the time-delay circuit 103 so that it will be switched off in overvoltage situations.
  • the first control output Uk of the time- constant circuit 105 is connected to the first input II in a constant-current generator circuit 108 via a parallel connection formed by a resistor Rl and a capacitor Cl.
  • the second control output Up of the time- constant circuit 105 is connected to the second input 12 of the constant-current generator circuit 108 via a resistor R2.
  • the time-constant circuit supplies the control voltage Uk of the inrush mode, through its first output, to the constant-current generator circuit 108, and correspondingly it supplies the control voltage Up of the normal mode (continuous mode), through its second control output, to said constant-current generator circuit (in this connection, the outputs and their signals are denoted by the same reference symbols).
  • the control voltage Up of the normal mode is zero, so the constant- current generator circuit is controlled during the inrush mode solely by means of the control voltage Uk.
  • the control voltage Uk is zero, so that the constant-current generator circuit is controlled solely by means of the control voltage Up.
  • the output Uv of the constant-current generator circuit is connected to the first input of the voltage comparator 106, and the input of the constant-current generator circuit, the voltage of which is denoted by Ukk, is connected to the second input of the comparator.
  • the output of the comparator is connected to the second resetting input R of the .time-constant circuit to reset the time-constant circuit as soon as information about the charging of the input capacitor Cin, connected across the input terminals of the power supply 107, is obtained from the constant-current generator circuit.
  • the output of the time-delay circuit 103 is connected to the resetting input R of a separate starting block 104.
  • the actual start-up of the power supply 107 i.e. the transition from the inrush mode to the normal mode, is achieved by means of the starting block 104.
  • the output Up of the time- constant circuit 105 is connected to the starting input S of the starting block 104.
  • FIG. 2 shows in greater detail one way known per se for implementing the constant-current generator circuit 108.
  • Both inputs II and 12 are connected to the non-inverted input of a differential amplifier 201.
  • the output of the differential amplifier is connected to the gate of a power transistor SW.
  • the transistor can be, for example, a power MOSFET (as shown in the figure) or any other corresponding switching element where the resistance can be adjusted by means of voltage control.
  • the drain electrode of the FET SW is connected to one terminal of the input capacitor Cin, and its source electrode is correspondingly connected through a resistor Rm to the negative pole of the input voltage Uac.
  • the other terminal of the input capacitor Cin is connected to the positive pole of the input voltage.
  • a voltage proportional to the charging current Ic is obtained from the resistor Rm to the inverted input of the differential amplifier 201.
  • the charging current Ic increases to a certain constant value ( Figure 3d), and the input capacitor Cin begins to be charged (the value of the "constant current" is determined by the resistor Rl and the capacitor Cl) .
  • the effect of the capacitor Cl is described in Figures 3d to 3f by a broken line.
  • the charging current Ic begins to decrease and then the voltage difference in the inputs of the differential amplifier 201 and also the output voltage Uv of the differential amplifier increase ( Figure 3e).
  • the differential amplifier thus aims at maintaining the constant current by controlling the resistance between the drain and source electrodes of the FET so that the resistance decreases.
  • the control voltage Uv remains lower than the control voltage Ukk, whereupon the operation is interrupted after a period (e.g. 1,000 ms) determined by the time-constant circuit.
  • the starting block 104 receives a starting pulse, whereupon it starts the power supply. This can take place by means of for example a relay or the like provided in the starting block, which provides information about the starting to the power supply.
  • the time-constant circuit 105 will not start up until the input voltage Uac is within its allowable range. If overvoltages occur in the normal mode, the power supply is switched off after a period (e.g. 10 ms) determined by the time-delay circuit 103, by resetting the starting block 104. The operation again returns to normal after the overvoltage has disappeared. If the input voltage Uac decreases below its lowest allowable value, the power supply is switched off. The operation again begins with the above described charging phase after the input voltage Uac has exceeded its lowest allowable value (min, Figure 3a).
  • FIG. 4 shows more closely a more detailed implementation of the time-constant circuit 105.
  • the circuit comprises in its input an AND gate 401, to which the over and undervoltage information Uo and Uu, respectively, from the over/undervoltage unit 102 is connected; and a resetting circuit 402, to the inputs of which the undervoltage information Uu and the operating voltage information DV (the DV is the voltage pulse occurring at the moment of switching on the operating voltage Uac) is connected.
  • the input voltage Uac is within its allowable range, both input signals (Uo and Uu) of the AND gate have the logic value "true” (logical one), whereupon the output of the AND gate also has the value "true”. This value is stored in a memory 403.
  • the output of the memory starts a pulse circuit 404, which supplies a pulse (control voltage Uk) the length of which determines the duration of the inrush mode.
  • a pulse control voltage Uk
  • Uk control voltage
  • the comparator 106 applies a control pulse to the resetting input R of the pulse circuit 404, the control voltage drops to the logical zero level, but the output of the AND gate 405 has time enough to rise to a logical one.
  • This value is stored in the memory 406, the output of which supplies the control signal Up of the continuous mode. A transition in the circuit from the charging phase mode to the normal mode occurs thus, after the comparator 106 has detected that the input capacitor Cin is charged.
  • the memories are needed in the circuit, so that random disturbance peaks would not influence the operation of the circuit, but the control would remain at the desired value for a desired period of time.
  • the output of the memory 406 can be connected in the starting block for example to one input of an AND gate (not shown here) .
  • an AND gate (not shown here)
  • a signal starting the power supply is obtained from the output of the AND gate.
  • the memories and the pulse circuit are reset, by means of the resetting circuit 402, whenever (a) the input voltage is switched on (signal DV) or (b) the input voltage is too low (signal Uu).
  • the constant-current generator circuit 108 can also be utilized as a current limiter after the inrush mode during the normal mode, and it is also possible to add a voltage limit circuit to the constant-current generator circuit in a simple manner.
  • Figure 5 shows one alternative way of implementing the voltage limit function. In this case another differential amplifier 501 is added to the circuit, the output of the amplifier controlling the gate of the FET through a diode Dl in the same way as the differential amplifier 201 controls the gate of the FET through the resistor R6.
  • the diode Dl prevents the current control provided by means of the differential amplifier 201 and the voltage control provided by the differential amplifier 501 from interfering with each other.
  • a zener diode Zl and a resistor R3 are connected in series between the terminals of the input voltage Uac.
  • a reference voltage Vref is supplied from their common terminal to the inverted input of the differential amplifier 501.
  • the voltage Ul acting across the input terminals (and the input capacitor) of the power supply is sampled to the non-inverted input of the differential amplifier by means of the voltage divider resistors R4 and R5. If the voltage Ul acting across the power supply exceeds its allowable value, the differential amplifier 501 reduces the control voltage of the FET by increasing the resistance of the current path between the drain and source electrodes of the FET.
  • the constant- current generator circuit provides, by means of the comparator 106, information indicating when the input capacitor is fully charged and a transition to the normal mode is possible.
  • the control voltage Uv which is affected by a drop in the charging current.
  • the constant-current generator circuit used here is known per se, but it is utilized according to the invention in a new manner.

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  • Engineering & Computer Science (AREA)
  • Physics & Mathematics (AREA)
  • Electromagnetism (AREA)
  • General Physics & Mathematics (AREA)
  • Radar, Positioning & Navigation (AREA)
  • Automation & Control Theory (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)
  • Direct Current Feeding And Distribution (AREA)

Abstract

L'invention concerne un procédé et un système de commutation d'une charge électrique, en particulier d'une alimentation. La charge est alimentée par une source de tension fournissant une tension d'entrée (Uac), un condensateur d'entrée (Cin) étant connecté aux bornes d'entrée de la charge (107). Dans le procédé selon l'invention, (a) lorsque la tension d'entrée (Uac) est débloquée, le fonctionnement se fait en mode d'appel de courant dans lequel le condensateur d'entrée (Cin) commence à être chargé au moyen d'un courant de charge (Ic) fourni par un circuit générateur de courant constant (108), lorsque la tension d'entrée (Uac) a dépassé sa valeur minimum; et (b) une fois le condensateur d'entrée chargé (Cin), une transition vers le mode continu suivant la mise en service se produit. Afin de permettre la mise sous tension de la charge en toute sécurité au moyen d'équipements aussi simples que possible, des informations sur la charge du condensateur d'entrée (Cin) sont dérivées d'un changement induit dans le circuit générateur de courant constant par une chute de courant de charge.
PCT/FI1994/000422 1993-09-22 1994-09-21 Procede et systeme de commutation pour la mise en service d'une alimentation WO1995008862A1 (fr)

Priority Applications (3)

Application Number Priority Date Filing Date Title
GB9606136A GB2297874B (en) 1993-09-22 1994-09-21 Method and circuit arrangement for switching on an electric load
DE4497069T DE4497069T1 (de) 1993-09-22 1994-09-21 Methode und Schaltungsanordnung für das Einschalten eines Stromversorgungsgerätes
AU76993/94A AU7699394A (en) 1993-09-22 1994-09-21 Method and switching arrangement for starting a power supply

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
FI934158 1993-09-22
FI934158A FI94195C (fi) 1993-09-22 1993-09-22 Menetelmä ja kytkentäjärjestely teholähteen käynnistämiseksi

Publications (1)

Publication Number Publication Date
WO1995008862A1 true WO1995008862A1 (fr) 1995-03-30

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ID=8538639

Family Applications (1)

Application Number Title Priority Date Filing Date
PCT/FI1994/000422 WO1995008862A1 (fr) 1993-09-22 1994-09-21 Procede et systeme de commutation pour la mise en service d'une alimentation

Country Status (5)

Country Link
AU (1) AU7699394A (fr)
DE (1) DE4497069T1 (fr)
FI (1) FI94195C (fr)
GB (1) GB2297874B (fr)
WO (1) WO1995008862A1 (fr)

Cited By (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE29519343U1 (de) * 1995-12-05 1997-01-16 Siemens AG, 80333 München Stromversorgung mit verlustarmer Einschaltstrombegrenzung
CN1043393C (zh) * 1995-08-11 1999-05-12 三星电子株式会社 用于防止电动机过流的方法和装置
US6094036A (en) * 1995-12-05 2000-07-25 Siemens Aktiengesellschaft Electrical power supply with low-loss inrush current limiter and step-up converter circuit
EP1162723A1 (fr) * 2000-06-08 2001-12-12 STMicroelectronics S.r.l. Générateur de courant avec protection thermique
CN103738139A (zh) * 2013-12-21 2014-04-23 博耐尔汽车电气系统有限公司 一种过压保护的汽车空调风量控制系统

Families Citing this family (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN111200355B (zh) * 2018-11-19 2021-04-09 上海微电子装备（集团）股份有限公司 上电缓冲电路

Citations (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US4678984A (en) * 1986-04-21 1987-07-07 Sperry Corporation Digital power converter input current control circuit
US5124630A (en) * 1990-07-30 1992-06-23 Nec Corporation Switching power supply apparatus

Patent Citations (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US4678984A (en) * 1986-04-21 1987-07-07 Sperry Corporation Digital power converter input current control circuit
US5124630A (en) * 1990-07-30 1992-06-23 Nec Corporation Switching power supply apparatus

Cited By (7)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN1043393C (zh) * 1995-08-11 1999-05-12 三星电子株式会社 用于防止电动机过流的方法和装置
DE29519343U1 (de) * 1995-12-05 1997-01-16 Siemens AG, 80333 München Stromversorgung mit verlustarmer Einschaltstrombegrenzung
US6094036A (en) * 1995-12-05 2000-07-25 Siemens Aktiengesellschaft Electrical power supply with low-loss inrush current limiter and step-up converter circuit
EP1162723A1 (fr) * 2000-06-08 2001-12-12 STMicroelectronics S.r.l. Générateur de courant avec protection thermique
US6552518B2 (en) 2000-06-08 2003-04-22 Stmicroelectronics S.R.L. Current generator with thermal protection
CN103738139A (zh) * 2013-12-21 2014-04-23 博耐尔汽车电气系统有限公司 一种过压保护的汽车空调风量控制系统
CN103738139B (zh) * 2013-12-21 2016-03-16 博耐尔汽车电气系统有限公司 一种过压保护的汽车空调风量控制系统

Also Published As

Publication number Publication date
FI934158A0 (fi) 1993-09-22
GB9606136D0 (en) 1996-05-22
GB2297874B (en) 1998-04-15
DE4497069T1 (de) 1996-10-31
GB2297874A (en) 1996-08-14
FI94195C (fi) 1995-07-25
AU7699394A (en) 1995-04-10
FI94195B (fi) 1995-04-13

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