WO1992022953A1 - Alimentation electrique - Google Patents

Alimentation electrique Download PDF

Info

Publication number
WO1992022953A1
WO1992022953A1 PCT/AU1992/000293 AU9200293W WO9222953A1 WO 1992022953 A1 WO1992022953 A1 WO 1992022953A1 AU 9200293 W AU9200293 W AU 9200293W WO 9222953 A1 WO9222953 A1 WO 9222953A1
Authority
WO
WIPO (PCT)
Prior art keywords
power supply
load
bank
circuit
capacitive impedance
Prior art date
Application number
PCT/AU1992/000293
Other languages
English (en)
Inventor
Michael Bruce Dwyer
David Scott Whitby
Original Assignee
Golden Power Electronics Pty. Ltd.
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Golden Power Electronics Pty. Ltd. filed Critical Golden Power Electronics Pty. Ltd.
Publication of WO1992022953A1 publication Critical patent/WO1992022953A1/fr

Links

Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
    • H02M1/4208—Arrangements for improving power factor of AC input
    • H02M1/4266—Arrangements for improving power factor of AC input using passive elements
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
    • H05B41/14—Circuit arrangements
    • H05B41/16—Circuit arrangements in which the lamp is fed by dc or by low-frequency ac, e.g. by 50 cycles/sec ac, or with network frequencies
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Definitions

  • This invention relates to a power supply for an electrical circuit.
  • the invention has been developed to address problems that have become apparent with large scale usage of compact fluorescent lamps of the type that incorporate so-called electronic ballasts, and the invention is hereinafter described in the context of a power supply for such lamps. However, it will be understood that the invention may have broader applications.
  • a compact fluorescent lamp may comprise two folded discharge tubes which project outwardly from a base.
  • the lamp may be connectable to an AC mains supply grid by means of conventional bayonet or screw-type lamp sockets.
  • the base of the AC lamp may incorporate a switch mode converter/inverter.
  • the converter may rectify the mains supply voltage and the resultant direct current may be fed to the inverter which may be operated at a relatively high frequency of the order of 20 to 50kHz.
  • the converter stage may comprise AC to DC rectifying means such as a full-wave bridge rectifier (10) having a pair of input terminals connectable directly to the AC supply grid and a pair of output terminals for providing direct current (DC) .
  • a filter capacitor (11) may be connected across the output or D.C. terminals of the rectifier.
  • current (I ⁇ ) in such a circuit is drawn from the mains supply grid in the form of a pulse during a relatively short period in each half-cycle of the AC mains supply voltage (Vire) in order to restore the charge which is drawn by the load (R ⁇ l) from the filter capacitor.
  • Figure 3 shows a prior art circuit for reducing harmonic distortion in the supply current.
  • the circuit of Figure 3 includes a rectifier bridge 20 providing full-wave rectification of the single phase AC supply.
  • a filter capacitor 21 is connected across the output or DC terminals of bridge 20 with series resistor 22.
  • Resistor 22 increases the time constant of the circuit a d, thus increases the period during which current is conducted by bridge 20.
  • the supply current waveform I ⁇ which is shown in Figure 4, more closely resembles a sinusoidal form (when compared with the current waveform in Figure 2) .
  • the circuit of Figure 3 provides a degree of reduction of harmonic distortion in the supply current. However the improvement in harmonic distortion carries with it a penalty.
  • An object of the present invention is to alleviate the disadvantages of the prior art.
  • the present invention seeks to increase the pulse width or conduction time of the supply current (I g ) so that supply current will more closely approximate a sinusoidal form without increasing significantly undesirable ripple and power loss in the circuit.
  • the purpose of the added bank capacitors is to provide a leading phase addition to the input current waveform thereby further extending conduction time of the rectifier and reducing harmonic distortion.
  • Values of C n may be optimised to produce the best overall current wave-shape for given values of R*. , R L .
  • R L When C_ is correctly proportioned to suit R_, R L a leading phase is added to the input current which improves harmonic distortion and increases power to the load.
  • R,, , are in kilohms
  • C D is in microfarads
  • f is the supply frequency in Hertz.
  • the above relationship may minimize harmonic distortion in the input current if the discharge time constant (C-R-.) associated with the filter capacitor (C,) is greater than about 15 milliseconds and f is in the range of a supply frequency eg. 50-60 Hertz.
  • a window of C D values eg ⁇ 80% either side of predicted values may produce acceptable results.
  • the extent of adherence to predicted values may be dictated by a number of factors including efficiency, bulk, cost, industry standards etc.
  • a power supply circuit for supplying power to a load, said circuit being connectable directly to an AC supply and comprising:
  • AC to DC rectifying means having a pair of input terminals connected to said AC supply and a pair of output terminals; a filter capacitance means and a non-capacitive impedance means connected in series between said output terminals, said non-capacitive impedance means being adapted to increase conduction time of input current drawn from said AC supply; a bank capacitance means connected between said output terminals and one of said input terminals; wherein said bank capacitance means further increases said conduction time of said input current to more closely approximate a sinusoidal form, thereby reducing unwanted harmonic distortion in said input current.
  • connectionable directly to an AC supply includes within its scope a connection made via RFI suppression and/or various protective devices and the like.
  • the power supply of the present invention functions to increase the conduction period of the rectifying means which reduces distortion of the supply current waveform and the proportion of undesirable harmonics in the supply.
  • the rectifying means may comprise a full-wave bridge rectifier.
  • the non-capacitive impedance means located in series with the filter capacitor means may comprise a resistive and/or inductive element.
  • the non-capacitive impedance means may comprise, for example, a resistor, an inductor or the primary winding of a transformer. The latter may have its secondary winding connected to a circuit associated with the load.
  • the non-capacitive impedance means comprises a resistance it usually has the effect of increasing the depth of ripple which appears across the resistance, resulting in loss of power.
  • the presence of the bank capacitance means reduces the depth of ripple across the resistance thereby reducing the power loss attributable to the resistance or non-capacitive impedance means.
  • the bank capacitance effectively reduces the AC voltage to the load and raises the average or DC voltage to the load (V _ ⁇ J) thus increasing average power to the load. Because the raised
  • Figure 1 shows a power supply for a fluorescent lamp of a type that includes an inverter and a high frequency ballast
  • Figure 2 shows waveforms applicable to the supply voltage, supply current and load voltage in the circuit of Figure 1;
  • Figure 3 shows a prior art power supply circuit suitable for use with the fluorescent lamp load shown in dotted outline in Figure 1;
  • Figure 4 shows waveforms applicable to the supply votage, supply current and load voltage in the circuit of Figure 3;
  • Figure 5 shows a power supply circuit in accordance with a preferred mode of the present invention, the circuit also being suitable for use with the fluorescent lamp circuit shown in dotted outline in Figure 1;
  • Figure 6 shows waveforms applicable to the supply voltage, supply current and load voltage in the circuit of Figure 5;
  • Figure 7 shows a variation of the power supply circuit illustrated in Figure 5;
  • Figure 8 shows a further variation of the power supply circuit illustrated in Figure 5.
  • Figure 9 shows a power supply circuit which may be considered an electrical equivalent of the power supply circuit illustrated in Figure 5.
  • the power supply comprises a converter including bridge rectifier 10 and filter capacitor 11 providing full-wave rectification of a single phase AC supply.
  • Filter capacitor 11 is connected across the output or DC terminals of bridge rectifier 10 and the
  • inverter 12 is of a conventional configuration and comprises a solid state high frequency switching circuit which generates a lamp excitation current at a frequency which may be of the order of 20 to 50kHz.
  • the output from inverter 13 is fed to a gas discharge tube 13 via a high frequency inductor 14 and a lamp starting circuit 15.
  • supply current I Crow which leads the supply voltage V_
  • V_ supply voltage
  • I ⁇ current waveform
  • Figure 5 of the drawings One preferred form of the present invention is illustrated in Figure 5 of the drawings.
  • the circuit shown in Figure 5 uses components which may conveniently be located in the base moulding (not shown) of a compact fluorescent lamp.
  • the power supply of Figure 5 comprises a rectifier bridge 30 which provides full wave rectification of the single phase AC supply.
  • a filter capacitor 31 is connected across the output or DC terminals of bridge 30.
  • a resistor 32 is connected in series with filter capacitor 31.
  • a value (R, ) of resistor 32 may be chosen to provide a good compromise between unwanted distortion in the supply current I-, undesirable ripple in the load voltage L and power loss in resistor 32.
  • Resistance values (R, ) of resistor 32 which have been found suitable in practical circuits may fall in the range of 1% to 40%, preferably 3% to 24% of the value of the load (R ⁇ ⁇ Li) , ie. .01 ⁇ R1,/R ⁇ ⁇ .40, and preferably .03 ⁇
  • a clamping diode 33 and bypass capacitor 34 may optionally be connected in parallel with resistor 32.
  • Diode 33 may be included in the circuit to clamp and prevent the low voltage side of filter capacitor 31 from going significantly below zero volts. Diode 33 serves to bypass current in its forward bias direction thus reducing discharge time of capacitor 31 into the load and dissipation in resistor 32, thereby improving efficiency of the circuit.
  • Capacitor 34 serves to bypass high frequency (RF) currents produced in the circuit by high frequency switching in the load and the like. Capacitor 34 may " have a value which is significantly smaller than the value of filter capacitor 31 but which is sufficiently large to adequately bypass RFI but not appreciably affect harmonic distortion.
  • Bank capacitors 35 and 36 are connected between the output or DC terminals of bridge 30 and AC or input terminal 37 of bridge 30.
  • Bank capacitors 35 and 36 are connected in series with each other and in parallel with filter capacitor 31. Bank capacitors 35 and 36 increase the conduction time of bridge 30. This is achieved as a consequence of alternate charging of bank capacitors 35 and 36 from the AC supply. As one bank capacitor is charged during one-half cycle of the supply, the other bank capacitor discharges into the load and/or through the circuit including filter capacitor 32. This causes current to flow through the circuit for an extended period and thus to be drawn from the input or AC side of the bridge.
  • the two bank capacitors 35 and 36 are equal in capacitance value to provide a balanced circuit, in which current attributable to charging and discharging thereof flows during each half-cycle of the AC supply.
  • Figure 6 of the drawings shows the improvement which results in the supply current waveform I,- due to the circuit configuration shown in Figure 5.
  • the load voltage waveform V ⁇ is also improved, having less ripple depth, due to the presence of bank capacitors 35 and 36 and consequential flow of current through the load circuit.
  • the power supply illustrated in Figure 7 is similar in principle to that shown in Figure 5 but includes a primary winding of a transformer 38 located in series with filter capacitor 31 in place of resistor 32.
  • the secondary winding of transformer 38 is arranged to provide current to the load, for example by locating it to provide power for the base drive circuit of switching transistors
  • FIG. 8 A further embodiment of the present invention is shown in Figure 8.
  • the circuit shown in Figure 8 is self protecting when the load is removed, either intentionally in the case of a two part lamp or unintentionally in the case of lamp failure.
  • Figure 8 includes an optically-coupled triac 39 which is disabled when the load (R_) is removed or greatly increased.
  • R_ load
  • One effect of a reduced R*. is a reduction in ripple current flowing through filter capacitor 31, resistor 32 and LED diode 40. This switches off LED 40 and disables triac 39, disconnecting flow of AC supply grid current to capacitors 35, 36.
  • LED diode 40 effectively senses a change in the load and acts to disconnect AC power flowing to capacitors 35, 36. This prevents voltage doubler action associated with capacitors 35, 36 which, if allowed to continue, could damage sensitive components (semiconductors, capacitors etc.) in the load due to voltage rising above normal levels.
  • Diode 33 in Figure 5 has also been replaced in Figure 8 with zener diode 41. Zener diode 41 has the advantage that it acts as a normal diode in its forward bias mode. However, if its reverse breakdown voltage is chosen just above normal peak operating voltage ie.
  • zener diode 41 may break down in the event of spikes and other transients present in the AC supply grid, thus restoring the bypassing action of the power supply to protect voltage sensitive elements in the circuit.
  • means other than LED diode 40 may be used to sense a change in the load and that such means may be located elsewhere in the circuit so as to achieve this aim.
  • switch means other than triac 39 may be used to disconnect AC power from capacitors 35, 36, The switch means also may be located elsewhere in the circuit so as to disconnect power from capacitors 35, 36.
  • the circuit of Figure 9 will be substantially electrically equivalent to the circuit of Figure 5 providing that: the value of each resistor 44, 45 is equal to half the value of resitor 32 in Figure 5 (ie. R./2); the value of each capacitor 42, 43 is equal to twice the value of capacitor 31 in Figure 5 (ie. 2C ⁇ ) * ' an ⁇ impedance element 46 comprises a capacitor having a value substantially equal to twice the value of capacitor 35 or 36 in Figure 5 (ie. 2C_) . It is apparent that resistors 44, 45 each being of value R,/2 and connected in series between the DC rails of bridge 30 are equivalent to resistor 32 in Figure 5 having a value R, . It is further apparent that capacitors 42, 43 each being of value 2C, connected in series between the DC rails of bridge 30 are equivalent to capacitor 31 in Figure 5 having a value C,.
  • impedance element 46 having a capacitance value 2C n to capacitors 35, 36 in Figure 5 each having a value C n may be appreciated by considering element 46 as comprising notional first and second capacitors, each having a value C n , connected in parallel.
  • the first notional capacitor having a value C_. may be considered to be connected between AC or input terminal
  • capacitor 42 is substantially greater than (say 10 times) the value C D attributed to the first notional capacitor, the effective capacitance between terminal 37 and the positive DC rail of bridge 30 is about 91% C D , ie. it is substantially equivalent to capacitor 35 in Figure 5 having a value C Q .
  • the second notional capacitor may similarly be considered to be connected between AC or input terminal 37 and the negative DC rail of bridge 30 via resistor 45 and capacitor 43 (or via capacitor 43) and for similar reasons is substantially equivalent to capacitor 36 in Figure 5 having a value C-.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Rectifiers (AREA)

Abstract

On décrit un circuit d'alimentation électrique desservant un utilisateur, tel qu'un éclairage fluorescent compact, ledit circuit pouvant être relié directement au réseau c.a. Le circuit comporte un moyen de redressement c.a./c.c. (30), muni de deux bornes d'entrée reliées à l'alimentation c.a. ainsi que de deux bornes de sortie. Le circuit comporte en outre un condensateur filtre (31) et une impédance non capacitative reliés en série entre les bornes de sortie. L'impédance non capacitative est adaptée pour augmenter le temps de conduction du courant d'entrée provenant de l'alimentation c.a. Une batterie de condensateurs (35, 36) est reliée entre les bornes de sortie et l'une des bornes d'entrée (37) du moyen de redressement de manière que la batterie de condensateurs augmente encore plus le temps de conduction du courant d'entrée pour lui conférer une forme plus près de la forme sinusoïdale. De cette manière on évite les distorsions harmoniques indésirables caractérisant le courant d'entrée et on réduit les pertes survenant dans l'impédance non capacitative.
PCT/AU1992/000293 1991-06-19 1992-06-19 Alimentation electrique WO1992022953A1 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
AUPK6754 1991-06-19
AUPK675491 1991-06-19

Publications (1)

Publication Number Publication Date
WO1992022953A1 true WO1992022953A1 (fr) 1992-12-23

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Family Applications (1)

Application Number Title Priority Date Filing Date
PCT/AU1992/000293 WO1992022953A1 (fr) 1991-06-19 1992-06-19 Alimentation electrique

Country Status (3)

Country Link
NZ (1) NZ243218A (fr)
WO (1) WO1992022953A1 (fr)
ZA (1) ZA924549B (fr)

Cited By (7)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP0596397A1 (fr) * 1992-11-04 1994-05-11 Patent-Treuhand-Gesellschaft für elektrische Glühlampen mbH Circuit d'alimentation à haute fréquence
WO1996001002A1 (fr) * 1994-06-28 1996-01-11 Philips Electronics N.V. Agencement de circuit
EP0691800A3 (fr) * 1994-07-07 1996-05-01 Patent Treuhand Ges Fuer Elektrische Gluehlampen Mbh Circuit pour alimenter des lampes à décharge basse-pression
WO1996037038A1 (fr) * 1995-05-19 1996-11-21 Sgs-Thomson Microelectronics S.A. Dispositif d'alimentation electronique
WO2001078228A1 (fr) * 2000-04-10 2001-10-18 Speedy-Tech Electronics (S) Pte Ltd. Procede et appareil a bon rendement energetique pour la mise en forme de signaux formes d'onde d'entree
WO2010038093A2 (fr) * 2008-09-30 2010-04-08 Cathay Licensing Ltd Circuit électronique et procédé pour réduire la distorsion harmonique totale produite par la gradation de lampes à fluorescence
WO2014047563A1 (fr) * 2012-09-24 2014-03-27 Cooper Technologies Company Commutateur de commande de charge à basse tension

Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
AU949655A (en) * 1955-06-01 1955-12-01 Thegeneral Electric Company Limited Improvements in or relating to electric circuit arrangements for operating low pressure electric discharge lamps
GB853371A (en) * 1958-01-18 1960-11-02 Asea Ab Means for reducing the harmonic currents in a static converter plant
GB2057205A (en) * 1979-07-06 1981-03-25 Sonelt Corp Electronic ballast
EP0296859A2 (fr) * 1987-06-24 1988-12-28 Reliance Comm/Tec Corporation Circuit de correction du facteur de puissance

Patent Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
AU949655A (en) * 1955-06-01 1955-12-01 Thegeneral Electric Company Limited Improvements in or relating to electric circuit arrangements for operating low pressure electric discharge lamps
GB853371A (en) * 1958-01-18 1960-11-02 Asea Ab Means for reducing the harmonic currents in a static converter plant
GB2057205A (en) * 1979-07-06 1981-03-25 Sonelt Corp Electronic ballast
EP0296859A2 (fr) * 1987-06-24 1988-12-28 Reliance Comm/Tec Corporation Circuit de correction du facteur de puissance

Cited By (13)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP0596397A1 (fr) * 1992-11-04 1994-05-11 Patent-Treuhand-Gesellschaft für elektrische Glühlampen mbH Circuit d'alimentation à haute fréquence
WO1996001002A1 (fr) * 1994-06-28 1996-01-11 Philips Electronics N.V. Agencement de circuit
US5714846A (en) * 1994-07-07 1998-02-03 Patent-Treuhand-Gesellschaft F. Elektrische Gluehlampen Mbh Minimum harmonic distortion operating circuit for at least one low-pressure discharge lamp
EP0691800A3 (fr) * 1994-07-07 1996-05-01 Patent Treuhand Ges Fuer Elektrische Gluehlampen Mbh Circuit pour alimenter des lampes à décharge basse-pression
US6219263B1 (en) 1995-05-19 2001-04-17 Sgs-Thomson Microelectronics S.A. Electronic power supply device
FR2734424A1 (fr) * 1995-05-19 1996-11-22 Sgs Thomson Microelectronics Dispositif d'alimentation electronique
WO1996037038A1 (fr) * 1995-05-19 1996-11-21 Sgs-Thomson Microelectronics S.A. Dispositif d'alimentation electronique
WO2001078228A1 (fr) * 2000-04-10 2001-10-18 Speedy-Tech Electronics (S) Pte Ltd. Procede et appareil a bon rendement energetique pour la mise en forme de signaux formes d'onde d'entree
US6414859B1 (en) 2000-04-10 2002-07-02 Speedy-Tech Electronics (S) Pte Ltd Passive circuity for harmonic current regulation in a power supply by energy efficient input current shaping
WO2010038093A2 (fr) * 2008-09-30 2010-04-08 Cathay Licensing Ltd Circuit électronique et procédé pour réduire la distorsion harmonique totale produite par la gradation de lampes à fluorescence
WO2010038093A3 (fr) * 2008-09-30 2010-09-30 Cathay Licensing Ltd Circuit électronique et procédé pour réduire la distorsion harmonique totale produite par la gradation de lampes à fluorescence
WO2014047563A1 (fr) * 2012-09-24 2014-03-27 Cooper Technologies Company Commutateur de commande de charge à basse tension
US9342062B2 (en) 2012-09-24 2016-05-17 Cooper Technologies Company Low voltage load control switch

Also Published As

Publication number Publication date
ZA924549B (en) 1993-04-28
NZ243218A (en) 1996-02-27

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