WO1990013152A1 - Antenne de duplexage pour emetteur-recepteur radio portatif - Google Patents

Antenne de duplexage pour emetteur-recepteur radio portatif Download PDF

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Publication number
WO1990013152A1
WO1990013152A1 PCT/CA1990/000122 CA9000122W WO9013152A1 WO 1990013152 A1 WO1990013152 A1 WO 1990013152A1 CA 9000122 W CA9000122 W CA 9000122W WO 9013152 A1 WO9013152 A1 WO 9013152A1
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WO
WIPO (PCT)
Prior art keywords
transmit
receive
antenna
ground
patch
Prior art date
Application number
PCT/CA1990/000122
Other languages
English (en)
Inventor
Paul L. Camwell
Andrew E. Mcgirr
John G. Mcrory
Original Assignee
Novatel Communications Ltd.
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Novatel Communications Ltd. filed Critical Novatel Communications Ltd.
Publication of WO1990013152A1 publication Critical patent/WO1990013152A1/fr

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Classifications

    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q9/00—Electrically-short antennas having dimensions not more than twice the operating wavelength and consisting of conductive active radiating elements
    • H01Q9/04—Resonant antennas
    • H01Q9/0407—Substantially flat resonant element parallel to ground plane, e.g. patch antenna
    • H01Q9/0442—Substantially flat resonant element parallel to ground plane, e.g. patch antenna with particular tuning means
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/12—Supports; Mounting means
    • H01Q1/22—Supports; Mounting means by structural association with other equipment or articles
    • H01Q1/24—Supports; Mounting means by structural association with other equipment or articles with receiving set
    • H01Q1/241—Supports; Mounting means by structural association with other equipment or articles with receiving set used in mobile communications, e.g. GSM
    • H01Q1/242—Supports; Mounting means by structural association with other equipment or articles with receiving set used in mobile communications, e.g. GSM specially adapted for hand-held use
    • H01Q1/243—Supports; Mounting means by structural association with other equipment or articles with receiving set used in mobile communications, e.g. GSM specially adapted for hand-held use with built-in antennas
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/52—Means for reducing coupling between antennas; Means for reducing coupling between an antenna and another structure
    • H01Q1/521—Means for reducing coupling between antennas; Means for reducing coupling between an antenna and another structure reducing the coupling between adjacent antennas
    • H01Q1/525—Means for reducing coupling between antennas; Means for reducing coupling between an antenna and another structure reducing the coupling between adjacent antennas between emitting and receiving antennas

Definitions

  • This invention relates generally to antennas, and particularly to an antenna adapted for operation with portable radio transceivers, such as those used in hand-held cellular telephones.
  • hand-held a portable, hand-held cellular telephone
  • mobile mobile cellular telephone
  • a hand-held In order to remain competitive, however, a hand-held must be as physically small and lightweight as possible. Because hand-helds are purchased at a premium customers also expect excellent quality transmission and reception. Accordingly, the electronic radio frequency (RF) components used in a hand-held must be extremely efficient, not only in the range of functions provided in a given physical volume, but also in terms of power dissipation, since hand-helds invariably operate on battery power.
  • RF radio frequency
  • UHF Very High Frequency
  • Current designs provide adequate operation at these frequencies if the RF circuits are fairly narrowband. Since a cellular transceiver must be capable of operating on any one of hundreds of channels upon command from a base station, its required operating bandwidth usually exceeds 25 MHz. This is not considered to be a particularly narrow bandwidth.
  • duplexer Another RF design consideration in a cellular telephone is the duplexer.
  • the duplexer allows the transmitter and receiver to operate simultaneously, and hence allows the user to talk and listen at the same time, as with a conventional telephone. This so-called duplex operation typically requires that the transmitter operate at a different radio frequency than the receiver.
  • duplex operation requires the transmitter and receiver to share the antenna.
  • This sharing is accomplished by a duplexer, which is a three- port filter coupled to the antenna, the receiver, and the transmitter.
  • the duplexer prevents transmitter RF signals from damaging or interfering with the receiver.
  • the duplexer provides a low impedance path from the transmitter to the antenna for signals at the transmit frequency, and a high impedance path from the transmitter to the receiver, so that the receiver is isolated from the transmit signals.
  • the duplexer also provides a low impedance path between the antenna and receiver for signals at the receive frequency, and a high impedance path between the receiver and transmitter, so that the transmitter is isolated from the receive signals.
  • the duplexer presents a problem to the designer of a cellular transceiver because of the required proximity of the transmitter and receiver bands, broad bandwidth, and high isolation. In fact, these requirements cannot usually be met without a multiple pole bandpass filter positioned in the transmit signal path. The need for a filter with multiple poles between the transmitter and the antenna in turn means that a fairly large insertion loss must be accepted. This results in reduced transmitter efficiency, and a corresponding increase in the amount of power which the battery must provide. Because of these and other design requirements, a duplexer is often the most expensive single component of a hand-held cellular telephone.
  • Whip antennas are also considered to be a nuisance, whether they are of the fixed-geometry or retractable type. Fixed-geometry whip antennas tend to break, and are often in the way when the hand-held must be stored. Retractable whip antennas must be extended to operate the hand-held and then retracted after use.
  • the antenna should ease, or even eliminate, the front end filtering functions traditionally performed by a duplexer. It should also exhibit none of the undesirable features of whip antennas.
  • the antenna should be simple and inexpensive to fabricate.
  • an antenna constructed in accordance with the invention includes a pair of radiating patch elements.
  • the patch ⁇ elements are elevated above a conductive surface by a conductive pedestal.
  • the surface and pedestal define a reference ground plane such that the two patch elements are inherently electrically isolated.
  • the patches are shaped so that they resonate in a desired frequency band.
  • they are physically independent of one another, they each can be designed as a band-pass filter.
  • one of the patches is tuned to the transmit band and serves a transmit structure, and the other patch is tuned to the receive band and serves as a receive structure.
  • the ground plane can also include a ground patch disposed between and spaced away from the two radiating patches.
  • switching devices such as positive-intrinsic negative (PIN) diodes are disposed along the space between the ground patch and the transmit patch, as well as along the space between the ground patch and the receive patch.
  • the receive and transmit patches are electrically tuned to a desired operating channel within their respective bands by selectively opening and closing the switches to adjust the impedance of the radiation patches.
  • the transmit and receive patches are inherent band-pass structures, significant isolation between the transmitter and receiver is provided. And because of this inherent isolation, the filtering requirements normally associated with duplex radio operation are reduced. In addition, insertion loss is minimized, since at least some rejection of out-of-band frequencies is inherent in the physical structure of the antenna.
  • the tunable structure significantly reduces or eliminates the filtering requirements of the duplexer, it can occupy much less space than the conventional antenna and duplexer.
  • the near-field of the antenna is such that direct radiation into the user's head is minimized.
  • Fig. 1 is a perspective view of a hand-held cellular telephone which makes use of a planar antenna constructed in accordance with this invention
  • Fig. 2 is an isometric view of a planar antenna in accordance with this invention.
  • Fig. 3 is an isometric view of the antenna as configured for use at cellular telephone frequencies
  • Fig. 4 is an isometric view of a tunable embodiment of the invention.
  • Fig. 5 is a detailed printed circuit board layout which can be used to construct the antenna of Fig. 4;
  • Fig. 6 is a detailed circuit diagram of one of the switch units in Fig. 4.
  • Fig. 7 shows s parameter diagrams which exhibit the extent of the duplexing action achievable with an antenna constructed in accordance with this invention.
  • Hand-held 10 includes the elements of a conventional cellular telephone, including a mouthpiece 11, an earpiece 12, a keypad and display 19 and a transceiver 14 which includes a transmitter 15 and receiver 16,all mounted inside an enclosure 13 shaped generally as a telephone handset.
  • the transmitter 15 is modulated by the audio signals received at the mouthpiece 11 to provide radio frequency (RF) transmit signals.
  • RF radio frequency
  • the receiver 16 demodulates RF receive signals to provide audio signals to the earpiece 12.
  • circuits 17 in the transceiver 14 perform standard functions such as reading the keypad and operating the display 19 to obtain a telephone number, initiating a telephone call over the cellular network. issuing instructions to the transmitter 15 and receiver 16 to tune to a particular cellular telephone channel, and so forth.
  • an antenna 18, also contained in the enclosure 13, is fed the RF transmit signal from the transmitter 15, and provides the RF receive signal to the receiver 16. Note that the antenna 18 does not protrude beyond the enclosure 13 as does a conventional whip antenna.
  • antenna 18 includes a pair of radiating elements, or patches 20, and 30 positioned above and facing a reference ground plane 40. More particularly, the antenna 18 consists of a printed circuit board 45 on which two radiating structures are formed, a receive patch 20 and a transmit patch 30.
  • the circuit board 45 is preferably formed of a low-loss dielectric such as duroid or other such material, and is plated on at least one side. (Duroid is a registered trademark of E.I.DuPont de Nemours and Company for dielectric circuit board materials.)
  • the circuit board 45 is formed or mounted so as to be integral to the enclosure 13.
  • a feedpoint 24 provides direct connection from the transmitter 15 to the transmit element 20, while feedpoint 34 provides direct connection from the receiver element 30 to the receiver 16.
  • the ground plane 40 for the radiating patches 20 and 30 comprises an electrically conductive surface 42 of the enclosure 13, together with a conductive pedestal 44 extending from the flat surface 42.
  • Pedestal 44 and surface 42 can be integral to enclosure or separately fabricated.
  • the surface 42 may be formed of metal or of a conductively coated plastic.
  • the pedestal 44 divides the conductive surface 42 into a right surface section 42a positioned adjacent the receive patch 20 and a left surface section 42b positioned adjacent the transmit patch 30.
  • the physical arrangement of the patches 20 and 30 and ground plane 40 provides inherent isolation between the receive patch 20 and transmit patch 30. Because of this inherent isolation, the invention enables the filtering constraints required in high frequency transceivers to be relaxed.
  • a receive antenna 21 is formed by the receive patch 20 and portions of the ground plane 40.
  • the receive patch 20 is electrically shorted to the ground plane 40 via a shorting stub 22 which transfers energy from a point on the surface of the receive patch 20 to the right section 42a.
  • a line 23 connected from the receiver 16 to a feed point 24 couples electromagnetic energy from the receiver 16 to the receive patch 20.
  • Receive antenna 21 is thus similar to what is commonly known as a planar inverted-F (PIFA) antenna, to the extent it includes a receive patch 20 and the right section 42a of a ground plane. However, it differs from a conventional PIFA antenna in that the ground plane 40 includes a pedestal 44 as well.
  • PIFA planar inverted-F
  • receive antenna 21 is thus essentially a resonant cavity, with the geometry of the components determining the resonant frequency.
  • the position of the feedpoint 24, shorting stub 22, and the shape of receive patch 20 are accordingly chosen to achieve the correct terminal impedance at the frequency of interest.
  • different impedances presented by the receiver 16 to antenna 21 will affect the resonant frequency and thus the exact desired length also.
  • its length is preferably approximately one quarter of the wavelength of the carrier frequency used by the receiver 16. All of these parameters are interrelated, so that determination of the exact dimensions to achieve optimum radiation at the frequency of interest usually requires several iterations.
  • a transmit antenna 31 is formed by the transmit patch 30, pedestal 44, and left conductive surface 42b.
  • Transmit patch 30 has a shorting stub 32 positioned to achieve operation at the frequency of the transmitter 15.
  • the feedpoint 34 is where electrical connection is made to pass transmitter signals to the transmit antenna 31 from the transmitter.
  • the two patch elements along with their associated components, form high Q resonant circuits tuned to different frequencies.
  • the near field radiation pattern lines 38a emanating from the right side edge of the transmit patch 30. Because of the proximity of the pedestal 44 formed part of the ground plane 40, the near field lines 38a tend to terminate at the pedestal 44, and tend not to radiate into the receive patch 20.
  • the near field radiation pattern lines 38b tend to terminate along the outer edge of the ground plane section 42b, and not continue to radiate into the user's head, which is on the other side of the enclosure 13 from the radiating elements 20 and 30.
  • the far field antenna pattern contains mixed polarization because the ground plane is not large compared with the radiating elements, the ground plane is three dimensional, the elements are relatively wide, and the enclosure 13 has a non- uniform shape.
  • the assigned frequency channels for cellular telephone operation in North America are between 824 to 849 MHz for the transmitter, and approximately 45 MHz higher, or between 869 to 894 MHz for the receiver. Since a conventional whip antenna is shared by the transmitter and receiver, it must cover the entire range from 824 to 894 MHz, or 70 MHz.
  • an antenna 18 constructed in accordance with the invention allocates the transmit and receive antenna functions to two separate structures. Thus, each structure need only operate over a much smaller bandwidth, namely 25 MHz.
  • Fig. 3 shows one embodiment of antenna 18 adapted for use in the 800 to 900 megahertz (MHz) range, the band of interest for cellular operation.
  • receive patch 20 which includes a rectangular upper section 25 and rectangular lower section 27 joined by a narrower center section 26. Rectangular sections 25 and 27 are essentially capacitive, and the center section 26 is essentially inductive. With this arrangement, the inductance and capacitance at the resonant frequency of the receive patch 20 can be chosen essentially independently.
  • transmit patch 30 has approximately the same geometry as receive patch 20.
  • the upper section 25 and lower section 27 have a horizontal dimension 52 of 1 centimeter (cm) , and vertical dimensions 53 and 55, respectively, of 2 cm.
  • the center section 26 is also about 2 cm in the vertical dimension 54, but about 4 millimeters (mm) wide in the horizontal dimension 56.
  • the circuit board 45 has a thickness 50 of 1 mm, and is spaced a distance 51 of approximately 7 mm from the surface of the flat section 42.
  • the transmit patch 30 is similarly dimensioned, with its exact dimensions chosen to optimize operation at the carrier frequency of the transmitter.
  • each of the receive antenna 21 and transmit antenna 31 acts as a bandpass filter.
  • a minimum 10 decibel (dB) isolation between the transmit and receive sections has been observed across the 800 to 900 MHz range.
  • the 10 dB inherent isolation may not satisfy design specifications.
  • an auxiliary bandpass filter should normally be placed between the receive antenna 21 and the receiver 16, as well as in the path between the transmitter 15 and transmit antenna 31.
  • the requirements of that auxiliary filter are greatly reduced when compared to that which is required when a more conventional antenna is used.
  • Fig. 4 shows another embodiment of the invention which is capable of being tuned over a bandwidth as large as the cellular operating band. As will be seen, this embodiment reduces auxiliary filtering requirements even further.
  • antenna 18 includes two radiators, that is, a receive patch 20 and transmit patch 30, positioned above a ground plane 40.
  • ground plane 40 includes a conductive surface 42 divided into two sections 42a and 42b, as well as a ground patch 60.
  • the circuit board 45 and conductive patches 20, 30, and 60 are preferably constructed using known microstrip circuit technology.
  • This embodiment is thus referred to as a microstrip element antenna elevated over a ground plane, or, simply, an elevated microstrip antenna. Not only is the elevated microstrip embodiment tunable, but also it can be more easily manufactured than the antenna of Fig. 1.
  • the receive antenna 21 is disposed between the receive patch 20 and transmit patch 30.
  • the receive antenna 21 is formed by the receive patch 20, ground patch 60, right section 42a, and pedestal 44.
  • the transm antenna 31 is formed by the transmit patch 30, and a ground plane 40 consisting of ground patch 60, left section 42b, and pedestal 44.
  • An electrical connection between the ground patch 60 and the ground plane 40 at pedestal 44 is provided by insuring that the distance 68 between the lower surface of the ground patch 60 is sufficiently close to the upper surface of the pedestal 44 to thereby provide capacitive coupling between them.
  • capacitors 62 are connected in series with a like number of switches 65 between the receive patch 20 and the ground patch 60.
  • the capacitors 62 and switches 65 enable the impedance of the receive patch 20 to be adjusted.
  • capacitors 62 are switched in or out to provide a change in the impedance and hence the resonant frequency of the receive antenna 21.
  • Switches 65 preferably comprise an appropriate RF switch element such as positive- intrinsic-negative (PIN) diodes.
  • capacitors 72 and switches 75 are disposed in series between the ground patch 60 and transmit patch 30 to enable tuning of the transmit antenna 31.
  • a switch 65a which receives an appropriate control signal from the circuits 17 (Fig. 1) to either connect or disconnect its associated capacitor 62a. Whether the control signal connects or disconnects the capacitor 62a depends upon the particular channel within the receiver band to which the receive antenna 21 is to be tuned.
  • the impedance of the receive patch 20 is altered.
  • the receive antenna 21 operates at its lowest possible frequency.
  • the impedance of receive antenna 21 can also be adjusted by switching inductive components in or out of a series circuit arranged between the receive patch 20 and the ground patch 60.
  • the radiating elements 20 and 30 can now be much narrower in bandwidth.
  • the desired bandwidth is covered by simply tuning each radiating element to the range in which operation is desired, by appropriate application of signals to the control inputs of the switches 65 and 75.
  • the receive and transmit antennas 21 and 31 each use four switches. With four switches 65 as shown there are 2 4 or sixteen possible frequencies to which each antenna 21 and 31 can be tuned.
  • the transmit antenna 31 covers the transmit band of 824 to 849 MHz in 16 sub-bands of approximately 25MHZ/16 or 1.6 MHz
  • the receive antenna 21 also covers the receive band of 869 to 894 MHz in 16 sub-bands of approximately 1-6 MHz.
  • each antenna need cover a much smaller bandwidth on the order of 2 MHz instead the 70 MHz required of a conventional antenna and, because the antennas are tunable, they inherently provide rejection of out-of-band signals.
  • the receive antenna 21 acts as a 1.6 MHz bandwidth filter tuned to a particular sub-band within the receive band, there is greater inherent rejection of the corresponding transmitter frequency 45 MHz away.
  • rejection of some in-band signals from adjacent channels is also inherent. That is, the receive antenna 21 inherently rejects signals which are within the receive band but which are outside the 1.6 MHz sub-band to which it is presently tuned.
  • antenna 18 is less expensive to manufacture then the whip antenna and duplexer which it replaces.
  • the designer can, within reason, make the antenna as narrow- band as desired, and simply tune it up and down the band of interest.
  • the narrower the bandwidth the more capacitors and switches ill be need to cover a given frequency range.
  • the tuning capability also greatly improves the inherent rejection qualities of the structure. That is, while each capacitance 62 and 72 is chosen such that there is very little loss in the center of the receive band, the receive antenna 21 can be designed to have high loss at the corresponding transmit frequency, which will always be 45 MHz lower.
  • the bandwidth of the receive antenna 21 can be slightly less than that of the receive band divided by the number of possible switch settings.
  • Fig. 5 shows a detailed layout for the antenna 18 in Fig. 4 on two-sided microstrip circuit board.
  • the upper or outer layer metal shown in the lighter shade, is shaped to form the receive patch 20, ground patch 60, and transmit patch 30.
  • the lower layer metal shown in the darker shade, is used primarily to define the capacitors 62 and 72 as well as the signal trace lines which form electrical connections between components.
  • an exemplary capacitor 62a is embodied as a rectangular section of metal. Since the corresponding PIN diode is a discrete component, the switch 65a is not explicitly visible in the printed circuit layout of Fig. 5. However, the mounting pads 80 and 81 to which it attaches are visible in portions of the lower layer metal adjacent the ground patch 60 and receive patch 20, respectively.
  • a signal trace 83 provides a part of the connection between the PIN diode and the capacitor 62a.
  • the preferred embodiment uses additional discrete components in the switch 65a, and thus additional mounting pads 80 and 81 are need to secure them between the receive patch 20 and ground patch 60, as well as in another area 84 reserved for discrete components.
  • An input signal pad 82 provides the control signal which determines the state of the switch 65a.
  • the radiating patches 20 and 30 were shown in Fig. 4 as physically separate from the ground patch 60. As is evident from Fig. 5, however, it may be desirable to provide a known high impedance between the radiating patches 20 and 30 and the ground patch 60 by including inductive sections 86.
  • a trimmer capacitor 90 may be formed so as to be placed permanently in series with the receive patch 20 and ground patch 60. Portions of the trimmer capacitor 90 can then be etched during the manufacturing process to further exactly tune the rece_ve antenna 21. This compensates for inconsistencies in the manufacturing process. The trimmer capacitor is etched so that the receive antenna 21 is properly retuned to the highest-frequency sub-band when all capacitors 62 and 72 are switched out of the circuit. Similarly, a trimmer capacitor 92 can be disposed in series between the transmit patch 30 and ground patch 60.
  • the dimension of this layout are such that the distance 93 from top to bottom is approximately 5.9 cm.
  • the printed circuit board on which this antenna 18 was fabricated was a 'dual-sided 0.75 mm thick duroid board.
  • Fig. 6 is a detailed circuit diagram of the components of switch 65a.
  • switch 65a includes positive-intrinsic- negative (PIN) diodes Dl and D2, field effect transistor (FET) Ql, capacitor Cl, and resistors Rl, R2, R3, and R4.
  • PIN diode Dl is connected in series between the capacitor 62a and the ground patch 60, so that when PIN diode Dl is forward biased, current may flow from capacitor 62a (and hence the receive patch 20 to which capacitor 62a is attached) to ground patch 60 *
  • the gate of the FET Ql receives the control signal from input signal pad 82.
  • the source of FET Ql is tied to a positive supply voltage, V cc , the magnitude of which depends on the type of logic circuit which supplies the control signal. For example if the circuit is transistor-transistor logic (TTL) type, V cc will be 5 volts.
  • the drain of FET Ql is tied through resistor R3 to a negative voltage V ⁇ . A V ⁇ of -36 volts was used in this embodiment, but the exact preferred voltage depends on the type of FET Ql and PIN diode Dl used.
  • the drain of FET Ql is also tied through resistor.R2 to the anode of PIN diode D2.
  • the anode of PIN diode D2 is also tied to one terminal of resistor Rl and one terminal of capacitor Cl.
  • the other terminal of PIN diode Dl is connected to the cathode of PIN diode D2 and thus to the node 93 formed at the cathode of PIN diode D2.
  • the anode of PIN diode Dl is also tied to this node 93; the voltage at node 93 thus determines whether the PIN diode Dl is in a low or high impedance state.
  • the cathode of PIN diode Dl is connected to the ground patch 60.
  • the resistor R4 is connected across the terminals of the PIN diode Dl.
  • a simpler switch 65a would include only the PIN diode Dl, FET Ql, resistors R2 and R3, and capacitor Cl. However, it can be shown that the addition of PIN diode D2 and resistors Rl and R4 reduces attenuation due to the switch 65a.
  • Fig. 7 is an s-parameter measurement which shows the duplexing action obtainable with the antenna 18 of Figs. 4 and 5. The measurement was taken by insuring that the antenna 18 sees a 50 ohm load.
  • the transmitter feedpoint 34 was connected to port 1, and the receiver feedpoint 24 to port 2 of the s- para eter so that network s-parameter sll measures the amount of power reflected back to the transmitter feedpoint 34, otherwise known as the transmit return loss.
  • S-parameter s22 is thus the receiver return loss.
  • S-parameter sl2 is thus the power measured at the receiver port with power applied to the transmitter port.
  • any signals directly passing from the transmitter to the receiver are attenuated by approximately 20 dB.
  • receive signals are attenuated 26dB.
  • an antenna 18 constructed in accordance with the invention achieves the various advantages mentioned previously. Because the transmit and receive patches are inherent resonant or band-pass structures, significant isolation between the transmitter and receiver is provided. Because of this inherent isolation, the filtering requirements normally associated with duplex radio operation are reduced. Insertion loss is minimized, since rejection of at least some out-of-band frequencies is due to the physical structure of the antenna.
  • the antenna can be fabricated to be tunable, it significantly reduces the requirements of front- end filters and duplexers normally required in high frequency radio transceivers.
  • the antenna can occupy less space than a conventional antenna and duplexer.
  • the near-field of the antenna is such that direct radiation into the user's head is minimized.

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  • Engineering & Computer Science (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Waveguide Aerials (AREA)
  • Transceivers (AREA)

Abstract

L'antenne décrite (18), qui est conçue pour être utilisée avec des émetteurs-récepteurs radio duplexe portatifs, tels que ceux qu'on trouve dans les téléphones à cellules tenant dans la main, comprend une paire d'éléments pastilles rayonnant coplanaires (20, 30), surélevés par rapport à une surface conductrice (40) au moyen d'une barre conductrice (44). La surface (40) et la barre (44) définissent un plan horizontal de référence, qui isole de façon inhérente les pastilles (20, 30). Les pastilles (20, 30) sont conçues avec une forme qui leur permet de fonctionner dans une bande de fréquences désirée et de servir également de filtres passe-bande, l'une des pastilles (30) étant syntonisée sur la bande émettrice et servant de structure émettrice et l'autre bande (20) étant syntonisée sur la bande réceptrice et servant de structure réceptrice. Des dispositifs de commutation (65), constitués par des diodes PIN (positif-intrinsèque négatif), peuvent être disposés le long de l'espace compris entre les pastilles (20, 30) et le plan horizontal (40), de façon à permettre la syntonisation de chaque structure. Une telle antenne est efficace, en raison de l'isolation inhérente obtenue entre la pastille réceptrice et la pastille émettrice, et facilite les fonctions de filtrage d'extrémité frontale traditionnellement assurées par un duplexeur. Elle peut être complétement enfermée à l'intérieur du châssis d'un téléphone tenant dans la main.
PCT/CA1990/000122 1989-04-18 1990-04-17 Antenne de duplexage pour emetteur-recepteur radio portatif WO1990013152A1 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
US33957389A 1989-04-18 1989-04-18
US339,573 1989-04-18

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WO1994014208A1 (fr) * 1992-12-16 1994-06-23 University Of Bradford Ameliorations concernant les telephones portatifs
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WO2002005382A1 (fr) * 2000-07-10 2002-01-17 Allgon Mobile Communications Ab Systeme antenne et dispositif de radiocommunication portable
WO2002011236A1 (fr) * 2000-08-01 2002-02-07 Sagem Sa Antenne a surface(s) rayonnante(s) plane(s) et telephone portable comportant une telle antenne
US6894649B2 (en) 2000-07-10 2005-05-17 Amc Centurion Ab Antenna arrangement and portable radio communication device
WO2009136876A1 (fr) 2008-05-06 2009-11-12 Vinko Kunc Agencement d'antenne émettrice et d'antenne réceptrice
CN108780945A (zh) * 2016-03-17 2018-11-09 松下知识产权经营株式会社 无线模块以及图像显示装置
EP3605734A1 (fr) * 2018-08-02 2020-02-05 Commissariat à l'Énergie Atomique et aux Énergies Alternatives Dispositif d'antenne comportant au moins deux antennes à même substrat de raccordement électrique
US10826181B2 (en) 2017-07-11 2020-11-03 Sensus Spectrum, Llc Hybrid patch antennas, antenna element boards and related devices

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FR2724793A1 (fr) * 1994-09-15 1996-03-22 Motorola Inc Antenne a composants multiples et methode de realisation de celle-ci
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EP0892459A1 (fr) * 1997-07-08 1999-01-20 Nokia Mobile Phones Ltd. Structure d'antenne à double résonance pour plusieurs gammes de fréquences
EP1498984A1 (fr) * 1997-07-08 2005-01-19 Nokia Corporation Structure d'antenne à double résonance pour plusieurs gammes de fréquences
US6140966A (en) * 1997-07-08 2000-10-31 Nokia Mobile Phones Limited Double resonance antenna structure for several frequency ranges
US6314275B1 (en) 1997-08-19 2001-11-06 Telit Mobile Terminals, S.P.A. Hand-held transmitting and/or receiving apparatus
US6198446B1 (en) 1999-01-19 2001-03-06 Trw Inc. Dual-feed system for a multifunction, conformal, loadearing structure excitation antenna
EP1022802A1 (fr) * 1999-01-19 2000-07-26 TRW Inc. Système d'alimentation double pour une antenne d'excitation multifonctionnel, conformée, portante
US6268831B1 (en) 2000-04-04 2001-07-31 Ericsson Inc. Inverted-f antennas with multiple planar radiating elements and wireless communicators incorporating same
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US6894649B2 (en) 2000-07-10 2005-05-17 Amc Centurion Ab Antenna arrangement and portable radio communication device
US6909401B2 (en) 2000-07-10 2005-06-21 Amc Centurion Ab Antenna device
WO2002005382A1 (fr) * 2000-07-10 2002-01-17 Allgon Mobile Communications Ab Systeme antenne et dispositif de radiocommunication portable
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WO2002011236A1 (fr) * 2000-08-01 2002-02-07 Sagem Sa Antenne a surface(s) rayonnante(s) plane(s) et telephone portable comportant une telle antenne
WO2009136876A1 (fr) 2008-05-06 2009-11-12 Vinko Kunc Agencement d'antenne émettrice et d'antenne réceptrice
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US10826181B2 (en) 2017-07-11 2020-11-03 Sensus Spectrum, Llc Hybrid patch antennas, antenna element boards and related devices
EP3605734A1 (fr) * 2018-08-02 2020-02-05 Commissariat à l'Énergie Atomique et aux Énergies Alternatives Dispositif d'antenne comportant au moins deux antennes à même substrat de raccordement électrique
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