US7792226B2 - Method and apparatus for carrier power and interference-noise estimation in space division multiple access and multiple-input/multiple-output wireless communication systems - Google Patents

Method and apparatus for carrier power and interference-noise estimation in space division multiple access and multiple-input/multiple-output wireless communication systems Download PDF

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US7792226B2
US7792226B2 US11/839,759 US83975907A US7792226B2 US 7792226 B2 US7792226 B2 US 7792226B2 US 83975907 A US83975907 A US 83975907A US 7792226 B2 US7792226 B2 US 7792226B2
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noise
variance
interference
estimate
equalizer
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US20090046772A1 (en
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Xiaoyong Yu
Jian J. Wu
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Google Technology Holdings LLC
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Motorola Inc
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Priority to PCT/US2008/072910 priority patent/WO2009026050A1/fr
Priority to KR1020107003234A priority patent/KR101076483B1/ko
Priority to CN200880103177.7A priority patent/CN101855833B/zh
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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/0202—Channel estimation
    • H04L25/0224—Channel estimation using sounding signals
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B17/00—Monitoring; Testing
    • H04B17/20—Monitoring; Testing of receivers
    • H04B17/26—Monitoring; Testing of receivers using historical data, averaging values or statistics
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B17/00—Monitoring; Testing
    • H04B17/30—Monitoring; Testing of propagation channels
    • H04B17/309—Measuring or estimating channel quality parameters
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B17/00—Monitoring; Testing
    • H04B17/30—Monitoring; Testing of propagation channels
    • H04B17/309—Measuring or estimating channel quality parameters
    • H04B17/336—Signal-to-interference ratio [SIR] or carrier-to-interference ratio [CIR]
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/0413—MIMO systems
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/06—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station
    • H04B7/0697—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using spatial multiplexing
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
    • H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
    • H04B7/08—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the receiving station
    • H04B7/0837—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the receiving station using pre-detection combining
    • H04B7/0842—Weighted combining
    • H04B7/0845—Weighted combining per branch equalization, e.g. by an FIR-filter or RAKE receiver per antenna branch
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2647—Arrangements specific to the receiver only
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B17/00—Monitoring; Testing
    • H04B17/30—Monitoring; Testing of propagation channels
    • H04B17/309—Measuring or estimating channel quality parameters
    • H04B17/318—Received signal strength
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/03—Shaping networks in transmitter or receiver, e.g. adaptive shaping networks
    • H04L25/03006—Arrangements for removing intersymbol interference
    • H04L25/03159—Arrangements for removing intersymbol interference operating in the frequency domain

Definitions

  • Link adaptation In order to manage radio resources efficiently in a broadband wireless access network, the characteristics of the wireless link are adapted. Link adaptation relies upon receiver channel condition measurements such as carrier to interference-noise ratio (CINR), received signal strength indicator (RSSI), noise and interference levels, instantaneous capacity, a number of retries and a number of packets lost. In particular, an accurate estimate of the carrier to interference-noise ratio (CINR) is required. This estimate allows radio signal strengths to be controlled.
  • CINR carrier to interference-noise ratio
  • RSSI received signal strength indicator
  • CINR carrier to interference-noise ratio
  • r k,n is the received sample n within signal k
  • s k,n represents a detected or pilot sample with channel state weighting
  • N is the number of samples used in the estimate. It is also stated in the WiMAX specification that the estimate should be accurate to within +/ ⁇ 2 dB.
  • This CINR estimation method is suitable for multiple receive antennas that use maximum ratio combining (MRC) or non-SDMA (space division multiple access) systems.
  • MRC maximum ratio combining
  • non-SDMA space division multiple access
  • the CINR for each antenna is calculated separately then added up to form a total signal quality indicator.
  • this estimate is no longer valid, because antenna beam-forming or MIMO equalizer results in some interference cancellation.
  • the effective interference seen in the output of a MIMO equalizer or a beam-former is not a summation of interference on each antenna.
  • FIG. 1 is a simplified diagram of an exemplary communication system in accordance with some embodiments of the invention.
  • FIG. 2 and FIG. 3 show the tile structures used in PUSC (partial usage of sub-channels) mode.
  • FIG. 4 is a flow chart of a method for estimating the CINR in a wireless communication system in accordance with some embodiments of the invention.
  • FIG. 5 is a block diagram of system for estimating CINR in accordance with some embodiments of the present invention.
  • FIG. 6 is a graphical comparison of CINR estimates.
  • embodiments of the invention described herein may comprise one or more conventional processors and unique stored program instructions that control the one or more processors to implement, in conjunction with certain non-processor circuits, some, most, or all of the functions of carrier to interference-noise ratio (CINR) estimation described herein.
  • the non-processor circuits may include, but are not limited to, radio receivers, radio transmitters, signal drivers, clock circuits, power source circuits, and user input devices. As such, these functions may be interpreted as a method to perform CINR estimation. Some or all functions could be implemented by a state machine that has no stored program instructions, or in one or more application specific integrated circuits (ASICs), in which each function or some combinations of certain of the functions are implemented as custom logic.
  • ASICs application specific integrated circuits
  • FIG. 1 is a simplified diagram of an exemplary communication system, 100 .
  • Symbols 102 from a first subscriber are encoded in encoder 104 and the encoded symbols passed through an inverse Fourier transform unit 106 .
  • the unit 106 may perform an inverse fast Fourier transform (IFFT).
  • IFFT inverse fast Fourier transform
  • the output from the unit 106 comprises a number of tonal signals that are modulated and passed to an antenna 108 for transmission.
  • data 110 from a second subscriber is encoded in encoder 112 and the encoded symbols passed through an inverse Fourier transform unit 114 .
  • the output from the unit 114 comprises a number of tonal signals that are modulated and passed to an antenna 116 for transmission.
  • the signal from antenna 108 propagates over a signal path with characteristic h 11 to the first antenna 118 of a receiving station.
  • the receiving station may be a base station or network access point. However, in other embodiments of the present invention, the receiving station may be a mobile subscriber station that receives signals from multiple sources.
  • the received signal is passed through Fourier transform unit 120 (which may be a fast Fourier transform (FFT) unit) to obtain the frequency components of the signal.
  • FFT fast Fourier transform
  • the signal also propagates over a signal path with characteristic h 21 to the second antenna 122 of the receiving station.
  • the signal received by the second antenna 122 is passed through Fourier transform unit 124 to obtain the frequency components of the signal.
  • the signal from antenna 116 propagates over a signal path with characteristic h 12 to the first antenna 118 of the receiving station.
  • the received signal is passed through Fourier transform unit 124 to obtain the frequency components of the signal.
  • the signal also propagates over a signal path with characteristic h 22 to the second antenna 122 of the receiving station.
  • the signal received by the second antenna 122 is passed through Fourier transform unit 124 to obtain the frequency components of the signal.
  • Equalizer 126 is applied to the frequency components of the signals received by antennas 118 and 122 to obtain estimates 128 and 130 for the signals transmitted by the two users. These estimates are then processed further to recover the original symbols. Since SDMA is used, the signals from the users share the same frequency band and interfere with one another. One role of the equalizer 126 is to cancel this interference. However, the antennas 118 and 122 are also subject to noise, denoted by the signals n 1 and n 2 in FIG. 1 , which prevents perfect equalization.
  • the CINR of the signals 128 and 130 output from the equalizer is dependent upon the characteristics of the equalizer. However, equalizer characteristics are not used in prior CINR estimation methods.
  • the signals are transmitted using orthogonal frequency division multiplexing (OFDM).
  • OFDM orthogonal frequency division multiplexing
  • each user channel comprises a cluster of frequency bands, called sub-channels.
  • Each OFDM symbol is encoded into the sub-channels.
  • FIG. 2 and FIG. 3 show the tile structures used in PUSC (partial usage of sub-channels) mode.
  • PUSC partial usage of sub-channels
  • FIG. 2 and FIG. 3 show the tile structures used in PUSC (partial usage of sub-channels) mode.
  • four sub-carriers are used.
  • Each column of the tile corresponds to a symbol or time interval, while each row of tile corresponds to a sub-carrier or frequency.
  • FIG. 2 shows a tile 200 for user 1 .
  • the tile 200 is arranged in a first pattern that includes a number of data symbols 202 , denoted by the circles labeled ‘D’, two null symbols 204 , and two pilot symbols 206 , denoted by the circles labeled ‘P.’
  • FIG. 3 shows a tile 300 for user 2 .
  • the tile 300 is arranged in a second pattern that includes a number of data symbols 302 , denoted by the circles labeled ‘D’, two null symbols 304 , and two pilot symbols 306 denoted by the circles labeled ‘P.’
  • the pilot symbols are orthogonal for the first and second patterns.
  • the two users with these tile patterns are paired together to share the same uplink (UL) resource that is composed of frequency bandwidth and time interval.
  • Y 1 and Y 2 are received signals on antenna 1 ( 118 in FIG. 1 ) and antenna 2 ( 122 in FIG. 1 ), respectively
  • X 1 and X 2 represent the transmitted signals of user 1 and user 2 , respectively
  • N 1 and N 2 are additive white Gaussian noise for antennas 1 and 2
  • H 1,1 , H 2,1 , H 1,2 and H 2,2 denote the Fourier transforms of the channel characteristics h 11 , h 21 , h 12 , and h 21 .
  • the transmitted signals X 1 and X 2 may be estimated by applying an equalizer to the received signals, Y 1 and Y 2 .
  • the signal of user 1 that is fed into a corresponding channel decoder can be expressed as
  • ⁇ z 1 2 ( ⁇ w 1 , 1 ⁇ 2 + ⁇ w 2 , 1 ⁇ 2 ) ⁇ ⁇ 2 and the interference variance can be determined as
  • ⁇ X 2 is the variance of the transmitted signal.
  • ⁇ X 2 1 for a normalized QAM (quadrature amplitude modulation) constellation.
  • the effective interference plus noise seen at the channel decoder for user 1 within in a tile is
  • NI t , 1 ⁇ ( w 1 , 1 * ⁇ H 1 , 2 + w 2 , 1 * ⁇ H 2 , 2 ) ⁇ 2 ⁇ ⁇ X 2 + ( ⁇ w 1 , 1 ⁇ 2 + ⁇ w 2 , 1 ⁇ 2 ) ⁇ ⁇ 2 .
  • the equalized carrier signal power for user 1 within in a tile is
  • channel estimate can be calculated using the pilot symbols.
  • H 1,1 , H 2,1 , H 1,2 and H 2,2 maybe estimated as follows
  • Y 1 A,1 means received pilot 1 in tile pattern A on antenna 1 .
  • H ⁇ a , u 1 2 ⁇ ( Y a u , 1 P u , 1 + Y a u , 2 P u , 2 ) , where Y a u,s denotes the received signal from antenna a for pilot s in the PUSC (partial usage sub-channel) tile pattern u and P u,s denotes the pilot s in the PUSC tile pattern u.
  • the CINR estimate may be used for adaptation of the wireless links.
  • effective signal power S and interference noise power NI are used separately for radio source management. Therefore it is desired to report the two measurements independently instead of in a value of ratio. They are calculated as
  • S 1 and NI 1 are the signal and interference noise power for user 1
  • S 2 and NI 2 are the signal and interference noise power for user 2 .
  • FIG. 4 is a flow chart of a method for estimating the CINR for a user, such as user 1 , in a wireless communication system.
  • the transfer function H is estimated at block 404 from the pilot tones as described in equations (10)-(13) above.
  • the noise variance ⁇ 2 at each antenna is estimated from the null symbols.
  • the equalization matrix W is calculated from H and ⁇ 2 using equation (3) above.
  • the carrier to interference-noise ratio (CINR) of user 1 within a tile is calculated as
  • the values of CINR 1 , S 1 , and/or NI 1 may be calculated over all tiles for the user. The method terminates at block 420 .
  • Calculation of the CINR for other users can be performed in a corresponding manner.
  • the estimate of carrier to interference-noise ratio (CINR) at the output of the equalizer in a wireless communication system is obtained by (i) determining the variance, ⁇ Z 1 2 and ⁇ Z 2 2 , of the noise at the output of the equalizer dependent upon the equalization matrix W H and an estimate of the variance ⁇ 2 of the noise at the receiving antennas, (ii) determining the interference power, ⁇ I 1 2 and ⁇ I 2 2 , at the output of the equalizer dependent upon the equalization matrix W H , a transfer function matrix H of transmission paths between a plurality of transmitting antennas and the plurality of receiving antennas, and a known value ⁇ X 2 of the variance of the signals transmitted from the transmitting antennas and (iii) determining the desired signal power, S 1 and S 2 , of the signal at the output of the equalizer dependent upon the equalization matrix W H , the transfer function matrix H, and the known value ⁇ X 2 of the variance of the signal at the transmitting antennas.
  • CINR carrier to
  • This CINR or independent S and NI values is outputted to facilitate adaptation of wireless communication system.
  • FIG. 5 is a block diagram of a system for estimating CINR in accordance with some embodiments of the present invention.
  • antennas 118 and 112 receive transmitted signals.
  • the cyclic prefix is removed and the signals are passed to a processing element 502 which performs a Fourier transform to obtain the frequency components of the signals and also decodes the corresponding symbols.
  • some of the frequency components correspond to pilot tones 504 in some time slots and to null symbols 506 in other time slots.
  • Other frequency components correspond to data symbols 508 .
  • the pilot tones 504 (which include the frequency components Y and the corresponding symbols P) are passed to a third processing unit 510 and used to determine the transfer function matrix H.
  • the frequency components 506 corresponding to null symbols are passed to a fourth processing unit 512 and used to generate estimates, ⁇ 2 , of the antenna noise variance.
  • the transfer function matrix H and the noise variance estimate ⁇ 2 are then used by a fifth processing unit 514 to determine the equalization matrix W, using a MMSE technique for example.
  • the equalization matrix W and transfer function matrix H are then used in a first processing unit 516 , along with known value ⁇ X 2 of the variance of the signals transmitted from the transmitting antennas, to determine the signal power estimate, S, and the interference variance, ⁇ I 2 .
  • the equalization matrix W and the antenna noise variance estimate ⁇ 2 are used in a second processing unit 518 to determine the estimated channel noise variance, ⁇ Z 2 .
  • the channel noise variance estimate ⁇ Z 2 and the interference variance ⁇ I 2 are summed at a summing unit 520 and divided into the signal power estimate S at a division unit 522 to give the CINR estimate 524 .
  • the first processing unit 516 is operable to produce an estimate, S, of the power of the signal at the output of the equalizer dependent upon the equalization matrix W H , a transfer function matrix H between the transmitting antennas and the receiving antennas, and the known value ⁇ X 2 of the transmitted signal and further is operable to produce the estimate, ⁇ I 2 , of the variance of the interference at the output of the equalizer dependent upon the equalization matrix W H , the transfer function matrix H, and the variance ⁇ X 2 of the transmitted signal.
  • the second processing unit 518 is operable to generate an estimate, ⁇ Z 2 , of the variance of the noise at the output of the equalizer dependent upon the equalization matrix W H and an estimate of the variance ⁇ 2 of the noise at the receiving antennas.
  • the summing unit 520 is operable to sum the estimate, ⁇ I 2 , of the variance of the interference and the estimate, ⁇ Z 2 , of the variance of the noise at the output of the equalizer
  • the division unit 522 is operable to produce the CINR by dividing the estimate, S, of the power of the signal at the output of the equalizer by the sum the estimate, ⁇ I 2 , of the variance of the interference and the estimate, ⁇ Z 2 , of the variance of the noise at the output of the equalizer.
  • the third processing unit 510 is operable to receive pilot tone symbols and corresponding sub-channel components 504 from the receiving antennas and to generate, therefrom, the transfer function matrix H between the transmitting antennas and the receiving antennas.
  • the fourth processing unit 512 is operable to receive sub-channel components corresponding to null symbols from the receiving antennas and is operable to generate, therefrom, the antenna noise variance estimate ⁇ 2 .
  • the fifth processing unit 514 is coupled to the processing units 510 and 512 and is operable to generate the equalization matrix W H dependent the transfer function matrix H and the antenna noise variance estimate ⁇ 2 .
  • the processing units may be implemented, for example, on a programmed processor such as a computer microprocessor or a digital signal processor.
  • the processing elements may be implemented using custom integrated circuits or programmable logic circuits (such as field programmable gate arrays).
  • Other embodiments, including combinations of the aforementioned embodiments, will be apparent to those of ordinary skill in the art.
  • the CINR may be estimated by a subscriber station, an intermediate station, or a base station.
  • the estimated CINR may be passed to other nodes in a network.
  • the carrier to interference-noise ratio of user 1 would be calculated as follows (assuming channel estimate is performed on tile basis):
  • CINR spec ⁇ ( ⁇ H ⁇ 1 , 1 ⁇ P A , 1 ⁇ 2 + ⁇ H ⁇ 1 , 1 ⁇ P A , 2 ⁇ 2 + ⁇ H ⁇ 2 , 1 ⁇ P A , 1 ⁇ 2 + ⁇ H ⁇ 2 , 1 ⁇ P A , 2 ⁇ 2 ) ⁇ ( ⁇ Y 1 A , 1 - H ⁇ 1 , 1 ⁇ P A , 1 ⁇ 2 + ⁇ Y 1 A , 2 - H ⁇ 1 , 1 ⁇ P A , 2 ⁇ 2 + ⁇ Y 1 A , 2 - H ⁇ 2 , 1 ⁇ P A , 1 ⁇ 2 + ⁇ Y 1 A , 2 - H ⁇ 2 , 1 ⁇ P A , 1 ⁇ 2 + ⁇ Y 1 A , 2 - H ⁇ 2 , 1 ⁇ P A , 2 ⁇ 2 ) ( 17 )
  • this is a poor estimate for MIMO and
  • the CINR estimate per tile for user 1 can be written as
  • the channel noise variance for user u is
  • FIG. 6 shows a plot of true CINR values (broken line 602 ) for an exemplary system together with an estimate (line 604 ) of the CINR obtained using the method of the present invention and a further estimate (line 606 ) of the CINR obtained using the method given in the WiMAX specification.
  • the estimate derived as recommended in the WiMAX specification is very poor. This is because the method was designed for systems that do not utilize SDMA.
  • the method of the present invention provides a CINR estimate that is in good agreement with true values.
  • the broken lines 608 indicate error bars that are +/ ⁇ 2 dB from the true CINR.
  • the method of the present invention produces estimates well within 2 dB of the true value, while the estimate derived as recommended in the WiMAX specification is often in error by much more than 2 dB.

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  • Engineering & Computer Science (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Signal Processing (AREA)
  • Physics & Mathematics (AREA)
  • Electromagnetism (AREA)
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  • Probability & Statistics with Applications (AREA)
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US11/839,759 US7792226B2 (en) 2007-08-16 2007-08-16 Method and apparatus for carrier power and interference-noise estimation in space division multiple access and multiple-input/multiple-output wireless communication systems
PCT/US2008/072910 WO2009026050A1 (fr) 2007-08-16 2008-08-12 Procédé et appareil pour estimer le bruit dû aux brouillages et la puissance d'un signal porteur dans des systèmes de communication sans fil à accès multiple par répartition spatiale et des systèmes de communication sans fil à entrées multiples/sorties multiples
KR1020107003234A KR101076483B1 (ko) 2007-08-16 2008-08-12 공간 분할 다중 접속 및 다중 입력/다중 출력 무선 통신 시스템에서 반송파 전력 및 간섭-잡음 추정을 위한 방법 및 장치
CN200880103177.7A CN101855833B (zh) 2007-08-16 2008-08-12 用于空分多址和多输入/多输出无线通信系统中的载波功率和干扰噪声估计的方法和装置

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US20090046772A1 (en) 2009-02-19
WO2009026050A1 (fr) 2009-02-26

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