US6853836B2 - Polar loop transmission circuit - Google Patents

Polar loop transmission circuit Download PDF

Info

Publication number
US6853836B2
US6853836B2 US10/000,694 US69401A US6853836B2 US 6853836 B2 US6853836 B2 US 6853836B2 US 69401 A US69401 A US 69401A US 6853836 B2 US6853836 B2 US 6853836B2
Authority
US
United States
Prior art keywords
output
signal
amplifier
input
phase
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Expired - Fee Related, expires
Application number
US10/000,694
Other languages
English (en)
Other versions
US20020080716A1 (en
Inventor
Michael Asam
Stefan Herzinger
Gunther Kraut
Martin Simon
Xiaopin Zhang
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Infineon Technologies AG
Original Assignee
Infineon Technologies AG
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Infineon Technologies AG filed Critical Infineon Technologies AG
Publication of US20020080716A1 publication Critical patent/US20020080716A1/en
Assigned to INFINEON TECHNOLOGIES AG reassignment INFINEON TECHNOLOGIES AG ASSIGNMENT OF ASSIGNORS INTEREST (SEE DOCUMENT FOR DETAILS). Assignors: ZHANG, XIAOPIN, HERZINGER, STEFAN, KRAUT, GUNTHER, SIMON, MARTIN, ASAM, MICHAEL
Application granted granted Critical
Publication of US6853836B2 publication Critical patent/US6853836B2/en
Adjusted expiration legal-status Critical
Expired - Fee Related legal-status Critical Current

Links

Images

Classifications

    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03C—MODULATION
    • H03C5/00—Amplitude modulation and angle modulation produced simultaneously or at will by the same modulating signal

Definitions

  • GSM global system for mobile communications
  • TDMA time-division multiplex access
  • GMSK Gaussian minimum shift keying
  • GMSK is particularly characterized in that its modulated signals exhibit a constant envelope, so that simple, nonlinear amplifiers can be used at the transmission end.
  • an amplitude modulation is to be used in the radio channel in order to take into account the bandwidth need in the mobile radio telephone service which increased as a result of internet applications, for example.
  • Information to be transmitted then, is not only encoded in the signal phase but also in the signal amplitude. Then, the envelope of the modulation signal is no longer constant. Linear transmission concepts are necessary for such a phase-accurate and amplitude-accurate signal transmission.
  • Linear power amplifiers have a low efficiency of approximately 25% to 35% compared to the nonlinear power amplifiers that can be used for the traditional GSM standard, whereby the nonlinear power amplifiers reach an efficiency of approximately 50%.
  • the efficiency is indicated as a quotient from transmitted high-frequency performance and utilized d.c. power.
  • the necessary insulator at the antenna output and the complicated power regulation—with incorporation of the base band—required for this concept is disadvantageous.
  • burst Even during a transmission time slot (burst), the amplifying properties of the power high-level stage or end stage are subject to modifications as a result of temperature fluctuations, fluctuations regarding the supply voltage etc. Furthermore, measuring bursts during the measuring-in of the transmitter can lead to specification violations of the allowed transmission performance.
  • U.S. Pat. No. 4,481,672 proposes a polar loop transmitter.
  • An input signal, which is to be transmitted and which is provided by a generator, and a feedback output signal, which is attenuated by an attenuator and which is converted into a deeper frequency level by a mixer is respectively separated into its polar components, i.e., into amplitude and phase.
  • a “polar resolver” having two limiters for acquiring the phase information is provided for this purpose.
  • An oscillator is driven by a phase detector, whereby the phase positions of both signals are supplied to it.
  • a differential amplifier is provided which compares the amplitudes of the two signals and which modulates the envelope of a high-frequency signal generated by an oscillator.
  • a power amplifier subsequently amplifies and filters the high-frequency signal, so that a transmitted signal is available.
  • a peak value sampling is also provided in order to avoid negative spikes.
  • the polar loop transmitter with a feedback branch can also function as a phase-locked loop (PLL).
  • PLL phase-locked loop
  • a polar loop transmission circuit includes a generator outputting an input signal and an oscillator having an output and generating a high-frequency signal dependent on a phase comparison signal.
  • the high-frequency signal is available at the output.
  • An amplitude modulator is connected to the output of the oscillator and receives the high-frequency signal.
  • the amplitude modulator has an output and, in dependence on an amplitude modulation signal received by the amplitude modulator, outputs an output signal derived from the high-frequency signal, at the output of the amplitude modulator.
  • a feedback path has an amplifier with an input connected to the output of the amplitude modulator and an output.
  • the amplifier has a control terminal for receiving a control signal.
  • the feedback path has a mixer with a mixer output and an input connected to the output of the amplifier.
  • the mixer outputs an intermediate frequency signal derived from the output signal and is available at the mixer output.
  • a first circuit is provided for generating the amplitude modulation signal by comparing amplitudes of the input signal and the intermediate frequency signal.
  • the first circuit is connected downstream of the generator and upstream of the amplitude modulator.
  • a second circuit is provided for generating the phase comparison signal by comparing phases of the input signal and the intermediate frequency signal.
  • the second circuit is connected downstream of the generator and upstream of the oscillator.
  • the power high-level stage referred to as amplitude modulator can be fashioned as a nonlinear amplifier which can be operated in saturation.
  • an amplifier having an efficiency of 50% can thus be utilized.
  • the described polar loop architecture shows linear transmission properties.
  • Input signals which have an additional amplitude modulation in addition to a phase modulation, therefore can be transmitted via a radio channel.
  • An amplifier is provided in the feedback path, whereby the output signal of the transmission circuit can be supplied to the amplifier at an input and whereby the amplifier, at the output, is connected to a first mixer fashioned as a downward mixer.
  • the amplifier is fashioned as a linear amplifier and is preferably configured such that it is suitable for attenuating the output signal.
  • the linear amplifier enables a controlled power level adjustment of the output signal.
  • the amplifier in the feedback path makes it possible to meet TDMA specifications, particularly with respect to the transmission time slots (bursts) in the modulation method 8PSK, Phase Shift Keying or other quadrature amplitude modulations (QAM), for example.
  • the high efficiency of the described transmission circuit which can be particularly achieved by a nonlinear amplitude modulator, enables long airtimes or, respectively, long operating times of the circuit and makes it possible to use small batteries or accumulators given mobile applications. This is particularly advantageous in the mobile radio telephone service.
  • the power level adjustability with the amplifier in the feedback path reduces the outlay of the power level compensation during the production.
  • the components following the feedback path can be configured for lower dynamics and can be constructed more simply when the linear amplifier is applied at the beginning of the feedback path.
  • the transmission circuit is less sensitive to temperature fluctuations and fluctuations in the operating voltage and feedbacks of an antenna that can be connected to the output, so that an insulator is not necessary at the output of the amplitude modulator.
  • Dual-mode mobile radio telephone devices For assuring a downward compatibility with respect to the GMSK modulation methods used in the previous GSM system, it can be desirable to set up what are referred to as dual-mode mobile radio telephone devices.
  • a nonlinear power amplifier is necessary in the transmitter and not a nonlinear one for GMSK and a linear one for 8 PSK, for example.
  • Even two power amplifiers can be foregone in dual-band devices since only two nonlinear power amplifiers are required instead of two nonlinear ones and two linear high-level stages.
  • Dual-band mobile radio telephone devices are suitable for the GSM standard in the 900 MHz band and in the 1800 MHz band, for example.
  • the described polar loop transmission circuit can be constructed with a small chip surface, low costs and a simple connection to a baseband component.
  • the polar loop architecture can effect a linearization of a nonlinear high-level stage or of a nonlinear amplitude modulator regarding the transmission data, whereby the transmission data are amplified in a phase-accurate and amplitude-accurate manner.
  • the amplitude modulator is a nonlinear controllable amplifier.
  • Nonlinear amplifiers such as class C-amplifiers are clearly more efficient than linear amplifiers and therefore have a lower current consumption.
  • the amplifier in the feedback path is a programmable amplifier (PGC, Programmable Gain Control) attenuating the output signal.
  • PPC Programmable Gain Control
  • the programmable amplifier thereby provides a constant signal level at its output.
  • the amplifier, with respect to its input signal, i.e., with respect to the output signal of the transmission circuit, is a linear amplifier attenuating a signal at its input in a linear fashion.
  • a control signal can be supplied to the control terminal of the amplifier in the feedback branch.
  • the output power level of the entire configuration can be controlled on the basis of the control signal. Therefore, the control signal is a set amplification signal. Since the amplifier is disposed in the branch of a negative feedback, the output level at the output of the amplitude modulation is greater the lower the amplification of the programmable amplifier.
  • the circuitry for providing the phase comparison signal includes a phase and frequency detector followed by a low-pass filter and a first limiter to which the intermediate frequency signal can be supplied and a second limiter to which the input signal can be supplied, whereby the limiters, at the output side, can be connected to an input of the phase and frequency detector respectively.
  • the input of the first limiter can be coupled with the output of the first mixer.
  • the input of the second limiter can be connected to the generator.
  • the generator can be fashioned as a single sideband generator, but, generally, it can also be fashioned as a modulation generator.
  • the output of the first limiter via a switch for example, can be connected to an input of the phase and frequency detector.
  • the output of the second limiter can be connected to a further input of the phase and frequency detector.
  • the output of the phase and frequency detector can be connected to the input of a low-pass filter.
  • the output of the low-pass filter can be connected to an input of the oscillator.
  • the oscillator can be a voltage-controlled oscillator.
  • the phase and frequency detector can be configured for forming a difference of a set phase and an actual phase, namely for forming a difference of the phase positions of the input signal and intermediate frequency signal.
  • a bypass branch having a second mixer is provided which is connected to the output of the oscillator and which provides a further intermediate frequency signal at its output, which, at an input, can be supplied to the phase and frequency detector as a set signal.
  • the described transmission circuit is suitable for the transmission in time slots (bursts). A useable output signal, however, is not available until the beginning of a transmission time slot, so that a feedback signal cannot be consulted either in the phase and frequency detector for the transient effect of the control loop.
  • the bypass branch can be used for this purpose, which is active prior to the beginning of a transmission time slot and which, with the second mixer, converts a signal that is derivable at the oscillator VCO into an intermediate frequency signal, which, via a switch for example, can be supplied to the phase and frequency detector at an input.
  • the second mixer can be connected to the same local oscillator, whereby the first mixer can also be connected to it.
  • a switch which, dependent on its switch position, either connects the output of the first limiter to an input of, the phase and frequency detector or connects the output of the second mixer to the input of the phase and frequency detector.
  • the circuit for providing the amplitude modulation signal has a difference amplifier which has a plus-input and a minus-input and which is followed by a low-pass filter, whereby the rectified input signal can be supplied to the plus-input and the rectified intermediate frequency signal to the minus-input.
  • a rectifier For rectifying the input signal and the intermediate frequency signal, a rectifier can be respectively provided, whereby a first rectifier, at the input side, can be connected to the generator and, at the output side, can be connected to an input of the difference amplifier, and a second one, at the input side, can be connected to the feedback path and, at the output side, can be connected to a further input of the difference amplifier.
  • a low-pass filter which can be connected at its output to the control input of the amplitude modulator, can be connected to an output of the difference amplifier.
  • a diode rectifier is respectively provided for rectifying the input signal and the intermediate frequency signal. It is particularly simple to implement diode rectifiers.
  • a synchronous rectifier can be respectively provided for rectifying the input signal and the intermediate frequency signal.
  • the synchronous rectifiers additionally via auxiliary inputs, can be connected to the corresponding limited signal, to the outputs of the limiters, for example.
  • a ramping amplifier fashioned as a linear, controllable amplifier is provided. It serves the purpose of adjusting the performance of the output signal at the beginning and the end of transmission time slots.
  • the ramping amplifier with its input, is preferably connected to the output of the first mixer.
  • FIGURE of the drawing is a block diagram of a first exemplary embodiment according to the invention.
  • a polar loop transmission circuit with a generator SSB providing a signal at its output that is fashioned as a single sideband signal.
  • an output of the generator SSB is connected to respectively one input of a limiter LIM 2 and of a diode rectifier SG 1 .
  • the limiter LIM 2 provides a piece of phase information of the input signal at its output, while the amplitude of the input signal can be derived at the output of the diode rectifier SG 1 .
  • the set phase information provided by the limiter LIM 2 , to a phase and frequency detector PFD, is compared to actual phase information provided by a limiter LIM 1 by subtraction of the phase positions.
  • the phase and frequency detector PFD provides a phase comparison signal PS at its output.
  • An input of the limiter LIM 1 is thereby connected to a feedback path RK.
  • a low-pass filter TP having a voltage-controlled oscillator VCO connected to its output is connected to an output of the phase and frequency detector PFD.
  • An amplitude modulator AM which is fashioned as a power amplifier and which is an amplifier operated in saturation, is connected, with its input, to the output of the voltage-controlled oscillator VCO.
  • the amplitude modulator AM has a control input to which an amplitude modulation signal AS can be supplied.
  • a difference amplifier DV having a low-pass filter TP connected to its output provides the amplitude modulation signal AS, whereby the output of the low-pass filter TP is connected to the control input of the amplitude modulator AM.
  • the difference amplifier DV has a non-inverting input, whereby the first diode rectifier SG 1 is connected to it, and has an inverting input having a second diode rectifier SG 2 connected to it.
  • the input of the first diode rectifier SG 1 is connected to the generator SSB; the first diode rectifier SG 1 , therefore, provides the amplitude information of the input signal as a set value at its output.
  • the input of the second diode rectifier SG 2 is connected to the feedback path RK and provides the amplitude information or, respectively, the envelope of a signal derived from the output signal as an actual value at its output.
  • the feedback path RK starts at the output of the amplitude modulator AM which is connected to an input of a programmable amplifier PV.
  • the programmable amplifier PV has a control terminal S.
  • the output of the programmable amplifier PV is connected to a first input of a first mixer M 1 .
  • a local oscillator LO is connected to a further input of the first mixer M 1 .
  • the first mixer M 1 provides an intermediate frequency signal ZF at its output, whereby the intermediate frequency signal ZF has a carrier frequency that can be derived from subtracting the carrier frequency from a high-frequency signal HF and a local oscillator signal.
  • a ramping amplifier PR whose output is connected to the input of the limiter LIM 1 and to the input of the diode rectifier SG 2 , is connected to the output of the first mixer M 1 with its input.
  • the ramping amplifier PR has a terminal for supplying a ramping signal RS.
  • the local oscillator LO is also connected to an input of a second mixer M 2 , which sets back the output signal of the voltage-controlled oscillator VCO into a further intermediate frequency signal.
  • a further input of the second mixer M 2 is connected to the output of the voltage-controlled oscillator VCO.
  • the second mixer M 2 with its output, is connected to a switch SW, which can connect through the output signal of the second mixer M 2 onto an input of the phase and frequency detector PFD.
  • a transmitting antenna can be connected to the high-frequency output OUT.
  • the output signal provided at the high-frequency output OUT thereby is the input signal which is amplified in a phase-accurate and amplitude-accurate fashion and which is provided at the output of the generator SSB.
  • the output signal provided at the high-frequency output OUT of the transmission circuit is attenuated with the programmable amplifier PV in the feedback path. Therefore, a high-frequency signal HF having a defined power level is pending at its output, whereby the power level is constant apart from fluctuations that are caused by the amplitude modulation.
  • the power level at the output OUT can be controlled at the control terminal S on the basis of a control signal.
  • the programmable amplifier PV is a linear amplifier that linearity attenuates the signal that can be supplied to its input.
  • the voltage of the high-frequency signal HF provided at its output, nonlinear is dependent on an adjustment signal that can be supplied to the control terminal S and is 2 dB per least-significant bit change of the adjustment signal in the present example.
  • the first mixer M 1 transforms the high-frequency signal HF back into an intermediate frequency signal.
  • the power ramping amplifier PR which can have the intermediate frequency signal ZF supplied to its input, effects a controlled upward adjustment of the performance of the output signal at the output OUT at the beginning of a transmission time slot (burst) and correspondingly effects a controlled downward adjustment of the output power at the output OUT at the end of transmission time slots.
  • the ramping amplifier PR has a control input for this purpose, whereby a ramping signal RS controlling an amplification factor or attenuation factor of the ramping amplifier PR can be supplied to it.
  • a locking of the phase-locked loop already before the beginning of the transmission time slot is effected by activating the bypass path BP with the switch SW, so that the switch SW is switched at the beginning of the transmission time slot such that the output of the limiter LIM 1 is connected to an input of the phase and frequency detector PFD, the ramp-shaped upward adjustment of the output power of the transmission circuit does not start prior to this.
  • the circuit features with the ramping amplifier PR and the bypass path BP allow a controlled adjustment of the power level at the output OUT and therefore make it possible to meet specification limiting values that are typically provided with respect to TDMA systems.
  • the amplitude modulator AM is fashioned as a nonlinear, controllable power amplifier, it is highly efficient, i.e., the quotient from the output power and used d.c. power is relatively large and is at 50% in the described example.
  • an insulator is not necessary at the output OUT.
  • the generator SSB can also be fashioned as a generator providing a modulated signal at its output.
  • the programmable amplifier PV is disposed at the beginning of the feedback path RK, the following stages in the feedback path can be configured for lower dynamics, however, they should be sufficient for high linearity requirements.
  • the described control concept compensates temperature fluctuations and operating voltage fluctuations.
  • the complicated power level compensation which normally arises during the production of the device, and therefore the outlay associated with it can also be clearly reduced.
  • the described amplitude modulator AM which is fashioned as a nonlinear amplifier and which sometimes is also referred to as power amplifier, at the same time, can serve as a power amplifier in a traditional GMSK modulation method used for the established GSM standard, so that two power amplifiers, namely a nonlinear one and a linear one, are no longer necessary in future dual-mode devices but only one power amplifier, namely a nonlinear one. This is associated with less outlay, considerable cost savings and savings regarding the chip surface or, respectively, printed circuit board space.
  • the described transmission architecture is particularly suitable for the application in future mobile radio telephone systems which are based on modulation methods that also have an amplitude modulation in addition to a phase modulation.

Landscapes

  • Transmitters (AREA)
  • Digital Transmission Methods That Use Modulated Carrier Waves (AREA)
US10/000,694 2000-11-15 2001-11-15 Polar loop transmission circuit Expired - Fee Related US6853836B2 (en)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
DE10056472.0 2000-11-15
DE10056472A DE10056472A1 (de) 2000-11-15 2000-11-15 Polar-Loop-Sendeschaltung

Publications (2)

Publication Number Publication Date
US20020080716A1 US20020080716A1 (en) 2002-06-27
US6853836B2 true US6853836B2 (en) 2005-02-08

Family

ID=7663311

Family Applications (1)

Application Number Title Priority Date Filing Date
US10/000,694 Expired - Fee Related US6853836B2 (en) 2000-11-15 2001-11-15 Polar loop transmission circuit

Country Status (4)

Country Link
US (1) US6853836B2 (fr)
EP (1) EP1211801B1 (fr)
JP (1) JP3698669B2 (fr)
DE (2) DE10056472A1 (fr)

Cited By (20)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20030109240A1 (en) * 2001-12-12 2003-06-12 D.S.P.C. Technologies Ltd. Method and polar-loop transmitter with origin offset for zero-crossing signals
US20040166885A1 (en) * 2001-06-20 2004-08-26 Sarachi Mohsen Power control for non-constant envelope modulation
US20040180639A1 (en) * 2002-05-29 2004-09-16 Ralf Herzberg Circuit arrangement for switching a mobile radio transmitter between two modulation modes
US20040198257A1 (en) * 2002-05-31 2004-10-07 Ryoichi Takano Communication semiconductor integrated circuit, a wireless communication apparatus, and a loop gain calibration method
US20050059360A1 (en) * 2003-09-16 2005-03-17 Andrew Corporation, A Delaware Corporation Compensation of filters in radio transmitters
US20050059372A1 (en) * 2003-09-17 2005-03-17 Satoshi Arayashiki Communication semiconductor integrated circuit device
US20050176388A1 (en) * 2002-05-31 2005-08-11 Taizo Yamawaki Transmitter and wireless communication apparatus using the transmitter
US20050191973A1 (en) * 2004-02-27 2005-09-01 Matsushita Electric Industrial Co., Ltd. High-frequency circuit device
US20050233714A1 (en) * 2002-09-26 2005-10-20 Renesas Technology Corporation Variable gain amplifier for use in communications
US20060008029A1 (en) * 2002-12-18 2006-01-12 Houman Jafari Transmitter stage
US20060068726A1 (en) * 2004-08-26 2006-03-30 Taizo Yamawaki Transmitter and radio communication terminal using the same
US20060234634A1 (en) * 2002-12-11 2006-10-19 Benoit Agnus Integrated circuit comprising a transmission channel with an integrated independent tester
WO2007005139A1 (fr) * 2005-06-29 2007-01-11 Agilent Technologies, Inc. Analyse de reseau et dispositif d'analyse portant independamment sur la partie valeur et la partie phase
US20080088320A1 (en) * 2005-06-29 2008-04-17 Koji Harada Network measuring and apparatus for magnitude and phase portion independently
US20080297247A1 (en) * 2007-05-30 2008-12-04 Sige Semiconductor Inc. Method and apparatus for distortion correction of RF amplifiers
US20080318620A1 (en) * 2007-06-21 2008-12-25 Stefan Van Waasen Multi-mode modulator
US7689182B1 (en) * 2006-10-12 2010-03-30 Rf Micro Devices, Inc. Temperature compensated bias for AM/PM improvement
US7805115B1 (en) * 2003-06-02 2010-09-28 Analog Devices, Inc. Variable filter systems and methods for enhanced data rate communication systems
US8224265B1 (en) 2005-06-13 2012-07-17 Rf Micro Devices, Inc. Method for optimizing AM/AM and AM/PM predistortion in a mobile terminal
US9496827B2 (en) 2015-04-14 2016-11-15 Stmicroelectronics (Grenoble 2) Sas Radio frequency signal power amplification circuit

Families Citing this family (10)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
GB2416254B (en) 2002-05-31 2006-06-28 Renesas Tech Corp Semiconductor integrated circuit for communication, radio-communications apparatus, and transmission starting method
GB2389253B (en) 2002-05-31 2005-09-21 Hitachi Ltd Transmitter and semiconductor integrated circuit for communication
GB2389255B (en) * 2002-05-31 2005-08-31 Hitachi Ltd Apparatus for radio telecommunication system and method of building up output power
DE10257435B3 (de) * 2002-11-14 2004-09-09 Fraunhofer-Gesellschaft zur Förderung der angewandten Forschung e.V. Sendestufe
ATE339805T1 (de) 2002-11-14 2006-10-15 Fraunhofer Ges Forschung Sendestufe mit phasen und amplitudenregelschleife
ATE551773T1 (de) * 2003-02-20 2012-04-15 Sony Ericsson Mobile Comm Ab Effizienter modulation von hochfrequenzsignalen
DE102004048702B3 (de) * 2004-10-06 2006-06-14 Siemens Ag Polar Loop-Schaltungsanordnung mit Verzerrungsunterdrückung und Verfahren zur Verzerrungsunterdrückung in einer Polar Loop-Schaltungsanordnung
US8070224B2 (en) * 2005-04-20 2011-12-06 Audiovox Corporation Vehicle entertainment system incorporated within the armrest/console of a vehicle
US7412215B1 (en) * 2005-06-03 2008-08-12 Rf Micro Devices, Inc. System and method for transitioning from one PLL feedback source to another
US10955450B2 (en) * 2019-03-14 2021-03-23 Rohde & Schwarz Gmbh & Co. Kg System and method for real-time visualization of radiation pattern

Citations (20)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US4481672A (en) 1982-03-26 1984-11-06 U.S. Philips Corporation Polar loop transmitter
US4933986A (en) * 1989-08-25 1990-06-12 Motorola, Inc. Gain/phase compensation for linear amplifier feedback loop
US5222250A (en) * 1992-04-03 1993-06-22 Cleveland John F Single sideband radio signal processing system
US5226167A (en) * 1989-12-21 1993-07-06 Mitsubishi Denki Kabushiki Kaisha Microcomputer circuit for attenuating oscillations in a resonant circuit by reversing phase and feeding back resonant circuit output oscillation voltage
EP0638994A1 (fr) 1993-08-13 1995-02-15 Philips Electronics Uk Limited Emetteur et amplificateur de puissance pour un tel émetteur
US5430416A (en) 1994-02-23 1995-07-04 Motorola Power amplifier having nested amplitude modulation controller and phase modulation controller
US5732333A (en) * 1996-02-14 1998-03-24 Glenayre Electronics, Inc. Linear transmitter using predistortion
US5920556A (en) * 1996-05-07 1999-07-06 Nokia Mobile Phones Limited Frequency modulation using a phase-locked loop
US6002923A (en) * 1997-11-07 1999-12-14 Telefonaktiebolaget Lm Ericsson Signal generation in a communications transmitter
US6047168A (en) * 1996-06-28 2000-04-04 Telefonaktiebolaget Lm Ericsson Device and method for radio transmitters
US6101224A (en) * 1998-10-07 2000-08-08 Telefonaktiebolaget Lm Ericsson Method and apparatus for generating a linearly modulated signal using polar modulation
US6194963B1 (en) * 1998-11-18 2001-02-27 Ericsson Inc. Circuit and method for I/Q modulation with independent, high efficiency amplitude modulation
US6215986B1 (en) * 1997-09-26 2001-04-10 Nortel Networks Corporation Reducing radio transmitter distortion
US6240278B1 (en) * 1998-07-30 2001-05-29 Motorola, Inc. Scalar cost function based predistortion linearizing device, method, phone and basestation
US6377784B2 (en) * 1999-02-09 2002-04-23 Tropian, Inc. High-efficiency modulation RF amplifier
US6477371B1 (en) * 1997-03-27 2002-11-05 Siemens Aktiengesellschaft Method and configuration for transmitting data
US6590940B1 (en) * 1999-05-17 2003-07-08 Ericsson Inc. Power modulation systems and methods that separately amplify low and high frequency portions of an amplitude waveform
US6631254B1 (en) * 1999-05-10 2003-10-07 Securicor Wireless Technology Limited Apparatus for producing a radio-frequency signal
US6708044B1 (en) * 2000-04-04 2004-03-16 Nec America, Inc. Apparatus and method for automated band selection via synthesizer bit insertion
US6792282B1 (en) * 2000-09-21 2004-09-14 Skyworks Solutions, Inc. Multiple step switched translation loop for power amplifier feedback control

Patent Citations (21)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US4481672A (en) 1982-03-26 1984-11-06 U.S. Philips Corporation Polar loop transmitter
US4933986A (en) * 1989-08-25 1990-06-12 Motorola, Inc. Gain/phase compensation for linear amplifier feedback loop
US5226167A (en) * 1989-12-21 1993-07-06 Mitsubishi Denki Kabushiki Kaisha Microcomputer circuit for attenuating oscillations in a resonant circuit by reversing phase and feeding back resonant circuit output oscillation voltage
US5222250A (en) * 1992-04-03 1993-06-22 Cleveland John F Single sideband radio signal processing system
EP0638994A1 (fr) 1993-08-13 1995-02-15 Philips Electronics Uk Limited Emetteur et amplificateur de puissance pour un tel émetteur
DE4480702C2 (de) 1994-02-23 2000-04-20 Motorola Inc Leistungsverstärker mit einer Amplitudenmodulationssteuervorrichtung und einer damit verbundenen Phasenmodulationsvorrichtung
US5430416A (en) 1994-02-23 1995-07-04 Motorola Power amplifier having nested amplitude modulation controller and phase modulation controller
US5732333A (en) * 1996-02-14 1998-03-24 Glenayre Electronics, Inc. Linear transmitter using predistortion
US5920556A (en) * 1996-05-07 1999-07-06 Nokia Mobile Phones Limited Frequency modulation using a phase-locked loop
US6047168A (en) * 1996-06-28 2000-04-04 Telefonaktiebolaget Lm Ericsson Device and method for radio transmitters
US6477371B1 (en) * 1997-03-27 2002-11-05 Siemens Aktiengesellschaft Method and configuration for transmitting data
US6215986B1 (en) * 1997-09-26 2001-04-10 Nortel Networks Corporation Reducing radio transmitter distortion
US6002923A (en) * 1997-11-07 1999-12-14 Telefonaktiebolaget Lm Ericsson Signal generation in a communications transmitter
US6240278B1 (en) * 1998-07-30 2001-05-29 Motorola, Inc. Scalar cost function based predistortion linearizing device, method, phone and basestation
US6101224A (en) * 1998-10-07 2000-08-08 Telefonaktiebolaget Lm Ericsson Method and apparatus for generating a linearly modulated signal using polar modulation
US6194963B1 (en) * 1998-11-18 2001-02-27 Ericsson Inc. Circuit and method for I/Q modulation with independent, high efficiency amplitude modulation
US6377784B2 (en) * 1999-02-09 2002-04-23 Tropian, Inc. High-efficiency modulation RF amplifier
US6631254B1 (en) * 1999-05-10 2003-10-07 Securicor Wireless Technology Limited Apparatus for producing a radio-frequency signal
US6590940B1 (en) * 1999-05-17 2003-07-08 Ericsson Inc. Power modulation systems and methods that separately amplify low and high frequency portions of an amplitude waveform
US6708044B1 (en) * 2000-04-04 2004-03-16 Nec America, Inc. Apparatus and method for automated band selection via synthesizer bit insertion
US6792282B1 (en) * 2000-09-21 2004-09-14 Skyworks Solutions, Inc. Multiple step switched translation loop for power amplifier feedback control

Non-Patent Citations (2)

* Cited by examiner, † Cited by third party
Title
Peter B. Kennington: "Linearised RF Amplifier and Transmitter Techniques", Wireless Systems International Ltd., 1998, pp. 10-11.
V. Petrovic et al.: "Polar-Loop Transmitter", School of Electrical Engineering, Mar. 1979;.

Cited By (34)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US7289777B2 (en) 2001-06-20 2007-10-30 Nokia Corporation Power control for non-constant envelope modulation
US20040166885A1 (en) * 2001-06-20 2004-08-26 Sarachi Mohsen Power control for non-constant envelope modulation
US7088968B2 (en) * 2001-12-12 2006-08-08 Intel Corporation Method and polar-loop transmitter with origin offset for zero-crossing signals
US20030109240A1 (en) * 2001-12-12 2003-06-12 D.S.P.C. Technologies Ltd. Method and polar-loop transmitter with origin offset for zero-crossing signals
US20040180639A1 (en) * 2002-05-29 2004-09-16 Ralf Herzberg Circuit arrangement for switching a mobile radio transmitter between two modulation modes
US7050772B2 (en) * 2002-05-29 2006-05-23 Siemens Aktiengesellschaft Circuit arrangement for switching a mobile radio transmitter between two modulation modes
US20050176388A1 (en) * 2002-05-31 2005-08-11 Taizo Yamawaki Transmitter and wireless communication apparatus using the transmitter
US7424276B2 (en) * 2002-05-31 2008-09-09 Renesas Technology Corp. Transmitter and wireless communication apparatus using the transmitter
US7082290B2 (en) * 2002-05-31 2006-07-25 Renesas Technology Corp. Communication semiconductor integrated circuit, a wireless communication apparatus, and a loop gain calibration method
US20040198257A1 (en) * 2002-05-31 2004-10-07 Ryoichi Takano Communication semiconductor integrated circuit, a wireless communication apparatus, and a loop gain calibration method
US20060189285A1 (en) * 2002-05-31 2006-08-24 Ryoichi Takano Communication semiconductor integrated circuit, a wireless communication apparatus, and a loop gain calibration method
US20050233714A1 (en) * 2002-09-26 2005-10-20 Renesas Technology Corporation Variable gain amplifier for use in communications
US20060234634A1 (en) * 2002-12-11 2006-10-19 Benoit Agnus Integrated circuit comprising a transmission channel with an integrated independent tester
US20060008029A1 (en) * 2002-12-18 2006-01-12 Houman Jafari Transmitter stage
US7805115B1 (en) * 2003-06-02 2010-09-28 Analog Devices, Inc. Variable filter systems and methods for enhanced data rate communication systems
US7149482B2 (en) * 2003-09-16 2006-12-12 Andrew Corporation Compensation of filters in radio transmitters
US20050059360A1 (en) * 2003-09-16 2005-03-17 Andrew Corporation, A Delaware Corporation Compensation of filters in radio transmitters
US20050059372A1 (en) * 2003-09-17 2005-03-17 Satoshi Arayashiki Communication semiconductor integrated circuit device
US7187911B2 (en) * 2003-09-17 2007-03-06 Renesas Technology Corp. Calibrated PLL for wide band communication semiconductor integrated polar loop transmitter
US20070111675A1 (en) * 2003-09-17 2007-05-17 Satoshi Arayashiki Communication semiconductor integrated circuit device
US7450921B2 (en) 2003-09-17 2008-11-11 Renesas Technology Corp. Communication semiconductor integrated circuit device for use in a mobile communication device for correcting variations in the oscillation frequency of a transmission oscillator by calibrating a current of the charge pump
US20050191973A1 (en) * 2004-02-27 2005-09-01 Matsushita Electric Industrial Co., Ltd. High-frequency circuit device
US20080233899A1 (en) * 2004-02-27 2008-09-25 Matsushita Electric Industrial Co., Ltd. High-frequency circuit device
US7706835B2 (en) 2004-02-27 2010-04-27 Panasonic Corporation High-frequency circuit device
US20060068726A1 (en) * 2004-08-26 2006-03-30 Taizo Yamawaki Transmitter and radio communication terminal using the same
US8224265B1 (en) 2005-06-13 2012-07-17 Rf Micro Devices, Inc. Method for optimizing AM/AM and AM/PM predistortion in a mobile terminal
US20080088320A1 (en) * 2005-06-29 2008-04-17 Koji Harada Network measuring and apparatus for magnitude and phase portion independently
WO2007005139A1 (fr) * 2005-06-29 2007-01-11 Agilent Technologies, Inc. Analyse de reseau et dispositif d'analyse portant independamment sur la partie valeur et la partie phase
US7689182B1 (en) * 2006-10-12 2010-03-30 Rf Micro Devices, Inc. Temperature compensated bias for AM/PM improvement
US20080297247A1 (en) * 2007-05-30 2008-12-04 Sige Semiconductor Inc. Method and apparatus for distortion correction of RF amplifiers
US7702301B2 (en) * 2007-05-30 2010-04-20 Sige Semiconductor Inc. Method and apparatus for distortion correction of RF amplifiers
US20080318620A1 (en) * 2007-06-21 2008-12-25 Stefan Van Waasen Multi-mode modulator
US7853212B2 (en) 2007-06-21 2010-12-14 Infineon Technologies Ag Multi-mode modulator
US9496827B2 (en) 2015-04-14 2016-11-15 Stmicroelectronics (Grenoble 2) Sas Radio frequency signal power amplification circuit

Also Published As

Publication number Publication date
EP1211801A3 (fr) 2003-10-29
DE10056472A1 (de) 2002-05-29
DE50106875D1 (de) 2005-09-01
US20020080716A1 (en) 2002-06-27
JP3698669B2 (ja) 2005-09-21
EP1211801A2 (fr) 2002-06-05
EP1211801B1 (fr) 2005-07-27
JP2002208864A (ja) 2002-07-26

Similar Documents

Publication Publication Date Title
US6853836B2 (en) Polar loop transmission circuit
US7359685B2 (en) Transmitting stage
JP4527713B2 (ja) Ｒｆ信号の効率的な変調
US7672648B1 (en) System for linear amplitude modulation
US8081935B2 (en) Multiple-mode modulator to process baseband signals
US6975686B1 (en) IQ modulation systems and methods that use separate phase and amplitude signal paths
US5251331A (en) High efficiency dual mode power amplifier apparatus
US7366481B2 (en) Apparatus for radio telecommunication system and method of building up output power
US6587511B2 (en) Radio frequency transmitter and methods thereof
JP2964883B2 (ja) 送信器
US7062236B2 (en) Transmitter circuits
US8548400B2 (en) System and method for polar modulation using power amplifier bias control
US7558542B2 (en) System and method for providing a transmitter for polar modulation and power amplifier linearization
US7412213B1 (en) Envelope limiting for polar modulators
US6947713B2 (en) Amplitude- and frequency- or phase-modulated radio frequency signal generator and the transmitter incorporating same
US20070183532A1 (en) Method and system for transmitter envelope delay calibration
US20060066398A1 (en) High frequency power amplifier circuit and electric component for high frequency power amplifier
WO2003103162A1 (fr) Emetteur et dispositif de communication hertzienne employant l'emetteur
WO2002047249A2 (fr) Montage d'amplificateur a boucle polaire
US7269232B2 (en) Device for producing a phase and amplitude modulated radio frequency signal
US7024167B2 (en) Method for amplitude modulation of a radio frequency signal, and device therefor
US5247542A (en) QPSK power amplifier distortion correction system
JP2008072735A (ja) Ｉｑ変調システム並びに個別的な位相パス及び信号パスを使用する方法
US7983632B2 (en) Feedback control loop for amplitude modulation in a polar transmitter with a translational loop
US20160373071A1 (en) Temperature compensation technique for envelope tracking system

Legal Events

Date Code Title Description
FEPP Fee payment procedure

Free format text: PAYOR NUMBER ASSIGNED (ORIGINAL EVENT CODE: ASPN); ENTITY STATUS OF PATENT OWNER: LARGE ENTITY

AS Assignment

Owner name: INFINEON TECHNOLOGIES AG, GERMANY

Free format text: ASSIGNMENT OF ASSIGNORS INTEREST;ASSIGNORS:ASAM, MICHAEL;HERZINGER, STEFAN;KRAUT, GUNTHER;AND OTHERS;REEL/FRAME:016123/0653;SIGNING DATES FROM 20011130 TO 20020111

FPAY Fee payment

Year of fee payment: 4

FPAY Fee payment

Year of fee payment: 8

REMI Maintenance fee reminder mailed
LAPS Lapse for failure to pay maintenance fees
STCH Information on status: patent discontinuation

Free format text: PATENT EXPIRED DUE TO NONPAYMENT OF MAINTENANCE FEES UNDER 37 CFR 1.362

FP Lapsed due to failure to pay maintenance fee

Effective date: 20170208