US4510465A - Linear gain voltage controlled oscillator with modulation compensation - Google Patents
Linear gain voltage controlled oscillator with modulation compensation Download PDFInfo
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- US4510465A US4510465A US06/522,623 US52262383A US4510465A US 4510465 A US4510465 A US 4510465A US 52262383 A US52262383 A US 52262383A US 4510465 A US4510465 A US 4510465A
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- controlled oscillator
- voltage controlled
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- 230000000694 effects Effects 0.000 description 3
- 230000005236 sound signal Effects 0.000 description 3
- 230000033228 biological regulation Effects 0.000 description 2
- 230000005540 biological transmission Effects 0.000 description 2
- 230000000295 complement effect Effects 0.000 description 2
- 238000012986 modification Methods 0.000 description 2
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Classifications
-
- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03C—MODULATION
- H03C3/00—Angle modulation
- H03C3/02—Details
- H03C3/09—Modifications of modulator for regulating the mean frequency
- H03C3/0908—Modifications of modulator for regulating the mean frequency using a phase locked loop
- H03C3/0958—Modifications of modulator for regulating the mean frequency using a phase locked loop applying frequency modulation by varying the characteristics of the voltage controlled oscillator
-
- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03B—GENERATION OF OSCILLATIONS, DIRECTLY OR BY FREQUENCY-CHANGING, BY CIRCUITS EMPLOYING ACTIVE ELEMENTS WHICH OPERATE IN A NON-SWITCHING MANNER; GENERATION OF NOISE BY SUCH CIRCUITS
- H03B5/00—Generation of oscillations using amplifier with regenerative feedback from output to input
- H03B5/08—Generation of oscillations using amplifier with regenerative feedback from output to input with frequency-determining element comprising lumped inductance and capacitance
- H03B5/12—Generation of oscillations using amplifier with regenerative feedback from output to input with frequency-determining element comprising lumped inductance and capacitance active element in amplifier being semiconductor device
- H03B5/1203—Generation of oscillations using amplifier with regenerative feedback from output to input with frequency-determining element comprising lumped inductance and capacitance active element in amplifier being semiconductor device the amplifier being a single transistor
-
- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03B—GENERATION OF OSCILLATIONS, DIRECTLY OR BY FREQUENCY-CHANGING, BY CIRCUITS EMPLOYING ACTIVE ELEMENTS WHICH OPERATE IN A NON-SWITCHING MANNER; GENERATION OF NOISE BY SUCH CIRCUITS
- H03B5/00—Generation of oscillations using amplifier with regenerative feedback from output to input
- H03B5/08—Generation of oscillations using amplifier with regenerative feedback from output to input with frequency-determining element comprising lumped inductance and capacitance
- H03B5/12—Generation of oscillations using amplifier with regenerative feedback from output to input with frequency-determining element comprising lumped inductance and capacitance active element in amplifier being semiconductor device
- H03B5/1228—Generation of oscillations using amplifier with regenerative feedback from output to input with frequency-determining element comprising lumped inductance and capacitance active element in amplifier being semiconductor device the amplifier comprising one or more field effect transistors
-
- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03B—GENERATION OF OSCILLATIONS, DIRECTLY OR BY FREQUENCY-CHANGING, BY CIRCUITS EMPLOYING ACTIVE ELEMENTS WHICH OPERATE IN A NON-SWITCHING MANNER; GENERATION OF NOISE BY SUCH CIRCUITS
- H03B5/00—Generation of oscillations using amplifier with regenerative feedback from output to input
- H03B5/08—Generation of oscillations using amplifier with regenerative feedback from output to input with frequency-determining element comprising lumped inductance and capacitance
- H03B5/12—Generation of oscillations using amplifier with regenerative feedback from output to input with frequency-determining element comprising lumped inductance and capacitance active element in amplifier being semiconductor device
- H03B5/1237—Generation of oscillations using amplifier with regenerative feedback from output to input with frequency-determining element comprising lumped inductance and capacitance active element in amplifier being semiconductor device comprising means for varying the frequency of the generator
- H03B5/124—Generation of oscillations using amplifier with regenerative feedback from output to input with frequency-determining element comprising lumped inductance and capacitance active element in amplifier being semiconductor device comprising means for varying the frequency of the generator the means comprising a voltage dependent capacitance
- H03B5/1243—Generation of oscillations using amplifier with regenerative feedback from output to input with frequency-determining element comprising lumped inductance and capacitance active element in amplifier being semiconductor device comprising means for varying the frequency of the generator the means comprising a voltage dependent capacitance the means comprising voltage variable capacitance diodes
-
- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03C—MODULATION
- H03C3/00—Angle modulation
- H03C3/10—Angle modulation by means of variable impedance
- H03C3/12—Angle modulation by means of variable impedance by means of a variable reactive element
- H03C3/22—Angle modulation by means of variable impedance by means of a variable reactive element the element being a semiconductor diode, e.g. varicap diode
- H03C3/225—Angle modulation by means of variable impedance by means of a variable reactive element the element being a semiconductor diode, e.g. varicap diode using field effect transistors
-
- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03C—MODULATION
- H03C2200/00—Indexing scheme relating to details of modulators or modulation methods covered by H03C
- H03C2200/0037—Functional aspects of modulators
- H03C2200/005—Modulation sensitivity
-
- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03C—MODULATION
- H03C2200/00—Indexing scheme relating to details of modulators or modulation methods covered by H03C
- H03C2200/0037—Functional aspects of modulators
- H03C2200/0079—Measures to linearise modulation or reduce distortion of modulation characteristics
- H03C2200/0083—Predistortion of input modulating signal to obtain a linear modulation characteristic
-
- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03L—AUTOMATIC CONTROL, STARTING, SYNCHRONISATION OR STABILISATION OF GENERATORS OF ELECTRONIC OSCILLATIONS OR PULSES
- H03L2207/00—Indexing scheme relating to automatic control of frequency or phase and to synchronisation
- H03L2207/06—Phase locked loops with a controlled oscillator having at least two frequency control terminals
Definitions
- This invention relates generally to the field of phase locked loop frequency synthesizers. More particularly, this invention relates to wide band phase-locked loop frequency synthesizers for angular modulation systems requiring constant modulation levels over the entire radio frequency band of operation of the synthesizer.
- Conventional voltage controlled oscillators which are used in the phase locked loop frequency synthesizers for such broadband transmitters, typically utilize voltage variable capacitor elements known as varactor diodes. These varactor diodes can resonate with an inductive element such that as the voltage applied to a varactor diode varies, the capacitance changes resulting in a shift in the resonant frequency of the oscillator.
- the output frequency versus control voltage characteristics of such an oscillator is shown in a broken line as curve 10 of FIG. 1.
- the VCO gain factor K 0 (expressed in MHz/volt) exhibits a similar non-linear shape as shown in FIG. 2 as curve 15, also shown in a broken line.
- control voltage of the VCO is typically modulated with audio frequency voltages to produce a resultant FM deviation. If the conventional voltage controlled oscillator is operated over a wide frequency band the non-linearities of FIGS. 1 and 2 manifest themselves as a variation in FM deviation across the frequency band.
- this variation in FM deviation or non-linearity is seen in curve 20 shown in a broken line.
- modulation is directly proportioned to K 0 so that at lower frequencies where a low level of control voltage is utilized, resultant modulation may be quite high, while at higher frequencies where the control voltage must be at a higher level the resultant modulation falls off substantially.
- Such wide variations and resultant modulations can produce undermodulation at higher frequencies, overmodulation at lower frequencies and thereby produce a failure to meet government regulations.
- An input is provided for receiving an input signal to be modulated.
- the input is connected to a compensation network which is also coupled to the controlled oscillator and is responsive to the control signal.
- a linear compensation network provides a compensated output signal having a substantially constant change in signal levels for a constant change in control signal over the predetermined range of frequencies so that the product of a compensated output signal and the gain factor is itself substantially constant over the predetermined range of frequencies.
- FIG. 1 is a plot of frequency vs. control voltage for the prior art VCO (broken line) as well as the VCO of the present invention (solid line).
- FIG. 2 is a plot of VCO gain factor K 0 expressed in Mhz per volt vs. control voltage for the voltage controlled oscillator of the present invention (solid line) as well as the prior art (broken line).
- FIG. 3 shows a plot of resultant modulation vs. control voltage for the VCO of the prior art (broken line) as well as the compensated VCO of the present invention (solid line).
- FIG. 4 shows a system block diagram for a synthesizer arrangement utilizing the compensated voltage controlled oscillator of the present invention.
- FIG. 5 shows a plot of compensated audio response as a function of control voltage for the audio compensator network of the present invention.
- FIG. 6 is a schematic drawing of the audio compensator and voltage controlled oscillator of the present invention.
- FIG. 4 a frequency synthesizer arrangement incorporating the present invention is shown.
- the principles of frequency synthesis incorporating phase locked loops are well known in the art. Details of the operation of such circuits may be found, for example, in a text book entitled, Phaselock Techniques, by Floyd M. Gardner, published in 1979 by John Wiley and Sons, Inc.
- the synthesizer arrangement of FIG. 4 includes a reference oscillator 30 for providing a standard reference frequency for the system.
- the output of reference 30 is coupled to one input of a phase detector or phase comparator 35.
- the phase detector's output 40 provides a control voltage through a loop filter 45.
- Loop filter 45 is typically a multiple order low pass filter and serves to smooth the response of the control voltage signal. This filtered control voltage signal appears at an output of loop filter 45.
- the filtered control voltage appearing at the output 50 of loop filter 45 is applied to the input of a voltage controlled oscillator (VCO) 55, the output of VCO 55 provides the radio frequency signal to be utilized for example in a radio transmitter.
- VCO voltage controlled oscillator
- the output of VCO 55 is also fed back to the second input of phase comparator 35.
- a frequency divider which may be a programmable frequency divider 60, is inserted between the path of the VCO output and the phase detector input.
- the output frequency may be divided by inserting a frequency divider between reference oscillator 30 and phase detector 35 (not shown) as is well known in the art.
- an audio compensator 65 is included in the circuit arrangement of FIG. 4.
- audio compensator is used herein due to the fact that the preferred embodiment synthesizer is used to modulate audio signals, this is not intended to be limiting as the present circuit arrangement may equally well be utilized to modulate digital data, tone codes, etc or combinations thereof.
- Audio signals or other signals to be modulated are supplied to an audio input 70 of the audio compensator.
- the control voltage signal present at the output 40 of phase detector 35 is coupled to a second input of the audio compensator 65.
- the output of the audio compensator 65 is coupled to the modulation port of VCO 55.
- the voltage controlled oscillator 55 In order to obtain the desired enhanced modulation characteristics of the present invention, the voltage controlled oscillator 55 must be carefully designed to obtain the appropriate characteristics. A circuit arrangement for obtaining the appropriate characteristics will be discussed in detail later, but in order to understand the operation of the present invention an overview is first desirable.
- solid line curve 110 shows the frequency vs. control voltage characteristic of the linear voltage controlled oscillator 55 of the present invention.
- the linearization techniques, to be discussed later have been utilized to obtain a more linear frequency vs. control voltage curve than that of the prior art shown in a broken line as curve 10.
- a considerably more linearized characteristic manifests itself in FIG. 2 as curve 115 for the present VCO.
- This plot of VCO gain factor K 0 as a function of control voltage also shows a wide range of control voltage over which the gain factor may be considered linear.
- the desired characteristics of audio compensator 65 is shown.
- the compensated audio output increases as control voltage increases and does so in a linear fashion.
- the slope and shape of curve 117 may be adjusted to compliment the slope of curve 115 so that the resultant modulation shown as solid line curve 120 of FIG. 3 is substantially flat having approximately zero slope over a wide range of control voltages. This directly results in flat resultant modulation over a very wide range of frequencies.
- FIG. 6 a circuit arrangement for practicing the present invention in the range of 95 to 125 Mhz is disclosed.
- Reference oscillator 30, phase detector 35, loop filter 45 and frequency divider 60 are not shown in detail as these are well known in the art.
- Voltage controlled oscillator 55 is shown enclosed in broken lines. Its input from the audio compensator 65 is coupled to a resistor 200 the other terminal of which is connected to a negative voltage source. The value of this negative voltage source determines the range of operation of the VCO in the preferred embodiment; for example: -2 volts sets the frequency range between 95 and 110 MHz and -3 volts sets the frequency range from 105 to 125 Mhz.
- a capacitor 205 is coupled from the audio compensator input port of VCO 55 to ground.
- An inductor 210 is coupled from the audio input of the VCO to the anodes of two hyperabrupt varactor diodes 215 and 220.
- these varactor diodes are hyperabrupt varactor diodes such as the Ferranti ZC834 but many other hyperabrupt varactor diodes will function well in this circuit.
- capacitor 225 Also coupled to the junction of the anodes of these two varactor diodes is a capacitor 225.
- the other terminal of capacitor 225 is coupled to the junction of the source of an N-Channel FET 230 and an inductor 235.
- the other terminal of inductor 235 is coupled to a resistor 240 having the other terminal grounded.
- a capacitor 242 is coupled from the drain of FET 230 to ground.
- the drain of FET 230 provides the output of the VCO through capacitor 245.
- An inductor 250 connects the drain of FET 230 to a positive 7.5 volt DC power supply designated as V + .
- Capacitor 245 and inductor 250 form a matching network for translating the output impedance to approximately 50 ohms.
- the gate of transistor 230 is grounded through an inductor 255.
- the gate of transistor 230 is also coupled to a capacitor 260 which is connected in series to the cathode of varactor diode 215.
- An inductor 265 is connected from the junction of capacitor 260 and the cathode of varactor diode 215 in series to an inductor 270 which is coupled to the cathode of varactor diode 220.
- a capacitor 275 is connected from the junction of inductors 265 and 270 to ground.
- Another capacitor 280 is connected from the junction of the cathode of varactor diode 220 and inductor 270 to ground.
- the output of loop filter 45 is coupled to the junction of inductors 265 and 270.
- VCO 55 Although the topology of VCO 55 initially appears to be somewhat similar to many VCO designs, its gain factor is linearized by applying a feedback signal through capacitor 225 to the junction of diodes 215 and 220. This in combination with utilizing hyperabrupt varactor diodes produces a highly linearized response.
- the anodes of both varactor diodes 216 and 220 are held at a low voltage by bias resistor 200 which is coupled to a negative DC voltage source.
- the control voltage is applied to the cathodes of varactor diodes 215 and 220 through inductors 265 and 270 respectively. The control voltage is therefore the same at varactors 215 and 220.
- This circuit topology has been found to produce linear gain response over a control voltage range of 1.5 to 4.5 volts over the range of 95 to 125 MHz when the component values specified below are utilized.
- Voltage controlled oscillator 55 is shown in a Colpitts configuration, but this is not to be limiting as other oscillator configurations may lend themselves to use in the present invention, utilizing varactor diodes 215 and 220 coupled back to back and resonant with a single air wound inductor 255. It should be noted that no tapped inductors are necessary with the present configuration.
- the FET 230 provides amplification. Feedback is provided from an output of FET 230 through capacitor 225 to return an in phase signal to the anodes of varactor diodes 215 and 220. Since hyperabrupt varactor diodes exhibit the greatest change in capacitance for any given change in voltage of all presently available varactor diodes, a wide tuning range is achieved.
- Capacitors 260 and 280 are large in value compared to the varactors and serve as DC blocking capacitors used to complete the resonant circuit with inductor 255.
- the FET 230 obtains DC bias through inductors 235 and 250 and resistor 240.
- Resistor 240 sets the bias of FET 230 while inductor 235 decouples radio frequency energy from ground allowing it to be fed back to the resonant circuit through capacitor 225.
- Inductor 250 in conjunction with capacitor 245 serve as a matching network. Their values may be adjusted to obtain maximum power output into a 50 OHM load over the frequency range of interest.
- Reverse bias is provided to the hyperabrupt varactor diodes through RF blocking inductors 210, 265, 270.
- Capacitor 205 and 275 function to shunt any RF present on the extremes of these inductors to ground.
- Negative bias is derived from a negative supply coupled through resistor 200 to the anodes of the varactors. This high impedance line is also used as the modulation port of the oscillator.
- frequency control voltage is derived from the output of the loop filter and is coupled to the oscillator through inductors 265 and 270.
- FIG. 6 also shows a detail schematic of the preferred embodiment of compensation network 65 of the present invention.
- the audio input of compensation network 65 is coupled to one terminal of a resistor 300.
- the other terminal of resistor 300 is coupled to the drain of a P-channel field effect transistor 305 and to one terminal of a resistor 310.
- the other terminal of resistor 310 is grounded as is the source of transistor 305.
- a capacitor 315 which serves as a DC blocking capacitor.
- the output of the compensation network is taken at the second terminal of capacitor 315.
- the gate of transistor 305 is connected to the anode of a diode 320.
- the cathode of diode 320 is connected through a resistor 325 to ground.
- a resistor 330 is connected to the junction of diode 320 and the gate of transistor 305 at one terminal while its other terminal provides the control voltage input to the audio compensator.
- Compensation network 65 operates as an active voltage divider with transistor 305 being biased in the variable resistance region. Transistor 305 therefore forms an active resistor which is in parallel with resistor 310.
- the value of resistor 310 determines largely the shape of solid line curve 117 of FIG. 5 so that the value of resistor 310 may be used to adjust the compensation network to obtain a flat resultant compensation.
- the amount of voltage division which takes place is a function of the value of resistor 325 and bias voltage applied to the base of transistor 305 by the bias network composed of resistors 325, 330 and diode 320.
- the control voltage applied to resistor 330 and the value of resistor 325 therefore actively adjusts this divider ratio as necessary to maintain constant modulation over the frequency range of interest.
- Diode 320 is utilized to obtain temperature compensation for the audio compensator and is effective from approximately -40° to +90° Celcius.
- Resistor 325 may be adjusted to change the amount of audio compensation obtained at the high end of the frequency band.
- a low value of resistance provides a small amount of compensation and a higher resistance value provides a higher degree of compensation in this region.
- the component values tabulated below provide an appropriate circuit arrangement for use in conjunction with the VCO previously described.
- the circuit can accomodate up to approximately 3 volts peak to peak applied at the audio input at frequencies up to approximately 100 Khz.
- the values shown below may be used to realize the compensation network of the present invention, the invention is not to be limited to those particular circuit values shown.
- the oscillator is very sensitive, having a K 0 on the order of 7 MHz/V, and any small signal sent to the oscillator is highly amplified to obtain the final modulation level.
- the audio is coupled to the anodes of varactor diodes 215 and 220 through capacitor 315 which may be chosen as large as possible to obtain the best low frequency response suitable for low frequency digital transmissions if required.
- the control voltage fed to the oscillator is also used to control the FET 305 in order to effect a change in FET resistance.
- This voltage is taken before the loop filter in order not to compromise loop filter dynamics and is also fed through a voltage division network made up of resistors 330 and 325 and diode 320 to the gate of the FET.
- K 0 drops off linearly.
- gate voltage also increases through the divider network causing the FET Drain-Source resistance to increase. This provides less attenuation through the audio divider network.
- the K 0 decrease may be complemented by this decrease of attenuation in linear fashion, to provide constant modulation over the oscillator frequency range.
- resistor 325 may be adjusted while monitoring deviation at the upper and lower oscillator extremes to adjust the level of compensation to be exactly the same at these two extremes. Once accomplished, the modulation is held to within 1% between the extremes and hence, linearized. Diode 320 is used as thermal compensation for FET 305 so that linearity is also achieved through a temperature range of approximately -40° C. to +90° C.
Landscapes
- Inductance-Capacitance Distribution Constants And Capacitance-Resistance Oscillators (AREA)
- Oscillators With Electromechanical Resonators (AREA)
- Stabilization Of Oscillater, Synchronisation, Frequency Synthesizers (AREA)
Priority Applications (5)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
US06/522,623 US4510465A (en) | 1983-08-12 | 1983-08-12 | Linear gain voltage controlled oscillator with modulation compensation |
PCT/US1984/001179 WO1985000942A1 (en) | 1983-08-12 | 1984-07-26 | Linear gain voltage controlled oscillator with modulation compensation |
AU32197/84A AU3219784A (en) | 1983-08-12 | 1984-07-26 | Linear gain voltage controlled oscillator with modulation compensation |
EP19840903115 EP0151629A4 (en) | 1983-08-12 | 1984-07-26 | LINEAR GAIN VOLTAGE CONTROL OSCILLATOR WITH MODULATION COMPENSATION. |
NO851459A NO851459L (no) | 1983-08-12 | 1985-04-12 | Spenningsutstyrt oscillator med modulerings-kompensasjon |
Applications Claiming Priority (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
US06/522,623 US4510465A (en) | 1983-08-12 | 1983-08-12 | Linear gain voltage controlled oscillator with modulation compensation |
Publications (1)
Publication Number | Publication Date |
---|---|
US4510465A true US4510465A (en) | 1985-04-09 |
Family
ID=24081625
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
US06/522,623 Expired - Lifetime US4510465A (en) | 1983-08-12 | 1983-08-12 | Linear gain voltage controlled oscillator with modulation compensation |
Country Status (5)
Country | Link |
---|---|
US (1) | US4510465A (no) |
EP (1) | EP0151629A4 (no) |
AU (1) | AU3219784A (no) |
NO (1) | NO851459L (no) |
WO (1) | WO1985000942A1 (no) |
Cited By (16)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US4714899A (en) * | 1986-09-30 | 1987-12-22 | Motorola, Inc. | Frequency synthesizer |
US4721927A (en) * | 1986-05-07 | 1988-01-26 | Alps Electric Co., Ltd. | Voltage-controlled-oscillator with modulator |
US4748425A (en) * | 1987-02-18 | 1988-05-31 | Motorola, Inc. | VCO range shift and modulation device |
US4864257A (en) * | 1988-09-15 | 1989-09-05 | General Electric Company | Phase locked frequency synthesizer with single input gain compensated wideband modulation system |
US4866404A (en) * | 1988-09-15 | 1989-09-12 | General Electric Company | Phase locked frequency synthesizer with single input wideband modulation system |
US4904964A (en) * | 1988-12-27 | 1990-02-27 | Motorola, Inc. | Voltage control oscillator with modulation compensation |
US4977379A (en) * | 1989-06-30 | 1990-12-11 | Motorola, Inc. | Differential pair, push-push oscillator |
US5144264A (en) * | 1991-11-01 | 1992-09-01 | Motorola, Inc. | Wideband voltage controlled oscillator having open loop gain compensation |
US5625325A (en) * | 1995-12-22 | 1997-04-29 | Microtune, Inc. | System and method for phase lock loop gain stabilization |
US6046650A (en) * | 1997-04-16 | 2000-04-04 | Motorola, Inc. | Oscillator circuit having optimized frequency modulation circuit |
WO2001078227A2 (en) * | 2000-04-07 | 2001-10-18 | Motorola Israel Limited | Frequency modulator using a pll |
US6311050B1 (en) * | 1998-05-29 | 2001-10-30 | Silicon Laboratories, Inc. | Single integrated circuit phase locked loop for synthesizing high-frequency signals for wireless communications and method for operating same |
FR2813481A1 (fr) * | 2000-08-28 | 2002-03-01 | Samsung Electronics Co Ltd | Modulateur de frequence a faible bruit ayant une frequence porteuse variable |
US6504443B1 (en) | 2000-05-17 | 2003-01-07 | Nec America, Inc., | Common anode varactor tuned LC circuit |
US6717476B2 (en) * | 2001-09-19 | 2004-04-06 | Oki Electric Industry Co., Ltd. | Modulator |
US20060109171A1 (en) * | 2004-11-19 | 2006-05-25 | Moch Thomas A | Methods and devices for determining the linearity of signals |
Families Citing this family (3)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JPH0250606A (ja) * | 1988-08-12 | 1990-02-20 | Nec Corp | 周波数シンセサイザ |
US5373264A (en) * | 1993-01-21 | 1994-12-13 | Hewlett-Packard Company | Negative resistance oscillator with electronically tunable base inductance |
JPH0758637A (ja) * | 1993-08-13 | 1995-03-03 | Nec Corp | 周波数シンセサイザ |
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US3534295A (en) * | 1968-09-05 | 1970-10-13 | Shaw Robert | Linearized frequency modulated crystal oscillators compensated for ambient temperature variations |
US3579281A (en) * | 1969-06-04 | 1971-05-18 | Sierra Research Corp | Combining network providing compensated tuning voltage for varactor |
US3593204A (en) * | 1969-05-22 | 1971-07-13 | Westinghouse Electric Corp | High frequency voltage controlled oscillator |
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US4378534A (en) * | 1981-03-31 | 1983-03-29 | Motorola, Inc. | Wideband modulation sensitivity compensated voltage controlled oscillator |
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DE2060647C3 (de) * | 1970-12-09 | 1974-08-15 | Siemens Ag, 1000 Berlin Und 8000 Muenchen | In der Frequenz modulierbarer Oszillator |
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-
1983
- 1983-08-12 US US06/522,623 patent/US4510465A/en not_active Expired - Lifetime
-
1984
- 1984-07-26 AU AU32197/84A patent/AU3219784A/en not_active Abandoned
- 1984-07-26 EP EP19840903115 patent/EP0151629A4/en not_active Withdrawn
- 1984-07-26 WO PCT/US1984/001179 patent/WO1985000942A1/en not_active Application Discontinuation
-
1985
- 1985-04-12 NO NO851459A patent/NO851459L/no unknown
Patent Citations (12)
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US3617947A (en) * | 1964-10-29 | 1971-11-02 | Garold K Jensen | Wide band frequency modulator |
US3534295A (en) * | 1968-09-05 | 1970-10-13 | Shaw Robert | Linearized frequency modulated crystal oscillators compensated for ambient temperature variations |
US3593204A (en) * | 1969-05-22 | 1971-07-13 | Westinghouse Electric Corp | High frequency voltage controlled oscillator |
US3579281A (en) * | 1969-06-04 | 1971-05-18 | Sierra Research Corp | Combining network providing compensated tuning voltage for varactor |
US4003004A (en) * | 1975-04-09 | 1977-01-11 | Nasa | Frequency modulated oscillator |
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Cited By (21)
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US4721927A (en) * | 1986-05-07 | 1988-01-26 | Alps Electric Co., Ltd. | Voltage-controlled-oscillator with modulator |
US4714899A (en) * | 1986-09-30 | 1987-12-22 | Motorola, Inc. | Frequency synthesizer |
US4748425A (en) * | 1987-02-18 | 1988-05-31 | Motorola, Inc. | VCO range shift and modulation device |
US4864257A (en) * | 1988-09-15 | 1989-09-05 | General Electric Company | Phase locked frequency synthesizer with single input gain compensated wideband modulation system |
US4866404A (en) * | 1988-09-15 | 1989-09-12 | General Electric Company | Phase locked frequency synthesizer with single input wideband modulation system |
US4904964A (en) * | 1988-12-27 | 1990-02-27 | Motorola, Inc. | Voltage control oscillator with modulation compensation |
US4977379A (en) * | 1989-06-30 | 1990-12-11 | Motorola, Inc. | Differential pair, push-push oscillator |
US5144264A (en) * | 1991-11-01 | 1992-09-01 | Motorola, Inc. | Wideband voltage controlled oscillator having open loop gain compensation |
US5625325A (en) * | 1995-12-22 | 1997-04-29 | Microtune, Inc. | System and method for phase lock loop gain stabilization |
US6046650A (en) * | 1997-04-16 | 2000-04-04 | Motorola, Inc. | Oscillator circuit having optimized frequency modulation circuit |
US6311050B1 (en) * | 1998-05-29 | 2001-10-30 | Silicon Laboratories, Inc. | Single integrated circuit phase locked loop for synthesizing high-frequency signals for wireless communications and method for operating same |
WO2001078227A2 (en) * | 2000-04-07 | 2001-10-18 | Motorola Israel Limited | Frequency modulator using a pll |
WO2001078227A3 (en) * | 2000-04-07 | 2003-01-23 | Motorola Israel Ltd | Frequency modulator using a pll |
US6504443B1 (en) | 2000-05-17 | 2003-01-07 | Nec America, Inc., | Common anode varactor tuned LC circuit |
FR2813481A1 (fr) * | 2000-08-28 | 2002-03-01 | Samsung Electronics Co Ltd | Modulateur de frequence a faible bruit ayant une frequence porteuse variable |
US6476684B2 (en) * | 2000-08-28 | 2002-11-05 | Samsung Electronics Co., Ltd. | Low noise frequency modulator having variable carrier frequency |
US6717476B2 (en) * | 2001-09-19 | 2004-04-06 | Oki Electric Industry Co., Ltd. | Modulator |
US20040108912A1 (en) * | 2001-09-19 | 2004-06-10 | Kazuo Suto | Modulator |
US7292118B2 (en) * | 2001-09-19 | 2007-11-06 | Oki Electric Industry Co., Ltd. | Modulator |
US20060109171A1 (en) * | 2004-11-19 | 2006-05-25 | Moch Thomas A | Methods and devices for determining the linearity of signals |
US7333051B2 (en) | 2004-11-19 | 2008-02-19 | Lockheed Martin Corporation | Methods and devices for determining the linearity of signals |
Also Published As
Publication number | Publication date |
---|---|
EP0151629A4 (en) | 1985-12-19 |
WO1985000942A1 (en) | 1985-02-28 |
AU3219784A (en) | 1985-03-12 |
NO851459L (no) | 1985-04-12 |
EP0151629A1 (en) | 1985-08-21 |
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