US4507569A - Electrical control system and driver - Google Patents

Electrical control system and driver Download PDF

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Publication number
US4507569A
US4507569A US06/567,264 US56726483A US4507569A US 4507569 A US4507569 A US 4507569A US 56726483 A US56726483 A US 56726483A US 4507569 A US4507569 A US 4507569A
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Prior art keywords
switching means
electronic switching
state
voltage
switch
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US06/567,264
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English (en)
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II John E. Hess
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CONSERVOLITE Inc A PA CORP
CONSERVOLITE Inc
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CONSERVOLITE Inc
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Priority to US06/567,264 priority Critical patent/US4507569A/en
Application filed by CONSERVOLITE Inc filed Critical CONSERVOLITE Inc
Assigned to CONSERVOLITE INC A PA CORP reassignment CONSERVOLITE INC A PA CORP ASSIGNMENT OF ASSIGNORS INTEREST. Assignors: HESS, JOHN E. II
Priority to GB08431025A priority patent/GB2152772B/en
Priority to AU36617/84A priority patent/AU587170B2/en
Priority to CA000470432A priority patent/CA1265577A/en
Priority to JP59272700A priority patent/JPS60229124A/ja
Priority to FR8419925A priority patent/FR2557753B1/fr
Priority to DE3447486A priority patent/DE3447486C2/de
Publication of US4507569A publication Critical patent/US4507569A/en
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Assigned to AMERICAN NATIONAL BANK AND TRUST COMPANY OF CHICAGO reassignment AMERICAN NATIONAL BANK AND TRUST COMPANY OF CHICAGO SECURITY INTEREST (SEE DOCUMENT FOR DETAILS). Assignors: CONSERVOLITE, INC.
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M5/00—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases
    • H02M5/02—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc
    • H02M5/04—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc by static converters
    • H02M5/22—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M5/275—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M5/293—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
    • H05B41/14—Circuit arrangements
    • H05B41/36—Controlling
    • H05B41/38—Controlling the intensity of light
    • H05B41/39—Controlling the intensity of light continuously
    • H05B41/392—Controlling the intensity of light continuously using semiconductor devices, e.g. thyristor
    • H05B41/3921—Controlling the intensity of light continuously using semiconductor devices, e.g. thyristor with possibility of light intensity variations
    • H05B41/3922—Controlling the intensity of light continuously using semiconductor devices, e.g. thyristor with possibility of light intensity variations and measurement of the incident light
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M5/00—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases
    • H02M5/02—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc
    • H02M5/04—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc by static converters
    • H02M5/22—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M5/275—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M5/293—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M5/2932—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage, current or power
    • H02M5/2935—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage, current or power using reverse phase control, i.e. turn-on of switches in series with load at zero crossing of input voltage, turn-off before next zero crossing
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y10—TECHNICAL SUBJECTS COVERED BY FORMER USPC
    • Y10S—TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y10S315/00—Electric lamp and discharge devices: systems
    • Y10S315/04—Dimming circuit for fluorescent lamps

Definitions

  • the invention relates to electrical control systems and, more particularly, to an electrical control system and driver which repeatedly applies power to and removes power from an electrical load to reduce the energy consumed by the load or to control its output.
  • the present invention can be utilized with a wide variety of types of electrical load apparatus. Accordingly, while the discussion of the invention and the prior art is primarily directed toward the control of fluorescent lights and fluorescent lighting systems, such a discussion is not to be construed as a limitation on the application of the present invention.
  • a gas discharge type lamp and its associated ballast are among the most difficult electrical loads to regulate and control.
  • the term gas discharge lamp includes a fluorescent lamp with or without a separate heater, a high intensity discharge lamp and any lamp which typically exhibits a negative resistance characteristic.
  • Such a lamp requires a ballast circuit to provide a stable operating condition when it is used with a standard AC power source.
  • the ballast also provides additional striking voltage to start the lamp and, in some cases, to provide power for internal lamp cathode heaters.
  • the time at which all such conventional circuits reapply energizing voltage to the load during a half cycle of the supply voltage does not depend on the relative electrical potential between the load, due to back EMF, and the supply voltage. Accordingly, the conventional circuits nearly always reapply energizing voltage to the load when an electric potential exists between the supply voltage and the load that creates an extremely large and damaging voltage transient at the time the energizing voltage is reapplied to the load.
  • the voltage transient can cause immediate destruction or shortened life of the control components and can create annoying audible noise.
  • Another problem is caused by the very fast switching times employed by many conventional circuits, relative to the 50 to 60 Hz voltage being supplied to the ballasts, which can cause shortened ballast life. Also, removing and applying energizing voltage from the load prior to the 90° point of each half cycle of the supply voltage causes high crest factors and very fast voltage changes which stress the ballast and lamp. Increased noise results from significant swings in voltage during the half cycle, which produce multiple harmonics within the audible range. Switching prior to the 90° point in each half cycle of the supply voltage causes the further problem that voltage of an amplitude sufficient to ignite the lamps may not be applied to the load, which will cause some lamps to be extinguished completely.
  • the invention provides a driver and a control system that employs the driver.
  • the invention is used to control electrical load apparatus, including apparatus which presents an inductive load to the control system.
  • the driver of the present invention includes a first electronic switching device, operatively connected to the load, which has a first state in which supply voltage is applied to the load and a second state in which supply voltage is not applied to the load.
  • a second electronic switching device operatively associated with the first electronic switching device effects the transition of the first electronic switching device between the first and second states thereof, and is selectively switchable between a first state and a second state. In the first state of the second switching device, the first switching device is in its first state and in the second state of the second switching device, the first switching device is in its second state.
  • switching of the second switching device from its first state to its second state causes the first switching device to switch to its second state from its first state.
  • the second switching device is switched into its second state by a command signal.
  • the driver causes the second switching device to remain in its second state until a determinable circuit condition is present between the power supply and the load.
  • FIG. 1 is a block diagram of the preferred control system of the present invention, which incorporates a driver provided by the present invention
  • FIG. 2A is a schematic diagram of the preferred embodiment of the driver of the present invention and FIGS. 2B through 2G show wave forms taken at various test points of the driver;
  • FIG. 3 is a schematic diagram of an alternate embodiment of the driver of the present invention for use with a relatively light inductive load, such as two gas discharge lamps;
  • FIG. 4 is a schematic diagram of an alternate embodiment of the driver of the present invention for use with between about two and eight gas discharge lamps, or an equivalent inductive load;
  • FIG. 5 is a schematic diagram of an alternate embodiment of the driver of the present invention for use with more than about eight gas discharge lamps, or an equivalent inductive load;
  • FIG. 6 is a schematic diagram of an alternate embodiment of the driver of the present invention that permits manual dimming of gas discharge lamps.
  • FIGS. 2A through 2G a preferred embodiment of the driver of the present invention is described in detail. It is to be understood that the values of the various components associated with the present invention can be modified to meet various applications and requirements without departing from the spirit and scope of the invention.
  • the drivers are described herein as they are used with a control system that controls the operation of one or more gas discharge lamps. As is stated above, the drivers provided by the present invention can be used with systems that control the operation of any, even noninductive, loads.
  • Driver 11 shown in FIG. 2A, can be viewed as having two modes of operation, mode A and mode B.
  • Driver 11 includes a first electronic switching device, generally indicated at 51, a second electronic switching device 53, a full wave bridge rectifier with capacitor generally indicated at 55 and a zero cross circuit 54.
  • the first mode of operation, or mode A is a state of energizing voltage application to the load L from the AC power supply 56.
  • the second mode of operation, or mode B energizing voltage from power supply 56 is removed from the load L, but control voltage is still applied to the control portions of the control circuit through bridge 55.
  • Driver 11 is electrically connected to load L, a gas discharge lamp, by leads 500 and 501.
  • load L a gas discharge lamp
  • One side, the return, of AC power supply 56 is connected to load L with lead 501 and the remaining side of power supply 56 is connected to bridge 55 by a lead 502.
  • Power supply 56 supplies AC energizing voltage to load L during mode A, and supplies control power to the control components of driver 11 during both modes A and B through bridge 55.
  • a resistor R5 is shown as connected with lead 500 to load L and by lead 503 to bridge 55. Resistor R5 is included in FIG. 2A only for the purpose of providing a test measurement, as shown in FIG. 2D, and would be omitted from a commercial driver.
  • Bridge 55 includes four diodes D1, D2, D3 and D4 connected together in the configuration of a full wave bridge rectifier. Bridge 55 receives AC supply voltage from power supply 56 and produces rectified control power for the control portion of driver 11 and energizing voltage for load L along leads 504 and 505. A capacitor C1 is connected by lead 506 to point 400 of bridge 55 and by lead 507 to a resistor R4. The remaining side of resistor R4 is connected by lead 508 to point 401 of bridge 55. Capacitor C1 absorbs the power generated by the back EMF produced by load L when driver 11 switches from mode A to mode B. Resistor R4 is included in FIG. 2A only to provide a test measurement, as shown in FIG. 2C, and would not be included in a commercial driver.
  • Zero cross circuit 54, switch 53, switch 51 and resistor R1 constitute the control portion of driver 11.
  • Resistor R1 is connected to lead 504 to output 403 of bridge 55 and by lead 509 to switches 51 and 53.
  • Lead 504 also connects resistor R1 to zero cross circuit 54.
  • the value of the resistance of resistor R1 affects the amount of voltage which driver 11 switches from mode A to mode B. The higher the resistance of resistor R1, the higher the voltage at which switching occurs, and the lower the phase angle at which driver 11 switches back to mode A.
  • Switch 51 includes a transistor S1. When transistor S1 is conducting, switch 51 is closed and energizing voltage is applied to load L through transistor S1 and bridge 55. When transistor S1 is not conducting, or cut off, switch 51 is open and energizing voltage from power supply 56 is not all applied to load L.
  • the collector of transistor S1 is connected to line 504 and the emitter of transistor S1 is connected to line 505, the negative side of rectifier 55, through a resistor R2. Resistor R2 is used only to record current levels, if desired.
  • the base of transistor S1 is connected to the source of a field effect transistor, or FET, S2. The source of FET S2 and the base of transistor S1 are tied to lead 505 through a resistor R3.
  • Resistor R3 improves the cutoff condition of transistor S1.
  • the gate of FET S2 is connected to line 509.
  • the drain of FET S2 is connected by line 510 to a DC voltage supply 57.
  • the level of the voltage produced by DC supply 57 must be sufficient to cause transistor S1 to enter its conducting, or saturated, state when it is applied to the base of transistor S1. Accordingly, when the voltage from the gate to the source of FET S2 is sufficiently high to cause FET S2 to conduct, which occurs during mode A, the voltage produced by DC source 57 is applied to the base of transistor S1 and transistor S1 enters its conducting state to permit application of energizing voltage to load L from AC source 56.
  • the anode of the silicon controlled rectifier, or SCR, S3 of switch 53 is connected to lead 509.
  • the cathode of SCR S3 is connected to the negative output 505 of bridge 55.
  • a resistor R6 is used to bias SCR S3 in its nonconducting state.
  • the gate of SCR S3 is connected to the high side of resistor R6 and to lead 511.
  • Lead 511 carries the command signal from a suitable control circuit that causes SCR S3 to fire and conduct.
  • a Zener diode Z1 is connected between leads 509 and 505 and provides protection for SCR S3 and FET S2.
  • SCR S3 When the gate of SCR S3 receives a suitable command signal, usually a pulse, along lead 511, SCR S3 begins conducting, which reduces the voltage between the gate and source of FET S2 to a level that is insufficient to cause FET S2 to conduct which, as described above, causes switch 51 to enter its second state, where it is not conducting.
  • a suitable command signal usually a pulse
  • Zero cross circuit 54 ensures that application of power to driver 11 occurs only at the beginning of the first half cycle.
  • FIG. 1 illustrates in block diagram form a preferred control system 10, which employs preferred driver 11, that is used to control one or more gas discharge lamps.
  • Control system 10 causes driver 11 to repeatedly connect the AC supply 13 to and to disconnect the AC supply 13 from load L.
  • the amount of time the AC supply 13 is disconnected from load L during each cycle of the AC voltage produced by AC supply 13 determines the extent of lamp dimming and, accordingly, the extent of energy savings realized. The longer the AC supply is disconnected from load L, the less light is produced by the load L and the greater are the energy savings realized.
  • AC voltage is always applied to load L during the peak, positive or negative, of each half cycle to ensure that ignition voltage is always applied to the lamps of load L.
  • control system 10 applies to load L a sinusoidal voltage with gaps or notches created when control system 10 disconnects the AC supply from load L.
  • the AC supply is initially switched off in a half cycle, that is, the first time driver 11 switches from mode A to mode B during a half cycle, beyond the 90° phase angle to ensure that proper ignition voltage is applied to load L during each half cycle.
  • the angle at which driver 11 switches from mode B to mode A is determined by the angle at which the relative potential difference between load L, due to its back EMF, and the AC supply voltage is reduced to a predetermined level. Therefore, the width of the gaps created in the AC supply voltage is determined by the angle at which driver 11 first switches from mode A to mode B in each half cycle.
  • the control system 10, and the inputs to it that represent desired light output of load L, must be calibrated to achieve proper lighting.
  • the electrical load apparatus L comprising at least one gas discharge lamp, is in electrical communication with a power supply 13 through line 15 and through driver 11, line 17, zero cross circuit 18, and line 20.
  • Line 15 is the return and line 25 is the main supply.
  • the power supply 13 can consist of, for example, a transformer type or capacitor charge pump type.
  • an appropriate DC voltage B+ is provided along line 19 to the control circuit 21 and to driver 11 by control circuit 21.
  • Voltage B+ can be the DC supply 57 shown in FIG. 2A.
  • the control circuit 21 is also provided with an AC synchronous voltage along line 23 that is synchronous with the AC line power provided through input lines 25 and 15 of the power supply 13.
  • An appropriate ground system is provided by line 27.
  • An EMS interface circuit can supply commands pertaining to the desired light output of load L along line 38 to control circuit 21.
  • direct light input representing desired light output of load L
  • a light sensitive device as indicated by dashed line 33, that converts the light commands to electrical command signals.
  • the external commands can be provided to control circuit 21 by a polycrystalline silicon solar cell 12 which produces a signal on line 14 having a level that is proportional to the level of the light received by solar cell 12.
  • Control circuit 21 is a phase control circuit which applies a control signal to driver 11.
  • Control circuit 21 receives the AC synchronous signal along line 23 and uses it to generate a ramp signal, the frequency of which is twice the frequency of the AC synchronous signal on lines 23.
  • Control circuit 21 compares the ramp signal with the external control signal provided at 29 or 37, as will be hereinafter explained, to generate a command or control signal to driver 11 along line 31.
  • the command signal provided to driver 11 along line 31 represents a voltage phase delay, that is, the angle at which driver 11 first switches from mode A to mode B for each half cycle.
  • a voltage phase delay of 90° represents the preferred maximum reduction of voltage to the load L, while an increase of the phase delay of up to about 180°, for example, represents a minimum level of voltage reduction.
  • EMS circuit 35 can be any suitable energy management system that coordinates lighting control for more than one system 10.
  • the external control signal provided along line 29 is converted into a DC voltage level which control circuit 21 converts into the desired phase angle delay. In the case of a voltage phase delay of 90°, the DC voltage level would be equal to one-half of the peak voltage of the ramp signal of control circuit 21.
  • Control circuit 21 compares the command signal on line 38 with the ramp signal. Each time the ramp signal crosses the command signal, control circuit 21 provides to driver 11 a pulse that causes driver 11 to disconnect the AC supply 13 from load L. The higher the level of the command signal on line 38, the narrower the gap created in each cycle of energizing voltage applied to load L, and the greater the light level produced by load L.
  • Zero cross circuit 18 is conventional and ensures that, on start-up, application of power to driver 11 occurs at the beginning of a half cycle and that deenergization of driver 11 occurs at the end of a half cycle. If driver 11 has a zero cross circuit integral with it, for example, circuit 54 shown in FIG. 2A, circuit 18 is not necessary.
  • FIGS. 2B through 2G show in detail current and voltage wave forms for the two modes of operation of driver 11.
  • FIG. 2B shows the current flowing through resistor R2
  • FIG. 2C shows the current flowing through resistor R4
  • FIG. 2D shows the current flowing through resistor R5
  • FIG. 2E shows the current flowing through resistor R1.
  • the wave forms shown in dashed lines in FIGS. 2B through 2E show the voltage appearing across the load.
  • the solid line alone shown in FIG. 2F represents the voltage appearing across SCR S3 in mode B for turning off at 90°; the dashed line in FIG. 2F represents the voltage across the load in mode B for 90° turn off; the dotted line in FIG. 2F represents 100% turn on or continuous mode A.
  • FIG. 2G shows the voltage applied to load L and shows the gaps created in the AC supply voltage for 30%, 50% and 75% application of AC supply voltage.
  • the dashed line shown in FIG. 2G shows application of 100% of AC supply voltage.
  • FIGS. 3, 4, 5 and 6 Alternate embodiments of the controller of the present invention are shown in FIGS. 3, 4, 5 and 6. Again, the values of the various components associated with these embodiments can be modified to meet various applications and requirements.
  • FIG. 3 shows a driver 110 having a first switch, FET 151, operated by a second switch 153. Since driver 110 is designed for use with a control system that controls two lamps or less, FET 151 can handle the relatively low current that must be supplied to load L. Accordingly, the transistor, designated S1 in FIG. 1, is not needed. Further, driver 110 illustrates an alternate means of switching on switch 153. Switch 153 is a photo SCR which responds to direct light-input, shown at 155 in FIG. 3. Also, driver 110 needs no separate DC power supply and is connected in series with the load L.
  • FIG. 4 shows driver 210 which is designed for use with a control system that controls the operation of from about two to eight lamps.
  • Driver 210 includes a first switch 251 and a second switch 253.
  • Switch 251 requires a transistor Q1 to enable switch 251 to handle the higher current that must be supplied to a load of from two to eight lamps.
  • switch 253 is a photo SCR that accepts and operates on light input.
  • FIG. 5 shows driver 310 which is designed for use in a control system that controls the operation of more than about eight lamps. Resistor R1 must be introduced to ensure proper switching of transistor Q1 in view of increased current requirements of load L.
  • FIG. 6 shows a driver 610 which is similar to driver 110. However, driver 610 includes a potentiometer 612 which permits direct manual adjustment of lighting level and energy savings.
  • each driver 110, 210, 310 and 610 can be used in a control system identical to control system 10, but with the B+ line eliminated.
  • the driver of the invention controls and utilizes the back EMF generated by inductive loads when power is removed from the load as a feedback signal in determining when the power is to be reapplied to the load.
  • R4 and R5 are used for test purposes only.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Circuit Arrangements For Discharge Lamps (AREA)
  • Control Of Electrical Variables (AREA)
US06/567,264 1983-12-30 1983-12-30 Electrical control system and driver Expired - Fee Related US4507569A (en)

Priority Applications (7)

Application Number Priority Date Filing Date Title
US06/567,264 US4507569A (en) 1983-12-30 1983-12-30 Electrical control system and driver
GB08431025A GB2152772B (en) 1983-12-30 1984-12-07 Electrical power control system
AU36617/84A AU587170B2 (en) 1983-12-30 1984-12-13 Electrical control system and driver
CA000470432A CA1265577A (en) 1983-12-30 1984-12-18 Electrical control system and driver
JP59272700A JPS60229124A (ja) 1983-12-30 1984-12-24 電気制御システム及び駆動装置
DE3447486A DE3447486C2 (de) 1983-12-30 1984-12-27 Schaltungsanordnung zum Betrieb eines elektrischen Verbrauchers
FR8419925A FR2557753B1 (fr) 1983-12-30 1984-12-27 Dispositif de commande electrique et circuit d'excitation pour charge electrique

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
US06/567,264 US4507569A (en) 1983-12-30 1983-12-30 Electrical control system and driver

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Publication Number Publication Date
US4507569A true US4507569A (en) 1985-03-26

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US06/567,264 Expired - Fee Related US4507569A (en) 1983-12-30 1983-12-30 Electrical control system and driver

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US (1) US4507569A (de)
JP (1) JPS60229124A (de)
AU (1) AU587170B2 (de)
CA (1) CA1265577A (de)
DE (1) DE3447486C2 (de)
FR (1) FR2557753B1 (de)
GB (1) GB2152772B (de)

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US4733136A (en) * 1984-12-18 1988-03-22 Volker Schaft Method of regulating the power of vapor discharge lamps
EP0311995A2 (de) * 1987-10-14 1989-04-19 Citation Marketing Patricia A. Bailey Leistungssparschaltung
EP0380833A1 (de) * 1989-01-31 1990-08-08 Lutron Electronics Co., Inc. Dimmer mit umgekehrter Phasenanschnittsteuerung
US5038081A (en) * 1987-12-16 1991-08-06 Lutron Electronics Co., Inc. Reverse phase-controlled dimmer
DE4210993A1 (de) * 1992-04-02 1993-10-14 Telefunken Microelectron Schaltungsanordnung zur Phasen-Abschnitt-Steuerung
EP0623991A1 (de) * 1993-05-05 1994-11-09 PLUMER (Société Anonyme) Leistungs oder Geschwindigkeitssteuerung einer Last
US5504398A (en) * 1994-06-10 1996-04-02 Beacon Light Products, Inc. Dimming controller for a fluorescent lamp
US5519311A (en) * 1984-01-19 1996-05-21 Don Widmayer & Associates, Inc. Control of AC power to inductive loads
US5537010A (en) * 1994-06-10 1996-07-16 Beacon Light Products, Inc. Voltage-comparator, solid-state, current-switch starter for fluorescent lamp
US5652504A (en) * 1993-11-22 1997-07-29 Lti International, Inc. Energy saving power control system
US5736817A (en) * 1995-09-19 1998-04-07 Beacon Light Products, Inc. Preheating and starting circuit and method for a fluorescent lamp
US5754036A (en) * 1996-07-25 1998-05-19 Lti International, Inc. Energy saving power control system and method
US5861720A (en) * 1996-11-25 1999-01-19 Beacon Light Products, Inc. Smooth switching power control circuit and method
US5861721A (en) * 1996-11-25 1999-01-19 Beacon Light Products, Inc. Smooth switching module
US5942813A (en) * 1995-07-15 1999-08-24 Matra Bae Dynamics (Uk) Ltd. Power switching circuits
US5955847A (en) * 1994-06-10 1999-09-21 Beacon Light Products, Inc. Method for dimming a fluorescent lamp
US6172489B1 (en) 1999-12-28 2001-01-09 Ultrawatt.Com Inc. Voltage control system and method
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GB2379813A (en) * 2001-07-17 2003-03-19 Cheng Ching Chi An electronic in-line outdoor lighting switch responsive to ambient light
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GB2379813A (en) * 2001-07-17 2003-03-19 Cheng Ching Chi An electronic in-line outdoor lighting switch responsive to ambient light
US20070188105A1 (en) * 2003-09-22 2007-08-16 Peter Lurkens Method of determining a zero point of a current sensor
US7408356B2 (en) * 2003-09-22 2008-08-05 Koninklijke Philips Electronics N.V. Method of determining a zero point of a current sensor

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Publication number Publication date
AU587170B2 (en) 1989-08-10
JPS60229124A (ja) 1985-11-14
DE3447486C2 (de) 1994-08-18
AU3661784A (en) 1985-08-29
DE3447486A1 (de) 1985-07-11
JPH0323928B2 (de) 1991-04-02
FR2557753B1 (fr) 1988-09-16
GB2152772B (en) 1988-05-18
FR2557753A1 (fr) 1985-07-05
CA1265577A (en) 1990-02-06
GB2152772A (en) 1985-08-07
GB8431025D0 (en) 1985-01-16

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