US10444326B2 - FMCW radar - Google Patents

FMCW radar Download PDF

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Publication number
US10444326B2
US10444326B2 US15/443,423 US201715443423A US10444326B2 US 10444326 B2 US10444326 B2 US 10444326B2 US 201715443423 A US201715443423 A US 201715443423A US 10444326 B2 US10444326 B2 US 10444326B2
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Prior art keywords
signal
cancel
transmission signal
fmcw radar
mixer
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US15/443,423
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US20170168140A1 (en
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Yoshifumi Hosokawa
Isao Imazeki
Yoichi Nagaso
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Socionext Inc
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Socionext Inc
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Assigned to SOCIONEXT INC. reassignment SOCIONEXT INC. ASSIGNMENT OF ASSIGNORS INTEREST (SEE DOCUMENT FOR DETAILS). Assignors: NAGASO, YOICHI, IMAZEKI, ISAO, HOSOKAWA, YOSHIFUMI
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    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
    • G01S7/02—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S13/00
    • G01S7/35—Details of non-pulse systems
    • G01S7/352—Receivers
    • G01S7/354—Extracting wanted echo-signals
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S13/00—Systems using the reflection or reradiation of radio waves, e.g. radar systems; Analogous systems using reflection or reradiation of waves whose nature or wavelength is irrelevant or unspecified
    • G01S13/02—Systems using reflection of radio waves, e.g. primary radar systems; Analogous systems
    • G01S13/06—Systems determining position data of a target
    • G01S13/08—Systems for measuring distance only
    • G01S13/32—Systems for measuring distance only using transmission of continuous waves, whether amplitude-, frequency-, or phase-modulated, or unmodulated
    • G01S13/34—Systems for measuring distance only using transmission of continuous waves, whether amplitude-, frequency-, or phase-modulated, or unmodulated using transmission of continuous, frequency-modulated waves while heterodyning the received signal, or a signal derived therefrom, with a locally-generated signal related to the contemporaneously transmitted signal
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
    • G01S7/02—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S13/00
    • G01S7/40—Means for monitoring or calibrating
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/38—Transceivers, i.e. devices in which transmitter and receiver form a structural unit and in which at least one part is used for functions of transmitting and receiving
    • H04B1/40—Circuits
    • H04B1/50—Circuits using different frequencies for the two directions of communication
    • H04B1/52—Hybrid arrangements, i.e. arrangements for transition from single-path two-direction transmission to single-direction transmission on each of two paths or vice versa
    • H04B1/525—Hybrid arrangements, i.e. arrangements for transition from single-path two-direction transmission to single-direction transmission on each of two paths or vice versa with means for reducing leakage of transmitter signal into the receiver
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
    • G01S7/02—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S13/00
    • G01S7/03—Details of HF subsystems specially adapted therefor, e.g. common to transmitter and receiver
    • G01S7/038—Feedthrough nulling circuits
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/02—Transmitters
    • H04B1/04—Circuits
    • H04B1/0475—Circuits with means for limiting noise, interference or distortion
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/06—Receivers
    • H04B1/10—Means associated with receiver for limiting or suppressing noise or interference
    • H04B1/12—Neutralising, balancing, or compensation arrangements
    • H04B1/123—Neutralising, balancing, or compensation arrangements using adaptive balancing or compensation means

Definitions

  • the present disclosure relates to a frequency modulated continuous wave (FMCW) radar.
  • FMCW frequency modulated continuous wave
  • An FMCW radar is known as a type of distance measuring radar.
  • An FMCW radar continuously transmits a signal with a frequency varying with time, and receives a reflected wave from an object.
  • the radar can measure the distance to the object and its moving velocity by analyzing the reflected wave.
  • Such a radar includes a transmission system and a reception system.
  • a signal sometimes leaks from the transmission system to the reception system, resulting in a lower measurement precision.
  • the distance between the transmission and reception systems also decreases. As a result, the leakage signal comes to have an even more significant negative effect on its performance.
  • a receiver supplies an FM signal to a mixer through a delay device causing the same amount of time delay as that of a leakage signal component from a transmission system to a reception system, thereby converting the leakage signal component into a direct-current (DC) component. Then, the receiver further removes the DC component to attempt to cancel the leakage signal component (see Japanese Unexamined Patent Publication No. H11-183600).
  • the leakage signal component remains as an alternating current (AC) signal having the same period as one period of variation of the transmission frequency.
  • AC alternating current
  • an FMCW radar includes: a transmission signal generator configured to generate a frequency-modulated transmission signal; a transmission signal sender configured to send the transmission signal; a receiver configured to receive a reflected wave of the transmission signal; an adjuster configured to adjust an amplitude and phase of a cancel signal, which cancels a leakage signal component in a received signal, in accordance with a variation in a frequency of the transmission signal; and a superimposer configured to superimpose the cancel signal over the received signal to cancel the leakage signal component.
  • the amplitude and phase of a cancel signal which cancels a leakage signal component in a received signal, are adjusted in accordance with a variation in the frequency of a transmission signal.
  • the present disclosure provides an FMCW radar having the ability to effectively prevent the leakage signal from affecting the measurement precision, even if the transmission and reception systems are arranged close to each other, and to precisely measure the distance to the object, no matter how short it may be, even if the amplitude and phase of the leakage signal vary with the transmission frequency, in particular.
  • FIG. 1 is a block diagram of an FMCW radar according to an exemplary embodiment of the present disclosure.
  • FIG. 2 is a block diagram showing an exemplary detailed configuration for a radio frequency phase shift (RFPS) circuit shown in FIG. 1 .
  • RFPS radio frequency phase shift
  • FIG. 3 is a block diagram showing an exemplary detailed configuration for a clutter cancellation (CLC) section of an image rejection and clutter cancellation (IMR & CLC) circuit shown in FIG. 1 .
  • CLC clutter cancellation
  • IMR & CLC image rejection and clutter cancellation
  • FIG. 4 is a vector diagram describing how the CLC section shown in FIG. 3 operates.
  • FIG. 5 is a block diagram of an FMCW radar according to a variation of the exemplary embodiment shown in FIG. 1 .
  • FIG. 1 is a block diagram of an FMCW radar according to an exemplary embodiment of the present disclosure.
  • the FMCW radar shown in FIG. 1 is designed to adjust, in accordance with a variation in the frequency of a transmission signal, the amplitude and phase of a cancel signal for cancelling a leakage signal component (a clutter signal component) from a transmission system to a reception system.
  • a leakage signal component a clutter signal component
  • the FMCW radar includes a reference (clock) signal generator (CLK) 110 , a local oscillator (LO) 111 , first and second attenuators/low pass filters (ATTs/LPFs) 112 , 113 , a first mixer 114 , a power amplifier (PA) 115 , a transmission antenna 116 , a hybrid (HYB) circuit 117 , a radio frequency phase shift (RFPS) circuit 118 , a reception antenna 120 , a low noise amplifier (LNA) 121 , a second mixer 122 , an image rejection and clutter cancellation (IMR & CLC) circuit 123 , an intermediate frequency (IF) mixer 124 , analog-to-digital converters (ADCs) 125 , 126 , and a digital signal processor (DSP) 130 .
  • CLK reference
  • LO local oscillator
  • ATTs/LPFs first and second attenuators/low pass filters
  • PA power amplifier
  • RFPS radio frequency phase shift
  • the CLK 110 generates a reference signal for generating a transmission signal.
  • the first ATT/LPF 112 supplies, to the first mixer 114 , the reference signal separated into in-phase (I) and quadrature (Q) components.
  • the second ATT/LPF 113 supplies, to each of the IMR & CLC circuit 123 and the IF mixer 124 , the reference signal separated into I and Q components.
  • the LO 111 supplies, to the first and second mixers 114 , 122 , a frequency-modulated local oscillation signal, and sequentially supplies, to the DSP 130 , pieces of frequency information FI indicating frequencies at respective points in time during frequency sweeping.
  • the first mixer 114 upconverts the reference signal into an RF signal, based on the associated frequency-modulated local oscillation signal, thereby generating a frequency-modulated transmission signal.
  • the PA 115 amplifies the RF signal from the first mixer 114 to transmit the frequency-modulated transmission signal to the transmission antenna 116 .
  • the transmission antenna 116 radiates an electromagnetic wave toward an object.
  • the reception antenna 120 receives a reflected wave of the frequency-modulated transmission signal from the object, and receives a clutter signal component leaking from the transmission antenna 116 .
  • the HYB circuit 117 has an input capacitively coupled to the output of the PA 115 , and separates the transmission signal, which is a single signal, into I and Q signal components having a phase difference of 90°.
  • the RFPS circuit 118 adjusts, in accordance with a first adjustment value ADJ 1 supplied from the DSP 130 based on the frequency information FI, the amplitude of each of the I and Q signal components supplied from the HYB circuit 117 , thereby generating a cancel signal having an opposite phase to the clutter signal component.
  • the cancel signal is adjusted, for each frequency, to have the same amplitude as, and an opposite phase to, the clutter signal component.
  • the RFPS circuit 118 has an output connected to the input of the LNA 121 , where the cancel signal is superimposed over a received signal to cancel the clutter signal component.
  • the LNA 121 amplifies the received signal including the clutter signal component that may partially remain.
  • the second mixer 122 downconverts the received signal into an intermediate frequency (IF) signal separated into I and Q signal components, based on the associated frequency-modulated local oscillation signal.
  • IF intermediate frequency
  • the IMR & CLC circuit 123 provides image rejection, generates a cancel signal having an opposite phase to the clutter signal component in accordance with a second adjustment value ADJ 2 supplied from the DSP 130 based on the frequency information FI, and superimposes the cancel signal over the received signal to cancel the clutter signal component.
  • the IF mixer 124 downconverts the received signal from which the clutter signal component has been removed.
  • the first and second ADCs 125 and 126 each convert the output of the IF mixer 124 , separated into I and Q signal components, into a digital signal, and then passes it to the DSP 130 .
  • the DSP 130 calculates the distance to the object and the moving velocity of the object by analyzing the reflected wave from the object based on the outputs of the first and second ADCs 125 and 126 .
  • the DSP 130 operates in a calibration mode prior to the foregoing normal operation.
  • the DSP 130 stores, as a correction value in its internal memory, the first adjustment value ADJ 1 that is set such that the input level to the DSP 130 becomes minimum with no reflected wave input from the object.
  • This correction value corresponds to one of the pieces of frequency information FI received from the LO 111 at this point in time.
  • the RFPS circuit 118 may be appropriately adjusted based on the first adjustment value ADJ 1 derived from the correction value in the memory.
  • the calibration may be performed again either regularly or irregularly, not only during an initial stage.
  • the correction value may also be obtained sporadically at only some points in time in accordance with a variation in transmission frequency. In the interval between those points in time, an interpolation (e.g., a linear interpolation) may be performed to obtain the correction value.
  • a value obtained by performing an arithmetic operation on (e.g., by calculating a moving average of) the results of calibrations that have been carried out regularly or irregularly a number of times may be used as the correction value.
  • the above statement applies not only to the RFPS circuit 118 but also to the IMR & CLC circuit 123 .
  • a calibration mode of operation for the RFPS circuit 118 is initially performed, where no cancel signal is output from the IMR & CLC circuit 123 .
  • a calibration mode of operation for the IMR & CLC circuit 123 is performed, where the RFPS circuit 118 outputs a cancel signal in accordance with the first adjustment value ADJ 1 obtained during the calibration mode of operation previously performed. This allows the IMR & CLC circuit 123 to cancel the clutter signal component that has not been completely suppressed by the RFPS circuit 118 .
  • FIG. 2 shows an exemplary detailed configuration for the RFPS circuit 118 shown in FIG. 1 .
  • the RFPS circuit 118 shown in FIG. 2 includes two balanced-unbalanced converters (baluns (BLNs)) 201 , 202 on its input end, two variable gain amplifiers (VGAs) 203 , 204 , and one balun (BLN) 205 on its output end.
  • the two BLNs 201 , 202 each convert an associated one of the I and Q signal components, which are two single signal components, into a differential pair of signal components.
  • one of the VGAs i.e., the VGA 203
  • the other VGA i.e., the VGA 204
  • the amplitudes of the two outputs of each of these VGAs 203 , 204 are adjusted in accordance with the first adjustment value ADJ 1 .
  • these two pairs of amplified I and Q signal components are superimposed one over the other, thereby obtaining a single output signal.
  • the baluns and the variable gain amplifiers for two differential pairs of signal components are used.
  • variable gain amplifiers for single signal components may be used without using baluns.
  • FIG. 3 shows an exemplary detailed configuration for a CLC section of the IMR & CLC circuit 123 shown in FIG. 1 .
  • the CLC section shown in FIG. 3 includes an operational amplifier 210 serving as an inverting amplifier, first input resistors Rin 1 , second input resistors Rin 2 , and feedback resistors Rf, and synthesizes signals together at a virtual ground node.
  • the second input resistors Rin 2 each have a variable resistance value, which is adjusted in accordance with the second adjustment value ADJ 2 , thereby controlling the respective amplitudes of the cancel signals I and Q. Adjusting the respective amplitudes of these cancel signals I and Q as described above allows this CLC section to produce a cancel signal I+Q having the same amplitude as, and an opposite phase to, the clutter signal component as shown in FIG. 4 .
  • the configuration shown in FIG. 1 may curb a decline in the precision of the distance measured, no matter how short it may be, even if a variation in the transmission frequency has triggered a variation in the amplitude and phase of the clutter signal component.
  • the RFPS circuit 118 and the IMR & CLC circuit 123 may adjust the amplitude and phase of the cancel signal simply by adjusting only the respective amplitudes of the I and Q signal components. This may conveniently reduce the circuit size.
  • the RFPS circuit 118 is closer to the reception antenna 120 than the IMR & CLC circuit 123 , and therefore, more effectively cancels the clutter signal component. This reduces the power input to the LNA 121 and the second mixer 122 , thus alleviating the distortion characteristic. Nevertheless, the IMR & CLC circuit 123 operates in a lower frequency range and therefore, makes the cancellation control easier, than the RFPS circuit 118 does, which is beneficial.
  • the output of the RFPS circuit 118 may be connected between the LNA 121 and the second mixer 122 .
  • the CLK 110 may perform the frequency sweeping. In that case, not the frequency information FI of the LO 111 but frequency information of the CLK 110 is provided for the DSP 130 , which supplies the adjustment values ADJ 1 , ADJ 2 in accordance with this frequency information.
  • FIG. 5 is a block diagram of an FMCW radar according to a variation of the embodiment shown in FIG. 1 , and shows an example in which the reference signal is not separated into I and Q signal components.
  • the IMR & CLC circuit 123 shown in FIG. 1 is replaced with a simple CLC circuit 123 .
  • the configuration shown in FIG. 5 needs neither the ATTs/LPFs 112 , 113 nor the HYB circuit 117 unlike the configuration shown in FIG. 1 .
  • the FMCW radar updates the cancel signal in accordance with a variation in the transmission frequency, thus allowing the cancel signal to follow the variation pattern of the clutter signal component. This may effectively prevent the precision of the distance measured from declining, even if the transmission and reception systems are arranged close to each other.

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  • Engineering & Computer Science (AREA)
  • Radar, Positioning & Navigation (AREA)
  • Remote Sensing (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Physics & Mathematics (AREA)
  • General Physics & Mathematics (AREA)
  • Signal Processing (AREA)
  • Radar Systems Or Details Thereof (AREA)
US15/443,423 2014-08-28 2017-02-27 FMCW radar Active 2036-05-25 US10444326B2 (en)

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JP2014173729 2014-08-28
JP2014-173729 2014-08-28
PCT/JP2015/003062 WO2016031108A1 (fr) 2014-08-28 2015-06-18 Radar à onde continue modulée en fréquence

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* Cited by examiner, † Cited by third party
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US20200003866A1 (en) * 2018-06-29 2020-01-02 Imec Vzw System and method for performing spillover cancellation
US11047952B2 (en) * 2018-12-28 2021-06-29 Qualcomm Incorporated Mitigating mutual coupling leakage in small form factor devices

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* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
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JP6985612B2 (ja) * 2016-12-27 2021-12-22 株式会社ソシオネクスト レーダー装置
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US11054500B2 (en) * 2017-08-08 2021-07-06 Texas Instruments Incorporated Noise measurement in a radar system
CN107728116B (zh) * 2017-09-13 2020-10-16 加特兰微电子科技(上海)有限公司 雷达系统及其泄漏信号抵消电路和方法
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US11947031B2 (en) * 2018-11-13 2024-04-02 Texas Instruments Incorporated Radar transceiver
EP3667358B1 (fr) 2018-12-11 2024-03-06 NXP USA, Inc. Annulation de fuites dans un récepteur radar
US11402464B2 (en) 2019-02-25 2022-08-02 Samsung Electronics Co., Ltd. Radar leakage measurement update
US11656331B2 (en) * 2020-11-30 2023-05-23 Keysight Technologies, Inc. System and method of emulating echo signals from emulated targets with reduced interference

Citations (18)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPH11183600A (ja) 1997-12-19 1999-07-09 Toshiba Corp レーダ装置
US20020072344A1 (en) * 2000-08-22 2002-06-13 Souissi Slim Salah Method and apparatus for transmitter noise cancellation in an RF communications system
US20060198429A1 (en) * 2005-03-02 2006-09-07 Microelectronics Technology Inc. Isolating circuit of transmitting and receiving paths in same frequency carrier
JP2007071751A (ja) 2005-09-08 2007-03-22 Shimada Phys & Chem Ind Co Ltd レーダー装置
US20070085727A1 (en) 2005-10-19 2007-04-19 Honeywell International Inc. Methods and systems for leakage cancellation in radar equipped munitions
JP2007281592A (ja) 2006-04-03 2007-10-25 Brother Ind Ltd 無線通信装置
US20080041953A1 (en) * 2006-04-27 2008-02-21 Sirit Technologies Inc. Adjusting parameters associated with leakage signals
US20090130981A1 (en) 2006-04-03 2009-05-21 Takuya Nagai Radio-frequency communication device
US20090213770A1 (en) * 2008-02-27 2009-08-27 Fenghao Mu Active Cancellation of Transmitter Leakage in a Wireless Transceiver
US20090232260A1 (en) * 2005-09-06 2009-09-17 Mitsubishi Electric Corporation Leakage signal cancellation apparatus
US7772997B2 (en) * 2007-08-23 2010-08-10 Sirit Technologies, Inc. Reducing leakage noise in directly sampled radio frequency signals
US20120112956A1 (en) 2009-07-16 2012-05-10 Freescale Semiconductor, Inc. Integrated circuit, transceiver and method for leakage cancellation in a receive path
US20120249363A1 (en) * 2010-08-13 2012-10-04 Vladimir Kolinko Long range millimeter wave surface imaging radar system
US20130102254A1 (en) * 2010-05-27 2013-04-25 Ubiquam Ltd. Method and system of interference cancelation in collocated transceivers configurations
US20140220908A1 (en) * 2013-02-06 2014-08-07 Lup Meng Loh Adaptive transmitter leakage cancelation in a transceiver
US20140315501A1 (en) * 2013-04-22 2014-10-23 University Of Washington Through Its Center For Commercialization Systems, transceivers, receivers, and methods including cancellation circuits having multiport transformers
US9331735B1 (en) * 2014-05-22 2016-05-03 Hrl Laboratories, Llc GaN based active cancellation circuit for high power simultaneous transmit and receive systems
US9739871B2 (en) * 2012-10-17 2017-08-22 Murata Manufacturing Co., Ltd. Transmission-reception apparatus

Patent Citations (20)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPH11183600A (ja) 1997-12-19 1999-07-09 Toshiba Corp レーダ装置
US20020072344A1 (en) * 2000-08-22 2002-06-13 Souissi Slim Salah Method and apparatus for transmitter noise cancellation in an RF communications system
US20060198429A1 (en) * 2005-03-02 2006-09-07 Microelectronics Technology Inc. Isolating circuit of transmitting and receiving paths in same frequency carrier
US20090232260A1 (en) * 2005-09-06 2009-09-17 Mitsubishi Electric Corporation Leakage signal cancellation apparatus
JP2007071751A (ja) 2005-09-08 2007-03-22 Shimada Phys & Chem Ind Co Ltd レーダー装置
US20070085727A1 (en) 2005-10-19 2007-04-19 Honeywell International Inc. Methods and systems for leakage cancellation in radar equipped munitions
JP2007281592A (ja) 2006-04-03 2007-10-25 Brother Ind Ltd 無線通信装置
US20090130981A1 (en) 2006-04-03 2009-05-21 Takuya Nagai Radio-frequency communication device
US8233872B2 (en) * 2006-04-03 2012-07-31 Brother Kogyo Kabushiki Kaisha Radio-frequency communication device
US20080041953A1 (en) * 2006-04-27 2008-02-21 Sirit Technologies Inc. Adjusting parameters associated with leakage signals
US7772997B2 (en) * 2007-08-23 2010-08-10 Sirit Technologies, Inc. Reducing leakage noise in directly sampled radio frequency signals
US20090213770A1 (en) * 2008-02-27 2009-08-27 Fenghao Mu Active Cancellation of Transmitter Leakage in a Wireless Transceiver
US20120112956A1 (en) 2009-07-16 2012-05-10 Freescale Semiconductor, Inc. Integrated circuit, transceiver and method for leakage cancellation in a receive path
JP2012533255A (ja) 2009-07-16 2012-12-20 フリースケール セミコンダクター インコーポレイテッド 受信経路中の漏洩相殺のための集積回路、トランシーバおよびコンピュータ読取り可能記憶素子
US20130102254A1 (en) * 2010-05-27 2013-04-25 Ubiquam Ltd. Method and system of interference cancelation in collocated transceivers configurations
US20120249363A1 (en) * 2010-08-13 2012-10-04 Vladimir Kolinko Long range millimeter wave surface imaging radar system
US9739871B2 (en) * 2012-10-17 2017-08-22 Murata Manufacturing Co., Ltd. Transmission-reception apparatus
US20140220908A1 (en) * 2013-02-06 2014-08-07 Lup Meng Loh Adaptive transmitter leakage cancelation in a transceiver
US20140315501A1 (en) * 2013-04-22 2014-10-23 University Of Washington Through Its Center For Commercialization Systems, transceivers, receivers, and methods including cancellation circuits having multiport transformers
US9331735B1 (en) * 2014-05-22 2016-05-03 Hrl Laboratories, Llc GaN based active cancellation circuit for high power simultaneous transmit and receive systems

Non-Patent Citations (1)

* Cited by examiner, † Cited by third party
Title
International Search Report and Written Opinion dated Sep. 15, 2015 issued in International Patent Application No. PCT/JP2015/003062 (with partial English translation).

Cited By (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20200003866A1 (en) * 2018-06-29 2020-01-02 Imec Vzw System and method for performing spillover cancellation
US11428778B2 (en) * 2018-06-29 2022-08-30 Imec Vzw System and method for performing spillover cancellation
US11047952B2 (en) * 2018-12-28 2021-06-29 Qualcomm Incorporated Mitigating mutual coupling leakage in small form factor devices

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