TWI792944B - High Boost DC Converter Device - Google Patents

Abstract

A high boost DC converter device, comprising a first coupling inductor, a second coupling inductor, two switches, a clamping diode, a lifting capacitor, a first voltage doubler capacitor, a second voltage doubler diode, a second voltage doubler A double voltage capacitor, a first output stage, a second output stage, and a third output stage. The input parallel architecture can share the input current, so it is suitable for high input current applications. The first switch and the second switch are operated in an interleaved manner, so that the ripple current on the primary side of the coupled inductor has a canceling effect, and the input current ripple can be reduced. The first voltage doubler capacitor, the second voltage doubler diode, and the second voltage doubler capacitor provide the voltage doubling function, and use the lifting capacitor and three coupled inductors to perform voltage doubling and further connect with a first output stage and a second output The superimposed output of the stage and the third output stage further increases the voltage gain.

Description

High Boost DC Converter Device

The invention relates to a voltage conversion technology, in particular to a high boost DC converter device.

，參數V _O、V _in、D分別為輸出電壓、輸入電壓、開關的責任導通比，但是實務上受到寄生元件的影響，當導通比超過0.9以上時而使電壓增益不增反減，不符高電壓增益的需求，因此，無需極高導通比且同時為符合高電壓增益的需求的高升壓轉換器是未來的研究方向。 Referring to Figure 1, a conventional boost converter, the conventional boost converter operates at a very high conduction ratio to achieve high voltage gain

, the parameters V _O , V _in , and D are the output voltage, input voltage, and duty conduction ratio of the switch, but in practice, they are affected by parasitic elements. When the conduction ratio exceeds 0.9, the voltage gain does not increase but decreases, which is inconsistent with high The demand for voltage gain, therefore, a high boost converter that does not require a very high conduction ratio and at the same time meets the demand for high voltage gain is a future research direction.

Therefore, an object of the present invention is to provide a high-boost DC converter device capable of overcoming the disadvantages of the prior art.

Therefore, the high boost DC converter device includes a first coupled inductor, a second coupled inductor, a first switch, a second switch, a clamping diode, a lifting capacitor, a first regenerative diode, A first regenerative capacitor, a first voltage doubler diode, a first voltage doubler capacitor, a second regenerative diode, a second regenerative capacitor, a second voltage doubler diode, a second doubler piezocapacitor, a first output stage, a second output stage and a third output stage.

Each coupled inductor has a first winding, a second winding and a third winding, and each winding has a first end and a second end, wherein the first end of the first winding of the first coupled inductor is connected to the The first end of the second winding of the second coupled inductor is electrically connected together to receive a DC input voltage, and the second end of the second winding of the first coupled inductor is electrically connected to the second winding of the second coupled inductor. The second end, the second end of the third winding of the first coupled inductor is electrically connected to the second end of the third winding of the second coupled inductor.

The first switch has a first end electrically connected to the second end of the first winding of the first coupled inductor, and a second end that is grounded, and the first switch is controlled to switch between a conduction state and a non-conduction state , when the first switch is turned on, the first winding of the first coupled inductor receives a current for charging. The second switch has a first end electrically connected to the second end of the first winding of the second coupled inductor, and a second end that is grounded, and the second switch is controlled to switch between a conduction state and a non-conduction state .

The clamping diode has an anode electrically connected to the second end of the first winding of the second coupled inductor, and a cathode. The lifting capacitor is electrically connected between the second end of the first winding of the first coupled inductor and the cathode of the clamping diode.

The first regenerative diode has an anode electrically connected to the first end of the second winding of the second coupled inductor, and a cathode. The first regenerative capacitor is electrically connected between the first end of the second winding of the first coupled inductor and the cathode of the first regenerative diode. The first voltage doubler diode has an anode electrically connected to the cathode of the first regenerative diode, and a cathode. The first voltage doubler capacitor is electrically connected between the first end of the second winding of the second coupling inductor and the cathode of the first voltage doubler diode.

The second regenerative diode has an anode electrically connected to the first end of the third winding of the first coupled inductor, and a cathode. The second regenerative capacitor is electrically connected between the first end of the third winding of the second coupling inductor and the cathode of the second regenerative diode. The second voltage doubler diode has an anode electrically connected to the cathode of the second regenerative diode, and a cathode. The second voltage doubler capacitor is electrically connected between the first end of the third winding of the first coupling inductor and the cathode of the second voltage doubler diode.

The first output stage is electrically connected to the cathode of the clamping diode, and is used for generating a first DC voltage according to the discharge from the first winding and the lifting capacitor. The second output stage is electrically connected to the cathode of the first voltage doubler diode, and is used for generating a second DC voltage according to the discharge from the second winding and the first voltage doubler capacitor. The third output stage is electrically connected to the cathode of the second voltage doubler diode, and is used for generating a third DC voltage according to the discharge from the third winding and the second voltage doubler capacitor.

The first output stage is also stacked with the second output stage and the third output stage to generate an output voltage, which is proportional to the sum of the first voltage, the second voltage, and the third voltage.

The efficacy of the present invention lies in: using the lifting capacitor and the three windings of the two coupling inductors for voltage multiplication, so that the voltage gain has two design degrees of freedom: the coupling inductor turns ratio and the switch conduction ratio, so the high voltage gain can be achieved , need not operate at extremely large conduction ratios.

Before the present invention is described in detail, it should be noted that in the following description, similar elements are denoted by the same numerals.

Referring to FIG. 2, it is an embodiment of the high boost DC converter device of the present invention, which includes a first coupled inductor 1, a second coupled inductor 2, a first switch S ₁ , a second switch S ₂ , and a clamp Diode D _C , a lifting capacitor C _f , a first regenerative diode D ₁₁ , a first regenerative capacitor C ₁₁ , a first voltage doubler diode D ₁₂ , a first voltage doubler capacitor C ₁₂ , A second regenerative diode D ₂₁ , a second regenerative capacitor C ₂₁ , a second voltage doubler diode D ₂₂ , a second voltage doubler capacitor C ₂₂ , a first output stage O1, a second output stage O2, a third output stage O3, and a control unit 4.

Each coupled inductor 1, 2 respectively has a first winding N ₁ , P ₁ , a second winding N ₂ , P ₂ and a third winding N ₃ , P ₃ , each winding N ₁ ~N ₃ , P ₁ ~ _P3 has a first end and a second end, wherein, the first end of the first winding N1 of the first coupled inductor ₁ is electrically connected to the first end of the first winding P1 of the second coupled inductor ₂ connected together to receive a DC input voltage, the second end of the second winding _N2 of the first coupling inductor 1 is electrically connected to the second end of the second winding P2 of the second coupling inductor ₂ , the first coupling The second end of the third winding N ₃ of the inductor 1 is electrically connected to the second end of the third winding P ₃ of the second coupled inductor 2 . The first end of each first winding N ₁ , P ₁ is a dotted end, and the second end of each first winding N ₁ , P ₁ is a non-dotted end. The first end of each second winding N ₂ , P ₂ is a dotted end, and the second end of each second winding N ₂ , P ₂ is a non-dotted end. The first end of each third winding N ₃ , P ₃ is a dotted end, and the second end of each third winding N ₃ , P ₃ is a non-dotted end.

The first switch _S1 has a first end electrically connected to the second end of the first winding _N1 of the first coupled inductor 1, and a second end that is grounded, and the first switch _S1 is controlled to switch between Between the conducting state and the non-conducting state, when the first switch _S1 is conducting, the first winding N1 of the first coupled inductor ₁ receives a current for charging. The first switch _S1 is an N-type power semiconductor transistor, and the first end of the first switch _S1 is a drain, and the second end of the first switch _S1 is a source.

The second switch _S2 has a first end electrically connected to the second end of the first winding _P1 of the second coupled inductor 2, and a second end that is grounded, and the second switch _S2 is controlled to switch between Between the conduction state and the non-conduction state; the second switch _S2 is an N-type power semiconductor transistor, and the first end of the second switch _S2 is a drain, and the second end of the second switch _S2 is a source pole.

The clamping diode _DC has an anode electrically connected to the second terminal of the first winding P ₁ of the second coupled inductor 2 , and a cathode. The lifting capacitor C _f is electrically connected between the second end of the first winding N ₁ of the first coupling inductor 1 and the cathode of the clamping diode _DC .

The first regenerative diode D ₁₁ has an anode electrically connected to the first end of the second winding P ₂ of the second coupled inductor 2 , and a cathode. The first regenerative capacitor C ₁₁ is electrically connected between the first end of the second winding N ₂ of the first coupling inductor 1 and the cathode of the first regenerative diode D ₁₁ . The first voltage doubling diode _D12 has an anode electrically connected to the cathode of the first regenerative diode _D11 , and a cathode. The first voltage doubling capacitor C ₁₂ is electrically connected between the first end of the second winding P ₂ of the second coupled inductor 2 and the cathode of the first voltage doubling diode D ₁₂ .

The second regenerative diode D ₂₁ has an anode electrically connected to the first end of the third winding N ₃ of the first coupled inductor 1 , and a cathode. The second regenerative capacitor C ₂₁ is electrically connected between the first end of the third winding P ₃ of the second coupling inductor 2 and the cathode of the second regenerative diode D ₂₁ . The second voltage doubler diode _D22 has an anode electrically connected to the cathode of the second regenerative diode _D21 , and a cathode. The second voltage doubling capacitor C ₂₂ is electrically connected between the first end of the third winding N ₃ of the first coupling inductor 1 and the cathode of the second voltage doubling diode D ₂₂ .

The first output stage O1 is electrically connected to the cathode of the clamping diode _DC for generating a first DC voltage according to the discharge from the first coupling inductor 1 and the lifting capacitor C _f . The first output stage O1 includes a first output diode D _o1 and a first output capacitor C ₁ .

The first output diode D _o1 has an anode electrically connected to one end of the boost capacitor C _f and a cathode. The first output capacitor _C1 is electrically connected between the cathode of the first output diode D _o1 and ground for providing the first voltage.

The second output stage O2 is electrically connected to the cathode of the first voltage doubler diode D ₁₂ , and is used to generate a second DC voltage according to the discharge from the second coupling inductor 2 and the first voltage doubler capacitor _C12 . Voltage. The second output stage O2 includes a second output diode D _o2 and a second output capacitor C ₂ .

The second output diode D _o2 has an anode electrically connected to one end of the first voltage doubling capacitor C ₁₂ , and a cathode. The second output capacitor _C2 is electrically connected between the cathode of the second output diode D _o2 and the first output capacitor _C1 for providing the second voltage.

The third output stage O3 is electrically connected to the cathode of the second voltage doubling diode _D22 , and is used to generate a DC current according to the discharge from the third winding _N3 , _P3 and the second voltage doubling capacitor _C22 . the third voltage. The third output stage O3 includes a third output diode D _o3 and a third output capacitor C ₃ .

The third output diode D _o3 has an anode electrically connected to one end of the second voltage doubling capacitor C ₂₂ , and a cathode. The third output capacitor _C3 is electrically connected between the cathode of the third output diode D _o3 and the second output capacitor _C2 to provide the third voltage, wherein the first output capacitor _C1 and the The second output capacitor _C2 is stacked with the third output capacitor _C3 .

The first output stage O1 is also stacked with the second output stage O2 and the third output stage O3 to generate an output voltage V _o , the output voltage V _o is proportional to the first voltage and the second voltage and the summation of the third voltage.

The control unit 4 generates a first pulse modulation signal for switching the first switch _S1 and a second pulse modulation signal for switching the second switch _S2 , the first pulse modulation signal and the second pulse modulation signal The two pulse modulation signals have the same cycle time. A portion of the period time of the first and second pulse modulation signals overlaps. The switching timing diagram of the first switch S ₁ and the second switch S ₂ will be further described below in eight stages.

Referring to FIG. 3 , it is an equivalent circuit diagram of this embodiment, which is used to illustrate the respective magnetizing inductances L _m1 , L _m2 and their leakage inductances L _k1 , L _k2 in the non-ideal equivalent circuit of the two coupled inductors. Among them, the parameter V _in represents the input voltage, and the parameter V _o represents the output voltage.

Referring to FIG. 4 , it is an operation timing diagram of this embodiment, wherein the parameters v _gs1 and v _gs2 respectively represent the voltages of the first and second pulse signals controlling whether the first and second switches S ₁ and S ₂ are turned on, The parameters v _ds1 and v _ds2 respectively represent the voltage across the first and second switches S ₁ and S ₂ , and the parameter T _S is the cycle time of the first pulse signal. The parameter i _in represents the input current. The parameters i _Lk1 and i _Lk2 respectively represent the leakage inductance current flowing through the first winding N ₁ of the first coupled inductor 1 and the first winding P ₁ of the second coupled inductor 2 . The parameter i _Dc represents the current flowing through the clamping diode D _C , the parameter i _Do1 represents the current flowing through the first output diode D _o1 , the parameter i _D11 represents the current flowing through the first regenerative diode D ₁₁ , The parameter i _D21 represents the current flowing through the second regenerative diode D ₂₁ , the parameter i _D12 represents the current flowing through the first voltage doubler diode D ₁₂ , and the parameter i _D22 represents the current flowing through the second voltage doubler diode D ₂₂ The current, the parameter i _Do2 represents the current flowing through the second output diode D _o2 , and the parameter i _Do3 represents the current flowing through the third output diode D _o3 .

The following are the circuit diagrams of this embodiment operating in eight stages, each stage is described separately.

The first stage (time: t ₀ ~t ₁ ):

Referring to Fig. 4 and Fig. 5, the first switch S ₁ turns from non-conduction to conduction, and the second switch S ₂ conducts, the first output diode D _o1 , the clamping diode D _C , and the first voltage doubler diode D ₁₂ , the second regenerative diode D ₂₁ and the third output diode D _o3 are all reverse biased and non-conductive.

Due to the existence of the leakage inductance L _k1 , and the leakage inductance current i _Lk1 is 0 at time to, the first switch S ₁ is switched on with zero current switching (ZCS). In the first stage, the leakage inductance current i _Lk1 rises rapidly from 0. When i _Lk1 <i _Lm1 , the energy stored in the magnetizing inductance L _m1 is coupled and transmitted to the second winding N ₂ and the third winding N ₃ , so that the first regenerative diode D ₁₁ , the second output diode D _o2 and The second voltage doubler diode D ₂₂ is turned on, causing the currents i _D11 , i _Do2 and i _D22 to drop, and the rate of drop is controlled by the leakage inductance L _k1 and L _k2 , thus alleviating the reverse recovery problem of these diodes. When t=t ₁ , the current i _Lk1 rises to satisfy i _Lk1 = i _Lm1 , the ideal transformer current of the first winding N ₁ is equal to 0, so the current flowing through the second winding N ₂ and the third winding N ₃ drops to 0, Make the current i _D11 , i _Do2 and i _D22 drop to 0, and the first regenerative diode D ₁₁ , the second output diode D _o2 and the second voltage doubler diode D ₂₂ switch naturally with zero current switching (ZCS) This phase ends when the state becomes non-conductive. The current formula of the first stage is as follows:

。

.

）： second stage(

):

Referring to FIG. 4 and FIG. 6 , the second stage starts at t=t ₁ , the first switch S ₁ and the second switch S ₂ are both in the conduction state, and all the diodes are in the non-conduction state. The input voltage V _in straddles the magnetizing inductance L _m1 , L _m2 and the leakage inductance L _k1 , L _k2 , the leakage inductance current i _Lk1 and i _Lk2 rise linearly. The two magnetizing inductances L _m1 and L _m2 of 2 store energy. The first output capacitor C ₁ , the second output capacitor C ₂ and the third output capacitor C ₃ provide energy to the load. The current formula of the second stage is as follows:

,

,

）： The third phase(

):

Referring to Fig. 4 and Fig. 7, the first switch S ₁ is turned on, while the second switch S ₂ is switched to be non-conductive, because the leakage inductance current i _Lk2 has continuity, which makes the clamping diode _DC turn on, and the leakage inductance The current i _Lk2 flows through the clamping diode D _C , the lifting capacitor C _f and the first switch S ₁ to charge the lifting capacitor C _f . The voltage across the second switch _S2 clamps the voltage of the boost capacitor _Cf. The leakage inductance current i _Lk2 in the third stage decreases, and the energy stored in the magnetizing inductance L _m2 is transmitted to the second winding P ₂ and the third winding P ₃ . The current of the second winding P ₂ makes the first voltage doubler diode D ₁₂ turn on, and the current i _D12 charges the first voltage doubler capacitor C ₁₂ and discharges the first regenerative capacitor C ₁₁ at the same time; the third winding P ₃ The current makes the second regenerative diode D ₂₁ and the third output diode D _o3 turn on, the current i _D21 charges the second regenerative capacitor C ₂₁ , and the current i _Do3 discharges the second voltage doubler capacitor C ₂₂ And charge the third output capacitor _C3 . When t=t3, the leakage inductance current i _Lk2 drops to 0, and the clamping diode D _C turns to non-conduction naturally through zero-current switching (ZCS), and this stage ends.

）： Phase IV (

):

Referring to Fig. 4 and Fig. 8, the fourth stage starts at t=t ₃ , at this time, the energy of the leakage inductance i _Lk2 is released, and the clamping diode D _C turns non-conductive. The magnetizing inductor current L _m2 is completely reflected by the first winding P ₁ to the second winding P ₂ and the third winding P ₃ . In the fourth stage, the operation of the voltage multiplication module circuit composed of the second winding _P2 and the third winding _P3 is the same as that of the third stage. The current flowing through the first switch S1 in the fourth stage is as follows:

）： Fifth stage (

):

Referring to Fig. 4 and Fig. 9, the fifth phase begins at t=tk, the second switch S ₂ is switched on, and the first switch S ₁ remains on, the first output diode D _o1 , the clamping diode D _C , the first regenerative diode D ₁₁ , the second output diode D _o2 and the second voltage doubler diode D ₂₂ are all reverse biased and non-conductive. Due to the existence of the leakage inductance _Lk2 , and the leakage inductance current i _Lk2 at time _t4 is 0, the second switch _S2 is switched on with zero current switching (ZCS). In the fifth stage, the leakage inductance current i _Lk2 rises rapidly from 0. When i _Lk2 <i _Lm2 , the energy stored in the magnetizing inductance L _m2 is still transferred to the second winding P ₂ and the third winding P ₃ through the first winding P ₁ , so that the first voltage doubler diode D ₁₂ , the second winding The second regenerative diode D ₂₁ and the third output diode D _o3 are turned on, and the current i _D12 , i _D21 and i _Do3 decrease, and the rate of decrease is controlled by the leakage inductance L _k1 and L _k2 , thus easing the reaction of the diodes to restore the problem. When the current i _D12 , i _D21 and i _Do3 drop to 0, the first voltage doubler diode D ₁₂ , the second regenerative diode D ₂₁ and the third output diode D _o3 switch naturally in zero current switching (ZCS) When the state becomes non-conductive, the fifth stage ends. The current formula of the fifth stage is as follows:

）： Stage VI (

):

Referring to FIG. 4 and FIG. 10 , the sixth stage begins at t=t ₅ , the first switch S ₁ and the second switch S ₂ are both in the conduction state, and all the diodes are in the non-conduction state. The input voltage V _in straddles the magnetizing inductance L _m1 , L _m2 and the leakage inductance L _k1 , L _k2 , the leakage inductance current i _Lk1 and i _Lk2 rise linearly. The magnetizing inductance L _m1 and L _m2 of 2 store energy. The first output capacitor C ₁ , the second output capacitor C ₂ and the third output capacitor C ₃ provide energy to the load. When t=t ₅ , when the first switch S1 is switched off, the sixth stage ends. The current formula of the sixth stage is as follows:

,

,

）： Seventh stage (

):

Referring to Fig. 4 and Fig. 11, the seventh stage starts at t=t ₆ , and the first switch S1 is switched to non-conduction, because the leakage inductance current i _Lk1 has continuity, so that the first output diode D _O1 turns into conduction, The voltage across the first switch S ₁ is clamped at -V _Cf +V _C1 . In the seventh stage, the input voltage V _in , the magnetizing inductance L _m1 , the leakage inductance L _k1 and the lifting capacitor C _f release energy to the output capacitor C ₁ through the first output diode D _o1 , thus increasing the output capacitor C ₁ first voltage. As the leakage inductance current i _Lk1 decreases, the energy stored in the magnetizing inductance L _m1 is transmitted to the second winding N ₂ and the third winding N ₃ through the first winding N 1 , _and the current in the second winding N ₂ makes the first regenerative diode D ₁₁ , the second output diode D _o2 turns on, the current i _D11 charges the first regenerative capacitor C ₁₁ , the current i _D12 discharges the first capacitor C ₁₂ and the second output capacitor C ₂ Charging: the current of the third winding _N3 makes the diode _D22 turn on, and the current i _D22 charges the second voltage doubling capacitor _C22 and discharges the second regenerative capacitor _C21 at the same time. When the leakage inductance current i _Lk1 drops to 0, and the first output diode D _o1 naturally transitions to non-conduction through zero-current switching (ZCS), this stage ends.

）： Eighth stage (

):

Referring to FIG. 4 and FIG. 12 , the eighth stage starts at t=t ₇ , when the energy of the leakage inductance L _k1 is released, and the first output diode D _o1 turns non-conductive. The magnetizing inductor current i _Lm1 is completely reflected by the first winding N ₁ to the second winding N ₂ and the third winding N ₃ . The circuit operation of the voltage multiplier module (VMM) composed of the second winding _N2 and the third winding _N3 in the eighth stage is the same as that in the seventh stage. When t=t ₈ , when the first switch S ₁ is switched on, this phase ends and the next switching period enters. The formula for the current passing through the second switch in the eighth stage is as follows:

＜Voltage gain analysis＞

It can be seen from the operating principle of the converter that the lifting capacitor C _f is like the output capacitor of a traditional boost converter, and the magnetizing inductance L _m2 satisfies the principle of volt-second balance, so the voltage V _Cf can be derived as

In addition, since the magnetizing inductance L _m1 satisfies the volt-second balance theorem, it can be obtained

The lifting capacitor C _f boosts the voltage value of the first output capacitor C ₁ , so the voltage value of the first output capacitor C ₁ can be obtained

；

，

In the third stage, the magnetizing inductance voltage of the coupled inductor is

;

,

。 Therefore, the voltage of the second regenerative capacitor _C21 can be obtained

.

；

。 In addition, in the third stage, Kirchhoff's voltage law (KVL) can be used to obtain

;

.

In the seventh stage, the magnetizing inductance voltage of the coupled inductor is

；

;

Therefore, the capacitor C ₁₁ voltage can be obtained

In addition, in the seventh stage, KVL can be used to obtain

；

;

The voltage gain can be deduced as

，本轉換器在三種不同之耦合係數

，

，

和

情況下，電壓增益及導通比之關係曲線，由圖可知耦合係數對電壓增益影響很小。若忽略耦合電感之漏電感，即

，轉換器之理想電壓增益M如下： As shown in Figure 13, the relationship between voltage gain and conduction ratio under different coupling coefficients, when the coupling inductor turns ratio

, the converter has three different coupling coefficients

,

,

and

In this case, the relationship curve between voltage gain and conduction ratio can be seen from the figure that the coupling coefficient has little influence on the voltage gain. If the leakage inductance of the coupled inductor is neglected, that is

, the ideal voltage gain M of the converter is as follows:

(當耦合係數

)

(when the coupling coefficient

)

和導通比

。透過調整轉換器之耦合電感匝數比

，可使得高升壓之達成，轉換器不需操作在極大導通比。 From the formula of the ideal voltage gain M, it can be seen that the voltage gain of the converter has two design degrees of freedom: the coupling inductor turns ratio

and conduction ratio

. By adjusting the coupling inductor turns ratio of the converter

, can achieve a high boost, the converter does not need to operate at a very large conduction ratio.

及耦合電感匝數比

之曲線圖，由圖可知：當

及

時，電壓增益為20倍，當

及

時，電壓增益為35倍。 As shown in Figure 14, when the coupling coefficient k=1, the voltage gain and conduction ratio

and coupled inductor turns ratio

It can be seen from the graph that: when

and

, the voltage gain is 20 times, when

and

, the voltage gain is 35 times.

＜Switch voltage stress analysis＞

)，開關元件視為理想，即壓降為零。由第三階段及第七階段可知，第一開關

和第二開關

之電壓應力分別如下式： If the capacitor ripple voltage and the leakage inductance of the coupled inductor (coupling coefficient

), the switching element is considered ideal, that is, the voltage drop is zero. It can be seen from the third stage and the seventh stage that the first switch

and the second switch

The voltage stresses are as follows:

，

；

；

。 From the third stage, it can be found that the voltage stress of the first output diode D _o1 , the second output diode D _o2 , the first regenerative diode D ₁₁ , and the second regenerative diode D ₂₂ can be expressed as follows:

,

;

;

.

；

；

；

。 From the seventh stage, it can be found that the voltage stress of the clamping diode D _c , the first voltage doubler diode D ₁₂ , the second regenerative diode D ₂₁ , and the third output diode D _o3 can be expressed as follows:

;

;

;

.

Since the voltage stress of the power switch and diode of the traditional interleaved boost converter is the output voltage V _o , it can be known from the above formula that the voltage stress of the first switch S ₁ and the second switch S ₂ in this embodiment It is only 1/(6n+2) times of the output voltage V _o , so MOSFETs with low rated voltage and low on-resistance can be used to reduce the switch conduction loss. Moreover, the voltage stress of the diodes in this embodiment is far lower than the output voltage V _o , which belongs to low voltage stress diodes, and power diodes with lower forward conduction voltage drop can be used to reduce conduction loss.

In summary, the above embodiment has the following advantages:

1. Use the lifting capacitor C _f and coupling inductors 1 and 2 to perform voltage multiplication (wherein, the second winding N ₂ , P ₂ and the first voltage doubler diode D ₁₂ , the first voltage doubler capacitor C ₁₂ , the first The regenerative diode D ₁₁ forms a voltage multiplication module. The second winding N ₃ , P ₃ is composed of the second voltage doubling diode D ₂₂ , the second voltage doubling capacitor C ₂₂ , and the second regenerative diode D ₂₁ Another voltage multiplier module), so that the voltage gain has two design degrees of freedom: the coupling inductor turns ratio and the switch conduction ratio, so the achievement of high voltage gain does not need to operate at a very large conduction ratio. 2. The low voltage stress of the first switch _S1 and the second switch _S2 (far lower than the output voltage), can use low rated voltage MOSFETs with small on-resistance to reduce the conduction loss. The first switch _S1 and the second switch _S2 can be turned on by zero current switching (ZCS) to reduce switching loss. 3. For the low voltage stress of the diode (far lower than the output voltage), you can use a diode with a small forward conduction voltage drop to reduce the conduction loss. The leakage inductance alleviates the reverse recovery problem of the diode and improves the reverse recovery loss of the diode. 4. The leakage inductance energy of the coupled inductor can be recovered and transmitted to the output side, which not only avoids voltage surges on the first switch S ₁ and the second switch S ₂ , but also improves efficiency. 5. The parallel input structure of the converter reduces the component current stress, and the two power switches (the first switch S ₁ and the second switch S ₂ ) adopt interleaved operation to reduce the input current ripple.

But the above-mentioned ones are only embodiments of the present invention, and should not limit the scope of the present invention. All simple equivalent changes and modifications made according to the patent scope of the present invention and the content of the patent specification are still within the scope of the present invention. Within the scope covered by the patent of the present invention.

1: first coupled inductor 2: second coupled inductor N ₁ , P ₁ : first winding N ₂ , P ₂ : second winding N ₃ , P ₃ : third winding S ₁ : first switch S ₂ : second Switch D _C : clamping diode C _f : lifting capacitor D ₁₁ : first regeneration diode C ₁₁ : first regeneration capacitor D ₁₂ : first voltage doubler diode C ₁₂ : first voltage doubler capacitor D ₂₁ : second regenerative diode C ₂₁ : second regenerative capacitor D ₂₂ : second voltage doubler diode C ₂₂ : second voltage doubler capacitor O1: first output stage C ₁ : first output capacitor D _o1 : the first output diode O2: the second output stage C ₂ : the second output capacitor D _o2 : the second output diode O3: the third output stage C ₃ : the third output capacitor D _o3 : the third output diode Body 4: control unit Vin: input voltage V _o : output voltage L _m1 : magnetizing inductance L _m2 : magnetizing inductance v _gs1 : voltage of the first pulse wave signal v _gs2 : voltage of the second pulse wave signal v _ds1 : first switch The two-terminal voltage v _ds2 : the two-terminal voltage of the second switch i _LK1 : the leakage inductance current i _LK2 : the leakage inductance current i _Dc : the current i flowing through the clamping diode _Do1 : flowing through the first output diode _Body current i _D11 : current i _D21 flowing through the first regenerative diode: current i D12 flowing through the second regenerative diode: current i _D22 flowing through the first voltage doubler diode: flowing through the second Current i _Do2 of the voltage doubler diode: current flowing through the second output diode i _Do3 : current flowing through the third output diode

Other features and effects of the present invention will be clearly presented in the implementation manner with reference to the drawings, wherein: FIG. 1 is a circuit diagram of a conventional boost converter; Fig. 2 is a circuit diagram of an embodiment of the high boost DC converter device of the present invention; Fig. 3 is an equivalent circuit diagram of this embodiment; Fig. 4 is an operation sequence diagram of this embodiment; Fig. 5 is a circuit diagram of this embodiment operating in the first stage; Fig. 6 is a circuit diagram of this embodiment operating in the second stage; Fig. 7 is a circuit diagram of this embodiment operating in the third stage; Fig. 8 is a circuit diagram of this embodiment operating in the fourth stage; Fig. 9 is a circuit diagram of this embodiment operating in the fifth stage; Fig. 10 is a circuit diagram of this embodiment operating in the sixth stage; Fig. 11 is a circuit diagram of this embodiment operating in the seventh stage; Fig. 12 is a circuit diagram of this embodiment operating in the eighth stage; Figure 13 is a relational graph of different coupling coefficients and voltage gains of this embodiment; and FIG. 14 is a voltage gain curve diagram of the turns ratio and conduction ratio of the coupled inductor in this embodiment.

1: First coupled inductance

2: Second coupled inductor

N ₁ , P ₁ : first winding

N ₂ , P ₂ : Second winding

N ₃ , P ₃ : the third winding

S ₁ : first switch

S ₂ : second switch

D _C : clamping diode

C _f : Lift capacitor

D ₁₁ : first regenerative diode

C ₁₁ : the first regenerative capacitor

D ₁₂ : The first voltage doubler diode

C ₁₂ : the first voltage doubler capacitor

D ₂₁ : second regenerative diode

C ₂₁ : Second regenerative capacitor

D ₂₂ : Second voltage doubler diode

C ₂₂ : the second voltage doubler capacitor

O1: first output stage

C ₁ : the first output capacitor

D _o1 : the first output diode

O2: second output stage

C ₂ : Second output capacitor

D _o2 : second output diode

O3: third output stage

C ₃ : the third output capacitor

D _o3 : The third output diode

4: Control unit

Claims (10)

A high boost DC converter device comprising: A first coupled inductor and a second coupled inductor, each coupled inductor has a first winding, a second winding and a third winding, each winding has a first end and a second end, wherein the first The first end of the first winding of a coupled inductor is electrically connected to the first end of the first winding of the second coupled inductor to receive a DC input voltage, and the second end of the second winding of the first coupled inductor electrically connected to the second end of the second winding of the second coupled inductor, the second end of the third winding of the second coupled inductor is electrically connected to the second end of the third winding of the second coupled inductor, a first switch, having a first end electrically connected to the second end of the first winding of the first coupled inductor, and a second end connected to ground, and the first switch is controlled to switch between a conduction state and a non-conduction state During the state, when the first switch is turned on, the first winding of the first coupled inductor receives a current for charging; a second switch, having a first end electrically connected to the second end of the first winding of the second coupled inductor, and a second end connected to ground, and the second switch is controlled to switch between a conduction state and a non-conduction state between states; a clamping diode having an anode electrically connected to the second end of the first winding of the second coupled inductor, and a cathode; a lifting capacitor electrically connected between the second end of the first winding of the first coupling inductor and the cathode of the clamping diode; The first regenerative diode has an anode electrically connected to the first end of the second winding of the second coupled inductor, and a cathode; A first regenerative capacitor, electrically connected between the first end of the second winding of the first coupled inductor and the cathode of the first regenerative diode; a first voltage doubling diode having an anode electrically connected to the cathode of the first regenerative diode, and a cathode; A first voltage doubler capacitor, electrically connected between the first end of the second winding of the second coupled inductor and the cathode of the first voltage doubler diode; a second regenerative diode, having an anode electrically connected to the first end of the third winding of the first coupled inductor, and a cathode; A second regenerative capacitor, electrically connected between the first end of the third winding of the second coupled inductor and the cathode of the second regenerative diode; a second voltage doubling diode having an anode electrically connected to the cathode of the second regenerative diode, and a cathode; A second voltage doubler capacitor, electrically connected between the first end of the third winding of the first coupled inductor and the cathode of the second voltage doubler diode; a first output stage, electrically connected to the cathode of the clamping diode, for generating a first DC voltage according to the discharge from the first winding and the lifting capacitor; A second output stage, electrically connected to the cathode of the first voltage doubler diode, for generating a second DC voltage according to the discharge from the second winding and the first voltage doubler capacitor; A third output stage, electrically connected to the cathode of the second voltage doubler diode, for generating a third voltage in the form of direct current according to the discharge from the third winding and the second voltage doubler capacitor; The first output stage is also stacked with the second output stage and the third output stage to generate an output voltage, which is proportional to the sum of the first voltage, the second voltage, and the third voltage. The high-boost DC converter device as claimed in claim 1, wherein the first output stage includes: a first output diode having an anode electrically connected to one end of the boost capacitor, and a cathode; and A first output capacitor is electrically connected between the cathode of the first output diode and ground to provide the first voltage. The high-boost DC converter device as claimed in claim 2, wherein the second output stage includes: a second output diode having an anode electrically connected to one end of the first voltage doubler capacitor, and a cathode; and A second output capacitor is electrically connected between the cathode of the second output diode and the first output capacitor to provide the second voltage. The high-boost DC converter device as claimed in claim 3, wherein the third output stage includes: a third output diode having an anode electrically connected to one end of the second voltage doubler capacitor, and a cathode; and a third output capacitor electrically connected between the cathode of the third output diode and the second output capacitor to provide the third voltage, wherein the first output capacitor and the second output capacitor and the The third output capacitors are stacked together. The high boost DC converter device as claimed in claim 1, wherein the first end of each first winding is a dotted end, and the second end of each first winding is a non-dotted end. The high boost DC converter device as claimed in claim 1, wherein the first end of each second winding is a dotted end, and the second end of each second winding is a non-dotted end. The high-boost DC converter device as described in Claim 1, wherein the first switch is an N-type power semiconductor transistor, and the first end of the first switch is a drain, and the second end of the first switch terminal is the source. The high step-up DC converter device as described in claim 1, wherein the second switch is an N-type power semiconductor transistor, and the first end of the second switch is a drain, and the second end of the second switch terminal is the source. The high step-up DC converter device as described in claim 1, further comprising a control unit, the control unit generates a first pulse modulation signal for switching the first switch and a second pulse modulation signal for switching the second switch A pulse modulation signal, the first pulse modulation signal and the second pulse modulation signal have the same cycle time. The high-boost DC converter device as claimed in claim 9, wherein a part of the cycle time of the first and second pulse modulation signals overlaps.

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