TWI721802B - Switching controller circuit and method for controlling flyback powr converter - Google Patents
Switching controller circuit and method for controlling flyback powr converter Download PDFInfo
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- TWI721802B TWI721802B TW109106700A TW109106700A TWI721802B TW I721802 B TWI721802 B TW I721802B TW 109106700 A TW109106700 A TW 109106700A TW 109106700 A TW109106700 A TW 109106700A TW I721802 B TWI721802 B TW I721802B
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
- H02M3/33576—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
- H02M3/33592—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer having a synchronous rectifier circuit or a synchronous freewheeling circuit at the secondary side of an isolation transformer
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
- H02M1/083—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the ignition at the zero crossing of the voltage or the current
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/38—Means for preventing simultaneous conduction of switches
Abstract
Description
本發明係有關一種切換控制電路,特別是指一種用以控制返馳式電源供應電路之切換控制電路。本發明也有關於一種用以控制返馳式電源供應電路之方法。The present invention relates to a switching control circuit, in particular to a switching control circuit for controlling a flyback power supply circuit. The invention also relates to a method for controlling a flyback power supply circuit.
與本發明相關的先前技術有: “K.-H. Chen, T.-J. Liang, Design of Quasi-resonant flyback converter control IC with DCM and CCM operation, 2014 International Power Electronics Conference, IEEE”, “US8917068B2, S. Chen, J. Jin, Quasi-resonant controlling and driving circuit and method for a flyback converter, 2014”, “US 2011/0305048 A1, T.-Y. Yang, Y.-C. Su, C.-C. Lin, Active-Clamp Circuit for Quasi-Resonant Flyback Power Converter, 2011”, “A. A. Saliva, Design Guide for QR Flyback Converter, Design Note DN 2013-01, Infineon Technologies North America Corp”, “W. Yuan, etc., “ Novel Soft Switching Flyback Converter with Synchronous Rectification, IEEE IPEMC 2009” , 以及 “X. Huang, etc., A Novel Variable Frequency Soft Switching Method for Flyback Converter with Synchronous Rectifier, IEEE 2010”。The prior art related to the present invention includes: "K.-H. Chen, T.-J. Liang, Design of Quasi-resonant flyback converter control IC with DCM and CCM operation, 2014 International Power Electronics Conference, IEEE", "US8917068B2 , S. Chen, J. Jin, Quasi-resonant controlling and driving circuit and method for a flyback converter, 2014", "US 2011/0305048 A1, T.-Y. Yang, Y.-C. Su, C.- C. Lin, Active-Clamp Circuit for Quasi-Resonant Flyback Power Converter, 2011", "AA Saliva, Design Guide for QR Flyback Converter, Design Note DN 2013-01, Infineon Technologies North America Corp", "W. Yuan, etc ., "Novel Soft Switching Flyback Converter with Synchronous Rectification, IEEE IPEMC 2009", and "X. Huang, etc., A Novel Variable Frequency Soft Switching Method for Flyback Converter with Synchronous Rectifier, IEEE 2010".
請同時參閱第1A圖與第1B圖,第1A圖顯示一種先前技術之返馳式電源供應電路(返馳式電源供應電路1),第1B圖顯示對應於此先前技術之返馳式電源供應電路的操作波形示意圖。其中一次側控制電路80控制一次側開關S1以切換功率變壓器10而產生輸出電壓Vo,二次側控制電路90用以產生同步整流控制訊號S2C,以控制同步整流開關S2而進行二次側的同步整流。Please refer to Figure 1A and Figure 1B at the same time. Figure 1A shows a prior art flyback power supply circuit (flyback power supply circuit 1). Figure 1B shows a flyback power supply corresponding to this prior art. Schematic diagram of the circuit's operating waveforms. The primary
第1A與1B圖中所示之先前技術,其缺點在於,同步整流開關S2無法即時而精準地與一次側之一次側開關S1同步,且一次側開關S1在未進行柔性切換(Soft Switching)的情況下,電源轉換效率較差。The disadvantage of the prior art shown in Figures 1A and 1B is that the synchronous rectifier switch S2 cannot be synchronized with the primary switch S1 on the primary side in real time and accurately, and the primary switch S1 does not perform soft switching (Soft Switching). In this case, the power conversion efficiency is poor.
本發明相較於第1A與1B圖之先前技術,同步整流開關S2可精準地與一次側開關S1同步,且藉由同步整流開關S2的柔性切換脈波,使得一次側開關S1可於切換時達成柔性切換,有效提高電源轉換效率。此外,本發明之切換控制電路還可適應性地根據不同的操作模式,而決定最佳的柔性切換脈波的導通時段以及延遲時段。Compared with the prior art shown in Figures 1A and 1B, the synchronous rectification switch S2 can be accurately synchronized with the primary side switch S1, and the flexible switching pulse of the synchronous rectification switch S2 allows the primary side switch S1 to switch during switching. Achieve flexible switching and effectively improve power conversion efficiency. In addition, the switching control circuit of the present invention can also adaptively determine the optimal conduction period and delay period of the flexible switching pulse wave according to different operation modes.
就其中一個觀點言,本發明提供了一種切換控制電路,用以控制一返馳式電源供應電路,以轉換一輸入電壓而產生一輸出電壓,該切換控制電路包含:一功率變壓器,以電性絕緣的方式耦接於該輸入電壓與該輸出電壓之間;一一次側控制電路,用以產生一切換訊號,以控制該返馳式電源供應電路其中的一一次側開關,而切換該功率變壓器的一一次側繞組,其中該一次側繞組耦接於該輸入電壓;以及一二次側控制電路,用以產生一同步整流控制訊號,以控制該返馳式電源供應電路其中的一同步整流開關,而切換該功率變壓器的一二次側繞組而產生該輸出電壓,其中該同步整流控制訊號具有一同步整流(Synchronous Rectifying,SR)脈波以及一柔性切換(Soft Switching,SS)脈波,該同步整流脈波用以控制該同步整流開關導通一同步整流時段以達成二次側同步整流,該柔性切換脈波用以控制該同步整流開關導通一柔性切換時段,藉此使該一次側開關達成柔性切換;其中該功率變壓器於該一次側開關導通時感磁,且於該一次側開關轉為不導通時將感磁時所獲得的能量傳送到該輸出電壓;其中當該返馳式電源供應電路操作於邊界導通模式時,在該功率變壓器藉由該同步整流脈波而導通該同步整流開關以去磁,於該功率變壓器的該二次側繞組去磁完成之後,該二次側控制電路緊接著藉由該柔性切換脈波而持續地導通該同步整流開關,使得該一次側開關於下次導通時達成柔性切換,該柔性切換脈波具有第一導通時段;或者當該返馳式電源供應電路操作於不連續導通模式時,在該功率變壓器藉由該同步整流脈波而導通該同步整流開關以去磁,於該功率變壓器的該二次側繞組去磁完成之後,該二次側控制電路控制該同步整流開關不導通,接著,該二次側控制電路藉由該柔性切換脈波而再度導通該同步整流開關,使得該一次側開關於下次導通時達成柔性切換,該柔性切換脈波具有第二導通時段。In one aspect, the present invention provides a switching control circuit for controlling a flyback power supply circuit to convert an input voltage to generate an output voltage. The switching control circuit includes: a power transformer with electrical characteristics It is coupled between the input voltage and the output voltage in an insulated manner; a primary side control circuit is used to generate a switching signal to control a primary side switch of the flyback power supply circuit to switch the A primary winding of the power transformer, wherein the primary winding is coupled to the input voltage; and a secondary control circuit for generating a synchronous rectification control signal to control one of the flyback power supply circuits Synchronous rectifying switch, and switching a secondary winding of the power transformer to generate the output voltage, wherein the synchronous rectification control signal has a synchronous rectifying (Synchronous Rectifying, SR) pulse and a soft switching (Soft Switching, SS) pulse The synchronous rectification pulse is used to control the synchronous rectification switch to conduct a synchronous rectification period to achieve secondary-side synchronous rectification, and the flexible switching pulse is used to control the synchronous rectification switch to conduct a flexible switching period to enable the primary The side switch achieves flexible switching; wherein the power transformer is magnetized when the primary side switch is turned on, and when the primary side switch is turned non-conductive, the energy obtained during the magnetization is transferred to the output voltage; wherein when the flyback When the power supply circuit is operated in the boundary conduction mode, when the power transformer turns on the synchronous rectifier switch by the synchronous rectification pulse to demagnetize, after the demagnetization of the secondary winding of the power transformer is completed, the secondary The side control circuit then continuously turns on the synchronous rectification switch by the flexible switching pulse, so that the primary-side switch achieves flexible switching when it is turned on next time, and the flexible switching pulse has the first conduction period; or when the return When the free-wheeling power supply circuit is operated in discontinuous conduction mode, the power transformer turns on the synchronous rectifier switch to demagnetize by the synchronous rectification pulse wave. After the demagnetization of the secondary winding of the power transformer is completed, the The secondary-side control circuit controls the synchronous rectifier switch to be non-conducting, and then the secondary-side control circuit turns on the synchronous rectifier switch again by the flexible switching pulse, so that the primary-side switch achieves flexible switching when it is turned on next time, The flexible switching pulse wave has a second conduction period.
在一較佳實施例中,柔性切換脈波藉由導通該二次側繞組而自該輸出電壓汲取一負向電流,藉此使得該一次側開關於下次導通時達成柔性切換。In a preferred embodiment, the flexible switching pulse draws a negative current from the output voltage by turning on the secondary winding, thereby enabling the flexible switching of the primary switch when it is turned on next time.
在一較佳實施例中,該二次側控制電路偵測該相關於該同步整流開關的電壓,以偵測該功率變壓器的該二次側繞組去磁完成。In a preferred embodiment, the secondary-side control circuit detects the voltage related to the synchronous rectifier switch to detect the completion of the demagnetization of the secondary-side winding of the power transformer.
在一較佳實施例中,切換控制電路更包含一訊號整形電路,用以將該相關於該同步整流開關的電壓整形後提供於該二次側控制電路,以偵測該功率變壓器的該二次側繞組去磁完成。In a preferred embodiment, the switching control circuit further includes a signal shaping circuit for shaping the voltage related to the synchronous rectifier switch and providing it to the secondary side control circuit to detect the two parts of the power transformer. The demagnetization of the secondary winding is completed.
在一較佳實施例中,該一次側控制電路藉由該功率變壓器的一輔助繞組而偵測相關於該功率變壓器的電壓,以偵測該功率變壓器的該二次側繞組去磁完成。In a preferred embodiment, the primary-side control circuit detects the voltage related to the power transformer through an auxiliary winding of the power transformer to detect the completion of the demagnetization of the secondary-side winding of the power transformer.
在一較佳實施例中,切換控制電路更包含一訊號整形電路,用以將相關於該功率變壓器的電壓整形後提供於該一次側控制電路,以偵測該功率變壓器的該二次側繞組去磁完成。In a preferred embodiment, the switching control circuit further includes a signal shaping circuit for shaping the voltage related to the power transformer and providing it to the primary control circuit to detect the secondary winding of the power transformer Demagnetization is complete.
在一較佳實施例中,該一次側控制電路產生一時脈訊號,用以決定該切換訊號的一最高切換頻率,其中當該時脈訊號於該功率變壓器的該二次側繞組去磁完成之前產生時,該一次側控制電路於該時脈訊號延遲一第一延遲時段後控制該一次側開關導通,而當該時脈訊號於該功率變壓器的該二次側繞組去磁完成之後產生時,該一次側控制電路於該時脈訊號延遲一第二延遲時段後控制該一次側開關導通;其中於該第一延遲時段與該第二延遲時段的期間內,該一次側開關皆被禁止導通;其中該第一延遲時段長於該第二延遲時段。In a preferred embodiment, the primary-side control circuit generates a clock signal for determining a highest switching frequency of the switching signal, wherein the clock signal is before the completion of the demagnetization of the secondary winding of the power transformer When generated, the primary side control circuit controls the primary side switch to turn on after the clock signal is delayed by a first delay period, and when the clock signal is generated after the demagnetization of the secondary winding of the power transformer is completed, The primary side control circuit controls the primary side switch to be turned on after the clock signal is delayed by a second delay period; wherein during the first delay period and the second delay period, the primary side switch is forbidden to be turned on; The first delay period is longer than the second delay period.
在一較佳實施例中,該二次側控制電路具有一電流閾值,該二次側控制電路根據流經該同步整流開關的電流以及該電流閾值而確定該功率變壓器的該二次側繞組是否去磁完成,其中該電流閾值為一可設定值。In a preferred embodiment, the secondary-side control circuit has a current threshold, and the secondary-side control circuit determines whether the secondary winding of the power transformer is based on the current flowing through the synchronous rectifier switch and the current threshold. The demagnetization is completed, and the current threshold is a settable value.
在一較佳實施例中,該第一導通時段長於該第二導通時段。In a preferred embodiment, the first conduction period is longer than the second conduction period.
在一較佳實施例中,切換控制電路更包含一訊號變壓器,用以自該一次側控制電路傳送該時脈訊號至該二次側。In a preferred embodiment, the switching control circuit further includes a signal transformer for transmitting the clock signal from the primary side control circuit to the secondary side.
一種用以控制一返馳式電源供應電路的方法,以轉換一輸入電壓而產生一輸出電壓,其中該返馳式電源供應電路的一功率變壓器,以電性絕緣的方式耦接於該輸入電壓與該輸出電壓之間;該方法包含:於該返馳式電源供應電路的一次側產生一切換訊號,以控制該返馳式電源供應電路其中的一一次側開關,而切換該功率變壓器的一一次側繞組,其中該一次側繞組耦接於該輸入電壓;以及於該返馳式電源供應電路的二次側產生一同步整流控制訊號,以控制該返馳式電源供應電路其中的一同步整流開關,而切換該功率變壓器的一二次側繞組而產生該輸出電壓,其中該同步整流控制訊號具有一同步整流(Synchronous Rectifying,SR)脈波以及一柔性切換(Soft Switching,SS)脈波,該同步整流脈波用以控制該同步整流開關導通一同步整流時段以達成二次側同步整流,該柔性切換脈波用以控制該同步整流開關導通一柔性切換時段,藉此使該一次側開關達成柔性切換;其中該功率變壓器於該一次側開關導通時感磁,且於該一次側開關轉為不導通時將感磁時所獲得的能量傳送到該輸出電壓;其中當該返馳式電源供應電路操作於邊界導通模式時,在該功率變壓器藉由該同步整流脈波而導通該同步整流開關以去磁,於該功率變壓器的該二次側繞組去磁完成之後,緊接著藉由該柔性切換脈波而持續地導通該同步整流開關,使得該一次側開關於下次導通時達成柔性切換,該柔性切換脈波具有第一導通時段;或者當該返馳式電源供應電路操作於不連續導通模式時,在該功率變壓器藉由該同步整流脈波而導通該同步整流開關以去磁,於該功率變壓器的該二次側繞組去磁完成之後,控制該同步整流開關不導通,接著,該二次側控制電路藉由該柔性切換脈波而再度導通該同步整流開關,使得該一次側開關於下次導通時達成柔性切換,該柔性切換脈波具有第二導通時段。A method for controlling a flyback power supply circuit to convert an input voltage to generate an output voltage, wherein a power transformer of the flyback power supply circuit is electrically insulated coupled to the input voltage And the output voltage; the method includes: generating a switching signal on the primary side of the flyback power supply circuit to control a primary side switch of the flyback power supply circuit to switch the power transformer A primary winding, wherein the primary winding is coupled to the input voltage; and a synchronous rectification control signal is generated on the secondary side of the flyback power supply circuit to control one of the flyback power supply circuits Synchronous rectifying switch, and switching a secondary winding of the power transformer to generate the output voltage, wherein the synchronous rectification control signal has a synchronous rectifying (Synchronous Rectifying, SR) pulse and a soft switching (Soft Switching, SS) pulse The synchronous rectification pulse is used to control the synchronous rectification switch to conduct a synchronous rectification period to achieve secondary-side synchronous rectification, and the flexible switching pulse is used to control the synchronous rectification switch to conduct a flexible switching period to enable the primary The side switch achieves flexible switching; wherein the power transformer is magnetized when the primary side switch is turned on, and when the primary side switch is turned non-conductive, the energy obtained during the magnetization is transferred to the output voltage; wherein when the flyback When the power supply circuit is operated in the boundary conduction mode, the power transformer turns on the synchronous rectifier switch to demagnetize by the synchronous rectification pulse wave. After the demagnetization of the secondary winding of the power transformer is completed, it is followed by The synchronous rectification switch is continuously turned on by the flexible switching pulse, so that the primary side switch achieves flexible switching when it is turned on next time, and the flexible switching pulse has a first conduction period; or when the flyback power supply circuit operates In discontinuous conduction mode, when the power transformer turns on the synchronous rectifier switch for demagnetization by the synchronous rectification pulse wave, after the demagnetization of the secondary winding of the power transformer is completed, the synchronous rectifier switch is controlled to be non-conducting Then, the secondary-side control circuit turns on the synchronous rectification switch again by the flexible switching pulse, so that the primary-side switch achieves flexible switching when the primary-side switch is turned on next time, and the flexible switching pulse has a second conduction period.
在一較佳實施例中,該方法更包含:將該相關於該同步整流開關的電壓整形,以偵測該功率變壓器的該二次側繞組去磁完成。In a preferred embodiment, the method further includes: shaping the voltage related to the synchronous rectifier switch to detect the completion of the demagnetization of the secondary winding of the power transformer.
在一較佳實施例中,偵測該功率變壓器的該二次側繞組去磁完成的步驟包括:藉由該功率變壓器於該一次側的一輔助繞組而偵測相關於該功率變壓器的電壓,以偵測該功率變壓器的該二次側繞組去磁完成。In a preferred embodiment, the step of detecting the completion of demagnetization of the secondary winding of the power transformer includes: detecting the voltage related to the power transformer through an auxiliary winding of the power transformer on the primary side, This is done by detecting the demagnetization of the secondary winding of the power transformer.
在一較佳實施例中,該方法更包含:將相關於該功率變壓器的電壓整形,以偵測該功率變壓器的該二次側繞組去磁完成。In a preferred embodiment, the method further includes: shaping the voltage related to the power transformer to detect the completion of the demagnetization of the secondary winding of the power transformer.
在一較佳實施例中,該方法更包含:於該一次側產生一時脈訊號,用以決定該切換訊號的一最高切換頻率,其中當該時脈訊號於該功率變壓器的該二次側繞組去磁完成之前產生時,於該時脈訊號延遲一第一延遲時段後控制該一次側開關導通,而當該時脈訊號於該功率變壓器的該二次側繞組去磁完成之後產生時,於該時脈訊號延遲一第二延遲時段後控制該一次側開關導通;其中於該第一延遲時段與該第二延遲時段的期間內,該一次側開關皆被禁止導通;其中該第一延遲時段長於該第二延遲時段。In a preferred embodiment, the method further includes: generating a clock signal on the primary side to determine a highest switching frequency of the switching signal, wherein when the clock signal is on the secondary winding of the power transformer When it is generated before the demagnetization is completed, the primary side switch is controlled to be turned on after the clock signal is delayed by a first delay period, and when the clock signal is generated after the demagnetization of the secondary winding of the power transformer is completed, The clock signal is delayed by a second delay period to control the primary side switch to turn on; wherein during the first delay period and the second delay period, the primary side switch is prohibited from turning on; wherein the first delay period Longer than the second delay period.
在一較佳實施例中,確定該功率變壓器的該二次側繞組是否去磁完成的步驟包括:根據流經該同步整流開關的電流以及該電流閾值而確定該功率變壓器的該二次側繞組是否去磁完成,其中該電流閾值為一可設定值。In a preferred embodiment, the step of determining whether the demagnetization of the secondary winding of the power transformer is completed includes: determining the secondary winding of the power transformer according to the current flowing through the synchronous rectifier switch and the current threshold Whether the demagnetization is completed, wherein the current threshold is a settable value.
在一較佳實施例中,該方法更包含:以一訊號變壓器,自該返馳式電源供應電路的該一次側傳送該時脈訊號至該返馳式電源供應電路的該二次側。In a preferred embodiment, the method further includes: using a signal transformer to transmit the clock signal from the primary side of the flyback power supply circuit to the secondary side of the flyback power supply circuit.
底下藉由具體實施例詳加說明,當更容易瞭解本發明之目的、技術內容、特點及其所達成之功效。Detailed descriptions are given below by specific embodiments, so that it will be easier to understand the purpose, technical content, features, and effects of the present invention.
本發明中的圖式均屬示意,主要意在表示各電路間之耦接關係,以及各訊號波形之間之關係,至於電路、訊號波形與頻率則並未依照比例繪製。The drawings in the present invention are all schematic, and are mainly intended to show the coupling relationship between the circuits and the relationship between the signal waveforms. As for the circuits, signal waveforms, and frequencies, they are not drawn to scale.
請參閱第2A圖,第2A圖顯示本發明中的切換控制電路的一種實施例(切換控制電路100),如圖所示,切換控制電路100用以控制返馳式電源供應電路1000,以轉換輸入電壓Vin而產生輸出電壓Vo,而提供電源予負載電路(未示出,為本領域具有通常知識者所熟知,在此不予贅述)。切換控制電路100包含功率變壓器10、一次側控制電路20以及二次側控制電路30。Please refer to Figure 2A. Figure 2A shows an embodiment of the switching control circuit (switching control circuit 100) of the present invention. As shown in the figure, the
功率變壓器10以電性絕緣的方式耦接於輸入電壓Vin與輸出電壓Vo之間,一次側開關S1耦接於功率變壓器10的一次側繞組W1,其中一次側繞組W1耦接於輸入電壓Vin。同步整流開關S2與功率變壓器10的二次側繞組W2串接於輸出電壓Vo與二次側接地節點之間。在本實施例中,同步整流開關S2耦接於功率變壓器10的二次側繞組W2與二次側接地節點之間。同步整流開關S2亦可耦接於功率變壓器10的二次側繞組W2與輸出電壓Vo之間,如第2B圖顯示的實施例所示意。為簡化說明,接下來以如第2A圖所示之同步整流開關S2耦接於功率變壓器10的二次側繞組W2與二次側接地節點之間的實施例進行說明,然而相同的精神也可適用於上述第2B圖所示的另一種形式。The
一次側控制電路20用以產生切換訊號S1C,切換訊號S1C用以控制一次側開關S1以切換功率變壓器10的一次側繞組W1,其中一次側繞組W1耦接於輸入電壓Vin。二次側控制電路30用以產生同步整流控制訊號S2C,以控制同步整流開關S2之導通與關斷,而切換功率變壓器10的二次側繞組W2產生輸出電壓Vo。其中VDS1為一次側開關S1的汲極的電壓,而VDS2為同步整流開關S2的第一端的電壓。本實施例中,所述的同步整流開關S2的第一端為汲極(電流流出端),而同步整流開關S2的第二端為源極(電流流入端)。還需說明的是,在同步整流開關S2耦接於功率變壓器10的二次側繞組W2與輸出電壓Vo之間的實施例中,如第2B圖所示,所述的同步整流開關S2的第一端為源極(電流流入端),而同步整流開關S2的第二端為汲極(電流流出端)。The
請同時參閱第3圖,第3圖顯示對應於本發明之切換控制電路的實施例之波形示意圖。本實施例中,本發明之返馳式電源供應電路操作於不連續導通模式(DCM – Discontinuous Conduction Mode)。根據本發明,同步整流控制訊號S2C具有同步整流脈波PSR以及柔性切換(Soft Switching,SS)脈波PSS,在一次側開關S1導通後又再度關斷時(如第3圖之t3),同步整流脈波PSR用以控制同步整流開關S2導通一同步整流時段TSR以達成二次側的同步整流,其中,同步整流時段TSR大致上同步於二次側繞組W2的感應電流的導通時間,換言之,同步整流時段TSR開始於二次側繞組W2自一次側繞組W1轉移能量而產生二次側電流ISR的時點(t3),且同步整流時段TSR結束於二次側繞組W2的二次側電流ISR降為0的時點(t4),如此可提升電源轉換效率。其中n為一次側繞組與二次側繞組的圈數比。Please refer to FIG. 3 at the same time. FIG. 3 shows a waveform diagram corresponding to an embodiment of the switching control circuit of the present invention. In this embodiment, the flyback power supply circuit of the present invention operates in a discontinuous conduction mode (DCM-Discontinuous Conduction Mode). According to the present invention, the synchronous rectification control signal S2C has a synchronous rectification pulse wave PSR and a soft switching (Soft Switching, SS) pulse wave PSS. When the primary side switch S1 is turned on and then turned off again (such as t3 in Figure 3), the synchronization The rectified pulse wave PSR is used to control the synchronous rectification switch S2 to conduct a synchronous rectification period TSR to achieve synchronous rectification on the secondary side, wherein the synchronous rectification period TSR is substantially synchronized with the on-time of the induced current of the secondary winding W2, in other words, The synchronous rectification period TSR starts at the time (t3) when the secondary side winding W2 transfers energy from the primary side winding W1 to generate the secondary side current ISR (t3), and the synchronous rectification period TSR ends when the secondary side current ISR of the secondary side winding W2 drops When it is 0 (t4), the power conversion efficiency can be improved in this way. Where n is the ratio of the number of turns of the primary winding to the secondary winding.
請繼續參閱第3圖,另一方面,柔性切換脈波PSS則用以達成前述之一次側開關S1的柔性切換。詳言之,本實施例中,當返馳式電源供應電路1000之負載屬於相對較輕載,亦即負載不大於一預設負載閾值,而返馳式電源供應電路1000操作於不連續導通模式時,功率變壓器10於一次側開關S1導通時感磁(magnetizing,t2-t3,第3圖),且於該一次側開關S1轉為不導通時將感磁時所獲得的能量傳送到該輸出電壓Vo;當同步整流脈波PSR控制同步整流開關S2導通,而使得功率變壓器10之二次側繞組W2去磁完成後(demagnetized,t4,第3圖),同步整流開關S2會先控制為不導通(t4-t5,第3圖),而當同步整流開關S2再度根據柔性切換脈波PSS而導通時(如第3圖之t0或t5),功率變壓器10會在二次側繞組W2感應負向的二次側電流ISR,亦即如第3圖中,於導通時段TSS期間(如t0-t1),二次側電流ISR為負值時,二次側電流ISR會從輸出電容Co,亦即,柔性切換脈波PSS藉由導通二次側繞組W2而自輸出電壓Vo汲取負向電流(即負向的二次側電流ISR),轉移能量至二次側繞組W2,當同步整流開關S2於柔性切換脈波PSS結束再度關斷時(如t1),如第3圖所示,功率變壓器10會在一次側繞組W1感應負向的一次側電流Ip,在此期間(如t1-t2),負向的一次側電流Ip可將一次側開關S1之寄生電容Cp放電,使得一次側開關S1的汲極電壓VDS1下降至較低的電壓,並將電荷通過一次側繞組W1回充至輸入電容Ci,當一次側開關S1接著導通,可使一次側開關S1達成柔性切換(SS – Soft Switching)。在一較佳實施例中,負向的一次側電流Ip可將一次側開關S1之寄生電容Cp放電至大致上為0V,可使一次側開關S1達成零電壓切換(ZVS – Zero Voltage Switching)。Please continue to refer to Figure 3. On the other hand, the flexible switching pulse PSS is used to achieve the aforementioned flexible switching of the primary side switch S1. In detail, in this embodiment, when the load of the flyback
需說明的是,前述之「負載」,係指負載電路的消耗功率,也就是由輸出電壓Vo對負載電路提供電源,由負載電路所消耗的功率。而所謂的「輕載」(負載相對較小)與「重載」(負載相對較大),則是由前述預設負載閾值來區隔,這需要根據個別的返馳式電源供應電路的設計參數,例如輸入電壓、輸出電壓、變壓器的電感值等而有所不同。舉例而言,輸出功率大於一預設負載閾值為重載,而操作於邊界導通模式,輸出功率不大於另一或同一預設負載閾值為輕載,而操作於不連續導通模式此為本領域中具有通常知識者所熟知,在此不予贅述。當然,所謂的「輕載」與「重載」在實際電路應用上,也可以用相關於輸出功率的輸出電流來區隔,在此不予贅述。It should be noted that the aforementioned "load" refers to the power consumption of the load circuit, that is, the power consumed by the load circuit when the output voltage Vo provides power to the load circuit. The so-called "light load" (relatively small load) and "heavy load" (relatively large load) are separated by the aforementioned preset load threshold, which requires the design of individual flyback power supply circuits Parameters such as input voltage, output voltage, transformer inductance, etc. vary. For example, if the output power is greater than a preset load threshold for heavy load, and operating in boundary conduction mode, the output power is not greater than another or the same preset load threshold for light load, and operating in discontinuous conduction mode is in the art It is well known to those with general knowledge, so I won’t repeat it here. Of course, the so-called "light load" and "heavy load" can also be separated by the output current related to the output power in actual circuit applications, so I won't repeat them here.
另外,前述之「柔性切換」係指,在電晶體(如對應於一次側開關S1)將導通之前,藉由放電電流將電晶體之寄生電容的殘存電壓,通過無能損放電路徑(例如對應於一次側繞組W1),放電至較低的電壓,並將電荷回充至無能損之元件(如輸入電容Ci)中,使得電晶體導通時,其汲源極電壓已先降低為較低的電壓,由於其寄生電容所儲存的電荷在此過程中不以電晶體之導通電阻放電,可提高電源轉換效率。In addition, the aforementioned "flexible switching" means that before the transistor (for example, corresponding to the primary side switch S1) is turned on, the residual voltage of the parasitic capacitance of the transistor is passed through a lossless discharge path (for example, corresponding to the The primary winding W1) discharges to a lower voltage, and recharges the charge to a non-destructive component (such as the input capacitor Ci), so that when the transistor is turned on, its drain-source voltage has been reduced to a lower voltage first Because the charge stored in the parasitic capacitance is not discharged by the on-resistance of the transistor during this process, the power conversion efficiency can be improved.
此外需說明的是:因電路零件的本身之寄生效應或是零件間相互的匹配不一定為理想,因此,雖然欲使寄生電容Cp放電至0V,但實際可能並無法準確地放電至0V,而僅是接近0V,亦即,根據本發明,可接受由於電路的不理想性而使寄生電容Cp放電後之電壓與0V間具有一定程度的誤差,此即前述之放電至「大致上」為0V之意,本文中其他提到「大致上」之處亦同。In addition, it should be noted that the parasitic effects of the circuit components or the matching between the components are not necessarily ideal. Therefore, although the parasitic capacitance Cp is to be discharged to 0V, it may not be accurately discharged to 0V in practice. It is only close to 0V, that is, according to the present invention, it is acceptable to have a certain degree of error between the voltage of the parasitic capacitance Cp after discharge and 0V due to the imperfections of the circuit, which means that the aforementioned discharge is "substantially" 0V. The meaning of this article is the same for other references to "generally".
請參閱第4圖,第4圖顯示對應於本發明之返馳式電源供應電路的實施例之波形示意圖。本實施例中,本發明之返馳式電源供應電路操作於邊界導通模式(BCM – Boundary Conduction Mode)。本實施例與第3圖的實施例類似,本實施例的不同之處在於,如第4圖所示,於同步整流脈波PSR結束時(同步整流時段TSR結束時),亦即二次側電流ISR降為0時(如第4圖中的t4),同步整流控制訊號S2C同時接續柔性切換脈波PSS’(如第4圖中的t4-t5),換言之,本實施例中,同步整流控制訊號S2C的同步整流脈波PSR與柔性切換脈波PSS’相連,使得在一次側開關不導通的期間,同步整流控制訊號S2C的導通期間的外觀看似僅有一個脈波,其中柔性切換脈波PSS’具有導通期間TSS’。值得注意的是,在一較佳實施例中,在同步整流脈波PSR的期間,二次側電流ISR為正(本實施例中輸出電流為正),而柔性切換脈波PSS’期間,至少部分的二次側電流ISR則為負值(亦即負向電流)。Please refer to FIG. 4, which shows a waveform diagram of an embodiment of the flyback power supply circuit corresponding to the present invention. In this embodiment, the flyback power supply circuit of the present invention operates in the boundary conduction mode (BCM-Boundary Conduction Mode). This embodiment is similar to the embodiment in Fig. 3. The difference of this embodiment is that, as shown in Fig. 4, at the end of the synchronous rectification pulse PSR (the end of the synchronous rectification period TSR), that is, the secondary side When the current ISR drops to 0 (such as t4 in Figure 4), the synchronous rectification control signal S2C is simultaneously connected to the flexible switching pulse PSS' (such as t4-t5 in Figure 4). In other words, in this embodiment, the synchronous rectification The synchronous rectification pulse PSR of the control signal S2C is connected to the flexible switching pulse PSS', so that during the non-conduction period of the primary side switch, the external view of the synchronous rectification control signal S2C during the conduction period seems to have only one pulse, of which the flexible switching pulse The wave PSS' has an on-period TSS'. It is worth noting that, in a preferred embodiment, during the synchronous rectification pulse PSR, the secondary side current ISR is positive (in this embodiment, the output current is positive), and during the flexible switching pulse PSS', at least Part of the secondary side current ISR is negative (that is, negative current).
在一實施例中,於邊界導通模式下的柔性切換脈波PSS’的導通期間TSS’長於在不連續導通模式下的柔性切換脈波PSS的導通期間TSS。In one embodiment, the on-period TSS of the flexible switching pulse PSS' in the boundary conduction mode is longer than the on-period TSS of the flexible switching pulse PSS in the discontinuous conduction mode.
本發明之切換控制電路,對於前述功率變壓器10之二次側繞組W2去磁完成,可藉由數種不同方式偵測而得知。在一實施例中,二次側控制電路30偵測相關於同步整流開關S2的電壓,以偵測功率變壓器10之二次側繞組W2去磁完成,即二次側電流ISR達成0電流時。請參閱第5圖,第5圖顯示對應於第3圖的細節波形示意圖。具體以第5圖為例,二次側控制電路30偵測同步整流開關S2的汲極電壓VDS2,當二次側電流ISR為正,且同步整流開關S2根據同步整流脈波PSR而導通時,同步整流開關S2的汲極電壓VDS2為負值(如第5圖之t3-t4),而當功率變壓器10之二次側繞組W2去磁完成,亦即二次側電流ISR由正下降為0時,二次側控制電路30可根據同步整流開關S2的汲極電壓VDS2由負值上升至0,以偵測功率變壓器10之二次側繞組W2去磁完成。需說明的是,所謂的「偵測功率變壓器之二次側繞組去磁完成」,係指根據相關參數,而決定去磁程序的結束時間點,亦即二次側電流ISR達到0電流時,為了說明簡潔,而以「偵測功率變壓器之之二次側繞組去磁完成」示意,下同。In the switching control circuit of the present invention, the completion of the demagnetization of the secondary winding W2 of the
請同時參閱第5圖、第6A圖與第6B圖,第6A圖與第6B圖顯示本發明的切換控制電路中,二次側控制電路的兩種實施例(二次側控制電路30A與30B)。Please refer to Fig. 5, Fig. 6A and Fig. 6B at the same time. Fig. 6A and Fig. 6B show two embodiments of the secondary side control circuit in the switching control circuit of the present invention (the secondary
如第6A圖所示,在一實施例中,二次側控制電路30A包括電流比較器31A,用以比較二次側電流ISR與電流閾值Ith_ZC,而產生用以表示二次側電流ISR為0電流的訊號SRZC,其可用以表示功率變壓器10之二次側繞組W2去磁完成,即二次側電流ISR達成0電流時。在一實施例中,電流閾值Ith_ZC為可設定值。具體而言,電流閾值Ith_ZC可設定為一接近0的閾值,在一實施例中,電流閾值Ith_ZC可設定為一接近0但大於0的閾值。As shown in Fig. 6A, in one embodiment, the secondary-
如第6B圖所示,在一實施例中,二次側控制電路30B包括電壓比較器31B,用以比較相關於二次側電流ISR的訊號,與電流閾值Vth_ZC,而產生用以表示二次側電流ISR為0電流的訊號SRZC,其可用以表示功率變壓器10之二次側繞組W2去磁完成,其中相關於二次側電流ISR的訊號例如但不限於前述同步整流開關S2的汲極電壓VDS2。在一實施例中,電流閾值Vth_ZC為可設定值。具體而言,電流閾值Vth_ZC可設定為一接近0的閾值,在一實施例中,電流閾值Vth_ZC可設定為一接近0但小於0的閾值。As shown in Figure 6B, in one embodiment, the secondary-
在其他實施例中,也可通過一次側控制電路來偵測功率變壓器10之二次側繞組W2去磁完成。請參閱第7圖,第7圖顯示本發明中的切換控制電路的一種實施例(切換控制電路107),本實施例中,一次側控制電路20’藉由功率變壓器10’的輔助繞組W3而偵測相關於功率變壓器10’的電壓,以偵測功率變壓器10’ 之二次側繞組W2去磁完成,即二次側電流ISR達成0電流時。在另一實施例中,一次側控制電路20’可偵測一次側開關S1的汲極電壓VDS1而偵測相關於功率變壓器10’的電壓,以偵測功率變壓器10’之二次側繞組W2去磁完成,即二次側電流ISR達成0電流時。In other embodiments, the primary side control circuit can also be used to detect the completion of the demagnetization of the secondary winding W2 of the
請繼續參閱第3圖與第4圖,在一實施例中,本發明的切換控制電路中,一次側控制電路20包含時脈訊號CLK,用以決定切換訊號S1C的最高切換頻率,如第4圖所示,當時脈訊號CLK於功率變壓器10之二次側繞組W2去磁完成,即二次側電流ISR達成0電流之前產生時,一次側控制電路20於時脈訊號CLK起,經過延遲時段Td1後控制一次側開關S1導通,具體而言,本實施例中,負載較大,因此,時脈訊號CLK於功率變壓器10之二次側繞組W2去磁完成,即二次側電流ISR達成0電流時之前產生,根據本發明,在一實施例中,由時脈訊號CLK觸發柔性切換脈波PSS’(如第4圖中的t4-t5),以接續前述的同步整流脈波PSR,在此同時,時脈訊號CLK也觸發延遲時段Td1,由於延遲時段Td1有部分時段重疊著柔性切換脈波PSS’,因此,在延遲時段Td1的期間內,禁能切換訊號S1C的觸發,亦即,一次側開關S1被禁止導通,以避免一次側開關S1與同步整流開關S2同時導通。Please continue to refer to Figures 3 and 4. In one embodiment, in the switching control circuit of the present invention, the primary
請繼續參閱第3圖,在另一實施例中,當時脈訊號CLK於功率變壓器10之二次側繞組W2去磁完成,即二次側電流ISR達成0電流時之後產生脈波時,一次側控制電路20於時脈訊號CLK產生脈波起,延遲時段Td2後控制一次側開關S1導通,具體而言,本實施例中,負載較輕,因此,時脈訊號CLK於功率變壓器10之二次側繞組W2去磁完成,即二次側電流ISR達成0電流時之前即產生,根據本發明,在一實施例中,由時脈訊號CLK觸發柔性切換脈波PSS(如第3圖中的t0-t1),在此同時,時脈訊號CLK也觸發延遲時段Td2,在延遲時段Td2的期間內,禁能切換訊號S1C的觸發,亦即,一次側開關S1被禁止導通,以避免一次側開關S1與同步整流開關S2同時導通。Please continue to refer to Figure 3. In another embodiment, the time pulse signal CLK is demagnetized in the secondary winding W2 of the
在一實施例中,上述的延遲時段Td1長於延遲時段Td2。In an embodiment, the aforementioned delay period Td1 is longer than the delay period Td2.
在一實施例中,時脈訊號CLK由一次側控制電路20所產生。In one embodiment, the clock signal CLK is generated by the primary
請同時參閱第8圖與第9圖,第8圖顯示本發明的切換控制電路中,一次側控制電路的一種實施例(一次側控制電路20),第9圖顯示對應於本發明之切換控制電路的實施例之波形示意圖。在一實施例中,一次側控制電路20根據一次側開關S1的汲極電壓VDS1是否下降低於一膝點閾值Vth_knee而判斷功率變壓器10之二次側繞組W2去磁完成,即二次側電流ISR達成0電流的時點(去磁程序的結束時間點),具體而言,如第8圖與第9圖所示,在一實施例中,比較器21用以比較一次側開關S1的汲極電壓VDS1與膝點閾值Vth_knee而產生膝點訊號V1_knee,用以示意一次側開關S1的汲極電壓VDS1是否低於膝點。在另一實施例中,一次側控制電路20根據輔助繞組W3的電壓V3是否下降低於一膝點閾值Vth_knee而判斷功率變壓器10之二次側繞組W2去磁完成,即二次側電流ISR達成0電流的時點,具體而言,如第8圖與第9圖所示,在一實施例中,比較器22用以比較輔助繞組W3的電壓V3與膝點閾值Vth_knee而產生膝點訊號V1_knee,用以示意輔助繞組W3的電壓V3是否低於膝點。Please refer to Figures 8 and 9 at the same time. Figure 8 shows an embodiment of the primary side control circuit (primary side control circuit 20) in the switching control circuit of the present invention. Figure 9 shows the switching control corresponding to the present invention. Schematic diagram of the waveform of an embodiment of the circuit. In one embodiment, the
請繼續參閱第8圖與第9圖,在一實施例中,一次側控制電路20根據一次側開關S1的汲極電壓VDS1是否下降低於一波谷閾值Vth_vly而判斷一次側開關S1的汲極電壓VDS1是否處於波谷,具體而言,如第8圖與第9圖所示,在一實施例中,比較器22用以比較一次側開關S1的汲極電壓VDS1與波谷閾值Vth_vly而產生波谷訊號V1_vly,用以示意一次側開關S1的汲極電壓VDS1是否處於波谷。在另一實施例中,一次側控制電路20根據輔助繞組W3的電壓V3是否下降低於一波谷閾值Vth_vly而判斷輔助繞組W3的電壓V3是否處於波谷,具體而言,如第8圖與第9圖所示,在一實施例中,比較器22用以比較輔助繞組W3的電壓V3與波谷閾值Vth_vly而產生波谷訊號V1_vly,用以示意輔助繞組W3的電壓V3是否處於波谷。在一實施例中,於前述延遲時段(Td1、Td2)之後,才根據一次側開關S1的汲極電壓VDS1是否處於波谷而確定一次側開關S1導通的時點。在一較佳實施例中,則於前述延遲時段(Td1、Td2)之後,才根據一次側開關S1的汲極電壓VDS1是否接近0而確定一次側開關S1導通的時點。Please continue to refer to FIGS. 8 and 9. In one embodiment, the primary-
請參閱第10圖,第10圖顯示本發明的切換控制電路的一種實施例示意圖(切換控制電路110),本實施例與前述實施例類似,本實施例中,切換控制電路110更包含訊號變壓器40,用以自一次側控制電路20”傳送時脈訊號CLK至二次側,例如用以同步觸發前述的柔性切換脈波PSS、PSS’。Please refer to Figure 10. Figure 10 shows a schematic diagram of an embodiment of the switching control circuit of the present invention (switching control circuit 110). This embodiment is similar to the previous embodiment. In this embodiment, the switching
請參閱第11圖,第11圖顯示本發明的切換控制電路,與其中之訊號整形電路的實施例示意圖(切換控制電路111、訊號整形電路50A或50B)。如第11圖所示,本實施例與前述實施例類似,本實施例中,切換控制電路111更包含訊號整形電路(如訊號整形電路50A或50B),在一實施例中,訊號整形電路50A用以將一次側開關S1的汲極電壓VDS1進行訊號處理後才傳送給一次側控制電路20。在一實施例中,訊號整形電路50B用以將同步整流開關S2的汲極電壓VDS2進行訊號處理後才傳送給二次側控制電路30。Please refer to FIG. 11. FIG. 11 shows a schematic diagram of an embodiment of the switching control circuit of the present invention and the signal shaping circuit (switching
如第11圖所示,在一實施例中,訊號整形電路 (對應於前述的訊號整形電路50A或50B)包括分壓電路(如其中的分壓電阻)以及濾波電路(如其中的濾波電容器),用以濾除雜訊。As shown in Figure 11, in one embodiment, the signal shaping circuit (corresponding to the aforementioned
以上已針對較佳實施例來說明本發明,唯以上所述者,僅係為使熟悉本技術者易於了解本發明的內容而已,並非用來限定本發明之權利範圍。所說明之各個實施例,並不限於單獨應用,亦可以組合應用,舉例而言,兩個或以上之實施例可以組合運用,而一實施例中之部分組成亦可用以取代另一實施例中對應之組成部件。此外,在本發明之相同精神下,熟悉本技術者可以思及各種等效變化以及各種組合,舉例而言,本發明所稱「根據某訊號進行處理或運算或產生某輸出結果」,不限於根據該訊號的本身,亦包含於必要時,將該訊號進行電壓電流轉換、電流電壓轉換、及/或比例轉換等,之後根據轉換後的訊號進行處理或運算產生某輸出結果。由此可知,在本發明之相同精神下,熟悉本技術者可以思及各種等效變化以及各種組合,其組合方式甚多,在此不一一列舉說明。因此,本發明的範圍應涵蓋上述及其他所有等效變化。The present invention has been described above with respect to preferred embodiments, but the above descriptions are only for making it easier for those skilled in the art to understand the content of the present invention, and are not intended to limit the scope of rights of the present invention. The illustrated embodiments are not limited to individual applications, but can also be combined. For example, two or more embodiments can be used in combination, and part of the composition in one embodiment can also be used to replace another embodiment. Corresponding component parts. In addition, under the same spirit of the present invention, those skilled in the art can think of various equivalent changes and various combinations. For example, the “processing or calculation based on a certain signal or generating a certain output result” in the present invention is not limited to According to the signal itself, it also includes performing voltage-current conversion, current-voltage conversion, and/or ratio conversion on the signal when necessary, and then process or calculate an output result according to the converted signal. It can be seen from this that under the same spirit of the present invention, those skilled in the art can think of various equivalent changes and various combinations, and there are many combinations of them, which are not listed here. Therefore, the scope of the present invention should cover all the above and other equivalent changes.
1:返馳式電源供應電路1: Flyback power supply circuit
10, 10’:功率變壓器10, 10’: Power transformer
100, 107, 110, 111:切換控制電路100, 107, 110, 111: switching control circuit
20, 20’, 20”:一次側控制電路20, 20’, 20”: Primary side control circuit
30, 30A, 30B:二次側控制電路30, 30A, 30B: Secondary side control circuit
31A:電流比較器31A: current comparator
31B:電壓比較器31B: Voltage comparator
40:訊號變壓器40: signal transformer
50A, 50B:訊號整形電路50A, 50B: signal shaping circuit
80:一次側控制電路80: Primary side control circuit
90:二次側控制電路90: Secondary side control circuit
Ci:輸入電容Ci: Input capacitance
CLK:時脈訊號CLK: Clock signal
Co:輸出電容Co: output capacitance
Cp:寄生電容Cp: parasitic capacitance
Ith_ZC:電流閾值Ith_ZC: current threshold
Ip:一次側電流Ip: primary side current
ISR:二次側電流ISR: Secondary side current
nn
PSR:同步整流脈波PSR: Synchronous rectification pulse
PSS, PSS’:柔性切換脈波PSS, PSS’: Flexible switching pulse
S1:一次側開關S1: Primary side switch
S1C:切換訊號S1C: Switch signal
S2:同步整流開關S2: Synchronous rectifier switch
S2C:同步整流控制訊號S2C: Synchronous rectification control signal
SRZC:訊號SRZC: Signal
t0-t5, t2’:時點t0-t5, t2’: time point
Td1, Td2:延遲時段Td1, Td2: Delay period
TSR:同步整流時段TSR: Synchronous rectification period
TSS, TSS’:導通時段TSS, TSS’: On period
V3:電壓V3: Voltage
VDS1, VDS2:電壓VDS1, VDS2: Voltage
Vin:輸入電壓Vin: input voltage
Vo:輸出電壓Vo: output voltage
Vth_knee:膝點閾值Vth_knee: knee point threshold
Vth_vly:波谷閾值Vth_vly: trough threshold
Vth_ZC:電流閾值Vth_ZC: current threshold
W1:一次側繞組W1: Primary winding
W2:二次側繞組W2: Secondary winding
W3:輔助繞組W3: auxiliary winding
第1A圖顯示一種先前技術之返馳式電源供應電路。Figure 1A shows a flyback power supply circuit of the prior art.
第1B圖顯示對應於第1A圖先前技術之返馳式電源供應電路的操作波形示意圖。FIG. 1B shows a schematic diagram of the operation waveforms of the flyback power supply circuit of the prior art corresponding to FIG. 1A.
第2A圖顯示本發明中的切換控制電路的一種實施例。Figure 2A shows an embodiment of the switching control circuit in the present invention.
第2B圖顯示本發明中的切換控制電路的一種實施例。Figure 2B shows an embodiment of the switching control circuit in the present invention.
第3圖顯示對應於本發明之切換控制電路的實施例之波形示意圖。Figure 3 shows a schematic diagram of waveforms corresponding to an embodiment of the switching control circuit of the present invention.
第4圖顯示對應於本發明之返馳式電源供應電路的實施例之波形示意圖。FIG. 4 shows a schematic diagram of waveforms corresponding to an embodiment of the flyback power supply circuit of the present invention.
第5圖顯示對應於第3圖的細節波形示意圖。Figure 5 shows the detailed waveform diagram corresponding to Figure 3.
第6A圖與第6B圖顯示本發明的切換控制電路中,二次側控制電路的兩種實施例。Figures 6A and 6B show two embodiments of the secondary side control circuit in the switching control circuit of the present invention.
第7圖顯示本發明中的切換控制電路的一種實施例。Figure 7 shows an embodiment of the switching control circuit in the present invention.
第8圖顯示本發明的切換控制電路中,一次側控制電路的一種實施例。Figure 8 shows an embodiment of the primary side control circuit in the switching control circuit of the present invention.
第9圖顯示對應於本發明之切換控制電路的實施例之波形示意圖。Fig. 9 shows a waveform diagram corresponding to an embodiment of the switching control circuit of the present invention.
第10圖顯示本發明的切換控制電路的一種實施例示意圖。Figure 10 shows a schematic diagram of an embodiment of the switching control circuit of the present invention.
第11圖顯示本發明的切換控制電路,與其中之訊號整形電路的實施例示意圖。FIG. 11 shows a schematic diagram of an embodiment of the switching control circuit of the present invention and the signal shaping circuit therein.
CLK:時脈訊號 CLK: Clock signal
Ip:一次側電流 Ip: primary side current
ISR:二次側電流 ISR: Secondary side current
n:圈數比 n: turns ratio
PSR:同步整流脈波 PSR: Synchronous rectification pulse
PSS:柔性切換脈波 PSS: Flexible switching pulse
S1C:切換訊號 S1C: Switch signal
S2C:同步整流控制訊號 S2C: Synchronous rectification control signal
t0-t5,t2’:時點 t0-t5,t2’: time point
Td2:延遲時段 Td2: Delay period
TSR:同步整流時段 TSR: Synchronous rectification period
TSS:導通時段 TSS: On period
VDS1,VDS2:電壓 VDS1, VDS2: Voltage
Vin:輸入電壓 Vin: input voltage
Vo:輸出電壓 Vo: output voltage
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CN112713778B (en) | 2022-03-29 |
CN112713778A (en) | 2021-04-27 |
TW202118213A (en) | 2021-05-01 |
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